LMH6723/LMH6724/LMH6725 Single/Dual/Quad 370 MHz 1 mA Current Feedback Operational Amplifier General Description Features The LMH6723/LMH6724/LMH6725 provides a 260 MHz small signal bandwidth at a gain of +2 V/V and a 600 V/µs slew rate while consuming only 1 mA from ± 5V supplies. The LMH6723/LMH6724/LMH6725 supports video applications with its 0.03% and 0.11˚ differential gain and phase for NTSC and PAL video signals. The LMH6723/LMH6724/ LMH6725 also offers a flat gain response of 0.1 dB to 100 MHz. Additionally, the LMH6723/LMH6724/LMH6725 can deliver 110 mA of linear output current. This level of performance, as well as a wide supply range of 4.5 to 12V, makes the LMH6723/LMH6724/LMH6725 an ideal op amp for a variety of portable applications. The LMH6723/LMH6724/ LMH6725’s small packages (TSSOP, SOIC & SOT23), low power requirement and high performance allow the LMH6723/LMH6724/LMH6725 to serve a wide variety of portable applications. The LMH6723/LMH6724/LMH6725 is manufactured in National’s VIP10™ complimentary bipolar process. n Large signal bandwidth and slew rate 100% tested n 370 MHz bandwidth (AV = 1, VOUT = 0.5 VPP) −3 dB BW n 260 MHz (AV = +2 V/V, VOUT = 0.5 VPP) −3 dB BW n 1 mA supply current n 110 mA linear output current n 0.03%, 0.11˚ differential gain, phase n 0.1 dB gain flatness to 100 MHz n Fast slew rate: 600 V/µs n Unity gain stable n Single supply range of 4.5 to 12V n Improved replacement for CLC450, CLC452, (LMH6723) Applications n n n n Line driver Portable video A/D driver Portable DVD Typical Application 20078936 Single Supply Cable Driver VIP10™ is a trademark of National Semiconductor Corporation. © 2005 National Semiconductor Corporation DS200789 www.national.com LMH6723/LMH6724/LMH6725 Single/Dual/Quad 370 MHz 1 mA Current Feedback Op Amp August 2005 LMH6723/LMH6724/LMH6725 Absolute Maximum Ratings (Note 1) Human Body Model If Military/Aerospace specified devices are required, please contact the National Semiconductor Sales Office/ Distributors for availability and specifications. Machine Model (Note 4) VCC (V+ - V-) Thermal Resistance 120 mA (Note 3) Maximum Junction Temperature Storage Temperature Range Package ± VCC Common Mode Input Voltage +150˚C −65˚C to +150˚C Soldering Information Infrared or Convection (20 sec) (θJA) 8-Pin SOIC 166˚C/W 5-Pin SOT23 230˚C/W 14-Pin SOIC 130˚C/W 14-Pin TSSOP 235˚C Wave Soldering (10 sec) 200V Operating Ratings (Note 3) ± 6.75V IOUT 2000V 160˚C/W Operating Temperature Range 260˚C −40˚C to +85˚C Nominal Supply Voltage ESD Tolerance (Note 4) 4.5V to 12V ± 5V Electrical Characteristics Unless otherwise specified, AV = +2, RF = 1200Ω, RL = 100Ω. Boldface limits apply at temperature extremes. (Note 2) Symbol Parameter Conditions Min Typ LMH6723 90 110 LMH6724 LMH6725 85 95 Max Units Frequency Domain Response SSBW −3 dB Bandwidth Small Signal VOUT = 0.5 VPP LSBW −3dB Bandwidth Large Signal VOUT = 4.0 VPP 260 MHz MHz UGBW −3 dB Bandwidth Unity Gain VOUT = .2 VPP AV = 1 V/V 370 MHz .1dB BW .1 dB Bandwidth VOUT = 0.5 VPP 100 MHz DG Differential Gain RL = 150Ω, 4.43 MHz 0.03 % DP Differential Phase RL = 150Ω, 4.43 MHz 0.11 deg 2.5 ns Time Domain Response TRS Rise and Fall Time 4V Step TSS Settling Time to 0.05% 2V Step SR Slew Rate 4V Step 30 ns 600 V/µs 2 VPP, 5 MHz −65 dBc 2 VPP, 5 MHz −63 dBc > 1 MHz > 1 MHz > 1 MHz 4.3 nV/ 6 pA/ 6 pA/ 500 Distortion and Noise Response HD2 HD3 2nd Harmonic Distortion 3 rd Harmonic Distortion Equivalent Input Noise VN Non-Inverting Voltage Noise NICN Inverting Current Noise ICN Non-Inverting Current Noise Static, DC Performance VIO Input Offset Voltage IBN Input Bias Current Non-Inverting −2 IBI Input Bias Current Inverting 0.4 PSRR Power Supply Rejection Ratio DC, 1V Step www.national.com 1 2 LMH6723 59 57 64 LMH6724 59 55 64 LMH6725 59 56 64 ±3 ± 3.7 ±4 ±5 ±4 ±5 mV µA µA dB (Continued) Unless otherwise specified, AV = +2, RF = 1200Ω, RL = 100Ω. Boldface limits apply at temperature extremes. (Note 2) Symbol CMRR ICC Parameter Common Mode Rejection Ratio Supply Current (per amplifier) Conditions DC, 1V Step Min Typ LMH6723 57 55 60 LMH6724 57 53 60 LMH6725 57 54 60 RL = ∞ 1 Max Units dB 1.2 1.4 mA Miscellaneous Performance RIN+ Input Resistance Non-Inverting 100 kΩ RIN− Input Resistance (Output Resistance of Input Buffer) Inverting 500 Ω CIN Input Capacitance Non-Inverting 1.5 pF ROUT Output Resistance Ω Output Voltage Range Closed Loop RL = ∞ 0.01 VO LMH6723 LMH6724 LMH6725 ±4 ± 3.9 ±4 ± 3.85 ± 4.1 Output Voltage Range, High RL = 100Ω 3.6 3.5 3.7 Output Voltage Range, Low RL = 100Ω −3.25 −3.1 −3.45 CMVR Input Voltage Range Common Mode, CMRR > 50 dB ± 4.0 IO Output Current Sourcing, VOUT = 0 95 70 110 Sinking, VOUT = 0 −80 −70 110 VOL V ± 4.1 V V mA ± 2.5V Electrical Characteristics Unless otherwise specified, AV = +2, RF = 1200Ω, RL = 100Ω. Boldface limits apply at temperature extremes. (Note 2) Symbol Parameter Conditions Min Typ Max Units Frequency Domain Response SSBW −3 dB Bandwidth Small Signal VOUT = 0.5 VPP LSBW −3 dB Bandwidth Large Signal VOUT = 2.0 VPP 210 LMH6723 LMH6724 95 125 LMH6725 90 100 MHz MHz UGBW −3 dB Bandwidth Unity Gain VOUT = 0.5 VPP, AV = 1 V/V 290 MHz .1dB BW .1 dB Bandwidth VOUT = 0.5 VPP 100 MHz DG Differential Gain RL = 150Ω, 4.43 MHz .03 % DP Differential Phase RL = 150Ω, 4.43 MHz 0.1 deg Time Domain Response TRS Rise and Fall Time 2V Step SR Slew Rate 2V Step 4 ns 400 V/µs 2 VPP, 5 MHz −67 dBc 2 VPP, 5 MHz −67 dBc > 1 MHz 4.3 275 Distortion and Noise Response HD2 HD3 2nd Harmonic Distortion 3 rd Harmonic Distortion Equivalent Input Noise VN Non-Inverting Voltage 3 nV/ www.national.com LMH6723/LMH6724/LMH6725 ± 5V Electrical Characteristics LMH6723/LMH6724/LMH6725 ± 2.5V Electrical Characteristics (Continued) Unless otherwise specified, AV = +2, RF = 1200Ω, RL = 100Ω. Boldface limits apply at temperature extremes. (Note 2) Symbol Parameter NICN Inverting Current ICN Non-Inverting Current Conditions Min > 1MHz > 1MHz Typ Max Units 6 pA/ 6 pA/ Static, DC Performance VIO Input Offset Voltage IBN Input Bias Current Non-Inverting −2.7 IBI Input Bias Current Inverting −0.7 PSRR Power Supply Rejection Ratio DC, 0.5V Step CMRR ICC Common Mode Rejection Ratio Supply Current (per amplifier) −0.5 DC, 0.5V Step LMH6723 59 57 62 LMH6724 58 55 62 LMH6725 59 56 62 LMH6723 57 53 59 LMH6724 55 52 59 LMH6725 57 52 59 RL = ∞ .9 ±3 ± 3.4 ±4 ±5 ±4 ±5 mV µA µA dB dB 1.1 1.3 mA Miscellaneous Performance RIN+ Input Resistance Non-Inverting 100 kΩ RIN− Input Resistance (Output Resistance of Input Buffer) Inverting 500 Ω CIN Input Capacitance Non-Inverting 1.5 pF ROUT Output Resistance Closed Loop .02 Ω VO Output Voltage Range RL = ∞ VOL Output Voltage Range, High RL = 100Ω Output Voltage Range, Low RL = 100Ω ± 1.55 ± 1.4 ± 1.65 LMH6723 1.35 1.27 1.45 LMH6724 LMH6725 1.35 1.26 1.45 LMH6723 −1.25 −1.15 −1.38 LMH6724 LMH6725 −1.25 −1.15 −1.38 CMVR Input Voltage Range Common Mode, CMRR > 50 dB IO Output Current Sourcing 70 60 90 Sinking −30 −30 −60 www.national.com 4 ± 1.45 V V V V mA Note 2: Electrical Table values apply only for factory testing conditions at the temperature indicated. Factory testing conditions result in very limited self-heating of the device such that TJ = TA. No guarantee of parametric performance is indicated in the electrical tables under conditions of internal self heating where TJ > TA. See Applications Section for information on temperature derating of this device. Min/Max ratings are based on product characterization and simulation. Individual parameters are tested as noted. Note 3: The maximum continuous output current (IOUT) is determined by device power dissipation limitations. See the Power Dissipation section of the Application Section for more details. Note 4: Human Body Model, 1.5 kΩ in series with 100 pF. Machine Model, 0Ω In series with 200 pF. Connection Diagrams 5-Pin SOT23 8-Pin SOIC 20078937 20078938 Top View Top View 14-Pin TSSOP & SOIC 8-Pin SOIC 20078944 20078947 Top View Top View Ordering Information Package 5-Pin SOT23 8-Pin SOIC 8-Pin SOIC 14-Pin SOIC 14-Pin TSSOP Part Number LMH6723MF LMH6723MFX LMH6723MA LMH6723MAX LMH6724MA LMH6724MAX LMH6725MA LMH6725MAX LMH6725MT LMH6725MTX Package Marking Transport Media 1k Units Tape and Reel AB1A 3k Units Tape and Reel 95 Units/Rail LMH6723MA 2.5k Units Tape and Reel 95 Units/Rail LMH6724MA 2.5k Units Tape and Reel 55 Units/Rail LMH6725MA 2.5k Units Tape and Reel 94 Units/Rail LMH6725MT 2.5k Units Tape and Reel 5 NSC Drawing MF05A M08A M08A M14A MTC14 www.national.com LMH6723/LMH6724/LMH6725 Note 1: Absolute Maximum Ratings indicate limits beyond which damage to the device may occur. Operating Ratings indicate conditions for which the device is intended to be functional, but specific performance is not guaranteed. For guaranteed specifications, see the Electrical Characteristics tables. LMH6723/LMH6724/LMH6725 Typical Performance Characteristics AV = 2, RF = 1200Ω, RL = 100Ω, unless otherwise specified. Frequency Response vs. VOUT, AV = 2 Frequency Response vs. VOUT, AV = 2 20078928 20078926 Frequency Response vs. VOUT, AV = 1 Frequency Response vs. VOUT, AV = 1 20078929 20078927 Large Signal Frequency Response Frequency Response vs. Supply Voltage 20078930 20078921 www.national.com 6 LMH6723/LMH6724/LMH6725 Typical Performance Characteristics AV = 2, RF = 1200Ω, RL = 100Ω, unless otherwise specified. (Continued) Suggested RF vs. Gain Non-Inverting Suggested RF vs. Gain Inverting 20078905 20078906 Frequency Response vs. RF Frequency Response vs. RF 20078922 20078923 Open Loop Gain & Phase Open Loop Gain & Phase 20078917 20078918 7 www.national.com LMH6723/LMH6724/LMH6725 Typical Performance Characteristics AV = 2, RF = 1200Ω, RL = 100Ω, unless otherwise specified. (Continued) HD2 & HD3 vs. VOUT HD2 & HD3 vs. VOUT 20078913 20078911 HD2 & HD3 vs. Frequency HD2 & HD3 vs. Frequency 20078912 20078914 Frequency Response vs. CL Frequency Response vs. CL 20078925 www.national.com 20078924 8 LMH6723/LMH6724/LMH6725 Typical Performance Characteristics AV = 2, RF = 1200Ω, RL = 100Ω, unless otherwise specified. (Continued) Suggested ROUT vs. CL Suggested ROUT vs. CL 20078920 20078919 PSRR vs. Frequency PSRR vs. Frequency 20078916 20078915 Closed Loop Output Resistance CMRR vs. Frequency 20078908 20078907 9 www.national.com LMH6723/LMH6724/LMH6725 Typical Performance Characteristics AV = 2, RF = 1200Ω, RL = 100Ω, unless otherwise specified. (Continued) Differential Gain & Phase Channel Matching (LMH6724) 20078910 20078948 Channel Matching (LMH6724) Crosstalk (LMH6724) 20078946 20078949 Channel Matching (LMH6725) Channel Matching (LMH6725) 20078940 www.national.com 20078941 10 LMH6723/LMH6724/LMH6725 Typical Performance Characteristics AV = 2, RF = 1200Ω, RL = 100Ω, unless otherwise specified. (Continued) Crosstalk (LMH6725) 20078945 Application Section GENERAL INFORMATION The LMH6723/LMH6724/LMH6725 is a high speed current feedback amplifier manufactured on National Semiconductor’s VIP10 (Vertically Integrated PNP) complimentary bipolar process. LMH6723/LMH6724/LMH6725 offers a unique combination of high speed and low quiescent supply current making it suitable for a wide range of battery powered and portable applications that require high performance. This amplifier can operate from 4.5V to 12V nominal supply voltages and draws only 1 mA of quiescent supply current at 10V supplies ( ± 5V typically). The LMH6723/LMH6724/ LMH6725 has no internal ground reference so single or split supply configurations are both equally useful. will cause the frequency response to roll off faster. Reducing the value of RF too far below it’s recommended value will cause overshoot, ringing and, eventually, oscillation. EVALUATION BOARDS National Semiconductor provides the following evaluation boards as a guide for high frequency layout and as an aid in device testing and characterization. Many of the datasheet plots were measured with these boards. Device Package Board Part # LMH6723MA SOIC-8 CLC730227 LMH6723MF SOT-23 CLC730216 LMH6724MA SOIC-8 CLC730036 LMH6725MA SOIC-14 CLC730231 20078922 FIGURE 1. Frequency Response vs. RF Figure 1 shows the LMH6723/LMH6724/LMH6725’s frequency response as RF is varied (RL = 100Ω, AV = +2). This plot shows that an RF of 800Ω results in peaking. An RF of 1200Ω gives near maximal bandwidth and gain flatness with good stability. Since each application is slightly different it is worth some experimentation to find the optimal RF for a given circuit. In general a value of RF that produces ~0.1 dB of peaking is the best compromise between stability and maximal bandwidth. Note that it is not possible to use a current feedback amplifier with the output shorted directly to the inverting input. The buffer configuration of the LMH6723/ LMH6724/LMH6725 requires a 2000Ω feedback resistor for stable operation. For other gains see the charts "RF vs. Non These evaluation boards can be shipped when a device sample request is placed with National Semiconductor. FEEDBACK RESISTOR SELECTION One of the key benefits of a current feedback operational amplifier is the ability to maintain optimum frequency response independent of gain by using appropriate values for the feedback resistor (RF). The Electrical Characteristics and Typical Performance plots were generated with an RF of 1200Ω, a gain of +2V/V and ± 5V or ± 2.5V power supplies (unless otherwise specified). Generally, lowering RF from it’s recommended value will peak the frequency response and extend the bandwidth; however, increasing the value of RF 11 www.national.com LMH6723/LMH6724/LMH6725 Application Section (Continued) Inverting Gain" and "RF vs. Inverting Gain". These charts provide a good place to start when selecting the best feedback resistor value for a variety of gain settings. For more information see Application Note OA-13 which describes the relationship between RF and closed-loop frequency response for current feedback operational amplifiers. The value for the inverting input impedance for the LMH6723/LMH6724/LMH6725 is approximately 500Ω. The LMH6723/LMH6724/LMH6725 is designed for optimum performance at gains of +1 to +5V/V and −1 to −4V/V. Higher gain configurations are still useful; however, the bandwidth will fall as gain is increased, much like a typical voltage feedback amplifier. 20078906 FIGURE 3. RF vs. Inverting Gain ACTIVE FILTERS When using any current feedback operational amplifier as an active filter it is necessary to be careful using reactive components in the feedback loop. Reducing the feedback impedance, especially at higher frequencies, will almost certainly cause stability problems. Likewise capacitance on the inverting input should be avoided. See Application Notes OA-7 and OA-26 for more information on Active Filter applications for Current Feedback Op Amps. When using the LMH6723/LMH6724/LMH6725 as a lowpass filter the value of RF can be substantially reduced from the value recommended in the RF vs. Gain charts. The benefit of reducing RF is increased gain at higher frequencies, which improves attenuation in the stop band. Stability problems are avoided because in the stop band additional device bandwidth is used to cancel the input signal rather than amplify it. The benefit of this change depends on the particulars of the circuit design. With a high pass filter configuration reducing RF will likely result in device instability and is not recommended. 20078905 FIGURE 2. RF vs. Non-Inverting Gain Figure 2 and Figure 3 show the value of RF versus gain. A higher RF is required at higher gains to keep RG from decreasing too far below the input impedance of the inverting input. This limitation applies to both inverting and noninverting configurations. For the LMH6723/LMH6724/ LMH6725 the input resistance of the inverting input is approximately 500Ω and 100Ω is a practical lower limit for RG. The LMH6723/LMH6724/LMH6725 begins to operate in a gain bandwidth limited fashion in the region where RF must be increased for higher gains. Note that the amplifier will operate with RG values well below 100Ω; however, results will be substantially different than predicted from ideal models. In particular, the voltage potential between the Inverting and Non-Inverting inputs cannot be expected to remain small. For inverting configurations the impedance seen by the source is RG || RT. For most sources this limits the maximum inverting gain since RF is determined by the desired gain as shown in Figure 3. The value of RG is then RF/Gain. Thus for an inverting gain of −4 V/V the input impedance is equal to 100Ω. Using a termination resistor, this can be brought down to match a 50Ω or 75Ω source; however, a 150Ω source cannot be matched without a severe compromise in RF. 20078933 FIGURE 4. Typical Application with Suggested Supply Bypassing www.national.com 12 One possible remedy for this effect is to slightly increase the value of the feedback (and gain set) resistor. This will tend to offset the high frequency gain peaking while leaving other parameters relatively unchanged. If the device has a capacitive load as well as inverting input capacitance, using a series output resistor as described in the section on "Driving Capacitive Loads" will help. (Continued) 20078934 FIGURE 5. Decoupling Capacitive Loads DRIVING CAPACITIVE LOADS Capacitive output loading applications will benefit from the use of a series output resistor as shown in Figure 5. The charts "Suggested ROUT vs. Cap Load" give a recommended value for selecting a series output resistor for mitigating capacitive loads. The values suggested in the charts are selected for .5 dB or less of peaking in the frequency response. This gives a good compromise between settling time and bandwidth. For applications where maximum frequency response is needed and some peaking is tolerable, the value of ROUT can be reduced slightly from the recommended values. There will be amplitude lost in the series resistor unless the gain is adjusted to compensate; this effect is most noticeable with heavy loads (RL < 150Ω). An alternative approach is to place ROUT inside the feedback loop as shown in Figure 6. This will preserve gain accuracy, but will still limit maximum output voltage swing. 20078942 FIGURE 7. High Output Current Composite Amplifier When higher currents are required than a single amplifier can provide, the circuit of Figure 7 can be used. Although the example circuit was intended for the LMH6725 quad op amp, higher thermal efficiency can be obtained by using four separate SOIC op amps. Careful attention to a few key components will optimize performance from this circuit. The first thing to note is that the buffers need slightly higher value feedback resistors than if the amplifiers were individually configured. As well, R11 and C1 provide mid circuit frequency compensation to further improve stability. The composite amplifier has approximately twice the phase delay of a single circuit. The larger values of R8, R9 and R10, as well as the high frequency attenuation provided by C1 and R11, ensure that the circuit does not oscillate. Resistors R4, R5, R6, and R7 are necessary to ensure even current distribution between the amplifiers. Since they are inside the feedback loop they have no effect on the gain of the circuit. The circuit shown in Figure 7 has a gain of 5. The frequency response of this circuit is shown in Figure 8. 20078935 FIGURE 6. Series Output Resistor inside feedback loop INVERTING INPUT PARASITIC CAPACITANCE Parasitic capacitance is any capacitance in a circuit that was not intentionally added. It is produced through electrical interaction between conductors and can be reduced but never entirely eliminated. Most parasitic capacitances that cause problems are related to board layout or lack of termination on transmission lines. Please see the section on Layout Considerations for hints on reducing problems due to parasitic capacitances on board traces. Transmission lines should be terminated in their characteristic impedance at both ends. High speed amplifiers are sensitive to capacitance between the inverting input and ground or power supplies. This shows up as gain peaking at high frequency. The capacitor raises device gain at high frequencies by making RG appear smaller. Capacitive output loading will exaggerate this effect. 13 www.national.com LMH6723/LMH6724/LMH6725 Application Section LMH6723/LMH6724/LMH6725 Application Section therefore, best performance will be obtained with back terminated loads. The back termination reduces reflections from the transmission line and effectively masks transmission line and other parasitic capacitances from the amplifier output stage. Figure 4 shows a typical configuration for driving a 75Ω cable. The amplifier is configured for a gain of 2 to make up for the 6dB of loss in ROUT. (Continued) SINGLE 5V SUPPLY VIDEO With a 5V supply the LMH6723/LMH6724/LMH6725 is able to handle a composite NTSC video signal, provided that the signal is AC coupled and level shifted so that the signal is centered around VCC/2. POWER DISSIPATION Follow these steps to determine the maximum power dissipation for the LMH6723/LMH6724/LMH6725: 1. Calculate the quiescent (no-load) power: PAMP = ICC * (VS) VS = V+ - V2. Calculate the RMS power dissipated in the output stage: PD (rms) = rms ((VS-VOUT)*IOUT) where VOUT and IOUT are the voltage and current across the external load and VS is the total supply current. 3. Calculate the total RMS power: PT = PAMP +PD The maximum power that the LMH6723/LMH6724/LMH6725 package can dissipate at a given temperature can be derived with the following equation: PMAX = (150o - TAMB)/ θJA, where TAMB = Ambient temperature (˚C) and θJA = Thermal resistance, from junction to ambient, for a given package (˚C/W). For the SOIC-8 package θJA is 166˚C/W and for the SOT it is 230˚C/W. The SOIC-14 has a θJA of 130˚C/W. The TSSOP-14 has a θJA of 160˚C/W. 20078943 FIGURE 8. Composite Amplifier Frequency Response LAYOUT CONSIDERATIONS Whenever questions about layout arise, use the evaluation board as a guide. Evaluation boards are shipped with sample requests. To reduce parasitic capacitances ground and power planes should be removed near the input and output pins. Components in the feedback loop should be placed as close to the device as possible. For long signal paths controlled impedance lines should be used, along with impedance matching at both ends. Bypass capacitors should be placed as close to the device as possible. Bypass capacitors from each rail to ground are applied in pairs. The larger electrolytic bypass capacitors can be located anywhere on the board; however, the smaller ceramic capacitors should be placed as close to the device as possible. ESD PROTECTION The LMH6723/LMH6724/LMH6725 is protected against electrostatic discharge (ESD) on all pins. The LMH6723/ LMH6725 will survive 2000V Human Body Model or 200V Machine Model events. Under closed loop operation the ESD diodes have no effect on circuit performance. There are occasions, however, when the ESD diodes will be evident. If the LMH6723/LMH6724/ LMH6725 is driven into a slewing condition the ESD diodes will clamp large differential voltages until the feedback loop restores closed loop operation. Also, if the device is powered down and a large input signal is applied, the ESD diodes will conduct. VIDEO PERFORMANCE The LMH6723/LMH6724/LMH6725 has been designed to provide good performance with both PAL and NTSC composite video signals. The LMH6723/LMH6724/LMH6725 is specified for PAL signals. Typically, NTSC performance is marginally better due to the lower frequency content of the signal. Performance degrades as the loading is increased; www.national.com 14 LMH6723/LMH6724/LMH6725 Physical Dimensions inches (millimeters) unless otherwise noted 5-Pin SOT23 NS Product Number MF05A 8-Pin SOIC NS Product Number M08A 15 www.national.com LMH6723/LMH6724/LMH6725 Physical Dimensions inches (millimeters) unless otherwise noted (Continued) 14-Pin SOIC NS Product Number M14A 14-Pin TSSOP NS Product Number MTC14 www.national.com 16 National does not assume any responsibility for use of any circuitry described, no circuit patent licenses are implied and National reserves the right at any time without notice to change said circuitry and specifications. For the most current product information visit us at www.national.com. LIFE SUPPORT POLICY NATIONAL’S PRODUCTS ARE NOT AUTHORIZED FOR USE AS CRITICAL COMPONENTS IN LIFE SUPPORT DEVICES OR SYSTEMS WITHOUT THE EXPRESS WRITTEN APPROVAL OF THE PRESIDENT AND GENERAL COUNSEL OF NATIONAL SEMICONDUCTOR CORPORATION. As used herein: 1. Life support devices or systems are devices or systems which, (a) are intended for surgical implant into the body, or (b) support or sustain life, and whose failure to perform when properly used in accordance with instructions for use provided in the labeling, can be reasonably expected to result in a significant injury to the user. 2. A critical component is any component of a life support device or system whose failure to perform can be reasonably expected to cause the failure of the life support device or system, or to affect its safety or effectiveness. BANNED SUBSTANCE COMPLIANCE National Semiconductor manufactures products and uses packing materials that meet the provisions of the Customer Products Stewardship Specification (CSP-9-111C2) and the Banned Substances and Materials of Interest Specification (CSP-9-111S2) and contain no ‘‘Banned Substances’’ as defined in CSP-9-111S2. Leadfree products are RoHS compliant. National Semiconductor Americas Customer Support Center Email: [email protected] Tel: 1-800-272-9959 www.national.com National Semiconductor Europe Customer Support Center Fax: +49 (0) 180-530 85 86 Email: [email protected] Deutsch Tel: +49 (0) 69 9508 6208 English Tel: +44 (0) 870 24 0 2171 Français Tel: +33 (0) 1 41 91 8790 National Semiconductor Asia Pacific Customer Support Center Email: [email protected] National Semiconductor Japan Customer Support Center Fax: 81-3-5639-7507 Email: [email protected] Tel: 81-3-5639-7560 LMH6723/LMH6724/LMH6725 Single/Dual/Quad 370 MHz 1 mA Current Feedback Op Amp Notes