5V High Current Step-Down Switchers - Design Note 59 Ron Vinsant and Milton Wilcox volt • second balance is assured by the duty cycle limit of 50% inherent in the LT1241. The output inductor (L1) is made of Magnetics Kool-Mu material and is only 0.7 inches in diameter. Low Cost High Efficiency (80%), High Power Density DC/DC Converter The LT®1241 current mode PWM control IC can be used to make a simple high frequency step-down converter. This converter also has low manufacturing costs due to simple magnetic components. This circuit exhibits a wide input range of 30V to 60V while maintaining its 12A 5V output. It has short-circuit protection and uses minimal PC board area due to its 300kHz switching frequency. Short-circuit protection is provided through bootstrap operation of the LT1241. If the output is shorted the LT1241 limits its pulse width to ≤250ns. Because there is not enough current supplied to make the aux winding on the output inductor 15V, the LT1241 stops operation. It will then try to start by C11 charging through R4. If the output is still shorted it will stop again. Thus in a short, the circuit starts and stops, protecting itself from overload. Figure 1 shows the LT1241 being used to drive the switching transistor Q1 through a ferrite pulse transformer T2. This transformer is built on a high μ material resulting in an 11 turn bifilar wound toroid that is only 0.15 inches in diameter and can be surface mounted. T1 acts as a current sense transformer whose + INPUT 7o7 C5 ' 7 -9' D4 R9 36Ω .63 5 4 5 3 4 563/40/ ,00-.6 N" 5 CORE 8 2 + $ C4 ' ' 25V 5 #3 #(9" COILTRONICS $59 8 T2 '&&%#"$, C6 ' 3 L 4 8 4 C2 ' R2 L '# COMP OUTPUT V3&' RT/CT ISENSE GND 5 R5 L 4 '&&%#"$, + C7 ' 7 -9' + C3 ' 6 + 3 R3 8Ω D2 .#3$5- % BAT85 $ Q' /05&46/-&4405)&38*4&41&$*'*&% "--3&4*45"/$&4"3&*/0).48 "--$"1"$*5"/$&4"3&*/.*$30'"3"%47 .#3$5-.06/5*/(5"#*45*&%505)&%&7*$&4$"5)0%&4*/5&3/"--: 5.&5(-"4.11"'$03& Figure 1 06/92/59_conv 7 " $ ' 7 -9' VCC -5 6T D6 .63 7 2 7 "50" - 3 Ā 2 3 D5 /" 2 *3' 8 – R4 L – 7 '30.- 5 5 + L, LT, LTC, LTM, Linear Technology and the Linear logo are registered trademarks of Linear Technology Corporation. All other trademarks are the property of their respective owners. C8 ' 7 -9' R8 L RETURN = POWER GND = SIGNAL GND %/t' Synchronous Switching Eliminates Heat Sinks in a 50W DC/DC Converter The new LT1158 half-bridge N-channel power MOSFET driver makes an ideal synchronous switch driver to improve the efficiency of step-down (buck) switching regulators. The diode losses in a conventional stepdown regulator become increasingly significant as VIN is increased. By replacing the high current Schottky diode with a synchronously-switched power MOSFET, efficiencies well over 90% can be realized (see Figure 2). (2) 28mΩ power MOSFETs for each switch, reducing individual device dissipation to 0.7W worst case. This eliminates the need for heat sinks for operation up to 10A at a temperature of 50°C ambient. The inductor and current shunt losses for the Figure 3 circuit are 1.2W and 0.7W respectively at 10A. An additional loss potentially larger than those already mentioned results from the gate charge being delivered to multiple large MOSFETs at the switching frequency. This driver loss can only be controlled by running the oscillator at as low a frequency as practical — in the case of the Figure 3 circuit, 25kHz. A very low ESR (<20mΩ) output capacitor is used to limit output ripple to less than 50mVp-p with 2.5Ap-p ripple current. In the Figure 3 circuit an LT3525 provides a voltage mode PWM to drive the LT1158 input pin. The LT1158 drives 100 VIN = 12V The LT1158 also provides current limit for DC/DC converter applications. When the voltage across RS exceeds 110mV, the LT1158 fault pin conducts, and assumes control of the PWM duty cycle. This provides true current mode short-circuit protection with soft recovery. The Figure 3 regulator current limit is set at 15A which raises the dissipation in each bottom MOSFET to 1.7W during a short. Therefore 30°C/W heat sinking must be added for the bottom side MOSFETs if continuous short-circuit operation is required. Care should also be taken when routing the sense+ and sense– leads to prevent coupling from the inductor. EFFICIENCY (%) 90 VIN = 24V 80 70 60 0 2 6 4 8 10 OUTPUT CURRENT (A) %/t' Figure 2. Operating Efficiency for Figure 3 Circuit ' L ' 77*/ L L NI INV VREF + ' COMP V+ VC V+ + ' BIAS A T FB -5 IN / O' RS 7mΩ 7" OUT SEN+ + SEN– COUT ' * B DR FAULT + - ) L SRC L / 40'545 CIN ' (2) IRFZ44 B RT + (2) IRFZ44 * T DR ' CT %*4$)"3(& ' BST BST DR V+ LT3525 ' / .#3 B FB ' 27k Ā CINCOUT6/*5&%$)&.*$0/-9'7#.9-RS = 7*4)":6-530/*93$4 * = PARALLELED MOSFETS MAY REQUIRE INDIVIDUAL GATE DECOUPLING 3&4*45034$0/46-5."/6'"$563&343&$0..&/%"5*0/4 -."(/&5*$4.11"$03&563/4("8*3& %/t' Figure 3. High Efficiency 50W DC/DC Converter Data Sheet Download www.linear.com Linear Technology Corporation For applications help, call (408) 432-1900 dn59f_conv BA/GP 0492 190K • PRINTED IN THE USA 1630 McCarthy Blvd., Milpitas, CA 95035-7417 (408) 432-1900 ● FAX: (408) 434-0507 ● www.linear.com © LINEAR TECHNOLOGY CORPORATION 1992