Version 1.2 , February 2002 Application Note AN-SMPS-ICE2xXXX-1 CoolSET ICE2xXXX for OFF – Line Switch Mode Power Supply (SMPS) Authors: Harald Zöllinger Rainer Kling Published by Infineon Technologies AG http://www.infineon.com Power Management & Supply N e v e r s t o p t h i n k i n g ICE2xXXX for OFF – Line Switch Mode Power Supplies Contents: OPERATING PRINCIPLES ...................................................................................................................................... 3 PROTECTION FUNCTIONS ..................................................................................................................................... 9 OVERLOAD AND OPEN-LOOP PROTECTION (FIG. 6)........................................................................................... 11 OVERVOLTAGE PROTECTION DURING SOFT START (FIG. 7).............................................................................. 12 FREQUENCY REDUCTION ................................................................................................................................... 13 DESIGN PROCEDURE.......................................................................................................................................... 14 Input Diode Bridge (BR1):........................................................................................................................... 15 Determine Input Capacitor (C3): ................................................................................................................ 15 Transformer Design (TR1): ......................................................................................................................... 17 SENSE RESISTOR ................................................................................................................................................ 18 Winding Design: .......................................................................................................................................... 19 Output Rectifier (D1):.................................................................................................................................. 21 Output Capacitors (C5, C9): ....................................................................................................................... 22 Output Filter (L3, C23): .............................................................................................................................. 23 RC-Filter at Feedback Pin........................................................................................................................... 23 Soft-start capacitor ...................................................................................................................................... 24 VCC Capacitor: ........................................................................................................................................... 25 Start-up Resistor (R6, R7): .......................................................................................................................... 25 CLAMPING NETWORK:....................................................................................................................................... 26 CALCULATION OF LOSSES: ................................................................................................................................ 27 Switching losses:.......................................................................................................................................... 28 Conduction losses: ....................................................................................................................................... 28 REGULATION LOOP: .......................................................................................................................................... 29 Regulation Loop Elements:.......................................................................................................................... 30 Zeros and Poles of transfer characteristics: ............................................................................................... 31 Calculation of transient impedance ZPWM of ICE2AXXX ............................................................................. 32 Transfer characteristics:.............................................................................................................................. 33 CONTINUOUS CONDUCTION MODE (CCM) ....................................................................................................... 36 TRANSFORMER CALCULATION:.......................................................................................................................... 36 SLOPE COMPENSATION ...................................................................................................................................... 37 TRANSFORMER CONSTRUCTION ........................................................................................................................ 38 LAYOUT RECOMMENDATION:............................................................................................................................ 39 OUTPUT POWER TABLE ..................................................................................................................................... 40 SUMMARY OF USED NOMENCLATURE................................................................................................................ 41 REFERENCES...................................................................................................................................................... 42 AN-SMPS-ICE2xXXX-1 Page 2 of 44 Version 1.2 ICE2xXXX for OFF – Line Switch Mode Power Supplies Operating Principles The ICE2AXXX is designed for a current-mode flyback configuration in discontinous (DCM) or continous conduction (CCM) mode. The control circuit has a fixed frequency. The duty cycle (D) of the integrated CoolMOS Transistor is controlled to maintain a constant output voltage (VOUT). Fig. 1 shows the input voltage (VDC IN), the primary current(ILPK), and the secondary (ISEC) transformer currentof the flyback converter depicted on p. 3 When the CoolMOS Transistor is swiched on, the initial state of all windings on the transformer is at positive potential. The rectifier diode (D1) on the secondary side is reverse biased and therefore does not conduct. Consequently no current flows in the secondary winding. During this phase, energy is stored in the inductance of the primary winding and the transformer can be treated as a simple series inductor. Fig. 1 shows that there is a linear increase of the primary current (IPRI) while the CoolMOS Transistor is on. When the CoolMOS Transistor is swiched off, the voltage reverses on all transformer windings (flyback action) until it is clamped by rectifier diode on the secondary side. Now the secondary rectifier diode (D1) is conducting, and the magnetizing energy stored in the transformer core is transferred to the secondary side during the reset interval. In the discontinous conduction mode DCM the secondary current (ISEC) decreases from its peak value to zero (Fig. 1). During this period the whole energy stored in the primary inductance is transferred to the secondary side (neglecting losses and energy stored in the primary leakage inductance), then the next storage cycle starts. Taking into account the transformer turns ratio, the secondary voltage (VSEC) is “reflected” back (VR) to the primary winding and adds to the input voltage (VDC IN + VR). An additional transient voltage may appear on the primary winding due to energy stored in the uncoupled “leakage” inductance in the primary winding. This voltage is not clamped by the secondary side winding. If the flyback current (ILPK and ISEC) does not reach zero before the next “on” – cycle the converter is operating in continous conduction mode (Fig. 2). Note: When the system shifts to continous conduction operation, its transfer function is changed to a two pole system with low output impedance. In this case additional design rules have to be taken into account including different loop compensation and slope compensation on the primary side. AN-SMPS-ICE2xXXX-1 Page 3 of 44 Version 1.2 ICE2xXXX for OFF – Line Switch Mode Power Supplies Voltage and current waveforms in discontinous conduction mode (DCM) operation: Duty Cycle: D = 0,5 Duty Cycle: D < 0,5 VDC IN = VDC IN min VDC IN > VDC IN min VIN + VR VDC IN min + VR VDC IN VDC IN min Voltage ILPK IPEAK IPEAK IPEAK ILPK IPEAK ISEC ISEC Current 0 tON tOFF Light load Fig. 1 AN-SMPS-ICE2xXXX-1 Full load T 0 tON tOFF Duty Cycle: D= t ON T Page 4 of 44 Version 1.2 T ICE2xXXX for OFF – Line Switch Mode Power Supplies Comparison of continous conduction (CCM) and discontinous conduction (DCM) mode. CCM DCM VDC IN + VR VDC IN + VR VDC IN VDC IN ILPK IPEAK IPri0 ILPK IPEAK IPEAK ISEC ISEC ISec0 IPEAK 0 tON tOFF T 0 tON tOFF Fig. 2 AN-SMPS-ICE2xXXX-1 Page 5 of 44 Version 1.2 T ICE2xXXX for OFF – Line Switch Mode Power Supplies Input stage As shown in Fig. 3 the AC input power is rectified and filtered by the bridge rectifier (BR1) and the bulk capacitor C3. This create a DC high voltage bus which is connected to the primary winding of the transformer (TR1). The transformer is driven by the CoolSET rugged CoolMOS integrated high voltage, avalanche transistor, with an external sense resistor (R17) for precision current mesurement. Output stage The secondary winding power is rectified and filtered by a diode (D1), capacitors (C5, C9 and C20). The output LC-filter (L3, C23) reduces the output voltage ripple. Other output voltages Other output voltages can be realized by adjusting the transformer turn ratio and the output stage. Chip supply The current in the bias winding is rectified and filtered by a diode (D2) and a resistor (R8) in order to charge the the supply capacitor (C4). This creates a bias voltage that powers the CoolSET ICE 2AXXX. The resistors R6 and R7 charge the VCC Cap and supply the chip during startup. The Zener diode (D4) clamps the chip supply voltage (Vcc) in order to protect the chip in case of an over-voltage condition. Capacitor C13 filters high frequency ripples on the chip supply voltage (Vcc). Soft-Start A soft-start function is activated during start-up, and can be adjusted by capacitor C14. In addition to start-up, soft-start is activated at each restart attempt during auto-restart and when restarting after one of the several protection functions are activated. This effectively minimizes current and voltage stresses on the CoolMOS MOSFET, the snubber network, and the output rectifier during start-up. The soft-start feature further helps to minimize output overshoot and prevents saturation of the transformer during start-up. Clamping network The clamping network which consists of a diode (D3), a resistor (R10) and a capacitor (C12) clamps the voltage spike caused by the transformer leakage inductance to a safe value this limits the avalanche losses of the CoolMOS AN-SMPS-ICE2xXXX-1 transistor. Page 6 of 44 Version 1.2 ICE2xXXX for OFF – Line Switch Mode Power Supplies Control Loop The resistors R1 and R2 represent the voltage divider for the reference diode TL431CLP (IC2). R4 supplies the TL431CLP reference diode with a minimum current and R3 the LED of the optocoupler. The network which consists of capacitors C1 and C2 determines the corner frequencies fg1 and fg2. R5 sets the gain of the control loop. Slope Compensation The current mode controller becomes unstable whenever the steady – state duty cycle D is larger than 0.5. In order to realize a design with a duty cycle greater 0.5, the slope of the current needs to be compensated. The slope compensation is realized by the network consisting of capacitor C17, C18 and the resistor R19. Ripple Reduction Inductor L5 and capacitor C23 attenuate the differential – mode emission currents caused by the fundamental and harmonic frequencies of the primary current waveform. SMPS Calculation Software FLYCAL FLYCAL is an EXCEL spread sheet with all Equations needed for the easy calculaton of your SMPS. FLYCAL corresponds with the calculaton example in this application note. You only have to enter the main parameters of your application in FLYCAL and to follow step by step the principle outlined in the calculation example. FLYCAL contains all equations used in the example with the same consecutive numbering. AN-SMPS-ICE2xXXX-1 Page 7 of 44 Version 1.2 ICE2xXXX for OFF – Line Switch Mode Power Supplies Circuit Diagram: Fig. 3 AN-SMPS-ICE2xXXX-1 Page 8 of 44 Version 1.2 ICE2xXXX for OFF – Line Switch Mode Power Supplies Protection Functions The block diagram displayed in Fig. 4 shows the interal functions of the protection unit. The comparators C1, C2, C3 and C4 compare the soft-start and feedback-pin voltages. Logic gates connected to the comparator outputs ensure the combination of the signals and enables the setting of the “Error-Latch”. Fig. 4 AN-SMPS-ICE2xXXX-1 Page 9 of 44 Version 1.2 ICE2xXXX for OFF – Line Switch Mode Power Supplies Fig. 5 shows the relation between the voltages at the soft start (Vss) and the feedback pins (VFB) of ICE2AXXX, as a function of the supply voltage (Vcc) during an overvoltage condition at CoolSET soft start. Depending on the voltage levels at the inputs, the overvoltage and (Vcc – PIN 7) and overload (VFB – PIN 2) protection functions are activated. Soft start Voltage 6.5V Overload & open loop Detection 5.3V Normal Operation 4.0V Overvoltage shutdown when Vcc exceeds 16,5V 6.5V Soft-start 4.8V 0.8V Feedback Voltage Fig. 5 AN-SMPS-ICE2xXXX-1 Page 10 of 44 Version 1.2 ICE2xXXX for OFF – Line Switch Mode Power Supplies Overload and Open-Loop Protection • Feedback voltage (VFB) exceeds 4.8V and soft start voltage (VSS) is above 5.3V (soft start is completed) (t1) • After a 5µs delay the CoolMOS is switched off (t2) • Voltage at Vcc – Pin (VCC) decreases to 8.5V (t2) • Control logic is switched off (t3) • Start-up resistor charges Vcc capacitor (t3) • Operation starts again with soft start after Vcc voltage has exceeded 13.5V (t4) t1, t2 VCC VFB VSS t1 t2 t3 t4 Fig. 6 Fig. 7 t3 t4 VCC t1, t2 VFB VSS Fig. 8 AN-SMPS-ICE2xXXX-1 Page 11 of 44 Version 1.2 ICE2xXXX for OFF – Line Switch Mode Power Supplies Overvoltage Protection During Soft Start • Feedback voltage (VFB) exceeds 4.8V and soft-start voltage (VSS) is below 4.0V (soft start phase) (t1) • Voltage at Vcc pin (VCC) exceeds 16.5V (t2) • CoolMOS transistor is immediately switched off (t2) • Voltage at VCC pin decreases to 8.5V (t3) • Control logic is switched off (t3) • Start-up resistor charges VCC capacitor (t4) • Operation starts again with soft start after VCC voltage has exceeded 13.5V (t5) t2 t3 VCC VFB VSS t1 t2 t3 t4 t5 Fig. 9 Fig. 10 t1, t2 t4 t5 VCC t3 VFB VSS Fig. 11 AN-SMPS-ICE2xXXX-1 Page 12 of 44 Version 1.2 ICE2xXXX for OFF – Line Switch Mode Power Supplies Frequency Reduction The frequency of the oscillator depends on the voltage at pin FB. Below a voltage of typ. 1.75V the frequency decreases down to 21.5 kHz. Due to this frequency reduction the power losses in low load condition can be reduced very effectively. This dependency is shown in Fig. 12 Fig. 12 AN-SMPS-ICE2xXXX-1 Page 13 of 44 Version 1.2 ICE2xXXX for OFF – Line Switch Mode Power Supplies Design Procedure for fixed frequency Flyback Converter with ICE2AXXX operating in discontinuous current mode. Procedure Example Define input Parameters: Minimal AC input voltage: VAC min 90V Maximal AC input voltage: VAC max 264V Line frequency: fAC 50Hz Max. output power: POUT max 50W Nom. output power: POUT nom 40W Min. output power: POUT min 0,5W Output voltage: VOUT 16V Output ripple voltage: VOUT Ripple 0,05V Reflection voltage: VRmax 120V Estimated efficiency: η 0,85 DC ripple voltage: VDC IN Ripple 30V Auxiliary voltage: VAux 12V Optocoupler gain: GC 1 ICE2A365 Used CoolSET There are no special requirements imposed on the input rectifier and storage capacitor in the flyback converter. The components will be selected to meet the power rating and hold-up requirements. Maximum input power: PIN max = POUT max η AN-SMPS-ICE2xXXX-1 (Eq 1) PIN max = Page 14 of 44 50W = 59W 0,85 Version 1.2 ICE2xXXX for OFF – Line Switch Mode Power Supplies Input Diode Bridge (BR1): I ACRMS = PIN MAX V AC min ⋅ cos ϕ (Eq 2) I ACRMS = 59W = 1,09 A 90V ⋅ 0,6 Maximum DC IN voltage V DC max PK = V AC max ⋅ 2 (Eq 3) V DC max PK = 264V ⋅ 2 = 373V Determine Input Capacitor (C3): Minimum peak input voltage at ”no load” condition V DC min PK = V AC min ⋅ 2 (Eq 4) V DC min PK = 90V ⋅ 2 = 127V we choose a ripple voltage of 30V V DC min = V DC min PK − V Ripple (Eq 5) V DC min = 127V − 30V = 97V Calculation of discharging time at each half-line cycle: V æ ö ç arcsin DC min V DC min PK TD = 5ms ⋅ çç1 + 90 çç è (Eq 6) 97V ö æ ç arcsin 127V = 7,7ms T D = 5ms ⋅ ç1 + ç 90 ç è Required energy at discharging time of C3: W IN = PIN max ⋅ TD (Eq 7) WIN = 59W ⋅ 7,7ms = 0,46Ws (Eq 8) CIN = Calculation of input capacitor value CIN: CIN = 2 ⋅ W IN 2 V DC min PK 2 − V DC min AN-SMPS-ICE2xXXX-1 2 ⋅ 0,46Ws 16129V 2 − 9409V 2 Page 15 of 44 = 136,9µF Version 1.2 ICE2xXXX for OFF – Line Switch Mode Power Supplies Alternatively a rule of thumb for choosing CIN can be applied: Input voltage CIN 115V 2µF/W 230V 1µF/W 85V ...270V 2 ...3µF/W.................... 59W ⋅ 3 µF = 177 µF W Recalculation of input Capacitor: Select a capacitor from the Epcos Databook of Aluminium Electrolytic Capacitors. The following types are preferred: For 85°C Applications: Series B43303-........ 2000h life time B43501-........ 10000h life time For 105°C Applications: Series B43504-........ B43505-........ 2 V DC min = V DC min PK − We choose 150µF 400V (based on Eq 8) 3000h life time 5000h life time 2 ⋅ W IN C IN (Eq 9) V DC min = 16129V 2 − 2 ⋅ 0,46Ws = 100V 150 µF Note that special requirements for hold up time, including cycle skip/dropout, or other factors which affect the resulting minimum DC input voltage and capacitor time should be considered at this point also. AN-SMPS-ICE2xXXX-1 Page 16 of 44 Version 1.2 ICE2xXXX for OFF – Line Switch Mode Power Supplies Transformer Design (TR1): Calculation of peak current of primary inductance: Dmax = VR max VR max + VDC min (Eq 10a) D max = 120V = 0,55 120V + 100V I LPK = 2 ⋅ PIN MAX V DC min ⋅ Dmax (Eq 10b) I LPK = 2 ⋅ 59W = 2,16 A 100V ⋅ 0,55 I LRMS = I LPK ⋅ D max 3 (Eq 11) I LRMS = 2,16 A ⋅ 0,55 = 0,92 A 3 Calculation of primary inductance within the limit of maximum Duty-Cycle : LP = Dmax ⋅ V DC min I LPK ⋅ f (Eq 12) Select core type and inductance factor (AL) from Epcos LP = 0,55 ⋅100V 2,16 A ⋅100 *10 3 Hz = 253µH Selected core: E 25/13/7 Material = N27 „Ferrite Databook“ or CD-ROM AL = 111 nH „Passive Components“. s = 0,75 mm Fix maximum flux density: Bmax ≈ 0,2T ...0,3T for ferrite cores depending on core material. We choose 0,2T for material N27 Ae = 52 mm2 AN = 61 mm2 lN = 57,5 mm The number of primary turns can be calculated as: LP AL NP = (Eq 13) NP = 253µH = 47,7 turns 111nH we choose Np = 46 turns The number of secondary turns can be calculated as: Ns = N P ⋅ (VOUT + V FDIODE ) V R max (Eq 14) Ns = 46 ⋅ (16V + 0,8V ) = 6,46 120V we choose NS = 7 turns The number of auxiliary turns can be calculated as: N Aux = Ns ⋅ (V Aux + V FDIODE ) V R max (Eq 15) Ns = 46 ⋅ (12V + 0,7V ) = 5,6 120V we choose NAux = 5 turns AN-SMPS-ICE2xXXX-1 Page 17 of 44 Version 1.2 ICE2xXXX for OFF – Line Switch Mode Power Supplies Verification of primary inductance, primary peak current, max. duty cycle, flux density and gap: L P = N P2 ⋅ Al I LPK = VR = PIN max 0,5 ⋅ Lp ⋅ f (VOUT + V FDIODE ) ⋅ N P Ns (Eq 16) L P = 46 2 ⋅111nH = 235µH (Eq 17) I LPK = (Eq 18) VR = 59W 0,5 ⋅ 235µH ⋅100 *10 3 Hz = 2,24 A (16V + 0,8V ) ⋅ 46 = 110V 7 D max = L P ⋅ I LPK ⋅ f V DC min (Eq 19) D max = 235µH ⋅ 2,24 A ⋅100kHz = 0,53 100V D ' max = L P ⋅ I LPK ⋅ f VR (Eq 20) D ' max = 235µH ⋅ 2,24 A ⋅100kHz = 0,47 110V B max = L P ⋅ I LPK N P ⋅ Ae (Eq 21) B max = (Eq 22) s= s= 4 ⋅ π ⋅10 −7 ⋅ N P2 ⋅ Ae LP 235µH ⋅ 2,24 A 46 ⋅ 52mm 2 = 210mT 4 ⋅ π ⋅10 −7 ⋅ 46 2 ⋅ 52mm 2 = 0,588mm 235µH Sense resistor The sense resistance RSense can be used to individually define the maximum peak current and thus the maximum power transmitted. Caution: When calculating the maximum peak current, short term peaks in output-power must also be Vcsth = 1.0V typ. (taken from data sheet) taken into consideration. RSense = Vcsth I LPK (Eq23) R Sense = 1,0V = 0,45Ω 2,24 A we select 0,43Ω ILPK = 2,33A POUTmax = 54W AN-SMPS-ICE2xXXX-1 Page 18 of 44 Version 1.2 ICE2xXXX for OFF – Line Switch Mode Power Supplies Winding Design: see also page 38 Transformer Construction The primary winding of 46 turns has to be divided into 23+23 turns in order to get the best coupling between primary and secondary winding. From bobbin datasheet E25/13/7: BW = 15,6mm The effective bobbin width and winding cross Margin determined: M = 0mm we use triple insulated wire for secondary section can be calculated as: winding BWe = BW − 2 ⋅ M ANe = AN ⋅ BWe BW (Eq 24) BWe = 15,6mm (Eq 25) ANe = 61mm 2 Calculate copper section for primary and secondary winding: The winding cross section AN has to be subdivided according to the number of windings. Primary winding 0,5 Secondary winding 0,45 Auxiliary winding 0,05 We calculate the available area for each winding: Copper space factor fCu :0,2 ....0,4 AP = 0,5 ⋅ AN ⋅ f Cu ⋅ BWe N P ⋅ BW Used for calculation: fCu =0,3 (Eq 26) AP = 0,5 ⋅ 61mm 2 ⋅ 0,3 = 0,2mm 2 46 AWG = 9,97 ⋅ (1,8277 − (2 ⋅ log(d ))) (Eq 27) AN-SMPS-ICE2xXXX-1 Page 19 of 44 diameter dp ≈ 0,5mm 25 AWG Version 1.2 ICE2xXXX for OFF – Line Switch Mode Power Supplies As = 0,45 ⋅ AN ⋅ f Cu ⋅ BWe N s ⋅ BW (Eq 28) As = 0,45 ⋅ 61mm 2 ⋅ 0,3 = 1,18mm 2 7 diameter ds 2 x 0,8mm Aaux = 0,05 ⋅ AN ⋅ f Cu ⋅ BW e N aux ⋅ BW (Eq 29) Aaux = 2 x 20 AWG 0,05 ⋅ 61mm 2 ⋅ 0,3 = 0,18mm 2 5 diameter da ≈ 0,5mm 25 AWG With the effective bobbin width we check the number of turns per layer: NP = BWe dP Primary: (Eq 30) NP = 15,6mm = 31 turns per layer 0,46mm 2 layer needed Secondary: NS = 15,6mm = 6 turns per layer 2 ⋅1,21mm 2 layer needed Auxiliary: AN-SMPS-ICE2xXXX-1 Page 20 of 44 1 layer ! Version 1.2 ICE2xXXX for OFF – Line Switch Mode Power Supplies Output Rectifier (D1): The output rectifier diodes in flyback converters are subjected to a large PEAK and RMS current stress. The values depend on the load and operating mode. The voltage requirements depend on the output voltage and the transformer winding ratio. Calculation of the maximum reverse voltage: æ N ö V RDiode = VOUT + ççV DC max PK ⋅ S N P è (Eq 31) 7 ö æ V RDiode = 16V + ç 373V ⋅ = 72,8V 46 è Calculation of the maximum current on secondary side: I SPK = I LPK ⋅ NP NS I SRMS = I SPK ⋅ 1 ⋅ D' max 3 AN-SMPS-ICE2xXXX-1 (Eq 32) (Eq 33) I SPK = 2,33 A ⋅ 46 = 15,3 A 7 I SRMS = 15,3 A ⋅ 1 ⋅ 0,47 = 5,9 A 3 Page 21 of 44 Version 1.2 ICE2xXXX for OFF – Line Switch Mode Power Supplies To calculate the output capacitor, it is necessary Output Capacitors (C5, C9): to set the maximum voltage overshoot in case of switching off @ maximum load condition. Output capacitors are highly stressed in flyback After switching off the load, the control loop converters. Normally the capacitor will be selected needs about 10...20 internal clock periods to for 3 major parameters: capacitance value, low reduce the duty cycle. ESR and ripple current rating. Max. voltage overshoot: ∆VOUT ∆VOUT = 0,5V Number of clock periods: nCP nCP = 20 C OUT = I OUT max ⋅ n CP ∆VOUT ⋅ f I OUT = 3,1A ⋅ 20 = 1250µF (Eq 34) C OUT = POUT max VOUT (Eq 34a) I OUT = I Ripple = I SRMS 2 − I OUT 2 (Eq 34b) I Ripple = 5,9 A 2 − 3,1A 2 = 5,0 A 0,5V ⋅100 *10 3 Hz 50W = 3,1A 16V Select a capacitor out of Epcos Databook for Aluminium Electrolytic Capacitors. The following types are preferred: We select 1000µF 35V (based on Eq 34): For 105°C Applications low impedance: B41859-F7108-M Series B41856-........ 4000h life time ESR ≈ Zmax = 0,034Ω @ 100kHz For 105°C Applications lowest impedance: Series B41859-........ 4000h life time IacR = 1,94A we need 2 capacitors in parallel AN-SMPS-ICE2xXXX-1 Page 22 of 44 Version 1.2 ICE2xXXX for OFF – Line Switch Mode Power Supplies Output Filter (L3, C23): The output filter consists of one capacitor (C23) and one inductor (L3) in a L-C filter topology. Zero frequency of output capacitor (C5,C9, C20) and associated ESR: f ZCOUT = 1 2 ⋅ π ⋅ R ESR ⋅ C OUT (Eq 35) Calculation of the inductance (L3) needed for the f ZCOUT = 1 = 4,7 kHz 2 ⋅ π ⋅ 0,034Ω ⋅1000 µF We use CLC (C23) 470uF substitution of the zero caused by the output capacitors: LOUT = (C OUT ⋅ R ESR )2 C LC (Eq 36) LOUT = (1000uF ⋅ 0,034Ω) 2 = 2,5uH 470uF RC-Filter at Feedback Pin (C6, R9) The RC Filter at the Feedback pin is designed to supress any noise which may be coupled in on this track. Typical values: C6 : 1...4,7nF R9 : 22 Ohm Note that the value of C6 interacts with the internal pullup (3,7k typical) to create a filter. AN-SMPS-ICE2xXXX-1 Page 23 of 44 Version 1.2 ICE2xXXX for OFF – Line Switch Mode Power Supplies Soft-start capacitor (C14) The voltage at the soft-start pin together with feedback voltage controls the overvoltage, open loop and overcurrent protection functions. The softstart capacitor must be calculated in such a way that the output voltage and thus the feedback voltage is within the working range (VFB < 4.8V) before the over-current threshold (typ. 5.3V) is reached. Rsoft start = 50kΩ typ (from datasheet). t Sstart = Vo 2 ⋅ C SS = t Sstart ⋅ Cout POUT max − POUTnom (Eq37) 1 − R Soft − Start ⋅ ln(1 − V Soft − Start1 V REF (Eq38) ) t Sstart = 16V 2 ⋅ C SS = 45ms ⋅ 2470uF = 45ms 54W − 40W 1 5,1V − 50kΩ ⋅ ln(1 − ) 6,5V = 586nF choose 560nF AN-SMPS-ICE2xXXX-1 Page 24 of 44 Version 1.2 ICE2xXXX for OFF – Line Switch Mode Power Supplies VCC Capacitor: (C4, C13) The VCC capacitor needs to ensure the power supply of the IC until the power can be provided by the auxiliary winding. In parallel with the VCC Capacitor it is recommended to use a 100nF ceramic capacitor very close between pin 7 & 8. Alternatively, an HF type electrolytic with low ESR and ESL may be used. CVCC = I VCC 3 ⋅ t softstart VCCHY * 2 3 (Eq 39) CVCC = 8,2mA ⋅ 45ms 2 * = 49uF 3 5V we choose 47uF Start-up Resistor (R6, R7): ICCLmax = 55µA IVCC1 = max. quiescent current (Control IC) ILoadC = 70µA ILoadC = VCC-Capacitor load-current (C4) CVCC = Value of VCC-capacitor (C4) RStart = VDC min IVCC1 + I LoadC (Eq 40) 100V = 801kΩ (55 + 70) µA R Start = R6 = R7 =1/2 RStart = 400kΩ Choose 2 with value: 390kΩ Start up Time tStart: t Start = CVCC ⋅ VCCon I LoadC (Eq 41) t Start = 47 µF ⋅13,5V = 8,7 s 73µA Note: Before the IC can be plugged into the application board, the VCC capacitor must be always discharged! AN-SMPS-ICE2xXXX-1 Page 25 of 44 Version 1.2 ICE2xXXX for OFF – Line Switch Mode Power Supplies Clamping Network: (R10/C12/D3) VClamp = V( BR ) DSS − V DC max − V R (Eq 42) VClamp = 650V − 373V − 110V = 166V For calculating the clamping network it is necessary to know the leakage inductance. The most common way is to have the value of the leakage inductance (LLK) given in percentage of the primary inductance (Lp). If it is known that the transformer construction is very consistent, measuring the primary leakage inductance by shorting the secondary windings will give an exact number (assuming the availability of a good LCR In our example we choose 5% of the primary analyser). inductance for leakage inductance. L LK = Lp ⋅ x% L LK = 235µH ⋅ 5% = 11,8µH C Clamp = I LPK 2 ⋅ L LK V R + VClamp ⋅ VClamp ( ) (Eq 43) C Clamp = (2,24 A) 2 ⋅11,8µH = 1,2nF ≈ (110V + 166V )⋅166V we choose 1,5nF RClamp = (VClamp + V R )2 − V R2 0,5 ⋅ L LK ⋅ I LPK ⋅ f 2 (Eq 44) RClamp = (166V + 110V )2 − 110V 2 0,5 ⋅ 11,8µH ⋅ (2,24 A) 2 ⋅ 100 * 103 Hz = 23,9kΩ we choose 22kΩ AN-SMPS-ICE2xXXX-1 Page 26 of 44 Version 1.2 ICE2xXXX for OFF – Line Switch Mode Power Supplies Calculation of Losses: Input diode bridge (BR1): PDIN = I ACRMS ⋅ V F ⋅ 2 (Eq 45) PDIN = 1,1A ⋅1V ⋅ 2 = 2,2W Copper resistivity p100 @ 100°C = 0,0172Ωmm /m 2 Calculation of copper resistance RCu: RPCu = l N ⋅ N P ⋅ p100 AP (Eq 46) R PCu = RSCu = 0,0644m ⋅ 46 ⋅17,2mΩmm 2 / m 0,46mm 2 = 277,1mΩ 0,0644m ⋅ 7 ⋅ 17,2mΩmm2 / m = 6,6mΩ 2,10mm 2 Calculation of copper losses (TR1): 2 PPCu = I LPK ⋅ D MAX ⋅ 1 ⋅ R PCu 3 (Eq 47) 2 PSCu = I SPK ⋅ D ' MAX ⋅ 1 ⋅ R SCu 3 PPCu = (2,33 A) 2 ⋅ 0,53 ⋅ 1 ⋅ 277,1mΩ = 225,7 mW 3 PSCu = (15,3 A) 2 ⋅ 0,47 ⋅ 1 ⋅ 2,01mΩ = 227,4mW 3 PCu = 225,7mW + 227,4mW = 453,1mW Output rectifier diode (D1): PDDIODE = I SPK ⋅ D' max ⋅ V FDIODE 3 AN-SMPS-ICE2xXXX-1 (Eq 48) PDDIODE = 15,3 A ⋅ Page 27 of 44 0,47 ⋅ 0,8V = 5W 3 Version 1.2 ICE2xXXX for OFF – Line Switch Mode Power Supplies COOLMOS TRANSISTOR: ICE2A365 Co(er) = 30pF Calculated @ VDCmin = 100V CO ≈ 80pF (CO = CO(er) + CExtern) RDSON = 1,1Ω (@ 125°C) (see also ICE2AXXX Data Sheet) Switching losses: 2 PSON = 1 ⋅ C O ⋅ V DC min ⋅ f 2 (Eq 49) PSON = 1 ⋅ 80 pF ⋅100V 2 ⋅100 *10 3 Hz = 40mW 2 Conduction losses: 2 PD = 1 ⋅ R DSON ⋅ I LPK ⋅ D max 3 (Eq 50) PD = 1 ⋅1Ω ⋅ (2,33 A) 2 ⋅ 0,53 = 0,95W 3 Summary of Losses: PLosses = PSON + PD (Eq 51) PLosses = 40mW + 950mW = 0,99W Thermal Calculation: Table of typical thermal Resistance [ Heatsink No 3 cm² 6 cm² DIP8 90 64 56 DIP7 96 72 65 K ]: W TO220 74 dT = PLosses * Rth (Eq 52) Tj = dT + Ta (Eq 53) AN-SMPS-ICE2xXXX-1 dT = 0,99W * 56 K = 55,4 K W Tj = 55,4 K + 50°C = 115,4°C Page 28 of 44 Version 1.2 ICE2xXXX for OFF – Line Switch Mode Power Supplies 6,5 Regulation Loop: 3,7 Reference: TL431 (IC2) FB VFB VREF =2,5V IKAmin=1mA Fig. 13 Optocoupler: SFH617-3 (IC1) Gc = 1 ...2 ≡ CTR 100% ...200% Vout VFD = 1,2V IFmax =20mA (maximum current limit) R3 R1 R4 R5 Primary side: C1 Feedback voltage: C2 Values from ICE2AXXX datasheet VRef int = 6,5V typ. TL431 R2 VFBmax = 4,5V Av = 3,65 Fig. 14 RFB = 3,7k typ. I FB max = I FB min = VRe f int R FB VRe f int − V FB max R FB (Eq 54) (Eq 55) I FB max = 6,5V = 1,76mA 3,7kΩ I FB min = 6,5V − 4,6V = 0,5mA 3,7kΩ Secondary side: æV ö R1 = R2 çç OUT − 1 V è REF (Eq 56) æ 16V ö R1 = 4,3k ⋅ çç − 1 = 23,22k è 2,5V (Eq 57) R3 ≥ the value of R2 can be fixed at 4,3k R3 ≥ (VOUT − (V FD + V REF ) ) I F max I æ ö V FD + ç R3 ⋅ FB min Gc è R4 ≤ I KA min AN-SMPS-ICE2xXXX-1 (Eq 58) (16V − (1,2V + 2,5V )) = 0,74k ≈ 0,75k 20mA æ 0,5mA ö 1,2V + 0,75k ⋅ ç è 1 = 1,58k ≈ 1,5k R4 ≤ 1mA Page 29 of 44 Version 1.2 ICE2xXXX for OFF – Line Switch Mode Power Supplies Regulation Loop Elements: FPWR(p) VIN FLC(p) Vo KVD KFB Fr(p) + Vref Fig. 15 Transfer Characteristics of Regulation Loop Elements: K FB = GC ⋅ 3k 7 R3 (Eq 59) Feedback K VD = V R2 = REF R1 + R 2 VOUT (Eq 60) VoltageDivider (Eq 61) Powerstage (Eq 62) Output filter FPWR ( p) = 1 Z PWM æ ö ç (1 + p ⋅ R ESR ⋅ C 5 ) R L ⋅ L P ⋅ f ⋅η ç ⋅ ⋅ç 2 ö æ RL ö ç æç ÷ ç ç1 + p ⋅ çç 2 + R ESR ÷÷ ⋅ C 5 ÷ è è è ZPWM = Transimpedance ∆VFB/∆ID FLC ( p) = Fr ( p) = 1 + p ⋅ R ESR ⋅ C9 1 + p ⋅ RESR ⋅ C9 + p 2 ⋅ L ⋅ C9 1 + p ⋅ R5 ⋅ (C1 + C 2 ) R1 ⋅ R 2 p⋅ ⋅ C1 ⋅ (1 + p ⋅ R5 ⋅ C 2) R1 + R 2 AN-SMPS-ICE2xXXX-1 Page 30 of 44 (Eq 63) Regulator Version 1.2 ICE2xXXX for OFF – Line Switch Mode Power Supplies Zeros and Poles of transfer characteristics: Poles of powerstage @ min. and max. load: R LH = f OH = f OL = VOUT 2 16V 2 = = 4,9Ω POUT max 54W 1 R LL = (Eq 64) 1 π ⋅ R LL ⋅ C 5 f OL = (Eq 65) 1 = 31,1Hz π ⋅ 4,9Ω ⋅ 2000µF (Eq 66) 1 = 0,31Hz π ⋅ 512Ω ⋅ 2000µF (Eq 67) f OH = π ⋅ R LH ⋅ C 5 VOUT 2 16V 2 = = 512Ω POUT min 0,5W We use the gain (Gc) of the optocoupler stage KFB and the voltage divider KVD as a constant. K FB = GC ⋅ 3k 7 R3 K VD = V R2 = REF R1 + R 2 VOUT KFB = 4,9 KVD = 0,15 GFB = 13,9db GVD = -16,4db With adjustment of the transfer characteristics of the regulator we want to reach equal gain within the operating range and to compensate the pole fo of the powerstage FPWR(ω). Because of the compensation of the output capacitor‘s zero (see page 22 Eq35, Eq36) we neglect it as well as the LC-Filter pole. Consequently the transfer characteristic of the power stage is reduced to a single-pole response. In order to calculate the gain of the open loop we have to select the cross-over frequency. We calculate the gain of the Power-Stage with max. output power at the selected cross-over frequency fg = 3kHz: AN-SMPS-ICE2xXXX-1 Page 31 of 44 Version 1.2 ICE2xXXX for OFF – Line Switch Mode Power Supplies Calculation of transient impedance ZPWM of ICE2AXXX The transient impedance defines the direct relationship between the level of the peak current and the feedback pin voltage. It is required for the calculation of the power stage amplification. PWM-Op gain -Av = 3,65 (according to datasheet) Z PWM = ∆VFB R = Av ⋅ sense ∆I pk Vcsth Z PWM = ∆V FB 0,43Ω V = 3,65 ⋅ = 1,57 ∆I pk 1,00V A (Eq 68) Gain @ crossover frequency: FPWR ( fg ) = 1 Z PWM ö æ ç ç RL ⋅ L p ⋅ f ⋅ η ç 1 ⋅ ⋅ ç 2 2 ç 1 + æç fg ö÷ ç fo ÷ ç è è (Eq 69) ö æ ç ç 5,1R ⋅ 235µH ⋅100kHz ⋅ 0,8 ç 1 1 FPWR (3kHz) = ⋅ ⋅ = 0,05 ç 2 1,7 2 3000 æ ö ç 1+ ç ç 31,1 ÷÷ ç è è GPWR(3kHz) = -26,2db AN-SMPS-ICE2xXXX-1 Page 32 of 44 Version 1.2 ICE2xXXX for OFF – Line Switch Mode Power Supplies Transfer characteristics: 50 Gr(ω) GPWR(ω) KFB Low-load 0 KVD GLC(ω) GPWR(ω) 50 1 10 100 3 1 10 1 10 4 5 1 10 Full-load Fig. 16 At the crossover frequency (fg) we calculate the open loop gain: Gol(ω) = Gs ( ω) + Gr ( ω) = 0. With the equations for the transfer characteristics we calculate the gain of the regulation loop @ fg. For the gain of the regulation loop we calculate: Gs = GFB + GPWR + GVD = 13,9db – 26,2db – 16,4db Gs = -28,7db We calculate the separate components of the regulator: Gs (ω) + Gr ( ω) = 0 Gr = 0 – (-28,7db) = 28,7db AN-SMPS-ICE2xXXX-1 Page 33 of 44 Version 1.2 ICE2xXXX for OFF – Line Switch Mode Power Supplies Fr ( p) = 1 + p ⋅ R5 ⋅ (C1 + C 2) ) R1 ⋅ R 2 p⋅ ⋅ C1 ⋅ (1 + p ⋅ R5 ⋅ C 2) R1 + R 2 Gr = 20 ⋅ log R5 ⋅ (R1 + R 2) R1 ⋅ R 2 Gr R5 = 10 20 ⋅ R5 = 10 fp = 1 2 ⋅ π ⋅ R5 ⋅ C 2 C2 = 32 , 2 20 R1 ⋅ R 2 R1 + R 2 ⋅ 3,65k = 99,15k ≈ 100k (Eq 70) 1 2 ⋅ π ⋅ R5 ⋅ fg C2 = 1 = 530 pF ≈ 560pF 2 ⋅ π ⋅100k ⋅ 3kHz (Eq 71) In order to have enough phase margin @ low load condition we select the zero frequency of the compensation network to be at the middle between the min. and max. load poles of the power stage. f om = f oh ⋅ 10 fz = 0,5⋅log f ol f oh 1 2 ⋅ π ⋅ R5 ⋅ (C1 + C 2) f om = 31,1Hz ⋅10 C1 = C1 = AN-SMPS-ICE2xXXX-1 0,5⋅log 0,15 31,1 = 3,2 Hz 1 − C2 2 ⋅ π ⋅ R5 ⋅ fom 1 − 560 pF = 492nF ≈ 470nF 2 ⋅ π ⋅100k ⋅ 3,2 Hz Page 34 of 44 (Eq 72) Version 1.2 ICE2xXXX for OFF – Line Switch Mode Power Supplies Open Loop Gain 80 Low-load Full-load 67 54 41 28 15 2 11 24 37 50 1 10 100 1 10 3 4 1 10 5 1 10 Fig. 17 Open Loop Phase 10 28 66 104 142 180 1 10 100 1 10 3 4 1 10 5 1 10 Fig. 18 AN-SMPS-ICE2xXXX-1 Page 35 of 44 Version 1.2 ICE2xXXX for OFF – Line Switch Mode Power Supplies Continuous Conduction Mode (CCM) Ipk Iprim Isec A*Ipk tON tOFF Fig. 19 Transformer calculation: The transformer is calculated in such a way that DCM operation is just barely reached (A=0) at minimum output power POmin. Pomin = 2W Pomax = 10W Dmax = 0,6 p= p= Po max Po min Ipk = Lp = Po min + Po max Dmax ⋅ Vdc min ⋅ η Po max ⋅ ( p + 1)2 * Dmax Ipk 2 ⋅ f ⋅ p AN-SMPS-ICE2xXXX-1 10W =5 2W Ipk = Lp = 2W + 10W = 0,25 A 0,6 ⋅ 100V ⋅ 0,8 10W ⋅ (5 + 1)2 * 0,6 0,25 2 ⋅ 100kHz ⋅ 5 Page 36 of 44 = 6,91mH Version 1.2 ICE2xXXX for OFF – Line Switch Mode Power Supplies Slope Compensation Slope compensation is necessary for stable regulator operation in Continuous Conduction Mode (CCM), up to and beyond a duty cycle of 0.5 (see also [4]). An simple method of slope compensation using the components R19, C17 and C18 is illustrated in the circuit diagram on page 3 . VFB -VFBkorr Ipk mkorr = m2/2 Iprim m1=Vi/Lp m2=n*Vo/Lp ton Isec T Fig. 20 n= V R = n ⋅ Vo m2 = n ⋅ Vo V R = Lp Lp np ns m korr = V m2 = R 2 2 ⋅ Lp For duty cycle = 0,5 applies: m korr = æ V ⋅ 5us ö V FBkorr = ç R ⋅ Z PWM ç 2⋅ Lp è V FBkorr 5us CComp (C17) is selected at 10nF. C18 is selected at 100nF. RComp (R19): RComp = − t æ V ö lnçç1 − FBkorr ⋅ C Comp VCC è AN-SMPS-ICE2xXXX-1 Page 37 of 44 Version 1.2 ICE2xXXX for OFF – Line Switch Mode Power Supplies Transformer Construction The winding topology has a considerable influence on the performance and reliability of the transformer. In order to reduce leakage inductance and proximity to acceptable limits, the use of a sandwich construction is recommended. In order to meet international safety requirements a transformer for Off - Line power supply must have adequate insulation between primary and secondary windings. This can be achieved by using a margin-wound construction or by using triple insulated wire for the secondary winding. The creepage distance for the universal input voltage range is typically 8mm. This results in a minimum margin width (as a half of the creepage distance) of 4mm. Additionally the neccesary insulation between primary and secondary winding is provided using three layers of basic insulation tape. Example of winding topology for margin wound transformers: BW* BWe Primary second Creepage half distance Secondary Triple insulation Auxiliary Primary first half margin margin Fig. 21 Example of winding topology with triple insulated wire for secondary winding: BW* Primary second half Triple Insulated Secondary Wire Auxiliary Primary first half Fig. 22 BW* : value from bobbin datasheet AN-SMPS-ICE2xXXX-1 Page 38 of 44 Version 1.2 ICE2xXXX for OFF – Line Switch Mode Power Supplies Layout Recommendation: Fig. 23 In order to avoid crosstalk on the board between power and signal path we have to use care regarding the track layout when designing the PCB. The power path (see Fig. 23) has to be as short as possible and needs to be separated from the VCC Path and the feedback path. All GND paths have to be connected together at pin 8 (star ground) of ICE2AXX. AN-SMPS-ICE2xXXX-1 Page 39 of 44 Version 1.2 ICE2xXXX for OFF – Line Switch Mode Power Supplies CoolSET Table DevICE Package Current Rdson Pout @ Pout @ A Ω 190Vacin 85Vacin Ta=75°C / Tj = 125°C Ta=75°C / Tj = 125°C Heatsink Frequency KHz VDS=650V ICE2A0565 DIP8 0.5 6.0 23 13 6 cm² 100 ICE2A0565Z DIP7 0.5 6.0 21 12 6 cm² 100 ICE2A165 DIP8 1.0 3.0 31 18 6 cm² 100 ICE2B165 DIP8 1.0 3.0 31 18 6 cm² 67 ICE2A265 DIP8 2.0 0.9 52 32 6 cm² 100 ICE2B265 DIP8 2.0 0.9 52 32 6 cm² 67 ICE2A365 DIP8 3.0 0.45 67 45 6 cm² 100 ICE2B365 DIP8 3.0 0.45 73 45 6 cm² 67 ICE2A765P TO220 7.0 0.5 240 130 2.7 k/W 100 ICE2B765P TO220 7.0 0.5 240 130 2.7 k/W 67 VDS=800V ICE2A180 DIP8 1.0 3.0 31 18 6 cm² 100 ICE2A180Z DIP7 1.0 3.0 29 17 6 cm² 100 ICE2A280 DIP8 2.0 0.8 54 34 6 cm² 100 ICE2A280Z DIP7 2.0 0.8 50 31 6 cm² 100 Output Power Notes: The output power was created using the equations of this application note (see „Calculation of Losses“ on page 27). It shows the maximum practical continuous power @ Ta = 75 °C and Tj = 125 °C with the recommended heatsink as a copper area on PCB for DIP7 / 8 and PDSO14 packages. AN-SMPS-ICE2xXXX-1 Page 40 of 44 Version 1.2 ICE2xXXX for OFF – Line Switch Mode Power Supplies Summary of used Nomenclature Bmax Magnetic Inductance BW Bobbin Width BWe Effective Bobbin Width Capacitance of Bulk Capacitor CIN Output Capacitance COUT COSS Output Capacitance of CoolMOS Output Capacitance of external Components CExtern CClamp Capacitance of Clamping – Capacitor CVCC Capacitance of VCC – Capacitor D Duty Cycle Maximum Duty Cycle Dmax f Operating Frequency of CoolSET (f = 100kHz) Line Frequency (Germany FAC = 50Hz) fAC Crossover Frequency fg fCu Copper Space Factor (0,2 ... 0,4) Frequency Open Loop (High) fOH fOm Frequency Open Loop (middle) fOL Frequency Open Loop (Low) Zero Frequency of output Capacitor fZCOUT Optocoupler Gain GC IFBmax Maximum Feedback Current Minimum Feedback Current IFBmin Maximum Current (Optocoupler) IFmax IKAmin Minimum Current (TL431) VCC – Capacitor Load – Current ILoadC Peak Current through the primary Inductance ILPK IACRMS Root Mean Square Current through the primary Inductance Root Mean Square Current through the Bridge IACRMS Rectifier Primary Current @ time t IPRI Secondary Current @ time t ISEC ISPK Peak Current through the secondary diode RMS Current through the secondary diode ISRMS Maximum quiescent Current of CoolSET (Control IVCC1 IC) Inductance output Filter LOUT Primary Inductance LP LLK Leakage Inductance M Margin (of Transformer) Number of Clock Periods nCP npCOUT Number of parallel output Capacitors Number of primary Turns NP Number of secondary Turns NS NAux Number of auxiliary Turns Power losses of Copper Resistor PCu PD Conduction losses Power losses input Diode PDIN PDDIODE Power losses rectifier Diode (secondary side) PIN MAX Maximum Input Power POUT max Maximum Output Power POUT min Minimum Output Power PPCu Power losses of Copper Resistor (primary Inductance) Power losses of Copper Resistor (secondary PSCu Inductance) Switching losses of CoolMOS Transistor (Off – PSOFF Operation) AN-SMPS-ICE2xXXX-1 Switching losses of CoolMOS PSON Operation) Transistor (On – Copper Resistor (Transformer) RCu Resistance of switching CoolMOS Transistor (On RDSON – Operation) Load – Resistance RL Maximum Load RLH RLL Minimum Load (defined by Designer) Internal Feedback Resistor (CoolSET ) RFB Copper Resistor of primary Inductance RPCu RSCu Copper Resistor of secondary Inductance RClamp Clamping Resistor Start up Resistor RStart T Time of one Period Discharging Time of Input Capacitor C3 TD On Time (CoolMOS ) tON Off Time (CoolMOS ) tOFF Rising Time (Voltage) tr Start up Time tStart VAC min Minimal AC Input Voltage Maximal AC Input Voltage VAC max Auxiliary Voltage VAux V(BR)DSS Drain Source Breakdown Voltage Turn On Threshold for CoolSET @ Vcc - Pin VCCon DC Input Voltage VDC IN VDC IN max Maximum DC Input Voltage VDC IN min Minimum DC Input Voltage VDC max PK Maximum DC Input Voltage Peak VDC min PK Minimum DC Input Voltage Peak Minimum DC Input Voltage @ maximum load VDC min VDDIODE Reverse Voltage rectifier Diode (secondary side) VFBmax Maximum Feedback Voltage (CoolSET ) VFDIODE Output Diode Forward Voltage Forward Diode Voltage (Optocoupler) VFD VOUT Output Voltage (secondary Side) VOUT Ripple Output Ripple Voltage (secondary Side) Reflected Voltage (from secondary side to primary VR side) Reverse Voltage Diode VRDiode Internal Reference Voltage (CoolSET ) VRefint Reference Voltage TL431 VREF DC Ripple Voltage (on primary Side) VRipple Voltage on Sekondary Inductor VSEC VClamp Maximum Voltage overshoot @ clamping network Discharging Energie Input Capacitor WIN Transimpedanz ZPWM Page 41 of 44 Version 1.2 ICE2xXXX for OFF – Line Switch Mode Power Supplies References [1] Keith Billings, Switch Mode Power Supply Handbook [2] Ralph E. Tarter, Solid-State Power Conversion Handbook [3] R. D. Middlebrook and Slobodan Cuk, Advances in Switched-Mode Power Conversion [4] Herfurth Michael, Ansteuerschaltungen für getaktete Stromversorgungen mit Erstellung eines linearisierten Signalflußplans zur Dimensionierung der Regelung [5] Herfurth Michael, Topologie, Übertragungsverhalten und Dimensionierung häufig eingesetzter Regelverstärker [6] Infineon Technologies, Datasheet, CoolSET-II Off – Line SMPS Current Mode Controller with 650V/800V CoolMOS [7] on Board, Robert W. Erickson, Fundamentals of Power Electronics AN-SMPS-ICE2xXXX-1 Page 42 of 44 Version 1.2 ICE2xXXX for OFF – Line Switch Mode Power Supplies Revision History Application Note AN-SMPS-ICE2xXXX-1 Actual Release: V1.2 Date:05.02.2002 Page of Page of actual prev. Rel. Previous Release: V1.0 Subjects changed since last release Rel. 44 40 ---------- Second Issue ------------- CoolSET Table Update For questions on technology, delivery and prices please contact the Infineon Technologies Offices in Germany or the Infineon Technologies Companies and Representatives worldwide: see the address list on the last page or our webpage at http://www.infineon.com CoolMOS and CoolSET are trademarks of Infineon Technologies AG. We listen to Your Comments Any information within this dokument that you feel is wrong, unclear or missing at all? Your feedback will help us to continously improve the quality of this dokument. Please send your proposal (including a reference to this dokument) to: [email protected] Edition 2001-03-01 Published by Infineon Technologies AG, St.-Martin-Strasse 53, D-81541 München © Infineon Technologies AG 2000. All Rights Reserved. Attention please! The information herein is given to describe certain components and shall not be considered as warranted characteristics. Terms of delivery and rights to technical change reserved. We hereby disclaim any and all warranties, including but not limited to warranties of non-infringement, regarding circuits, descriptions and charts stated herein. Infineon Technologies is an approved CECC manufacturer. Information For further information on technology, delivery terms and conditions and prices please contact your nearest Infineon Technologies Office in Germany or our Infineon Technologies Representatives worldwide (see address list). Warnings Due to technical requirements components may contain dangerous substances. For information on the types in question please contact your nearest Infineon Technologies Office. Infineon Technologies Components may only be used in life-support devices or systems with the express written approval of Infineon Technologies, if a failure of such components can reasonably be expected to cause the failure of that life-support device or system, or to affect the safety or effectiveness of that device or system. Life support devices or systems are intended to be implanted in the human body, or to support and/or maintain and sustain and/or protect human life. If they fail, it is reasonable to assume that the health of the user or other persons may be endangered. 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Asia Tower,10th Floor 726 Yeoksam-dong,Kang-nam Ku CPO Box 3001 Seoul 135-080 T (+82)2-5 27 77 00 Fax (+82)2-5 27 77 79 RUS INTECH electronics ul.Smolnaya,24/1203 RUS-125 445 Moskva T (+7)0 95 -4 51 97 37 Fax (+7)0 95 -4 51 86 08 S Siemens Components Scandinavia Österögatan 1,Box 46 S-164 93 Kista T (+46)8-7 03 35 00 Fax (+46)8-7 03 35 01 Email: [email protected] Page 44 of 44 VRC Infineon Technologies Hong Kong Ltd. Beijing Office Room 2106,Building A Vantone New World Plaza No.2 Fu Cheng Men Wai Da Jie Jie 100037 Beijing T (+86)10 -68 57 90 -06,-07 Fax (+86)10 -68 57 90 08 Infineon Technologies Hong Kong Ltd. Chengdu Office Room14J1,Jinyang Mansion 58 Tidu Street Chengdu, Sichuan Province 610 016 T (+86)28-6 61 54 46 /79 51 Fax (+86)28 -6 61 01 59 Infineon Technologies Hong Kong Ltd. Shanghai Office Room1101,Lucky Target Square No.500 Chengdu Road North Shanghai 200003 T (+86)21-63 6126 18 /19 Fax (+86)21-63 61 11 67 Infineon Technologies Hong Kong Ltd. Shenzhen Office Room 1502,Block A Tian An International Building Renim South Road Shenzhen 518 005 T (+86)7 55 -2 28 91 04 Fax (+86)7 55-2 28 02 17 ZA Siemens Ltd. Components Division P.O.B.3438 Halfway House 1685 T (+27)11-6 52 -27 02 Fax (+27)11-6 52 20 42 Version 1.2