LT8609/LT8609A 42V, 2A/3A Peak Synchronous Step-Down Regulator with 2.5µA Quiescent Current FEATURES DESCRIPTION Wide Input Voltage Range: 3.0V to 42V nn Ultralow Quiescent Current Burst Mode® Operation: nn <2.5µA I Regulating 12V to 3.3V Q IN OUT nn Output Ripple <10mV P-P nn High Efficiency 2MHz Synchronous Operation: nn >93% Efficiency at 1A, 5V OUT from 12VIN nn 2A Maximum Continuous Output, 3A Peak Transient Output nn Fast Minimum Switch-On Time: 45ns nn Adjustable and Synchronizable: 200kHz to 2.2MHz nn Spread Spectrum Frequency Modulation for Low EMI nn Allows Use of Small Inductors nn Low Dropout nn Peak Current Mode Operation nn Accurate 1V Enable Pin Threshold nn Internal Compensation nn Output Soft-Start and Tracking nn Small 10-Lead MSOP Package The LT®8609/LT8609A is a compact, high efficiency, high speed synchronous monolithic step-down switching regulator that consumes only 1.7µA of non-switching quiescent current. The LT8609/LT8609A can deliver 2A of continuous current with peak loads of 3A (<1sec) to support applications such as GSM transceivers which require high transient loads. Top and bottom power switches are included with all necessary circuitry to minimize the need for external components. Low ripple Burst Mode operation enables high efficiency down to very low output currents while keeping the output ripple below 10mVP-P. A SYNC pin allows synchronization to an external clock, or spread spectrum modulation of switching frequencies for low EMI operation. Internal compensation with peak current mode topology allows the use of small inductors and results in fast transient response and good loop stability. The EN/ UV pin has an accurate 1V threshold and can be used to program VIN undervoltage lockout or to shut down the LT8609/LT8609A reducing the input supply current to 1µA. A capacitor on the TR/SS pin programs the output voltage ramp rate during start-up while the PG flag signals when VOUT is within ±8.5% of the programmed output voltage as well as fault conditions. The LT8609/LT8609A is available in a small 10-lead MSOP package. The LT8609A has slower switch edges for lower EMI emissions. nn APPLICATIONS nn nn General Purpose Step Down Low EMI Step Down L, LT, LTC, LTM, Linear Technology, the Linear logo and Burst Mode are registered trademarks of Linear Technology Corporation. All other trademarks are the property of their respective owners. TYPICAL APPLICATION 12VIN to 5VOUT Efficiency 100 5V, 2MHz Step Down 4.7µF ON OFF 1µF 18.2k VIN BST EN/UV SW SYNC LT8609 INTVCC PG TR/SS FB RT GND 90 0.1µF 2.2µH 10pF VOUT 5V 2A 1M EFFICIENCY (%) VIN 5.5V TO 40V 95 22µF 187k 8609 TA01a 85 80 75 70 65 60 55 50 fSW = 2MHz 0 0.50 1.50 1.00 IOUT (A) 2.00 2.50 8609 TA01b 8609fb For more information www.linear.com/LT8609 1 LT8609/LT8609A ABSOLUTE MAXIMUM RATINGS (Note 1) VIN, EN/UV, PG...........................................................42V FB, TR/SS ...................................................................4V SYNC Voltage ..............................................................6V Operating Junction Temperature Range (Note 2) LT8609E/LT8609AE................................ –40 to 125°C LT8609I/LT8609AI.................................. –40 to 125°C LT8609H................................................. –40 to 150°C Storage Temperature Range.......................–65 to 150°C ORDER INFORMATION PIN CONFIGURATION TOP VIEW 1 2 3 4 5 BST SW INTVCC RT SYNC 11 GND 10 9 8 7 6 EN/UV VIN PG TR/SS FB MSE PACKAGE 10-LEAD PLASTIC MSOP θJA = 40°C/W EXPOSED PAD (PIN 11) IS GND, MUST BE SOLDERED TO PCB http://www.linear.com/product/LT8609#orderinfo LEAD FREE FINISH TAPE AND REEL PART MARKING* PACKAGE DESCRIPTION TEMPERATURE RANGE LT8609EMSE#PBF LT8609EMSE#TRPBF LTGRW 10-Lead Plastic MSOP –40°C to 125°C LT8609IMSE#PBF LT8609IMSE#TRPBF LTGRW 10-Lead Plastic MSOP –40°C to 125°C LT8609HMSE#PBF LT8609HMSE#TRPBF LTGRW 10-Lead Plastic MSOP –40°C to 150°C LT8609AEMSE#PBF LT8609AEMSE#TRPBF LTGVR 10-Lead Plastic MSOP –40°C to 125°C LT8609AIMSE#PBF LT8609AIMSE#TRPBF LTGVR 10-Lead Plastic MSOP –40°C to 125°C Consult LTC Marketing for parts specified with wider operating temperature ranges. *The temperature grade is identified by a label on the shipping container. For more information on lead free part marking, go to: http://www.linear.com/leadfree/ For more information on tape and reel specifications, go to: http://www.linear.com/tapeandreel/. Some packages are available in 500 unit reels through designated sales channels with #TRMPBF suffix. 2 8609fb For more information www.linear.com/LT8609 LT8609/LT8609A ELECTRICAL CHARACTERISTICS The l denotes the specifications which apply over the full operating temperature range, otherwise specifications are at TA = 25°C. PARAMETER CONDITIONS MIN TYP MAX 2.7 V l 3.0 3.2 VEN/UV = 0V, VSYNC = 0V VEN/UV = 2V, Not Switching, VSYNC = 0V l 1 1.7 4 12 µA µA VIN Current in Regulation VIN = 6V, VOUT = 2.7V, Output Load = 100µA VIN = 6V, VOUT = 2.7V, Output Load = 1mA l l 46 480 90 700 µA µA Feedback Reference Voltage VIN = 6V, ILOAD = 100mA VIN = 6V, ILOAD = 100mA l 0.782 0.782 0.786 0.794 V V Feedback Voltage Line Regulation VIN = 4.0V to 40V, ILOAD = 0.5A l 0.02 0.04 %/V Feedback Pin Input Current VFB = 1V l ±20 nA Minimum On-Time ILOAD = 1.5A ILOAD = 1.5A, SYNC = 1.9V l l 75 60 ns ns Minimum Input Voltage VIN Quiescent Current 0.778 0.770 45 45 Minimum Off Time 115 Oscillator Frequency RFSET = 221k, ILOAD = 0.5A RFSET = 60.4k, ILOAD = 0.5A RFSET = 18.2k, ILOAD = 0.5A Top Power NMOS On-Resistance ILOAD = 1A l l l 155 640 1.925 ns 245 760 2.075 185 Top Power NMOS Current Limit l 3.4 Bottom Power NMOS On-Resistance 4.5 VIN = 42V, VSW = 40V l EN/UV Pin Threshold EN/UV Rising l EN/UV Pin Current VEN/UV = 2V l PG Upper Threshold Offset from VFB VFB Rising l 5.0 PG Lower Threshold Offset from VFB VFB Falling l 5.0 PG Leakage VPG = 42V l PG Pull-Down Resistance VPG = 0.1V 0.99 1.05 5.7 PG Hysteresis mΩ µA 1.11 V mV ±20 nA 8.5 13.0 % 8.5 13.0 % 0.5 550 Sync Low Input Voltage l INTVCC = 3.5V TR/SS Source Current l TR/SS Pull-Down Resistance Fault Condition, TR/SS = 0.1V Spread Spectrum Modulation Frequency VSYNC = 3.3V Note 1: Stresses beyond those listed under Absolute Maximum Ratings may cause permanent damage to the device. Exposure to any Absolute Maximum Rating condition for extended periods may affect device reliability and lifetime. Absolute Maximum Ratings are those values beyond which the life of a device may be impaired. Note 2: The LT8609E/LT8609AE is guaranteed to meet performance specifications from 0°C to 125°C junction temperature. Specifications over the –40°C to 125°C operating junction temperature range are assured by design, characterization, and correlation with statistical process controls. The LT8609I/LT8609AI is guaranteed over the full –40°C to 125°C 0.4 l 1 1 A 15 50 EN/UV Pin Hysteresis kHz kHz MHz mΩ 115 SW Leakage Current Sync High Input Voltage 200 700 2.00 UNITS % ±200 nA 1200 Ω 0.9 V 2.7 3.2 V 2 3 µA 300 900 3 6 Ω kHz operating junction temperature range. The LT8609H is guaranteed over the full –40°C to 150°C operating junction temperature range. High junction temperatures degrade operating lifetimes. Operating lifetime is derated at junction temperatures greater than 125°C. Note 3: This IC includes overtemperature protection that is intended to protect the device during overload conditions. Junction temperature will exceed 150°C when overtemperature protection is active. Continuous operation above the specified maximum operating junction temperature will reduce lifetime. 8609fb For more information www.linear.com/LT8609 3 LT8609/LT8609A TYPICAL PERFORMANCE CHARACTERISTICS Efficiency (3.3V Output, Burst Mode Operation) Efficiency (3.3V Output, Burst Mode Operation) 100 100 EFFICIENCY (%) 80 75 70 65 60 50 40 30 20 55 10 fSW = 700kHz 0 0.50 1.50 1.00 IOUT (A) 2.00 2.50 40 30 85 10 IOUT (mA) 50 1000 0 1.50 1.00 IOUT (A) 0.50 2.00 EFFICIENCY (%) 75 70 65 60 0.50 1.50 1.00 IOUT (A) 2.00 2.50 8609 G07 0.1 10 IOUT (mA) 1000 8609 G06 784 VIN = 12V 70 VIN = 24V 60 50 40 30 L = 2.2µH fSW = 2MHz 10 0 0.001 L = 2.2µH fSW = 2MHz FB Voltage 20 L = 2.2µH fSW = 2MHz 0 30 8609 G05 80 80 55 40 785 90 VIN = 24V 85 50 0 0.001 2.50 FB REGULATION VOLTAGE (mV) VIN = 12V 90 8609 G03 VIN = 24V 60 10 100 95 70 Efficiency (5V Output, 2MHz, Burst Mode Operation) 100 2.50 20 L = 2.2µH fSW = 2MHz 8609 G04 Efficiency (5V Output, 2MHz, Burst Mode Operation) 2.00 VIN = 12V 80 65 55 fSW = 700kHz 90 70 10 1.50 1.00 IOUT (A) 0.50 Efficiency (3.3V Output, 2MHz, Burst Mode Operation) 75 60 fSW = 700kHz 0 8609 G02 VIN = 24V 80 20 0.1 65 50 1000 EFFICIENCY (%) EFFICIENCY (%) EFFICIENCY (%) 50 EFFICIENCY (%) 10 IOUT (mA) VIN = 12V 90 60 0 0.001 70 100 95 VIN = 24V 70 4 0.1 100 80 75 Efficiency (3.3V Output, 2MHz, Burst Mode Operation) VIN = 12V 90 80 55 fSW = 700kHz 8609 G01 100 VIN = 24V 85 60 0 0.001 Log of Efficiency (5V Output, Burst Mode Operation) 50 90 VIN = 24V 70 60 VIN = 12V 95 80 VIN = 24V 85 EFFICIENCY (%) 90 VIN = 12V 90 100 VIN = 12V EFFICIENCY (%) 95 50 Efficiency (5V Output, Burst Mode Operation) 0.1 10 IOUT (mA) 1000 8609 G08 783 782 781 780 779 778 777 776 775 –50 –10 30 70 110 TEMPERATURE (°C) 150 8609 G09 8609fb For more information www.linear.com/LT8609 LT8609/LT8609A TYPICAL PERFORMANCE CHARACTERISTICS Load Load Regulation Regulation 0.50 Line Regulation 0.20 VIN = 12V VOUT = 3.3V 0.40 0.20 CHANGE IN VOUT (%) CHANGE IN VOUT (%) 0.30 0.10 –0.00 –0.10 –0.20 –0.30 0.10 0.05 –0.00 –0.05 –0.10 –0.15 –0.40 –0.50 ILOAD = 1A 0.15 –0.20 4.0 0.0 0.25 0.5 0.75 1.0 1.25 1.5 1.75 2.0 2.25 2.5 OUTPUT CURRENT (A) 11.6 19.2 26.8 34.4 INPUT VOLTAGE (V) 8609 G11 8609 G10 No-Load Supply Current vs Temperature No Load Supply Current Vs Temperature 5.0 3.3 4.5 3.1 4.0 2.9 3.5 2.7 INPUT CURRENT (µA) IIN (µA) No-Load Supply Current (3.3V Output) 3.0 2.5 2.0 1.5 2.3 2.1 1.9 1.7 0.5 1.5 0 10 30 20 VIN (V) 40 1.3 –50 50 30 70 110 TEMPERATURE (°C) 150 8609 G13 Top FET Current Limit vs Temperature Top FET Current Limit Vs Temperature 5.50 5.6 5.25 5.5 5.4 5.00 5.3 4.75 ISW (A) TOP FET CURRENT LIMIT (A) –10 8609 G12 Top FET Current Limit vs TopDuty Fet Cycle Current Limit vs Duty Cycle 4.50 4.25 5.2 5.1 5.0 4.9 4.00 4.8 3.75 3.50 VIN = 12V VOUT = 3.3V 2.5 1.0 0.0 42.0 4.7 0 20 40 60 DUTY CYCLE (%) 80 100 4.6 –50 –10 30 70 110 TEMPERATURE (°C) 8609 G14 150 8609 G15 8609fb For more information www.linear.com/LT8609 5 LT8609/LT8609A TYPICAL PERFORMANCE CHARACTERISTICS Switch Drop vs Temperature 350 Switch Drop vs Switch Current 800 SWITCH CURRENT = 1A 700 250 SWITCH DROP (mV) SWITCH DROP (mV) 300 200 150 100 50 600 500 400 300 200 100 TOP SW BOT SW 0 –50 –30 –10 10 30 50 70 90 110 130 150 TEMPERATURE (°C) 0 TOP SW 0 0.5 1 1.5 2 SWITCH CURRENT (A) 8609 G16 Minimum Off–Time Vs Temperature vs Temperature 150 70 140 MINIMUM OFF–TIME (ns) MINIMUM ON-TIME (ns) 60 30 20 10 VIN = 6V ILOAD = 1A 130 120 110 100 90 80 70 60 SYNC = 2V, 1.5A OUT SYNC = 0V, 1.5A OUT 0 –50 –30 –10 10 30 50 70 90 110 130 150 TEMPERATURE (°C) 50 –50 –30 –10 10 30 50 70 90 110 130 150 TEMPERATURE (°C) 8609 G19 8609 G18 Switching Frequency Switching Frequency Vs Temperature vs Temperature Dropout Voltage vs Load Current 2.005 800 SWITHCING FREQUENCY (Hz) DROPOUT VOLTAGE (mV) 700 600 500 400 300 200 100 0 0 0.5 1 2 1.5 LOAD CURRENT (A) 2.5 3 2.000 1.995 1.990 1.985 1.980 RT = 18.2kΩ 1.975 –50 –30 –10 10 30 50 70 90 110 130 150 TEMPERATURE (°C) 8609 G20 6 3 Minimum Off-Time Minimum On-Time 40 2.5 8609 G17 vs Temperature Minimum On-Time Vs Temperature 50 BOT SW 8609 G21 8609fb For more information www.linear.com/LT8609 LT8609/LT8609A TYPICAL PERFORMANCE CHARACTERISTICS Minimum Load to Full Frequency (SYNC Float to 1.9V) Burst Frequency vs Load Current L = 2.2µH VOUT = 3.3V VIN = 12V SYNC = 0V 80 1500 1000 500 Frequency Foldback 2500 VOUT = 5V fSW = 700kHz SYNC = FLOAT 90 LOAD CURRENT (mA) 2000 FREQUENCY (kHz) 100 VIN = 12V VOUT = 3.3V 2000 70 FREQUENCY (kHz) 2500 60 50 40 30 1500 1000 20 500 10 0 0 200 400 LOAD CURRENT (mA) 0 600 0 10 30 20 INPUT VOLTAGE (V) 8609 G22 Soft-Start Tracking 2.4 0.8 2.3 0.6 0.5 0.4 0.3 0.2 0.1 3.5 VSS = 0.1V 0.1 0.2 0.4 0.5 0.6 0.7 0.8 1.0 1.1 1.2 SS VOLTAGE (V) 2.1 2.0 1.9 1.8 1.5 –50 –30 –10 10 30 50 70 90 110 130 150 TEMPERATURE (°C) 2 1.5 0 –55 –25 5 35 65 95 TEMPERATURE (°C) CASE TEMPERATURE RISE (°C) 15 10 5 155 8609 G30 VIN = 12V VIN = 24V STANDBY LOAD = 50mA PULSED LOAD = 3A VOUT = 5V fSW = 2MHz 45 20 125 Case Temperature vs 3A Pulsed Load vs 3A Pulsed Load Case Temperature 50 25 0 VIN UVLO 8609 G26 VIN=12V VIN=24V VOUT = 5V ffSW = 2MHz 30 1 0.5 Case Temperature vs Load Case Current Temperature vs Load Current 35 0.8 1 1.7 8609 G25 40 0.4 0.6 FB VOLTAGE (V) 2.5 2.2 1.6 0 0.2 3 VIN UVLO (V) SOFT START CURRENT (µA) 0.9 0.7 0 8609 G24 Soft-Start Current Vs vs Temperature Soft Start Current 2.5 CASE TEMPERATURE RISE (°C) FB VOLTAGE (V) 0 50 8609 G23 1.0 0 40 40 35 30 25 20 15 10 5 0 0.2 0.4 0.6 0.8 1 1.2 1.4 1.6 1.8 2.0 LOAD CURRENT (A) 0 0 10 20 30 40 50 60 70 80 90 100 DUTY CYCLE (%) 8609 G31 8609 G32 8609fb For more information www.linear.com/LT8609 7 LT8609/LT8609A TYPICAL PERFORMANCE CHARACTERISTICS Switching Waveforms Switching Waveforms Switching Waveforms 1A/DIV 200mA/DIV 1A/DIV 5V/DIV 5V/DIV 10V/DIV 8609 G33 500ns/DIV 12VIN TO 5VOUT AT 1A Transient Response 500mA/DIV 100mV/DIV 100mV/DIV 8609 G36 50µs/DIV 0.5A TO 1.5A TRANSIENT 12VIN TO 5VOUT COUT = 47µF Start-Up Dropout Start-Up Start-Up Dropout Droupout 6 6 6 5 5 5 5 VOUT 4 4 3 3 2 2 VIN 1 0 0 1 2 3 4 5 INPUT VOLTAGE (V) 6 7 INPUT VOLTAGE (V) 6 RLOAD = 25Ω 7 RLOAD = 2.5Ω VOUT 4 4 3 3 2 1 1 0 0 2 VIN OUTPUT VOLTAGE (V) 7 OUTPUT VOLTAGE (V) 7 7 8609 G35 8609 G37 20µs/DIV 50mA TO 1A TRANSIENT 12VIN TO 5VOUT COUT = 47µF 1 0 1 2 3 4 5 INPUT VOLTAGE (V) 8609 G38 8 500ns/DIV 36VIN TO 5VOUT AT 1A Transient Response 500mA/DIV INPUT VOLTAGE (V) 8609 G34 10µs/DIV 12VIN TO 5VOUT AT 10mA SYNC = 0 6 7 0 8609 G39 8609fb For more information www.linear.com/LT8609 LT8609/LT8609A PIN FUNCTIONS BST (Pin 1): This pin is used to provide a drive voltage, higher than the input voltage, to the topside power switch. Place a 0.1µF boost capacitor as close as possible to the IC. Do not place a resistor in series with this pin. SW (Pin 2): The SW pin is the output of the internal power switches. Connect this pin to the inductor and boost capacitor. This node should be kept small on the PCB for good performance. INTVCC (Pin 3) Internal 3.5V Regulator Bypass Pin. The internal power drivers and control circuits are powered from this voltage. INTVCC max output current is 20mA. Voltage on INTVCC will vary between 2.8V and 3.5V. Decouple this pin to power ground with at least a 1μF low ESR ceramic capacitor. Do not load the INTVCC pin with external circuitry. RT (Pin 4): A resistor is tied between RT and ground to set the switching frequency. SYNC (Pin 5): External Clock Synchronization Input. Ground this pin for low ripple Burst Mode operation at low output loads. Tie to a clock source for synchronization to an external frequency. Leave floating for pulse-skipping mode with no spread spectrum modulation. Tie to INTVCC or tie to a voltage between 3.2V and 5.0V for pulse-skipping mode with spread spectrum modulation. When in pulseskipping mode, the IQ will increase to several mA. FB (Pin 6): The LT8609/LT8609A regulates the FB pin to 0.782V. Connect the feedback resistor divider tap to this pin. TR/SS (Pin 7): Output Tracking and Soft-Start Pin. This pin allows user control of output voltage ramp rate during start-up. A TR/SS voltage below 0.782V forces the LT8609/ LT8609A to regulate the FB pin to equal the TR/SS pin voltage. When TR/SS is above 0.782V, the tracking function is disabled and the internal reference resumes control of the error amplifier. An internal 2μA pull-up current from INTVCC on this pin allows a capacitor to program output voltage slew rate. This pin is pulled to ground with a 300Ω MOSFET during shutdown and fault conditions; use a series resistor if driving from a low impedance output. PG (Pin 8): The PG pin is the open-drain output of an internal comparator. PG remains low until the FB pin is within ±8.5% of the final regulation voltage, and there are no fault conditions. PG is valid when VIN is above 3.2V, regardless of EN/UV pin state. VIN (Pin 9): The VIN pin supplies current to the LT8609/ LT8609A internal circuitry and to the internal topside power switch. This pin must be locally bypassed. Be sure to place the positive terminal of the input capacitor as close as possible to the VIN pins, and the negative capacitor terminal as close as possible to the GND pins. EN/UV (Pin 10): The LT8609/LT8609A is shut down when this pin is low and active when this pin is high. The hysteretic threshold voltage is 1.05V going up and 1.00V going down. Tie to VIN if the shutdown feature is not used. An external resistor divider from VIN can be used to program a VIN threshold below which the LT8609/LT8609A will shut down. GND (Pin 11): Exposed Pad Pin. The exposed pad must be connected to the negative terminal of the input capacitor and soldered to the PCB in order to lower the thermal resistance. 8609fb For more information www.linear.com/LT8609 9 LT8609/LT8609A BLOCK DIAGRAM VIN VIN CIN R3 OPT EN/UV 1V + – SHDN PG ±8.5% ERROR AMP + + – VOUT R2 CSS RT FB TR/SS INTVCC CVCC OSCILLATOR 200kHz TO 2.2MHz VC SHDN TSD INTVCC UVLO VIN UVLO 2µA 3.5V REG SLOPE COMP R4 OPT R1 – + INTERNAL 0.782V REF BST BURST DETECT SWITCH LOGIC AND ANTISHOOT THROUGH SHDN TSD VIN UVLO CBST M1 L SW VOUT COUT M2 GND RT SYNC 8609 BD 10 8609fb For more information www.linear.com/LT8609 LT8609/LT8609A OPERATION The LT8609/LT8609A is a monolithic constant frequency current mode step-down DC/DC converter. An oscillator with frequency set using a resistor on the RT pin turns on the internal top power switch at the beginning of each clock cycle. Current in the inductor then increases until the top switch current comparator trips and turns off the top power switch. The peak inductor current at which the top switch turns off is controlled by the voltage on the internal VC node. The error amplifier servos the VC node by comparing the voltage on the VFB pin with an internal 0.782V reference. When the load current increases it causes a reduction in the feedback voltage relative to the reference leading the error amplifier to raise the VC voltage until the average inductor current matches the new load current. When the top power switch turns off the synchronous power switch turns on until the next clock cycle begins or inductor current falls to zero. If overload conditions result in excess current flowing through the bottom switch, the next clock cycle will be delayed until switch current returns to a safe level. If the EN/UV pin is low, the LT8609/LT8609A is shut down and draws 1µA from the input. When the EN/UV pin is above 1V, the switching regulator becomes active. To optimize efficiency at light loads, the LT8609/LT8609A enters Burst Mode operation during light load situations. Between bursts, all circuitry associated with controlling the output switch is shut down, reducing the input supply current to 1.7μA. In a typical application, 2.5μA will be consumed from the input supply when regulating with no load. The SYNC pin is tied low to use Burst Mode operation and can be floated to use pulse-skipping mode. If a clock is applied to the SYNC pin the part will synchronize to an external clock frequency and operate in pulse-skipping mode. While in pulse-skipping mode the oscillator operates continuously and positive SW transitions are aligned to the clock. During light loads, switch pulses are skipped to regulate the output and the quiescent current will be several mA. The SYNC pin may be tied high for spread spectrum modulation mode, and the LT8609/LT8609A will operate similar to pulse-skipping mode but vary the clock frequency to reduce EMI. Comparators monitoring the FB pin voltage will pull the PG pin low if the output voltage varies more than ±8.5% (typical) from the set point, or if a fault condition is present. The oscillator reduces the LT8609/LT8609A’s operating frequency when the voltage at the FB pin is low. This frequency foldback helps to control the inductor current when the output voltage is lower than the programmed value which occurs during start-up. When a clock is applied to the SYNC pin the frequency foldback is disabled. 8609fb For more information www.linear.com/LT8609 11 LT8609/LT8609A APPLICATIONS INFORMATION Achieving Ultralow Quiescent Current To enhance efficiency at light loads, the LT8609/LT8609A enters into low ripple Burst Mode operation, which keeps the output capacitor charged to the desired output voltage while minimizing the input quiescent current and minimizing output voltage ripple. In Burst Mode operation the LT8609/LT8609A delivers single small pulses of current to the output capacitor followed by sleep periods where the output power is supplied by the output capacitor. While in sleep mode the LT8609/LT8609A consumes 1.7μA. As the output load decreases, the frequency of single current pulses decreases (see Figure 1) and the percentage of time the LT8609/LT8609A is in sleep mode increases, resulting in much higher light load efficiency than for typical converters. By maximizing the time between pulses, 2500 L = 2.2µH VOUT = 3.3V VIN = 12V SYNC = 0V FREQUENCY (kHz) 2000 1500 1000 500 0 0 200 400 LOAD CURRENT (mA) 600 8609 G22 Figure 1a. SW Burst Mode Frequency vs Load 100 VOUT = 5V fSW = 700kHz SYNC = FLOAT 90 LOAD CURRENT (mA) 80 70 60 50 40 30 20 10 0 0 10 30 20 INPUT VOLTAGE (V) 40 50 200mA/DIV 10mV/DIV 2.00µs/DIV 8609 F02 Figure 2. Burst Mode Operation the converter quiescent current approaches 2.5µA for a typical application when there is no output load. Therefore, to optimize the quiescent current performance at light loads, the current in the feedback resistor divider must be minimized as it appears to the output as load current. While in Burst Mode operation the current limit of the top switch is approximately 600mA resulting in output voltage ripple shown in Figure 2. Increasing the output capacitance will decrease the output ripple proportionally. As load ramps upward from zero the switching frequency will increase but only up to the switching frequency programmed by the resistor at the RT pin as shown in Table 1. The output load at which the LT8609/LT8609A reaches the programmed frequency varies based on input voltage, output voltage, and inductor choice. For some applications it is desirable for the LT8609/ LT8609A to operate in pulse-skipping mode, offering two major differences from Burst Mode operation. First is the clock stays awake at all times and all switching cycles are aligned to the clock. In this mode much of the internal circuitry is awake at all times, increasing quiescent current to several hundred µA. Second is that full switching frequency is reached at lower output load than in Burst Mode operation as shown in Figure 1b. To enable pulse-skipping mode the SYNC pin is floated. To achieve spread spectrum modulation with pulse-skipping mode, the SYNC pin is tied high. While a clock is applied to the SYNC pin the LT8609/LT8609A will also operate in pulse-skipping mode. 8609 G23 Figure 1b. Full Switching Frequency Minimum Load vs VIN in Pulse Skipping Mode 12 8609fb For more information www.linear.com/LT8609 LT8609/LT8609A APPLICATIONS INFORMATION FB Resistor Network Operating Frequency Selection and Trade-Offs The output voltage is programmed with a resistor divider between the output and the FB pin. Choose the resistor values according to: Selection of the operating frequency is a trade-off between efficiency, component size, and input voltage range. The advantage of high frequency operation is that smaller inductor and capacitor values may be used. The disadvantages are lower efficiency and a smaller input voltage range. V R1= R2 OUT – 1 0.782V 1% resistors are recommended to maintain output voltage accuracy. The total resistance of the FB resistor divider should be selected to be as large as possible when good low load efficiency is desired: The resistor divider generates a small load on the output, which should be minimized to optimize the quiescent current at low loads. When using large FB resistors, a 10pF phase lead capacitor should be connected from VOUT to FB. Setting the Switching Frequency The LT8609/LT8609A uses a constant frequency PWM architecture that can be programmed to switch from 200kHz to 2.2MHz by using a resistor tied from the RT pin to ground. A table showing the necessary RT value for a desired switching frequency is in Table 1. When in spread spectrum modulation mode, the frequency is modulated upwards of the frequency set by RT. Table 1. SW Frequency vs RT Value fSW (MHz) RT (kΩ) 0.2 221 0.300 143 0.400 110 0.500 86.6 0.600 71.5 0.700 60.4 0.800 52.3 0.900 46.4 1.000 40.2 1.200 33.2 1.400 27.4 1.600 23.7 1.800 20.5 2.000 18.2 2.200 16.2 The highest switching frequency (fSW(MAX)) for a given application can be calculated as follows: fSW(MAX) = ( VOUT + VSW(BOT) tON(MIN) VIN – VSW(TOP) + VSW(BOT) ) where VIN is the typical input voltage, VOUT is the output voltage, VSW(TOP) and VSW(BOT) are the internal switch drops (~0.4V, ~0.25V, respectively at max load) and tON(MIN) is the minimum top switch on-time (see Electrical Characteristics). This equation shows that slower switching frequency is necessary to accommodate a high VIN/ VOUT ratio. For transient operation VIN may go as high as the Abs Max rating regardless of the RT value, however the LT8609/ LT8609A will reduce switching frequency as necessary to maintain control of inductor current to assure safe operation. The LT8609/LT8609A is capable of maximum duty cycle of greater than 99%, and the VIN to VOUT dropout is limited by the RDS(ON) of the top switch. In this mode the LT8609/ LT8609A skips switch cycles, resulting in a lower switching frequency than programmed by RT. For applications that cannot allow deviation from the programmed switching frequency at low VIN/VOUT ratios use the following formula to set switching frequency: VIN(MIN) = VOUT + VSW(BOT) 1– fSW • tOFF(MIN) – VSW(BOT) + VSW(TOP) where VIN(MIN) is the minimum input voltage without skipped cycles, VOUT is the output voltage, VSW(TOP) and VSW(BOT) are the internal switch drops (~0.4V, ~0.25V, respectively at max load), fSW is the switching frequency (set by RT), and tOFF(MIN) is the minimum switch off-time. Note that higher switching frequency will increase the 8609fb For more information www.linear.com/LT8609 13 LT8609/LT8609A APPLICATIONS INFORMATION minimum input voltage below which cycles will be dropped to achieve higher duty cycle. Inductor Selection and Maximum Output Current The LT8609/LT8609A is designed to minimize solution size by allowing the inductor to be chosen based on the output load requirements of the application. During overload or short circuit conditions the LT8609/LT8609A safely tolerates operation with a saturated inductor through the use of a high speed peak-current mode architecture. A good first choice for the inductor value is: L= VOUT + VSW(BOT) fSW where fSW is the switching frequency in MHz, VOUT is the output voltage, VSW(BOT) is the bottom switch drop (~0.25V) and L is the inductor value in μH. To avoid overheating and poor efficiency, an inductor must be chosen with an RMS current rating that is greater than the maximum expected output load of the application. In addition, the saturation current (typically labeled ISAT) rating of the inductor must be higher than the load current plus 1/2 of in inductor ripple current: 1 IL(PEAK) =ILOAD(MAX) + ∆L 2 where ∆IL is the inductor ripple current as calculated several paragraphs below and ILOAD(MAX) is the maximum output load for a given application. As a quick example, an application requiring 1A output should use an inductor with an RMS rating of greater than 1A and an ISAT of greater than 1.3A. To keep the efficiency high, the series resistance (DCR) should be less than 0.04Ω, and the core material should be intended for high frequency applications. The LT8609/LT8609A limits the peak switch current in order to protect the switches and the system from overload faults. The top switch current limit (ILIM) is at least 4.75A at low duty cycles and decreases linearly to 4.0A at D = 0.8. The inductor value must then be sufficient to supply the desired maximum output current (IOUT(MAX)), 14 which is a function of the switch current limit (ILIM) and the ripple current: IOUT(MAX) =ILIM – ∆IL 2 The peak-to-peak ripple current in the inductor can be calculated as follows: ∆IL = VOUT VOUT 1– L • fSW VIN(MAX) where fSW is the switching frequency of the LT8609/ LT8609A, and L is the value of the inductor. Therefore, the maximum output current that the LT8609/LT8609A will deliver depends on the switch current limit, the inductor value, and the input and output voltages. The inductor value may have to be increased if the inductor ripple current does not allow sufficient maximum output current (IOUT(MAX)) given the switching frequency, and maximum input voltage used in the desired application. The optimum inductor for a given application may differ from the one indicated by this design guide. A larger value inductor provides a higher maximum load current and reduces the output voltage ripple. For applications requiring smaller load currents, the value of the inductor may be lower and the LT8609/LT8609A may operate with higher ripple current. This allows use of a physically smaller inductor, or one with a lower DCR resulting in higher efficiency. Be aware that low inductance may result in discontinuous mode operation, which further reduces maximum load current. The internal circuitry of the LT8609/LT8609A is capable of supplying IOUT(MAX) up to 3A. Thermal limitations of the LT8609/LT8609A prevent continuous output of 3A loads due to unsafe operating temperatures. In order to ensure safe operating temperature, the average LT8609/ LT8609A current must be kept below 2A, but will allow transient peaks up to 3A or IOUT(MAX). If high average currents cause unsafe heating of the part, the LT8609/ LT8609A will stop switching and indicate a fault condition to protect the internal circuitry. 8609fb For more information www.linear.com/LT8609 LT8609/LT8609A APPLICATIONS INFORMATION For more information about maximum output current and discontinuous operation, see Linear Technology’s Application Note 44. Finally, for duty cycles greater than 50% (VOUT/VIN > 0.5), a minimum inductance is required to avoid sub-harmonic oscillation. See Application Note 19. Input Capacitor Bypass the input of the LT8609/LT8609A circuit with a ceramic capacitor of X7R or X5R type. Y5V types have poor performance over temperature and applied voltage, and should not be used. A 4.7μF to 10μF ceramic capacitor is adequate to bypass the LT8609/LT8609A and will easily handle the ripple current. Note that larger input capacitance is required when a lower switching frequency is used. If the input power source has high impedance, or there is significant inductance due to long wires or cables, additional bulk capacitance may be necessary. This can be provided with a low performance electrolytic capacitor. Step-down regulators draw current from the input supply in pulses with very fast rise and fall times. The input capacitor is required to reduce the resulting voltage ripple at the LT8609/LT8609A and to force this very high frequency switching current into a tight local loop, minimizing EMI. A 4.7μF capacitor is capable of this task, but only if it is placed close to the LT8609/LT8609A (see the PCB Layout section). A second precaution regarding the ceramic input capacitor concerns the maximum input voltage rating of the LT8609/LT8609A. A ceramic input capacitor combined with trace or cable inductance forms a high quality (under damped) tank circuit. If the LT8609/LT8609A circuit is plugged into a live supply, the input voltage can ring to twice its nominal value, possibly exceeding the LT8609/ LT8609A’s voltage rating. This situation is easily avoided (see Linear Technology Application Note 88). Output Capacitor and Output Ripple The output capacitor has two essential functions. Along with the inductor, it filters the square wave generated by the LT8609/LT8609A to produce the DC output. In this role it determines the output ripple, thus low impedance at the switching frequency is important. The second function is to store energy in order to satisfy transient loads and stabilize the LT8609/LT8609A’s control loop. Ceramic capacitors have very low equivalent series resistance (ESR) and provide the best ripple performance. A good starting value is: COUT = 100 VOUT • fSW where fSW is in MHz, and COUT is the recommended output capacitance in μF. Use X5R or X7R types. This choice will provide low output ripple and good transient response. Transient performance can be improved with a higher value output capacitor and the addition of a feedforward capacitor placed between VOUT and FB. Increasing the output capacitance will also decrease the output voltage ripple. A lower value of output capacitor can be used to save space and cost but transient performance will suffer and may cause loop instability. See the Typical Applications in this data sheet for suggested capacitor values. When choosing a capacitor, special attention should be given to the data sheet to calculate the effective capacitance under the relevant operating conditions of voltage bias and temperature. A physically larger capacitor or one with a higher voltage rating may be required. Ceramic Capacitors Ceramic capacitors are small, robust and have very low ESR. However, ceramic capacitors can cause problems when used with the LT8609/LT8609A due to their piezoelectric nature. When in Burst Mode operation, the LT8609/LT8609A’s switching frequency depends on the load current, and at very light loads the LT8609/LT8609A can excite the ceramic capacitor at audio frequencies, generating audible noise. Since the LT8609/LT8609A operates at a lower current limit during Burst Mode operation, the noise is typically very quiet to a casual ear. If this is unacceptable, use a high performance tantalum or electrolytic capacitor at the output. A final precaution regarding ceramic capacitors concerns the maximum input voltage rating of the LT8609/LT8609A. 8609fb For more information www.linear.com/LT8609 15 LT8609/LT8609A APPLICATIONS INFORMATION As previously mentioned, a ceramic input capacitor combined with trace or cable inductance forms a high quality (under damped) tank circuit. If the LT8609/LT8609A circuit is plugged into a live supply, the input voltage can ring to twice its nominal value, possibly exceeding the LT8609/ LT8609A’s rating. This situation is easily avoided (see Linear Technology Application Note 88). Enable Pin The LT8609/LT8609A is in shutdown when the EN pin is low and active when the pin is high. The rising threshold of the EN comparator is 1.05V, with 50mV of hysteresis. The EN pin can be tied to VIN if the shutdown feature is not used, or tied to a logic level if shutdown control is required. Adding a resistor divider from VIN to EN programs the LT8609/LT8609A to regulate the output only when VIN is above a desired voltage (see Block Diagram). Typically, this threshold, VIN(EN), is used in situations where the input supply is current limited, or has a relatively high source resistance. A switching regulator draws constant power from the source, so source current increases as source voltage drops. This looks like a negative resistance load to the source and can cause the source to current limit or latch low under low source voltage conditions. The VIN(EN) threshold prevents the regulator from operating at source voltages where the problems might occur. This threshold can be adjusted by setting the values R3 and R4 such that they satisfy the following equation: R3 VIN(EN) = +1 •1V R4 where the LT8609/LT8609A will remain off until VIN is above VIN(EN). Due to the comparator’s hysteresis, switching will not stop until the input falls slightly below VIN(EN). When in Burst Mode operation for light-load currents, the current through the VIN(EN) resistor network can easily be greater than the supply current consumed by the LT8609/ LT8609A. Therefore, the VIN(EN) resistors should be large to minimize their effect on efficiency at low loads. 16 INTVCC Regulator An internal low dropout (LDO) regulator produces the 3.5V supply from VIN that powers the drivers and the internal bias circuitry. The INTVCC can supply enough current for the LT8609/LT8609A’s circuitry and must be bypassed to ground with a minimum of 1μF ceramic capacitor. Good bypassing is necessary to supply the high transient currents required by the power MOSFET gate drivers. Applications with high input voltage and high switching frequency will increase die temperature because of the higher power dissipation across the LDO. Do not connect an external load to the INTVCC pin. Output Voltage Tracking and Soft-Start The LT8609/LT8609A allows the user to program its output voltage ramp rate by means of the TR/SS pin. An internal 2μA pulls up the TR/SS pin to INTVCC. Putting an external capacitor on TR/SS enables soft-starting the output to prevent current surge on the input supply. During the softstart ramp the output voltage will proportionally track the TR/SS pin voltage. For output tracking applications, TR/SS can be externally driven by another voltage source. From 0V to 0.782V, the TR/SS voltage will override the internal 0.782V reference input to the error amplifier, thus regulating the FB pin voltage to that of TR/SS pin. When TR/SS is above 0.782V, tracking is disabled and the feedback voltage will regulate to the internal reference voltage. An active pull-down circuit is connected to the TR/SS pin which will discharge the external soft-start capacitor in the case of fault conditions and restart the ramp when the faults are cleared. Fault conditions that clear the soft-start capacitor are the EN/UV pin transitioning low, VIN voltage falling too low, or thermal shutdown. Output Power Good When the LT8609/LT8609A’s output voltage is within the ±8.5% window of the regulation point, which is a VFB voltage in the range of 0.716V to 0.849V (typical), the output voltage is considered good and the open-drain PG pin goes high impedance and is typically pulled high with an external resistor. Otherwise, the internal drain pull-down 8609fb For more information www.linear.com/LT8609 LT8609/LT8609A APPLICATIONS INFORMATION device will pull the PG pin low. To prevent glitching both the upper and lower thresholds include 0.5% of hysteresis. D1 VIN VIN LT8609 The PG pin is also actively pulled low during several fault conditions: EN/UV pin is below 1V, INTVCC has fallen too low, VIN is too low, or thermal shutdown. EN/UV GND 8609 F03 Synchronization Figure 3. Reverse VIN Protection To select low ripple Burst Mode operation, tie the SYNC pin below 0.4V (this can be ground or a logic low output). To synchronize the LT8609/LT8609A oscillator to an external frequency connect a square wave (with 20% to 80% duty cycle) to the SYNC pin. The square wave amplitude should have valleys that are below 0.9V and peaks above 2.7V (up to 5V). The LT8609/LT8609A will not enter Burst Mode operation at low output loads while synchronized to an external clock, but instead will pulse skip to maintain regulation. The LT8609/LT8609A may be synchronized over a 200kHz to 2.2MHz range. The RT resistor should be chosen to set the LT8609/LT8609A switching frequency equal to or below the lowest synchronization input. For example, if the synchronization signal will be 500kHz and higher, the RT should be selected for 500kHz. The slope compensation is set by the RT value, while the minimum slope compensation required to avoid subharmonic oscillations is established by the inductor size, input voltage, and output voltage. Since the synchronization frequency will not change the slopes of the inductor current waveform, if the inductor is large enough to avoid subharmonic oscillations at the frequency set by RT, then the slope compensation will be sufficient for all synchronization frequencies. For some applications it is desirable for the LT8609/ LT8609A to operate in pulse-skipping mode, offering two major differences from Burst Mode operation. First is the clock stays awake at all times and all switching cycles are aligned to the clock. Second is that full switching frequency is reached at lower output load than in Burst Mode operation as shown in Figure 1b in an earlier section. These two differences come at the expense of increased quiescent current. To enable pulse-skipping mode the SYNC pin is floated. For some applications, reduced EMI operation may be desirable, which can be achieved through spread spectrum modulation. This mode operates similar to pulse skipping mode operation, with the key difference that the switching frequency is modulated up and down by a 3 kHz triangle wave. The modulation has the frequency set by RT as the low frequency, and modulates up to approximately 20% higher than the frequency set by RT. To enable spread spectrum mode, tie SYNC to INTVCC or drive to a voltage between 3.2V and 5V. The LT8609/LT8609A does not operate in forced continuous mode regardless of SYNC signal. Shorted and Reversed Input Protection The LT8609/LT8609A will tolerate a shorted output. Several features are used for protection during output short-circuit and brownout conditions. The first is the switching frequency will be folded back while the output is lower than the set point to maintain inductor current control. Second, the bottom switch current is monitored such that if inductor current is beyond safe levels switching of the top switch will be delayed until such time as the inductor current falls to safe levels. This allows for tailoring the LT8609/ LT8609A to individual applications and limiting thermal dissipation during short circuit conditions. Frequency foldback behavior depends on the state of the SYNC pin: If the SYNC pin is low or high, or floated the switching frequency will slow while the output voltage is lower than the programmed level. If the SYNC pin is connected to a clock source, the LT8609/LT8609A will stay at the programmed frequency without foldback and only slow switching if the inductor current exceeds safe levels. 8609fb For more information www.linear.com/LT8609 17 LT8609/LT8609A APPLICATIONS INFORMATION There is another situation to consider in systems where the output will be held high when the input to the LT8609/ LT8609A is absent. This may occur in battery charging applications or in battery backup systems where a battery or some other supply is diode ORed with the LT8609/ LT8609A’s output. If the VIN pin is allowed to float and the EN pin is held high (either by a logic signal or because it is tied to VIN), then the LT8609/LT8609A’s internal circuitry will pull its quiescent current through its SW pin. This is acceptable if the system can tolerate several μA in this state. If the EN pin is grounded the SW pin current will drop to near 0.7µA. However, if the VIN pin is grounded while the output is held high, regardless of EN, parasitic body diodes inside the LT8609/LT8609A can pull current from the output through the SW pin and the VIN pin. Figure 3 shows a connection of the VIN and EN/UV pins that will allow the LT8609/LT8609A to run only when the input voltage is present and that protects against a shorted or reversed input. PCB Layout For proper operation and minimum EMI, care must be taken during printed circuit board layout. Figure 4 shows the recommended component placement with trace, ground plane and via locations. Note that large, switched currents flow in the LT8609/LT8609A’s VIN pins, GND pins, and the input capacitor (CIN). The loop formed by the input capacitor should be as small as possible by placing the capacitor adjacent to the VIN and GND pins. When using a physically large input capacitor the resulting loop may become too large in which case using a small case/value capacitor placed close to the VIN and GND pins plus a larger capacitor further away is preferred. These components, along with the inductor and output capacitor, should be placed on the same side of the circuit board, and their connections should be made on that layer. Place a local, unbroken ground plane under the application circuit on the layer closest to the surface layer. The SW and BOOST nodes should be as small as possible. Finally, keep the FB and RT nodes small so that the ground traces will shield them from the GND BST 1 10 EN/UV 2 9 VIN INTVCC 3 8 PG RT 4 7 TR/SS SYNC 5 6 FB VOUT CIN SW VIAS TO GROUND PLANE VOUT 8609 F04 OUTLINE OF LOCAL GROUND PLANE Figure 4. PCB Layout 18 8609fb For more information www.linear.com/LT8609 LT8609/LT8609A APPLICATIONS INFORMATION SW and BOOST nodes. The exposed pad on the bottom of the package must be soldered to ground so that the pad is connected to ground electrically and also acts as a heat sink thermally. To keep thermal resistance low, extend the ground plane as much as possible, and add thermal vias under and near the LT8609/LT8609A to additional ground planes within the circuit board and on the bottom side. Thermal Considerations and Peak Current Output For higher ambient temperatures, care should be taken in the layout of the PCB to ensure good heat sinking of the LT8609/LT8609A. The exposed pad on the bottom of the package must be soldered to a ground plane. This ground should be tied to large copper layers below with thermal vias; these layers will spread heat dissipated by the LT8609/LT8609A. Placing additional vias can reduce thermal resistance further. The maximum load current should be derated as the ambient temperature approaches the maximum junction rating. Power dissipation within the LT8609/LT8609A can be estimated by calculating the total power loss from an efficiency measurement and subtract- ing the inductor loss. The die temperature is calculated by multiplying the LT8609/LT8609A power dissipation by the thermal resistance from junction to ambient. The LT8609/ LT8609A will stop switching and indicate a fault condition if safe junction temperature is exceeded. Temperature rise of the LT8609/LT8609A is worst when operating at high load, high VIN, and high switching frequency. If the case temperature is too high for a given application, then either VIN, switching frequency or load current can be decreased to reduce the temperature to an acceptable level. Figure 5 shows how case temperature rise can be managed by reducing VIN. The LT8609/LT8609A’s internal power switches are capable of safely delivering up to 3A of peak output current. However, due to thermal limits, the package can only handle 3A loads for short periods of time. This time is determined by how quickly the case temperature approaches the maximum junction rating. Figure 6 shows an example of how case temperature rise changes with the duty cycle of a 10Hz pulsed 3A load. Junction temperature will be higher than case temperature. Case Temperature vs 3A Pulsed Load Case Temperature vs Load Current 40 VIN=12V VIN=24V VOUT = 5V fSW = 2MHz 30 25 20 15 10 5 0 VIN = 12V VIN = 24V 40 STANDBY LOAD = 50mA PULSED LOAD = 3A 35 VOUT = 5V f = 2MHz 30 SW 45 CASE TEMPERATURE RISE (°C) 35 CASE TEMPERATURE RISE (°C) 50 25 20 15 10 5 0 0.2 0.4 0.6 0.8 1 1.2 1.4 1.6 1.8 2.0 LOAD CURRENT (A) 0 10 20 30 40 50 60 70 80 90 100 DUTY CYCLE (%) 8609 F06 8609 F05 Figure 5. Case Temperature vs Load Current 0 Figure 6. Case Temperature vs 3A Pulsed Load 8609fb For more information www.linear.com/LT8609 19 LT8609/LT8609A TYPICAL APPLICATIONS 3.3V Step Down VIN 3.6V TO 42V C2 4.7µF C1 0.1µF VIN EN/UV BST SYNC SW L1 2.2µH R4 100k LT8609 INTVCC C3 1µF C6 10nF R1 18.2k PG C5 10pF TR/SS RT GND FB fSW = 2MHz R3 309k R2 1M L1 = XFL4020-222ME VOUT 3.3V 2A POWER GOOD C4 22µF 8609 TA02 5V Step Down VIN 5.3V TO 42V C2 4.7µF C1 0.1µF VIN EN/UV BST SYNC SW L1 4.7µH R4 100k LT8609 INTVCC C3 1µF C6 10nF R1 110k PG C5 10pF TR/SS RT GND FB fSW = 400kHz R3 187k R2 1M L1 = XAL4030-472ME VOUT 5V 2A POWER GOOD C4 22µF 8609 TA03 12V Step Down VIN 12.3V TO 42V C2 4.7µF C1 0.1µF VIN EN/UV BST SYNC SW L1 10µH R4 100k LT8609 INTVCC C3 1µF C6 10nF R1 221k FSW = 200kHz 20 PG C5 10pF TR/SS RT GND FB R3 69.8k R2 1M L1 = XAL4040-103ME VOUT 12V 2A POWER GOOD C4 22µF 8609 TA04 8609fb For more information www.linear.com/LT8609 LT8609/LT8609A TYPICAL APPLICATIONS 1.8V 2MHz Step-Down Converter VIN 3.1V TO 42V C2 4.7µF C6 10nF R1 18.2k L1 2.2µH VOUT 1.8V 2A SW R4 100k LT8609 INTVCC C3 1µF M1 NFET BST EN/UV SYNC PSKIP C1 0.1µF VIN PG TR/SS RT GND FB R2 1M R3 768k fSW = 2MHz POWER GOOD C5 10pF C4 22µF L1 = XFL4020-222ME 8609 TA05 Ultralow EMI 5V 2A Step-Down Converter VIN 5.3V TO 40V L2 BEAD L3 4.7µH C8 4.7µF C7 4.7µF VIN C2 4.7µF BST EN/UV SYNC SW C1 0.1µF L1 3.3µH R4 100K LT8609 PG INTVCC C5 10pF TR/SS C3 1µF C6 10nF FB RT R1 60.4k fSW = 700kHz GND R3 187k R2 1M L1 = XFL4020-332ME VOUT 5V 2A POWER GOOD C4 22µF 8609 TA06 8609fb For more information www.linear.com/LT8609 21 LT8609/LT8609A PACKAGE DESCRIPTION Please refer to http://www.linear.com/product/LT8609#packaging for the most recent package drawings. MSE Package 10-Lead Plastic MSOP, Exposed Die Pad (Reference LTC DWG # 05-08-1664 Rev I) BOTTOM VIEW OF EXPOSED PAD OPTION 1.88 ±0.102 (.074 ±.004) 5.10 (.201) MIN 1 0.889 ±0.127 (.035 ±.005) 1.68 ±0.102 (.066 ±.004) 0.05 REF 10 0.305 ± 0.038 (.0120 ±.0015) TYP RECOMMENDED SOLDER PAD LAYOUT 3.00 ±0.102 (.118 ±.004) (NOTE 3) DETAIL “B” CORNER TAIL IS PART OF DETAIL “B” THE LEADFRAME FEATURE. FOR REFERENCE ONLY NO MEASUREMENT PURPOSE 10 9 8 7 6 DETAIL “A” 0° – 6° TYP 1 2 3 4 5 GAUGE PLANE 0.53 ±0.152 (.021 ±.006) DETAIL “A” 0.18 (.007) SEATING PLANE 0.86 (.034) REF 1.10 (.043) MAX 0.17 – 0.27 (.007 – .011) TYP 0.50 (.0197) BSC NOTE: 1. DIMENSIONS IN MILLIMETER/(INCH) 2. DRAWING NOT TO SCALE 3. DIMENSION DOES NOT INCLUDE MOLD FLASH, PROTRUSIONS OR GATE BURRS. MOLD FLASH, PROTRUSIONS OR GATE BURRS SHALL NOT EXCEED 0.152mm (.006") PER SIDE 4. DIMENSION DOES NOT INCLUDE INTERLEAD FLASH OR PROTRUSIONS. INTERLEAD FLASH OR PROTRUSIONS SHALL NOT EXCEED 0.152mm (.006") PER SIDE 5. LEAD COPLANARITY (BOTTOM OF LEADS AFTER FORMING) SHALL BE 0.102mm (.004") MAX 6. EXPOSED PAD DIMENSION DOES INCLUDE MOLD FLASH. MOLD FLASH ON E-PAD SHALL NOT EXCEED 0.254mm (.010") PER SIDE. 22 0.497 ±0.076 (.0196 ±.003) REF 3.00 ±0.102 (.118 ±.004) (NOTE 4) 4.90 ±0.152 (.193 ±.006) 0.254 (.010) 0.29 REF 1.68 (.066) 3.20 – 3.45 (.126 – .136) 0.50 (.0197) BSC 1.88 (.074) 0.1016 ±0.0508 (.004 ±.002) MSOP (MSE) 0213 REV I 8609fb For more information www.linear.com/LT8609 LT8609/LT8609A REVISION HISTORY REV DATE DESCRIPTION A 01/16 Added the LT8609A Version to Header PAGE NUMBER All Added the LT8609A Version to Description 1 Clarified Description 1 Clarified Electrical Specifications 3 Clarified Load Regulation, Line Regulation, No-Load Supply Current vs Temperature, Minimum On-Time vs Temperature Graphs, Frequency Foldback and Soft-Start vs Temperature Graphs B 06/16 5, 6, 7, 8 Clarified Block Diagram with Optional Input Resistors 10 Replaced Figure 1 with Table 1 in text 12 Clarified CIN Capacitor in Text and PCB Layout 18 Clarified Typical Application 24 Clarified Switch Drop vs Switch Current Graph axis units 6 Clarified Switching Waveforms conditions 8 8609fb Information furnished by Linear Technology Corporation is believed to be accurate and reliable. However, no responsibility is assumed for its use. Linear Technology Corporation makes no representaFor more information www.linear.com/LT8609 tion that the interconnection of its circuits as described herein will not infringe on existing patent rights. 23 LT8609/LT8609A TYPICAL APPLICATION VIN 3.6V TO 42V C2 4.7µF C1 0.1µF VIN BST EN/UV R1 18.2k R4 100k LT8609 INTVCC C6 10nF VOUT 3.3V, 2A SW SYNC C3 1µF L1 2.2µH PG C5 10pF TR/SS RT GND FB R2 1M R3 309k POWER GOOD C4 47µF fSW = 2MHz C8 4.7µF R9 10k BST EN/UV L2 2.2µH SW SYNC INTVCC C12 1µF C7 0.1µF VIN R8 100k LT8609 PG C11 10pF TR/SS R10 31.6k R5 18.2k RT GND FB R7 768k R6 1M fSW = 2MHz VOUT 1.8V 2A POWER GOOD C10 47µF 8609 TA07 RELATED PARTS PART NUMBER DESCRIPTION COMMENTS LT8610A/ LT8610AB 42V, 3.5A, 96% Efficiency, 2.2MHz Synchronous MicroPower Step-Down VIN = 3.4V to 42V, VOUT(MIN) = 0.97V, IQ = 2.5µA, ISD < 1µA, MSOP-16E Package DC/DC Converter with IQ = 2.5µA LT8610AC 42V, 3.5A, 96% Efficiency, 2.2MHz Synchronous MicroPower Step-Down VIN = 3V to 42V, VOUT(MIN) = 0.8V, IQ = 2.5µA, ISD < 1µA, MSOP-16E Package DC/DC Converter with IQ = 2.5µA LT8610 42V, 2.5A, 96% Efficiency, 2.2MHz Synchronous MicroPower Step-Down VIN = 3.4V to 42V, VOUT(MIN) = 0.97V, IQ = 2.5µA, ISD < 1µA, MSOP-16E Package DC/DC Converter with IQ = 2.5µA LT8611 42V, 2.5A, 96% Efficiency, 2.2MHz Synchronous MicroPower Step-Down VIN = 3.4V to 42V, VOUT(MIN) = 0.97V, IQ = 2.5µA, ISD < 1µA, DC/DC Converter with IQ = 2.5µA and Input/Output Current Limit/Monitor 3mm × 5mm QFN-24 Package LT8616 42V, Dual 2.5A + 1.5A, 95% Efficiency, 2.2MHz Synchronous MicroPower Step-Down DC/DC Converter with IQ = 5µA LT8620 65V, 2.5A, 96% Efficiency, 2.2MHz Synchronous MicroPower Step-Down VIN = 3.4V to 65V, VOUT(MIN) = 0.97V, IQ = 2.5µA, ISD < 1µA, MSOP-16E, 3mm × 5mm QFN-24 Packages DC/DC Converter with IQ = 2.5µA LT8614 42V, 4A, 96% Efficiency, 2.2MHz Synchronous MicroPower Step-Down DC/DC Converter with IQ = 2.5µA VIN = 3.4V to 42V, VOUT(MIN) = 0.97V, IQ = 2.5µA, ISD < 1µA, 3mm × 4mm QFN-18 Package LT8612 42V, 6A, 96% Efficiency, 2.2MHz Synchronous MicroPower Step-Down DC/DC Converter with IQ = 2.5µA VIN = 3.4V to 42V, VOUT(MIN) = 0.97V, IQ = 3.0µA, ISD < 1µA, 3mm × 6mm QFN-28 Package LT8640 42V, 5A/7A Peak, 96% Efficiency, 3MHz Synchronous MicroPower Step- VIN = 3.4V to 42V, VOUT(MIN) = 0.97V, IQ = 2.5µA, ISD < 1µA, 3mm × 4mm QFN-18 Package Down DC/DC Converter with IQ = 2.5µA LT8602 42V, Quad Output (2.5A+1.5A+1.5A+1.5A) 95% Efficiency, 2.2MHz Synchronous MicroPower Step-Down DC/DC Converter with IQ = 25µA 24 Linear Technology Corporation VIN = 3.4V to 42V, VOUT(MIN) = 0.8V, IQ = 5µA, ISD < 1µA, TSSOP-28E, 3mm × 6mm QFN-28 Packages VIN = 3V to 42V, VOUT(MIN)= 0.8V, IQ = 25µA, ISD < 1µA, 6mm × 6mm QFN-40 Package 1630 McCarthy Blvd., Milpitas, CA 95035-7417 For more information www.linear.com/LT8609 (408) 432-1900 ● FAX: (408) 434-0507 ● www.linear.com/LT8609 8609fb LT 0616 REV B • PRINTED IN USA LINEAR TECHNOLOGY CORPORATION 2015