EL8202, EL8203, EL8403 SIGNS NE W D E R O F D T ND E ACEMEN COMME ED REPL Center at N OT R E D N E M M Sheet April 26, 2006 REC O upport NOData chnical S .intersil.com/tsc e T r u o t contac ERSIL or www T 1-888-IN 500MHz Rail-to-Rail Amplifiers Features The EL8202, EL8203, and EL8403 represent rail-to-rail amplifiers with a -3dB bandwidth of 500MHz and slew rate of 600V/µs. Running off a very low supply current of 5.6mA per channel, the EL8202, EL8203, and EL8403 also feature inputs that go to 0.15V below the VS- rail. The EL8202 and EL8203 are dual channel amplifiers. The EL8403 is a quad channel amplifier. • 500MHz -3dB bandwidth The EL8202 includes a fast-acting disable/power-down circuit. With a 25ns disable and a 200ns enable, the EL8202 is ideal for multiplexing applications. • Input to 0.15V below VS- The EL8202, EL8203, and EL8403 are designed for a number of general purpose video, communication, instrumentation, and industrial applications. The EL8202 is available in a 10 Ld MSOP package, the EL8203 in 8 Ld SO and 8 Ld MSOP packages, and the EL8403 in 14 Ld SO and 16 Ld QSOP packages. All are specified for operation over the -40°C to +85°C temperature range. • 600V/µs slew rate • Low supply current = 5.6mA per channel • Supplies from 3V to 5.5V • Rail-to-rail output • Fast 25ns disable (EL8202 only) • Low cost • Pb-free plus anneal available (RoHS compliant) Applications • Video amplifiers • Portable/hand-held products • Communications devices Ordering Information (Continued) Ordering Information PART NUMBER FN7106.2 PART TAPE & MARKING REEL PACKAGE PKG. DWG. # PART NUMBER PART TAPE & MARKING REEL PACKAGE PKG. DWG. # EL8202IY m - 10 Ld MSOP MDP0043 EL8403IS 8403IS - 14 Ld SO MDP0027 EL8202IY-T7 m 7” 10 Ld MSOP MDP0043 EL8403IS-T7 8403IS 7” 14 Ld SO MDP0027 EL8202IY-T13 m 13” 10 Ld MSOP MDP0043 EL8403IS-T13 8403IS 13” 14 Ld SO MDP0027 EL8202IYZ (See Note) BAPAA - 10 Ld MSOP MDP0043 (Pb-free) EL8403ISZ (See Note) 8403ISZ - 14 Ld SO (Pb-free) MDP0027 EL8202IYZ-T7 (See Note) BAPAA 7” 10 Ld MSOP MDP0043 (Pb-free) EL8403ISZ-T7 (See Note) 8403ISZ 7” 14 Ld SO (Pb-free) MDP0027 EL8202IYZ-T13 BAPAA (See Note) 13” 10 Ld MSOP MDP0043 (Pb-free) EL8403ISZ-T13 8403ISZ (See Note) 13” 14 Ld SO (Pb-free) MDP0027 EL8203IS 8203IS - 8 Ld SO MDP0027 EL8403IU 8403IU - 16 Ld QSOP MDP0040 EL8203IS-T7 8203IS 7” 8 Ld SO MDP0027 EL8403IU-T7 8403IU 7” 16 Ld QSOP MDP0040 8403IU 13” 16 Ld QSOP MDP0040 13” 8 Ld SO MDP0027 EL8403IU-T13 8203ISZ - 8 Ld SO (Pb-free) MDP0027 EL8403IUZ (See Note) 8403IUZ - 16 Ld QSOP MDP0040 (Pb-free) 8203ISZ 7” 8 Ld SO (Pb-free) MDP0027 EL8403IUZ-T7 (See Note) 8403IUZ 7” 16 Ld QSOP MDP0040 (Pb-free) EL8203ISZ-T13 8203ISZ (See Note) 13” 8 Ld SO (Pb-free) MDP0027 EL8403IUZ-T13 8403IUZ (See Note) 13” 16 Ld QSOP MDP0040 (Pb-free) NOTE: Intersil Pb-free plus anneal products employ special Pb-free material sets; molding compounds/die attach materials and 100% matte tin plate termination finish, which are RoHS compliant and compatible with both SnPb and Pb-free soldering operations. Intersil Pb-free products are MSL classified at Pb-free peak reflow temperatures that meet or exceed the Pb-free requirements of IPC/JEDEC J STD-020. EL8203IS-T13 8203IS EL8203ISZ (See Note) EL8203ISZ-T7 (See Note) EL8203IY BJAAA - 8 Ld MSOP MDP0043 EL8203IY-T7 BJAAA 7” 8 Ld MSOP MDP0043 EL8203IY-T13 BJAAA 13” 8 Ld MSOP MDP0043 1 CAUTION: These devices are sensitive to electrostatic discharge; follow proper IC Handling Procedures. 1-888-INTERSIL or 1-888-468-3774 | Intersil (and design) is a registered trademark of Intersil Americas Inc. Copyright © Intersil Americas Inc. 2003, 2006. All Rights Reserved. All other trademarks mentioned are the property of their respective owners. EL8202, EL8203, EL8403 Pinouts EL8203 (8 LD SO, MSOP) TOP VIEW EL8202 (10 LD MSOP) TOP VIEW 10 INA- INA+ 1 + CEA 2 VS- 3 + - CEB 4 9 OUTA INA- 2 8 VS+ INA+ 3 7 OUTB 6 INB+ VS- 4 5 INB+ EL8403 (16 LD QSOP) TOP VIEW EL8403 (14 LD SO) TOP VIEW OUTA 1 14 OUTD A - + D + - INA+ 3 VS+ 4 - + B + C OUTB 7 OUTA 1 13 IND- INA- 2 12 IND+ INA+ 3 11 VS- INB+ 5 INB- 6 7 OUTB + 6 INB- INB+ 5 INA- 2 8 VS+ OUTA 1 INB+ 5 9 INC- INB- 6 OUTB 7 NC 8 2 - + + - 15 IND14 IND+ VS+ 4 10 INC+ 8 OUTC 16 OUTD 13 VS12 INC+ - + + - 11 INC10 OUTC 9 NC EL8202, EL8203, EL8403 Absolute Maximum Ratings (TA = 25°C) Power Dissipation . . . . . . . . . . . . . . . . . . . . . . . . . . . . . See Curves Storage Temperature . . . . . . . . . . . . . . . . . . . . . . . .-65°C to +150°C Ambient Operating Temperature . . . . . . . . . . . . . . . .-40°C to +85°C Operating Junction Temperature . . . . . . . . . . . . . . . . . . . . . . +125°C Supply Voltage from VS+ to VS- . . . . . . . . . . . . . . . . . . . . . . . . 5.5V Input Voltage . . . . . . . . . . . . . . . . . . . . . . . . VS+ +0.3V to VS- -0.3V Differential Input Voltage . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .2V Continuous Output Current . . . . . . . . . . . . . . . . . . . . . . . . . . . 40mA CAUTION: Stresses above those listed in “Absolute Maximum Ratings” may cause permanent damage to the device. This is a stress only rating and operation of the device at these or any other conditions above those indicated in the operational sections of this specification is not implied. IMPORTANT NOTE: All parameters having Min/Max specifications are guaranteed. Typ values are for information purposes only. Unless otherwise noted, all tests are at the specified temperature and are pulsed tests, therefore: TJ = TC = TA Electrical Specifications PARAMETER VS+ = 5V, VS- = GND, TA = 25°C, VCM = 2.5V, RL to 2.5V, AV = 1, Unless Otherwise Specified DESCRIPTION CONDITIONS MIN TYP MAX UNIT -8 -0.8 +8 mV INPUT CHARACTERISTICS VOS Offset Voltage TCVOS Offset Voltage Temperature Coefficient Measured from TMIN to TMAX IB Input Bias Current VIN = 0V IOS Input Offset Current VIN = 0V TCIOS Input Bias Current Temperature Coefficient Measured from TMIN to TMAX CMRR Common Mode Rejection Ratio VCM = -0.15V to +3.5V (EL8202,EL8203) CMIR Common Mode Input Range RIN Input Resistance CIN Input Capacitance AVOL Open Loop Gain VCM = -0.15V to +3.5V (EL8403) 3 -9 -6 0.1 µA 0.6 µA 2 nA/°C 70 95 dB 60 85 VS- 0.15 Common Mode VOUT = +1.5V to +3.5V, RL = 1k to GND µV/°C 75 dB VS+ 1.5 V 3.5 M 0.5 pF 90 dB VOUT = +1.5V to +3.5V, RL = 150 to GND 80 dB 30 m OUTPUT CHARACTERISTICS ROUT Output Resistance AV = +1 VOP Positive Output Voltage Swing RL = 1k 4.85 4.9 V RL = 150 4.6 4.7 V VON Negative Output Voltage Swing RL = 150 100 150 mV RL = 1k (EL8202,EL8203) 25 50 mV 50 100 RL = 1k (EL8403) IOUT Linear Output Current ISC (source) Short Circuit Current RL = 10 ISC (sink) Short Circuit Current mV 65 mA 60 80 mA RL = 10 120 150 mA VS+ = 4.5V to 5.5V 70 95 dB POWER SUPPLY PSRR Power Supply Rejection Ratio IS-ON Supply Current - Enabled (per amplifier) 5.6 6.2 mA IS-OFF Supply Current - Disabled (per amplifier) EL8202 only 40 90 µA ENABLE (EL8202 ONLY) tEN Enable Time 200 ns tDS Disable Time 25 ns VIH-ENB ENABLE Pin Voltage for Power-up 0.8 V VIL-ENB ENABLE Pin Voltage for Shut-down 2 V 3 EL8202, EL8203, EL8403 Electrical Specifications PARAMETER VS+ = 5V, VS- = GND, TA = 25°C, VCM = 2.5V, RL to 2.5V, AV = 1, Unless Otherwise Specified (Continued) DESCRIPTION CONDITIONS MIN TYP MAX UNIT IIH-ENB ENABLE Pin Input Current High 8.6 µA IIL-ENB ENABLE Pin Input for Current Low 0.01 µA AV = +1, RF = 0, CL = 2.5pF 500 MHz AV = -1, RF = 1k, CL = 2.5pF 140 MHz AV = +2, RF = 1k, CL = 2.5pF 165 MHz AV = +10, RF = 1k, CL = 2.5pF 18 MHz AC PERFORMANCE BW -3dB Bandwidth BW ±0.1dB Bandwidth AV = +1, RF = 0, CL = 2.5pF 35 MHz Peak Peaking AV = +1, RL = 1k, CL = 2.5pF 2 dB GBWP Gain Bandwidth Product 200 MHz PM Phase Margin RL = 1k, CL = 2.5pF 55 ° SR Slew Rate AV = 2, RL = 100, VOUT = 0.5V to 4.5V 600 V/µs tR Rise Time 2.5VSTEP, 20% - 80% 4 ns tF Fall Time 2.5VSTEP, 20% - 80% 2 ns OS Overshoot 200mV step 10 % tPD Propagation Delay 200mV step 1 ns tS 0.1% Settling Time 200mV step 15 ns dG Differential Gain AV = +2, RF = 1k, RL = 150 0.01 % dP Differential Phase AV = +2, RF = 1k, RL = 150 0.01 ° eN Input Noise Voltage f = 10kHz 12 nV/Hz iN+ Positive Input Noise Current f = 10kHz 1.7 pA/Hz iN- Negative Input Noise Current f = 10kHz 1.3 pA/Hz eS Channel Separation f = 100kHz 95 dB 500 Pin Descriptions EL8202 (MSOP-10) EL8203 (SO-8, MSOP-8) EL8403 (SO-14) EL8403 (QSOP-16) NAME 1, 5 3, 5 3, 5, 10, 12 3,5,12,14 IN+ Non-inverting input for each channel CE Enable and disable input for each channel 2, 4 FUNCTION 3 4 11 13 VS- Negative power supply 6, 10 2, 6 2, 6, 9, 13 2,6,11,15 IN- Inverting input for each channel 7, 9 1, 7 1, 7, 8, 14 1,7,10,16 OUT Amplifier output for each channel 8 8 4 4 VS+ Positive power supply 4 EL8202, EL8203, EL8403 Typical Performance Curves 3 2 GAIN (dB) 5 VS=5V AV=1 RL=1k CL=2.5pF NORMALIZED GAIN (dB) 5 4 VOP-P=200mV 1 0 -1 VOP-P=1V -2 -3 VOP-P=2V -4 -5 1M 10M 100M 3 RF=RG=1k 1 -1 -3 RF=RG=500 VS=5V AV=2 RL=1k CL=2.5pF -5 100K 1G 1M FREQUENCY (Hz) 4 NORMALIZED GAIN (dB) NORMALIZED GAIN (dB) 3 AV=1 2 AV=2 1 0 -1 -2 -3 -4 AV=5 AV=10 -5 1M 10M 100M 2 VS=5V CL=2.5pF RL=1k RF=1k AV=-1 AV=-5 -2 -4 AV=-10 -6 100K 1G 1M 11 9 RL=1k GAIN (dB) GAIN (dB) 1 0 -1 RL=500 7 5 RL=1k, 150 -5 1M 3 RL=500 -4 10M 100M 1G FREQUENCY (Hz) FIGURE 5. SMALL SIGNAL FREQUENCY RESPONSE FOR VARIOUS NON-INVERTING GAINS 5 1G VS=5V AV=2 CL=2.5pF RF=RG=1k -2 -3 100M FIGURE 4. SMALL SIGNAL FREQUENCY RESPONSE FOR VARIOUS INVERTING GAINS 5 RL=100 10M FREQUENCY (Hz) FIGURE 3. SMALL SIGNAL FREQUENCY RESPONSE FOR VARIOUS NON-INVERTING GAINS 2 1G 0 FREQUENCY (Hz) V =5V 4 AS=1 V 3 CL=2.5pF 100M FIGURE 2. SMALL SIGNAL FREQUENCY RESPONSE vs RF AND RG 5 VS=5V CL=2.5pF RL=1k 10M FREQUENCY (Hz) FIGURE 1. FREQUENCY RESPONSE FOR VARIOUS OUTPUT VOLTAGE LEVELS 4 RF=RG=2k 1 100K 1M 10M 100M 1G FREQUENCY (Hz) FIGURE 6. SMALL SIGNAL FREQUENCY RESPONSE vs VARIOUS RLOAD EL8202, EL8203, EL8403 Typical Performance Curves (Continued) 5 16 VS=5V AV=1 RL=1k 4 3 CL=5.4pF 12 CL=2.5pF 3 1 0 CL=1.5pF -1 -2 CL=20pF 8 6 CL=10pF 4 2 -3 0 -4 -2 -5 1M 10M 100M CL=2.5pF -4 100K 1G 1M FREQUENCY (Hz) RL=150 30 405 -10 315 -30 225 RL=150 -10 -50 135 RL=1k -90 1K 10K 1M 10M 100M VS=5V AV=1 RL=1k -50 -70 -110 1K -45 1G 10K FIGURE 9. OPEN LOOP GAIN AND PHASE vs FREQUENCY 600 100M 1G RL=1k CL=2.5pF 550 500 BANDWIDTH (MHz) -30 PSRR (dB) 10M FIGURE 10. DISABLED OUTPUT ISOLATION FREQUENCY RESPONSE -10 PSRR- -70 1M 100K FREQUENCY (Hz) FREQUENCY (Hz) -50 1G -90 45 100K 100M FIGURE 8. SMALL SIGNAL FREQUENCY RESPONSE FOR VARIOUS CL GAIN (dB) GAIN (dB) RL=1k PHASE (°) 110 10M FREQUENCY (Hz) FIGURE 7. SMALL SIGNAL FREQUENCY RESPONSE VS CL 70 CL=28.5pF 10 GAIN (dB) GAIN (dB) VS=5V AV=2 RF=RG=1k 14 PSRR+ -90 AV=1 450 400 350 300 250 AV=2 200 150 -110 1K 100 10K 100K 1M 10M 100M FREQUENCY (Hz) FIGURE 11. POWER SUPPLY REJECTION RATIO vs FREQUENCY 6 3 3.5 4.5 4 5 5.5 VS (V) FIGURE 12. SMALL SIGNAL BANDWIDTH vs SUPPLY VOLTAGE EL8202, EL8203, EL8403 Typical Performance Curves (Continued) 100 3.5 RL=1k CL=1.5pF 10 PEAKING (dB) IMPEDANCE () 3 1 0.1 AV=1 2.5 2 1.5 1 AV=2 0.5 0 0.01 10K 100K 1M 10M 100M 3 4 3.5 4.5 FREQUENCY (Hz) -15 10 -35 8 -55 6 -75 4 2 -95 0 -115 100K 1M 10M 100M 0 0.5 1 1.5 2 2.5 HD2 -90 1 HD2@5MHz Hz @ 1M HD3@ 5 -75 HD2@10MHz DISTORTION (dBc) -80 4 4.5 5 5.5 -70 VS=5V RL=1k CL=2.5pF AV=2 -70 3.5 FIGURE 16. SUPPLY CURRENT vs SUPPLY VOLTAGE (PER CHANNEL) FIGURE 15. COMMON-MODE REJECTION RATIO vs FREQUENCY -60 3 VS (V) FREQUENCY (Hz) DISTORTION (dBc) 5.5 FIGURE 14. SMALL SIGNAL PEAKING vs SUPPLY VOLTAGE IS (mA) CMRR (dB) FIGURE 13. OUPUT IMPEDANCE vs FREQUENCY -100 5 VS (V) H HD3@10M z MHz 2 3 4 5 VOP-P (V) FIGURE 17. HARMONIC DISTORTION vs OUTPUT VOLTAGE 7 -80 H D 2@ AV =2 AV =1 -85 VS=5V f=5MHz -90 -95 HD3@1MHz HD2@ H D 3@ VO=1VP-P for AV=1 VO=2VP-P for AV=2 -100 100 H D 3@ AV =2 AV =1 1K 2K RLOAD () FIGURE 18. HARMONIC DISTORTION vs LOAD RESISTANCE EL8202, EL8203, EL8403 Typical Performance Curves (Continued) -50 1K DISTORTION (dBc) -60 -70 AV=2 HD2@ -80 -90 -100 HD3@AV=2 VOLTAGE NOISE (nV/Hz) CURRENT NOISE (pA/Hz), VS=5V RL=1k CL=2.5pF VO=1VP-P for AV=1 VO=2VP-P for AV=2 HD2@AV=1 =1 @A V HD 3 10 1 100 eN 10 IN+ 1 10 40 100 FREQUENCY (MHz) 10K 100K 1M 10M FIGURE 20. VOLTAGE AND CURRENT NOISE vs FREQUENCY 0 CHANNEL SEPARATION (dB) 0 CHANNEL SEPARATION (dB) 1K FREQUENCY (Hz) FIGURE 19. HARMONIC DISTORTION vs FREQUENCY -10 -20 -30 -40 CH1<=>CH2 -50 -60 -70 -80 -90 -100 100K 1M 10M 100M 1G -10 -20 -30 -40 -50 FIGURE 21. CHANNEL SEPARATION vs FREQUENCY (EL8202 AND EL8203) VS=5V AV=1 RL=1k to 2.5V CL=5pF CH1<=>CH2 -60 -70 CH1<=>CH4 CH2<=>CH3 -80 CH1<=>CH3 CH2<=>CH4 -90 -100 100K 1M 10M 100M FIGURE 22. CHANNEL SEPARATION vs FREQUENCY (EL8403) VS=5V AV=1 RL=1k to 2.5V CL=5pF 3.5 2.5 2.5 1.5 1.5 2ns/DIV FIGURE 23. LARGE SIGNAL TRANSIENT RESPONSE - RISING 8 1G FREQUENCY (Hz) FREQUENCY (Hz) 3.5 IN- 2ns/DIV FIGURE 24. LARGE SIGNAL TRANSIENT RESPONSE - FALLING EL8202, EL8203, EL8403 Typical Performance Curves (Continued) 2.6 2.5 VS=5V, AV=1, RL=1k TO 2.5V, CL= 2.5pF VS=5V, AV=5, RL=1k to 2.5V VIN 5 2.4 2.5 2.6 VOUT 2.5 0 2.4 2µs/DIV 10ns/DIV FIGURE 25. SMALL SIGNAL TRANSIENT REPONSE VS=5V, AV=5, RL=1k TO 2.5V FIGURE 26. OUTPUT SWING CH1 ENABLE INPUT 5 2.5 CH2 VOUT 0 CH1, CH2, 1V/DIV, M=100ns 2µs/DIV FIGURE 27. OUTPUT SWING FIGURE 28. ENABLED RESPONSES (EL8202) CH1 CH2 POWER DISSIPATION (W) JEDEC JESD51-3 LOW EFFECTIVE THERMAL CONDUCTIVITY TEST BOARD ENABLE INPUT VOUT 1 0.9 833mW 0.8 0.3 FIGURE 29. DISABLED RESPONSE (EL8202) 9 JA = MSOP8/10 JA=206°C/W 0.2 SO 12 0 14 °C /W SO8 JA=160°C/W QSOP16 JA=158°C/W 0.1 0 CH1, CH2, 0.5V/DIV, M=20ns 0.7 625mW 0.6 633mW 0.5 0.4 486mW 0 25 50 75 85 100 125 150 AMBIENT TEMPERATURE (°C) FIGURE 30. PACKAGE POWER DISSIPATION vs AMBIENT TEMPERATURE EL8202, EL8203, EL8403 Typical Performance Curves (Continued) POWER DISSIPATION (W) 1.4 JEDEC JESD51-7 HIGH EFFECTIVE THERMAL CONDUCTIVITY TEST BOARD 1.2 1.136W 1 909mW 0.8 JA 893mW 870mW MSOP8/10 JA=115°C/W 0.6 0.4 SO =8 14 8° C/ W SO8 JA=110°C/W QSOP16 JA=112°C/W 0.2 0 0 25 50 75 85 100 125 150 AMBIENT TEMPERATURE (°C) FIGURE 31. PACKAGE POWER DISSIPATION vs AMBIENT TEMPERATURE Simplified Schematic Diagram VS+ I1 I2 Q5 IN+ Q1 R8 VBIAS1 Q6 R3 R1 R7 R6 Q7 R2 Q2 DIFFERENTIAL TO SINGLE ENDED DRIVE GENERATOR IN- VBIAS2 Q3 OUT Q4 Q8 R4 R5 R9 VS- Description of Operation and Application Information Product Description The EL8202, EL8203 and EL8403 are wide bandwidth, single supply, low power and rail-to-rail output voltage feedback operational amplifiers. The amplifiers are internally compensated for closed loop gain of +1 of greater. Connected in voltage follower mode and driving a 1k load, the EL8202, EL8203 and EL8403 have a -3dB bandwidth of 500MHz. Driving a 150 load, the bandwidth is about 350MHz while maintaining a 600V/us slew rate. The EL8202 is available with a power down pin to reduce power to 30µA typically while the amplifier is disabled. 10 Input, Output and Supply Voltage Range The EL8202, EL8203 and EL8403 have been designed to operate with a single supply voltage from 3V to 5.0V. Split supplies can also be used as long as their total voltage is within 3V to 5.0V. The amplifiers have an input common mode voltage range from 0.15V below the negative supply (VS- pin) to within 1.5V of the positive supply (VS+ pin). If the input signal is outside the above specified range, it will cause the output signal to be distorted. The output of the EL8202, EL8203 and EL8403 can swing rail to rail. As the load resistance becomes lower, the ability to drive close to each rail is reduced. For the load resistor 1k, the output swing is about 4.9V at a 5V supply. For the load resistor 150, the output swing is about 4.6V. EL8202, EL8203, EL8403 Choice of Feedback Resistor and Gain Bandwidth Product For applications that require a gain of +1, no feedback resistor is required. Just short the output pin to the inverting input pin. For gains greater than +1, the feedback resistor forms a pole with the parasitic capacitance at the inverting input. As this pole becomes smaller, the amplifier’s phase margin is reduced. This causes ringing in the time domain and peaking in the frequency domain. Therefore, RF has some maximum value that should not be exceeded for optimum performance. If a large value of RF must be used, a small capacitor in the few pF range in parallel with RF can help to reduce the ringing and peaking at the expense of reducing the bandwidth. As far as the output stage of the amplifier is concerned, the output stage is also a gain stage with the load. RF and RG appear in parallel with RL for gains other than +1. As this combination gets smaller, the bandwidth falls off. Consequently, RF also has a minimum value that should not be exceeded for optimum performance. For gain of +1, RF=0 is optimum. For the gains other than +1, optimum response is obtained with RF between 300 to 1k. The EL8202, EL8203 and EL8403 have a gain bandwidth product of 200MHz. For gains 5, its bandwidth can be predicted by the following equation: Gain BW = 200MHz allow extensive capacitive drive. However, other applications may have high capacitive loads without a back-termination resistor. Again, a small series resistor at the output can help to reduce peaking. Disable/Power-Down The EL8202 can be disabled and placed its output in a high impedance state. The turn off time is about 25ns and the turn on time is about 200ns. When disabled, the amplifier’s supply current is reduced to 40µA typically, thereby effectively eliminating the power consumption. The amplifier’s power down can be controlled by standard TTL or CMOS signal levels at the ENABLE pin. The applied logic signal is relative to VS- pin. Letting the ENABLE pin float or applying a signal that is less than 0.8V above VS- will enable the amplifier. The amplifier will be disabled when the signal at ENABLE pin is 2V above VS-. Output Drive Capability The EL8202, EL8203 and EL8403 do not have internal short circuit protection circuitry. They have a typical short circuit current of 80mA sourcing and 150mA sinking for the output is connected to half way between the rails with a 10 resistor. If the output is shorted indefinitely, the power dissipation could easily increase such that the part will be destroyed. Maximum reliability is maintained if the output current never exceeds ±40mA. This limit is set by the design of the internal metal interconnections. Power Dissipation Video Performance For good video performance, an amplifier is required to maintain the same output impedance and the same frequency response as DC levels are changed at the output. This is especially difficult when driving a standard video load of 150, because the change in output current with DC level. Special circuitry has been incorporated in the EL8202, EL8203 and EL8403 to reduce the variation of the output impedance with the current output. This results in dG and dP specifications of 0.01% and 0.01, while driving 150 at a gain of 2. Driving high impedance loads would give a similar or better dG and dP performance. Driving Capacitive Loads and Cables The EL8202, EL8203 and EL8403 can drive 5pF loads in parallel with 1k with less than 5dB of peaking at gain of +1. If less peaking is desired in applications, a small series resistor (usually between 5 to 50) can be placed in series with the output to eliminate most peaking. However, this will reduce the gain slightly. If the gain setting is greater than 1, the gain resistor RG can then be chosen to make up for any gain loss which may be created by the additional series resistor at the output. When used as a cable driver, double termination is always recommended for reflection-free performance. For those applications, a back-termination series resistor at the amplifier’s output will isolate the amplifier from the cable and 11 With the high output drive capability of the EL8202, EL8203 and EL8403. It is possible to exceed the 125C absolute maximum junction temperature under certain load current conditions. Therefore, it is important to calculate the maximum junction temperature for the application to determine if the load conditions or package types need to be modified for the amplifier to remain in the safe operating area. The maximum power dissipation allowed in a package is determined according to: T JMAX – T AMAX PD MAX = -------------------------------------------- JA Where: TJMAX = Maximum junction temperature TAMAX = Maximum ambient temperature JA = Thermal resistance of the package The maximum power dissipation actually produced by an IC is the total quiescent supply current times the total power supply voltage, plus the power in the IC due to the load, or: EL8202, EL8203, EL8403 For sourcing: V OUTi PD MAX = V S I SMAX + V S – V OUTi ----------------R Li For sinking: as well as the output signal with the negative going sync pulse removed. 5V VIN PD MAX = V S I SMAX + V OUTi – V S- I LOADi VS+ + - 75 VS- 75 VOUT 75 Where: 1K VS = Total supply voltage ISMAX = Maximum quiescent supply current 1K FIGURE 32. SYNC PULSE REMOVER VOUTi = Maximum output voltage of the application for each channel RLOADi = Load resistance tied to ground for each channel 1V ILOADi = Load current for each channel VIN 0V By setting the two PDMAX equations equal to each other, we can solve the output current and RLOADi to avoid the device overheat. 1V VOUT Power Supply Bypassing and Printed Circuit Board Layout As with any high frequency device, a good printed circuit board layout is necessary for optimum performance. Lead lengths should be as short as possible. The power supply pin must be well bypassed to reduce the risk of oscillation. For normal single supply operation, where the VS- pin is connected to the ground plane, a single 4.7µF tantalum capacitor in parallel with a 0.1µF ceramic capacitor from VS+ to GND will suffice. This same capacitor combination should be placed at each supply pin to ground if split supplies are to be used. In this case, the VS- pin becomes the negative supply rail. For good AC performance, parasitic capacitance should be kept to a minimum. Use of wire wound resistors should be avoided because of their additional series inductance. Use of sockets should also be avoided if possible. Sockets add parasitic inductance and capacitance that can result in compromised performance. Minimizing parasitic capacitance at the amplifier’s inverting input pin is very important. The feedback resistor should be placed very close to the inverting input pin. Strip line design techniques are recommended for the signal traces. Typical Applications VIDEO SYNC PULSE REMOVER Many CMOS analog to digital converters have a parasitic latch up problem when subjected to negative input voltage levels. Since the sync tip contains no useful video information and it is a negative going pulse, we can chop it off. Figure 32 shows a gain of 2 connections. Figure 33 shows the complete input video signal applied at the input, 12 0.5V 0.5V 0V M = 10µs/DIV FIGURE 33. VIDEO SIGNAL MULTIPLEXER Besides the normal power down usage, the ENABLE pin of the EL8202 can be used for multiplexing applications. Figure 34 shows two EL8202 with the outputs tied together, driving a back terminated 75 video load. A 2VP-P 2MHz sine wave is applied to Amp A and a 1VP-P 2MHz sine wave is applied to Amp B. Figure 33 shows the ENABLE signal and the resulting output waveform at VOUT. Observe the breakbefore-make operation of the multiplexing. Amp A is on and VIN1 is passed through to the output when the ENABLE signal is low and turns off in about 25ns when the ENABLE signal is high. About 200ns later, Amp B turns on and VIN2 is passed through to the output. The break-before-make operation ensures that more than one amplifier isn’t trying to drive the bus at the same time. EL8202, EL8203, EL8403 +2.5V B 2MHz 1VP-P 5V + 75 -2.5V VIN C1 47µF R1 10K R3 C3 470µF 75 + 1K 1K 75 VOUT RT 75 VOUT - R2 10K 75 +2.5V A 2MHz 2VP-P 75 + 75 RF 1k RG 1k - -2.5V 1K C2 220µF 1K FIGURE 36. 5V SINGLE SUPPLY NON INVERTING VIDEO LINE DRIVER ENABLE RF 1k FIGURE 34. TWO TO ONE MULTIPLEXER VIN 0V -0.5V ENABLE -1.5V C1 RG 47µF 500 5V RT 75 5V - R3 C3 470µF 75 VOUT + R1 10K 75 -2.5V R2 10K 1V C2 220µF 0V B A -1V FIGURE 37. SINGLE SUPPLY INVERTING VIDEO LINE DRIVER 4 M = 50ns/DIV SINGLE SUPPLY VIDEO LINE DRIVER The EL8202, EL8203 and EL8403 are wideband rail-to-rail output op amplifiers with large output current, excellent dG, dP, and low distortion that allow them to drive video signals in low supply applications. Figure 36 is the single supply non-inverting video line driver configuration and Figure 37 is the inverting video ling driver configuration. The signal is AC coupled by C1. R1 and R2 are used to level shift the input and output to provide the largest output swing. RF and RG set the AC gain. C2 isolates the virtual ground potential. RT and R3 are the termination resistors for the line. C1, C2 and C3 are selected big enough to minimize the droop of the luminance signal. 13 3 NORMALIZED GAIN (dB) FIGURE 35. 2 1 0 AV = 2 -1 -2 AV = -2 -3 -4 -5 -6 100K 1M 10M FREQUENCY (Hz) 100M 500M FIGURE 38. VIDEO LINE DRIVER FREQUENCY RESPONSE EL8202, EL8203, EL8403 SO Package Outline Drawing 14 EL8202, EL8203, EL8403 MSOP Package Outline Drawing 15 EL8202, EL8203, EL8403 QSOP Package Outline Drawing NOTE: The package drawing shown here may not be the latest version. To check the latest revision, please refer to the Intersil website at http://www.intersil.com/design/packages/index.asp All Intersil U.S. products are manufactured, assembled and tested utilizing ISO9001 quality systems. Intersil Corporation’s quality certifications can be viewed at www.intersil.com/design/quality Intersil products are sold by description only. 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