INTEGRATED CIRCUITS
DATA SHEET
TZA1035HL
High speed advanced analog DVD
signal processor and laser supply
Preliminary specification
2003 Jun 03
Philips Semiconductors
Preliminary specification
High speed advanced analog DVD signal
processor and laser supply
CONTENTS
7.4
1
FEATURES
2
GENERAL DESCRIPTION
3
ORDERING INFORMATION
4
QUICK REFERENCE DATA
7.4.1
7.4.2
7.5
7.5.1
7.5.2
5
BLOCK DIAGRAM
6
PINNING
7
FUNCTIONAL DESCRIPTION
7.1
7.2
7.2.1
7.2.2
7.2.3
7.2.4
7.2.4.1
7.2.4.2
7.2.4.3
RF data processing
Servo signal processing
Servo signal path set-up
Focus servo
Radial servo
Differential phase detection
Drop-out concealment
Push-pull and three-beam push-pull
Enhanced push-pull (dynamic offset
compensation for beam landing)
Offset compensation
Automatic dual laser supply
Power-on reset and general power on
Compatibility with TZA1033HL/V1
Software compatibility
Hardware compatibility
Interface to the system controller
Control registers
Register 0: power control
Register 1: servo and RF modes
Register 2: focus offset DAC
Register 3: RF path gain
Register 4: RF left and right, or sum offset
compensation
Register 5: RF sum offset compensation
Register 6: servo gain and dynamic radial
offset compensation factor
Register 7: servo path gain and bandwidth and
RF path bandwidth and pre-emphasis
Register 8: RF channel selection
Register 11: radial servo offset cancellation
Register 12: central servo offset cancellation
inputs A and B
Register 13: central servo offset cancellation
inputs C and D
Register 14: RF filter settings
Register 15: DPD filter settings
7.2.4.4
7.2.5
7.2.6
7.2.7
7.2.7.1
7.2.7.2
7.2.8
7.3
7.3.1
7.3.2
7.3.3
7.3.4
7.3.5
7.3.6
7.3.7
7.3.8
7.3.9
7.3.10
7.3.11
7.3.12
7.3.13
7.3.14
2003 Jun 03
7.5.5.3
7.5.5.4
Internal digital control, serial bus and external
digital input signal relationships
STANDBY mode
RF only mode
Signal descriptions
Data path signals through pins A to D
Data signal path through input pins RFSUMP
and RFSUMN
HF filtering
Focus signals
Radial signals
DPD signals (DVD-ROM mode) with no
drop-out concealment
DPD signals (DVD-ROM mode) with
drop-out concealment
Three-beam push-pull (CD mode)
Enhanced push-pull
8
LIMITING VALUES
9
THERMAL CHARACTERISTICS
10
CHARACTERISTICS
11
APPLICATION INFORMATION
11.1
11.1.1
11.1.2
11.2
11.3
11.4
11.4.1
11.4.2
11.4.3
11.4.4
Signal relationships
Data path
Servo path
Programming examples
Energy saving
Initial DC and gain setting strategy
Electrical offset from pick-up
Gain setting servo
DC level in RF path
Gain setting RF path
12
PACKAGE OUTLINE
13
SOLDERING
13.1
Introduction to soldering surface mount
packages
Reflow soldering
Wave soldering
Manual soldering
Suitability of surface mount IC packages for
wave and reflow soldering methods
7.5.3
7.5.4
7.5.5
7.5.5.1
7.5.5.2
13.2
13.3
13.4
13.5
2
TZA1035HL
14
DATA SHEET STATUS
15
DEFINITIONS
16
DISCLAIMERS
Philips Semiconductors
Preliminary specification
High speed advanced analog DVD signal
processor and laser supply
1
FEATURES
2
• Operates with DVD-ROM, DVD+RW, DVD-RW,
CD-ROM and CD-RW
GENERAL DESCRIPTION
The TZA1035HL is an analog preprocessor and laser
supply circuit for DVD and CD read-only players. The
device contains data amplifiers, several options for radial
tracking and focus control. The preamplifier forms a
versatile, programmable interface between single light
path voltage output CD or DVD mechanisms to Philips
digital signal processor family for CD and DVD (for
example, Gecko, HDR65 or Iguana). A separate
high-speed RFSUM input is available.
• Operates up to 64 × CD-ROM and 12 × DVD-ROM
• RF data amplifier with wide, fine pitch programmable
noise filter and equalizer equivalent to 64 × CD or
12 × DVD
• Programmable RF gain for DVD-ROM, CD-RW and
CD-ROM applications (approximately 50 dB range to
cover a large range of disc-reflectivity and OPUs)
The device contains several options for radial tracking:
• Additional RF sum input
• Conventional three-beam tracking for CD
• Balanced RF data signal transfer
• Differential phase detector for DVD
• Universal photodiode IC interface using internal
conversion resistors and offset cancellation
• Push-pull with flexible left and right weighting to
compensate dynamic offsets e.g. beam landing offset
• Input buffers and amplifiers with low-pass filtering
• A radial error signal to allow Fast Track Count (FTC)
during track jumps.
• Three different tracking servo strategies:
– Conventional three-beam tracking for CD
The dynamic range of this preamplifier and processor
combination can be optimized for LF servo and RF data
paths. The gain in both channels can be programmed
separately and so guarantees optimal playability for all
disc types.
– Differential Phase Detection (DPD) for DVD-ROM,
including option to emulate traditional drop-out
detection: Drop-Out Concealment (DOC)
– Advanced push-pull with dynamic offset
compensation.
The RF path is fully DC coupled. The DC content
compensation techniques provide fast settling after disc
errors.
• Enhanced signal conditioning in DPD circuit for optimal
tracking performance under noisy conditions
• Radial error signal for Fast Track Counting (FTC)
The device can accommodate astigmatic, single foucault
and double foucault detectors and can be used with P-type
lasers with N-sub or P-sub monitor diodes. After an initial
adjustment, the circuit will maintain control over the laser
diode current. With an on-chip reference voltage
generator, a constant stabilized output power is ensured
and is independent of ageing.
• RF only mode: servo outputs can be set to 3-state, while
RF data path remains active
• Radial servo polarity switch
• Flexible adaption to different light pen configurations
• Two fully automatic laser controls for red and infrared
lasers, including stabilization and an on/off switch
An internal Power-on reset circuit ensures a safe start-up
condition.
• Automatic selection of monitor diode polarity
• Digital interface with 3 and 5 V compatibility.
2003 Jun 03
TZA1035HL
3
Philips Semiconductors
Preliminary specification
High speed advanced analog DVD signal
processor and laser supply
3
TZA1035HL
ORDERING INFORMATION
PACKAGE
TYPE NUMBER
NAME
TZA1035HL
4
LQFP48
DESCRIPTION
VERSION
plastic low profile quad flat package; 48 leads; body 7 × 7 × 1.4 mm
SOT313-2
QUICK REFERENCE DATA
SYMBOL
PARAMETER
CONDITIONS
MIN.
TYP.
MAX.
UNIT
ambient temperature
0
−
60
°C
VDDA1, VDDA2,
VDDA3, VDDA4
analog supply voltage
4.5
5.0
5.5
V
VDDD3
3 V digital supply voltage
2.7
3.3
5.5
V
VDDD5
5 V digital supply voltage
4.5
5.0
5.5
V
IDD
supply current
Tamb
Supplies
VI(logic)
logic input compatibility
without laser supply
−
98
120
mA
STANDBY mode
−
−
1
mA
note 1
2.7
3.3
5.5
V
60
75
100
kHz
0
−
12
µA
Servo signal processing
BLF(−3dB)
−3 dB bandwidth of
LF path
IO(LF)
output current
VO(FTC)(p-p)
FTC output voltage
(peak-to-peak value)
BFTC
FTC bandwidth
VI(FTCREF)
FTC reference input
voltage
focus servo output
0
−
12
µA
2.0
−
−
V
FTCHBW = 0
−
600
−
kHz
FTCHBW = 1; note 2
−
1200
−
kHz
1.25
−
2.75
V
RF channels
6
−
49
dB
RFSUM channels
radial servo output
RF data processing
ARF
linear current gain
programmable gain
−6
−
+31
dB
BRF(−3dB)
−3 dB bandwidth of RFP
and RFN signal path
RFEQEN = 0;
RFNFEN = 0
200
300
−
MHz
f0(RF)
noise filter and equalizer
corner frequency
BWRF = 0
8
12.0
14.5
MHz
BWRF = 127
100
145
182
MHz
td(RF)
flatness delay in RF data
path
equalizer on; flat from
0 to 100 MHz;
BWRF = 127
−
−
0.5
ns
Zi
input impedance of
pins A to D
100
−
−
kΩ
2003 Jun 03
4
Philips Semiconductors
Preliminary specification
High speed advanced analog DVD signal
processor and laser supply
SYMBOL
Vi(RF)(FS)
PARAMETER
CONDITIONS
TZA1035HL
MIN.
TYP.
MAX.
UNIT
input voltage on
at the appropriate signal
pins A to D for full-scale at path gain setting
output
RF signal path
−
−
600
mV
LF signal path
−
−
700
mV
Vi(SUM)(dif)
differential input voltage
on pins RFSUMP and
RFSUMN
GRFSUM = −6 dB
−
−
1800
mV
VI(DC)
DC input voltage range on
pins RFSUMP and
RFSUMN
with respect to VSS
1.3
−
VDDA − 1.0
V
Vo(RF)(dif)(p-p)
differential output voltage
on pins RFP and RFN
(peak-to-peak value)
−
−
1.4
V
VO(RF)(DC)
DC output voltage on
pins RFP and RFN
0.35
−
VDDA − 1.9
V
Vi(RFREF)(CM)
input reference voltage on
pin RFREF for common
mode output
0.8
1.2
2.1
V
Io(laser)(max)
maximum current output
to laser
−120
−
−
mA
Vi(mon)
input voltage from laser
monitor diode
LOW level voltage
−
VDDA4 − 0.155 −
V
HIGH level voltage
−
VDDA4 − 0.190 −
V
LOW level voltage
−
0.155
−
V
HIGH level voltage
−
0.185
−
V
Laser supply
P-type monitor diode
N-type monitor diode
Notes
1. Input logic voltage level follows the supply voltage applied at pin VDDD3.
2. High FTC bandwidth is achieved when IS1 and IS2 > 1.5 µA.
2003 Jun 03
5
Philips Semiconductors
Preliminary specification
High speed advanced analog DVD signal
processor and laser supply
5
TZA1035HL
BLOCK DIAGRAM
VDDA1
handbook, full pagewidth
VDDA2
VDDA3
VDDA4
RFREF
VDDD3
VDDD5
43
37
32
38
15
23
5
RFSUMP
RFSUMN
1
RF DATA PROCESSING
2
VARIABLE
GAIN STAGES
MULTIPLEXER
A to D
OPUREF
5
39
40
RFP
RFN
4
TZA1035HL
36
A
B
C
D
E
F
OPUREF
FTCREF
VDDL
REXT
CDMI
CDLO
DVDMI
DVDLO
8
SERVO SIGNAL PROCESSING
4
9
34
3-BEAM
TRACKING
10
OA
35
33
OB
OC
OD
11
30
3
SELECT; SWAP
DPD
29
4
S1
12
PUSH-PULL
OFFSET
COMPENSATION
S2
28
25
FTC
S1
S2
OCENTRAL
FTC
27
47
20
VOLTAGE AND
CURRENT
REFERENCES
44
21
DUAL
LASER
SUPPLY
FTC
COMPARATOR
46
22
COP
COM
COO
LASER 1
45
SERIAL
INTERFACE
7
LASER 2
48
14
26
6
42
41
31
19
VSSA2
VSSA3
VSSA4
VSSD
16
17
TM
TDO
18
MCE104
VSSA1
SIDA
Fig.1 Block diagram.
2003 Jun 03
6
SICL
SILD
Philips Semiconductors
Preliminary specification
High speed advanced analog DVD signal
processor and laser supply
6
TZA1035HL
PINNING
SYMBOL
PIN
DESCRIPTION
RFSUMP
1
positive RF sum input
RFSUMN
2
negative RF sum input
E
3
input E
F
4
input F
VDDA1
5
analog supply voltage 1 (RF input stage)
VSSA1
6
analog ground 1
DVDMI
7
input signal from DVD laser monitor diode
A
8
input A
B
9
input B
C
10
input C
D
11
input D
OPUREF
12
reference input from Optical Pick-Up (OPU)
n.c.
13
not connected
TM
14
test mode input (factory test only)
VDDD3
15
digital supply voltage (serial interface 3 V I/O pads and FTC comparator)
SIDA
16
serial host interface data input
SICL
17
serial host interface clock input
SILD
18
serial host interface load
VSSD
19
digital ground
COP
20
positive FTC comparator input
COM
21
inverting FTC comparator input
COO
22
FTC comparator output
VDDD5
23
digital supply voltage (5 V digital core)
n.c.
24
not connected
FTC
25
fast track count output
TDO
26
test data output (factory test only)
FTCREF
27
FTC reference input
OCENTRAL
28
test pin for offset cancellation
S2
29
servo current output 2 for radial tracking
S1
30
servo current output 1 for radial tracking
VSSA4
31
analog ground 4
VDDA4
32
analog supply voltage 4 (servo signal processing)
OD
33
servo current output for focus D
OC
34
servo current output for focus C
OB
35
servo current output for focus B
OA
36
servo current output for focus A
VDDA3
37
analog supply voltage 3 (RF output stage)
RFREF
38
DC reference input for RF channel common mode output voltage
RFP
39
positive RF output
RFN
40
negative RF output
2003 Jun 03
7
Philips Semiconductors
Preliminary specification
High speed advanced analog DVD signal
processor and laser supply
SYMBOL
PIN
TZA1035HL
DESCRIPTION
CD laser output
46
input signal from CD laser monitor diode
VDDL
47
laser supply voltage
DVDLO
48
DVD laser output
handbook, full pagewidth
37 VDDA3
45
CDMI
38 RFREF
CDLO
39 RFP
reference current input (connect via 12.1 kΩ to VSSA4)
40 RFN
44
41 VSSA3
REXT
42 VSSA2
analog supply voltage 2 (internal RF data processing)
43 VDDA2
analog ground 2
43
44 REXT
42
VDDA2
45 CDLO
VSSA2
46 CDMI
analog ground 3
47 VDDL
41
48 DVDLO
VSSA3
1
36 OA
RFSUMN 2
35 OB
E 3
34 OC
RFSUMP
33 OD
F 4
32 VDDA4
VDDA1 5
VSSA1 6
31 VSSA4
TZA1035HL
DVDMI 7
30 S1
A 8
29 S2
2003 Jun 03
8
n.c. 24
COO 22
Fig.2 Pin configuration.
VDDD5 23
COP 20
COM 21
VSSD 19
25 FTC
SILD 18
OPUREF 12
SICL 17
26 TDO
SIDA 16
D 11
TM 14
27 FTCREF
VDDD3 15
28 OCENTRAL
n.c. 13
B 9
C 10
MGW551
Philips Semiconductors
Preliminary specification
High speed advanced analog DVD signal
processor and laser supply
7
7.1
When it is not possible to have a DC connection between
the TZA1035HL and the decoder, the signals on servo
outputs OA to OD can be used as they contain the same
LP-filtered and DC coupled information.
FUNCTIONAL DESCRIPTION
RF data processing
The RF data path is a fully DC-coupled, multi-stage
amplifier (see Fig.3). The input signal for data can be
selected from RF inputs A to D or from the summed
RF inputs RFSUMP and RFSUMN. Switching between the
two sets of signals is performed by an internal multiplexer.
The signals are fully balanced internally to improve signal
quality and reduce power supply interference.
Summing of the photodiode signals A to D is performed in
the second amplifier stage G2. Each individual diode
channel can be switched on, off or inverted with switches
SW-A to SW-D.
Switching between photodiode signals and RFSUM input
is performed immediately before the third amplifier
stage G3. This stage has a variable gain with fine
resolution to allow automatic gain adjustment to be
controlled by the decoder.
RF outputs RFP and RFN can be DC coupled to the
Analog-to-Digital Converter (ADC) of the decoder.
The RF input signals are from photodiodes and have
a large DC content by nature. This DC component must be
removed from the signals for good system performance.
Built-in DACs, located after the input stages
G1 and RFSUM, have the ability to do this. The DAC range
and resolution is scaled with the gain setting of the first
amplifier stage. When the DC content is removed, the
RF signal can be DC coupled to the decoder. The main
advantage of DC coupling is fast recovery from signal
swings due to disc defects since there is no AC coupling
capacitance to slow the recovery. When using DC
coupling, both AC and DC content in the data signal is
known. The Philips Iguana decoders have on-chip control
loops to support Automatic Gain Control (AGC) and DC
cancellation.
The filter stage limits the bandwidth according to the
maximum playback speed of the disc. This is to optimize
the noise performance. The filter stage consists of an
equalizer and a noise filter, both of which can be
bypassed, also the boost factor of the equalizer can be set.
The corner frequencies of the equalizer and noise filter are
equal and can be programmed to a 7-bit resolution.
The RF output signals RFP and RFN can be DC coupled
to a decoder with a differential input pair (as with Philips
Iguana decoders). The common mode output voltage can
be set externally at pin RFREF.
The signals for differential phase detection are tapped
from the inputs A to D at the RF amplifier G1 stages.
DC cancellation for the A to D and RFSUM signal paths
can be set independently or simultaneously.
Two separate DACs are available for cases where the left
and right side DC conditions can be different.
2003 Jun 03
TZA1035HL
9
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2
RFOFFSS
12
OPUREF
A
SW-A
8
G1
39
G3
NOISE
FILTER
EQUALIZER
DPD-A
40
RFP
RFN
RF
outputs
RFOFFSL
SW-B
10
B
9
TZA1035HL
G1
DPD-B
RF
inputs
SW-C
C
10
G1
G2
DPD
DPD-A
DPD-C
RFOFFSR
Philips Semiconductors
38
RFSUM
1
High speed advanced analog DVD signal
processor and laser supply
handbook, full pagewidth
2003 Jun 03
RFSUMP
RFSUMN
RFREF
30
DPD-D
FILTER
DOC
DPD-C
29
S1
S2
servo
radial
outputs
DPD-B
SW-D
11
central aperture signal
G1
DPD-D
Fig.3 RF data and DPD processing.
TZA1035HL
MCE105
Preliminary specification
D
Philips Semiconductors
Preliminary specification
High speed advanced analog DVD signal
processor and laser supply
7.2
TZA1035HL
Servo signal processing
The photodiode configurations and naming conventions
are shown in Figs 4 and 5.
left
handbook, halfpage
7.2.1
SERVO SIGNAL PATH SET-UP
tangential direction
A block diagram of the servo signal path is shown in Fig.6.
In general, the servo signal path comprises:
right
• A voltage-to-current converter with programmable offset
voltage source VLFOFFS that is common to all inputs
A
B C
D
MGW554
• A 4-bit DAC for each of the six channels to compensate
for offset per channel
• A variable gain stage to adapt the signal level to the
specific pick-up and disc properties
Data = A + B + C + D
Push-pull = A − D
Focus = C − B
DPD2 = phase (A, D)
DPD4 not applicable
• Low-pass filtering and output stage for the photodiode
current signals
• Error output stage in the radial data path for fast track
counting.
Fig.5 Foucault diode configuration.
Servo output signals OA to OD, S1 and S2 are unipolar
current signals which represent the low-pass filtered
photodiode signals. In DPD radial tracking, the S1 and S2
signals are the equivalent of the satellite signals commonly
found in traditional CD systems.
7.2.2
Focus information is reflected in the four outputs
OA to OD. Gain and offset can be programmed.
The servo output signals OA to OD, S1 and S2 are set to
3-state if bit RFonly = 1 (register 13, bit 11).
handbook, halfpage
A
B
FOCUS SERVO
For optical pick-ups where only channels B and C are
used for focus, channels A and D can be switched off
(bit Focus_mode = 0).
For initial alignment, a copy of the output currents can be
made available on pin OCENTRAL.
left
tangential direction
7.2.3
D
C
Radial information can be obtained from the two output
signals S1 and S2, and the gain and offset can be
programmed. The TZA1035HL provides differential phase
detection, push-pull and three-beam push-pull for radial
tracking. The signal FTC is made available for fast track
counting and is primarily the voltage error signal derived
from signals S1 or S2.
MGW553
Data = A + B + C + D
Push-pull = (A + B) − (C + D)
Focus = (A + C) − (B + D)
DPD2 = phase (A + B, C + D)
DPD4 = phase (A,D) + phase (C,B)
The polarity of the radial loop can be reversed via the serial
control bus (RAD_pol).
Fig.4 Astigmatic diode configuration.
2003 Jun 03
RADIAL SERVO
right
11
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FTC
DPD
A
8
V
/I
14k
α
COFFSA
B
9
V
/I
10
V
RF
inputs
/I
12
11
V
/I
14k
2− α
3
V
/I
4
V
/I
S1
S2
CA
14k
36
GLFC
OA
30k
14k
35
GLFC
OB
servo
focus
outputs
15k
34
GLFC
ROFFSE
F
29
GLFR
30k
COFFSD
E
30
30k
COFFSC
D
MUX
SWAP
GLFR
FTCREF
servo
radial
outputs
COFFSB
C
27
MUX
26k
Philips Semiconductors
25
High speed advanced analog DVD signal
processor and laser supply
handbook, full pagewidth
2003 Jun 03
FTC
OC
15k
33
GLFC
OD
ROFFSF
FOFFS
OCENTRAL
28
LFOFFS
MCE106
Fig.6 Servo signal path.
OCENTRAL
TZA1035HL
OPUREF
TZA1035HL
Preliminary specification
VLFOFFS
12
Philips Semiconductors
Preliminary specification
High speed advanced analog DVD signal
processor and laser supply
7.2.4
DIFFERENTIAL PHASE DETECTION
in a three-spot optical system with Three-Beam Push-Pull
(TBPP). The built-in multiplexer gives a flexible method of
dealing with many detector arrangements. For push-pull,
the input signals are taken from channels A to D. There is
also a command that switches off channels B and C,
leaving channels A and D for push-pull
(bits RT_mode[2:0]).
The TZA1035HL provides differential phase detection to
support DVD in various ways:
• DPD2 with four channels programmed to be active gives
DPD as required in the standard specification
• Two of the four channels can be excluded from the DPD
for pick-ups with an alternative photodiode arrangement
For TBPP, the input signal is taken from channels E and F,
irrespective of bit RFSUM setting.
• An increase in performance, dedicated for DVD+RW,
can be obtained by using the DPD4 method. Then two
truly separated phase detectors are active. After the
phase detection of the two input pairs the result is
summed.
7.2.4.3
S1 = ALFR × α × input left
S2 = ALFR × (2 − α) × input right.
Factor α can be programmed in a range from 0.6 to 1.35,
with 1.0 as the balanced condition (bits α[3:0]).
The DPD signal is low-pass filtered by two internal
capacitors. The signal is then fed to pins S1 and S2, or
directed via the drop-out concealment circuit to the outputs
(see Section 7.5).
7.2.4.4
Drop-out concealment
• A coarse DAC, common to all the input channels, adds
an offset that shifts the input signals in positive direction
until all inputs are ≥0. The DAC used (LFOFFS) has a
2-bit resolution (bits LFOFF[1:0]).
When the drop-out concealment function is enabled
(bit DOCEN = 1), a portion of the Central Aperture (CA)
signal is added to S1 and S2. Also, when the CA signal
drops below the DOC threshold, the DPD signal is
gradually attenuated.
• A fine setting per channel is provided to cancel the
remainder of the offset between the channels. This is
achieved by DACs subtracting the DC component from
the signals and bringing the inputs to approximately zero
offset (within ≈ 1 mV). The DACs (registers 11 to 13)
have a 4-bit resolution.
The DPD detection cannot work properly when the input
signal becomes very small. The output of the DPD may
then show a significant offset. The DOC may not conceal
this offset completely because:
The range of both DACs can be increased by a factor of
three to compensate for higher offset values by means of
control parameter bit SERVOOS.
• DOC is gradually controlled from the CA signal
With a switched-off laser, the result of the offset
cancellation can be observed at each corresponding
output pin, OA to OD, S1 and S2, or via a built-in
multiplexer to pin OCENTRAL (central channels only).
See registers 11 to 13 for DAC and multiplexer control.
• The CA signal may not become 0 during disc-defect.
For details see Section 7.5.5.2
Push-pull and three-beam push-pull
The TZA1035HL can also provide radial information by
means of push-pull signals (from the photodiode inputs) or
2003 Jun 03
Offset compensation
A provision is made to compensate electrical offset from a
light pen. The offset voltage from the light pen can be
positive or negative. In general, the offset between any two
channels is smaller than the absolute offsets. As negative
input signals cannot be handled by the TZA1035HL
internal servo channels, a two-step approach is adopted:
A special function is built in for compatibility with drop-out
detection strategies, based on level detection in the
S1 and S2 signals. When using DPD in a fundamental
way, there is no representation of mirror level information
from the light pen.
7.2.4.2
Enhanced push-pull (dynamic offset
compensation for beam landing)
This option cancels offsets due to beam landing. A factor α
can be programmed to re-balance the signal gain between
channels S1 and S2. In a simplified form this can be
described as:
Input signals for DPD are taken from input pins A to D after
the first gain stage G1 (see Fig.3). Pre-emphasis is applied
by means of a programmable lead/lag filter. Additionally, a
programmable low-pass filter is available to improve the
signal quality under noisy signal conditions at lower
speeds. For further signal improvements the DPD pulse
stretcher can be programmed to higher values at lower
speeds.
7.2.4.1
TZA1035HL
13
Philips Semiconductors
Preliminary specification
High speed advanced analog DVD signal
processor and laser supply
7.2.5
7.2.7
AUTOMATIC DUAL LASER SUPPLY
7.2.7.1
The TZA1035HL can control the output power of two
lasers; it has an Automatic Laser Power Control (ALPC)
that stabilizes the laser output power and compensates
the effects of temperature and ageing of the laser.
Software compatibility
Other conditions or restrictions are:
• Register bits of the TZA1035HL which were not defined
are programmed to a logic 0. Registers 9, 10, 14 and 15
may be left undefined
A protection circuit is included to prevent laser damage
due to dips in laser supply voltage VDDL. If a supply voltage
dip occurs, the output can saturate and restrict the
required laser current. Without the protection circuit, the
ALPC would try to maximize the output power with
destructive results for the laser when the supply voltage
recovers. The protection circuit monitors the supply
voltage and shuts off the laser when the voltage drops
below a safe value. The ALPC recovers automatically after
the dip has passed.
• The G4 stage high gain setting of the TZA1033HL/V1 is
not available in the TZA1035HL; if this value was set to
logic 0, there will be no difference
• When bit K2_Mode = 0 the RF bandwidth will be fixed to
the minimum value of 10 MHz (typical); bit K2_Mode = 1
to select a higher bandwidth; the bandwidth is now lower
than using a TZA1033HL/V1.
7.2.7.2
Only one laser can be activated at the same time.
An internal break-before-make circuit ensures safe
start-up for the laser when a toggle situation between the
two lasers is detected. When both lasers are programmed
on, neither laser will be activated.
Hardware compatibility
The package is changed from LQFP64 for the TZA1033HL
to LQFP48 for the TZA1035HL.
The hardware differences are:
• Input pins STB, HEADER and LAND of the TZA1033HL
are not present
POWER-ON RESET AND GENERAL POWER ON
• Input pins CD of TZA1033HL/V1 are not used;
TZA1035HL has RFSUM inputs instead; the RFSUM
inputs of TZA1035HL may be connected to ground
when not used.
When the supply voltage is switched on, bit PWRON is
reset by the Power-On Reset (POR) signal. This
concludes in a STANDBY mode at power up. POR is
intended to prevent the lasers being damaged due to
random settings. All other functions may be switched when
power is on. The TZA1035HL becomes active when
bit PWRON = 1.
2003 Jun 03
COMPATIBILITY WITH TZA1033HL/V1
The TZA1035HL is highly software compatible with the
TZA1033HL/V1. Provided that some conditions are met,
the software the TZA1035HL can be used as a successor
with just minor modifications. This compatibility is
achieved with the implementation of the TZA1035HL
mode control bit (bit K2_Mode). When bit K2_Mode = 0,
the TZA1035HL will act as a TZA1033HL/V1. When
bit K2_Mode = 1, the TZA1035HL will act as a
TZA1033HL/K2 and the new functions will be available
(but require a software update).
ALPC automatically detects if there is a P-type or N-type
monitor diode in use in either of the laser circuits. The
regulation loop formed by the ALPC, the laser, the monitor
diode and the associated adjustment resistor will settle at
the monitor input voltage. The monitor input voltage can be
programmed to HIGH (≈ 180 mV) or LOW (≈ 150 mV),
according to frequently-used pre-adjustments of the light
pen. This set point can be set independently for both
ALPCs. Bandwidth limitation and smooth switch-on
behaviour is realized using an internal capacitor.
7.2.6
TZA1035HL
14
Philips Semiconductors
Preliminary specification
High speed advanced analog DVD signal
processor and laser supply
7.2.8
INTERFACE TO THE SYSTEM CONTROLLER
TZA1035HL
should go uniquely with the SILD signal. When
SILD = HIGH, the TZA1035HL will not respond to any
signal on SIDA or SICL.
Programming the registers of TZA1035HL is done via a
serial bus (see Fig.7). The circuitry is formed by a serial
input shift register and a number of registers that store the
data. The registers can always be programmed,
irrespective of STANDBY mode.
During a transmission, the serial data is first stored in an
input shift register. At the rising edge of SILD, the content
of the input register is copied into the addressed register.
This is also the moment the programmed information
becomes effective.
If required, the bus lines can be connected in parallel with
an I2C-bus. The protocol needs no switching of the data
line during SICL = HIGH. This means that other I2C-bus
devices will not recognise any START or STOP
commands. Control words addressed to TZA1035HL
The input pins have CMOS compatible threshold levels for
both 3.3 and 5 V supplies.
handbook, full pagewidth
SICL
SIDA
D0 D1 D2 D3 D4 D5 D6 D7 D8 D9 D10 D11 A0 A1 A2 A3
D0 D1 D2 D3 D4
A1 A2 A3
t load(H)
SILD
MGW496
Fig.7 Two word transmission.
7.3
Control registers
The TZA1035HL is controlled by serial registers. To keep programming fast and efficient, the control bits are sent in 16-bit
words. Four bits of the word are used for the address and for each address there are 12 data bits.
Table 1
Overview of control parameters
SYMBOL
PARAMETER
VALUES
REGISTER
BITS
Data path
G1 (A1)
gain of first RF amplifier stage
(or linear amplification)
0, 6 and 12 dB (1×, 2× and 4×)
3
11 and 10
G2 (A2)
gain of second RF amplifier
stage (or linear amplification)
6, 12, 18 and 24 dB (2×, 4×, 8× and 16×)
3
9 and 8
G3 (A3)
gain of third RF amplifier
stage (or linear amplification)
0 to 13 dB in steps of 0.8 dB (1× to 4×)
3
7 to 4
GRFSUM
(ARFSUM)
gain of RFSUM input stage (or −6, 0, 6, 12 and 18 dB
linear amplification)
(0.5×, 1×, 2×, 4× and 8×)
0
7 to 5
BWRF
bandwidth limitation in
RF path
14
6 to 0
2003 Jun 03
f0(RF) = 12 to 145 MHz
15
Philips Semiconductors
Preliminary specification
High speed advanced analog DVD signal
processor and laser supply
SYMBOL
RFOFFSL
PARAMETER
DC offset compensation in left
RF input path
TZA1035HL
VALUES
RFSUM = 0; full range depends on
G1 setting:
REGISTER
BITS
4
11 to 6
4
5 to 0
4 or 5
5 to 0
11
11 and 10
G1 = 0 dB: 0 to 450 mV in 7.1 mV steps
G1 = 6 dB: 0 to 225 mV in 3.6 mV steps
G1 = 12 dB: 0 to 120 mV in 1.9 mV steps
RFOFFSR
DC offset compensation in
right RF input path
RFSUM = 0; full range depends on
G1 setting:
G1 = 0 dB: 0 to 450 mV in 7.1 mV steps
G1 = 6 dB: 0 to 225 mV in 3.6 mV steps
G1 = 12 dB: 0 to 120 mV in 1.9 mV steps
RFOFFSS
DC offset compensation in
RFSUM path
RFSUM = 1; full range depends on
GRFSUM setting:
GRFSUM = −6 dB; 0 to 1700 mV
GRFSUM = 0 dB; 0 to 850 mV
GRFSUM = 6 dB; 0 to 425 mV
GRFSUM = 12 dB; 0 to 210 mV
GRFSUM = 18 dB; 0 to 105 mV
Servo radial path
DC offset compensation for
LF path (common for all servo
inputs)
SERVOOS = 0:
VLFOFFS = 0, 5, 10 or 15 mV
RLFR
CD satellite path input
transresistance
15 kΩ fixed
−
−
RLFPP
DVD push-pull signal
transresistance
30 kΩ fixed
−
−
ROFFSE
DC offset compensation for
radial servo path (input E)
SERVOOS = 0: VROFFSE = 0 to 20 mV
11
7 to 4
11
3 to 0
LFOFFS
SERVOOS = 1:
VLFOFFS = 0, 15, 30 or 45 mV
SERVOOS = 1: VROFFSE = 0 to 60 mV
ROFFSF
DC offset compensation for
radial servo path (input F)
α
dynamic radial offset
compensation factor
α = 0.6 to 1.35 in 15 steps of 0.05
6
3 to 0
I(FS)(DPD),
I(FS)(DPD)(DOC)
full scale DPD current, fixed
value based on bandgap
voltage across external
resistor
DOCEN = 0: fixed value = 20 µA
1
5
IREFRAD(CM)
internally generated common
mode DC reference current in
DPD mode
3.5 µA fixed
−
−
fstart_DPD
start frequency lead/lag filter
of DPD block
fstart_DPD = 1, 5 or 10 MHz
(TZA1033HL/V1 compatible)
7
1 and 0
fstart_DPD = 1, 5, 10, 18 or 24 MHz
15
5 to 3
2003 Jun 03
SERVOOS = 0: VROFFSF = 0 to 20 mV
SERVOOS = 1: VROFFSF = 0 to 60 mV
DOCEN = 1: fixed value = 6.6 µA
16
Philips Semiconductors
Preliminary specification
High speed advanced analog DVD signal
processor and laser supply
SYMBOL
PARAMETER
TZA1035HL
VALUES
REGISTER
BITS
6
11 to 8
GLFR (ALFR)
low frequency gain, radial path −15 to +9 dB in steps of 3 dB
output stage (or linear
(0.18× to 2.8×)
amplification)
RFTC
gain of fast track count output
680 kΩ ±20% fixed for ±2 V (p-p)
−
−
RLFC
LF path input transresistance
14 kΩ fixed
−
−
COFFSA
DC offset compensation for
central servo path A
SERVOOS = 0: 0 to 20 mV
12
7 to 4
COFFSB
DC offset compensation for
central servo path B
SERVOOS = 0: 0 to 20 mV
12
3 to 0
COFFSC
DC offset compensation for
central servo path C
SERVOOS = 0: 0 to 20 mV
13
7 to 4
DC offset compensation for
central servo path D
SERVOOS = 0: 0 to 20 mV
13
3 to 0
GLFC (ALFC)
low frequency gain, central
path output stage (or linear
amplification)
−15 to +9 dB in steps of 3 dB
(0.18× to 2.8×)
6
7 to 4
β
focus offset compensation
β = 0 to 31⁄32
2
4 to 0
FOFFSEN
full range offset compensation DAC enabled: IFOFFS = 400 nA (fixed)
for focus
DAC disabled: IFOFFS = 0 nA
2
10
Servo focus path
COFFSD
7.3.1
SERVOOS = 1: 0 to 60 mV
SERVOOS = 1: 0 to 60 mV
SERVOOS = 1: 0 to 60 mV
SERVOOS = 1: 0 to 60 mV
REGISTER 0: POWER CONTROL
Table 2
Register address 0H
BIT
15
14
13
12
11
10
9
8
SYMBOL
AD3
AD2
AD1
AD0
−
−
−
−
BIT
7
6
5
4
3
2
1
0
SYMBOL
GRF
SUM2
GRF
SUM1
GRF
SUM0
DVD_ MILVL
CD_MILVL
DVD_ LDON
CD_LDON
PWRON
Table 3
Description of register bits (address 0H)
BIT
SYMBOL
FUNCTION
15 to 12
AD[3:0]
0000 = address 0H
11 to 8
−
not used
7 to 5
GRFSUM[2:0]
Gain of RFSUM input stage.
000 = −6 dB
001 = 0 dB
010 = 6 dB
011 = 12 dB
100 = 18 dB
4
2003 Jun 03
DVD_MILVL
DVD monitor input level. 0 = 150 mV; 1 = 180 mV.
17
Philips Semiconductors
Preliminary specification
High speed advanced analog DVD signal
processor and laser supply
BIT
TZA1035HL
SYMBOL
FUNCTION
3
CD_MILVL
CD monitor input level. 0 = 150 mV; 1 = 180 mV.
2
DVD_LDON
DVD laser on. 0 = laser off; 1 = laser on.
1
CD_LDON
CD laser on. 0 = laser off; 1 = laser on.
0
PWRON
Power on. 0 = STANDBY mode; 1 = power on.
7.3.2
REGISTER 1: SERVO AND RF MODES
Table 4
Register address 1H
BIT
15
14
13
12
11
10
9
8
SYMBOL
AD3
AD2
AD1
AD0
DPD_DCC
−
−
RAD_pol
BIT
7
6
5
4
3
2
1
0
−
−
DOCEN
Focus_
mode
RT_mode2
RT_mode1
RT_mode0
RFSUM
SYMBOL
Table 5
Description of register bits (address 1H)
BIT
15 to 12
11
SYMBOL
FUNCTION
AD[3:0]
0001 = address 1H
DPD_DCC
RF offset DAC for DPD signal control. 0 = DAC controlled by register 4,
bits RFOFFSL[5:0]; 1 = DAC controlled by register 5, bits RFOFFSS[5:0].
−
not used
RAD_pol
Radial polarity switch. 0 = inverse; 1 = normal (default).
−
not used
5
DOCEN
Drop-out concealment enable. 0 = disable; 1 = enable.
4
Focus_mode
Focus mode. 0 = two-channel focus (channels B and C only); 1 = four-channel
focus.
3 to 1
RT_mode[2:0]
Radial tracking mode.
10 and 9
8
7 and 6
000 = DPD2; DPD = phase (A,D)
001 = push-pull; channels A,D only
100 = DPD2; DPD = phase (A + C, B + D)
101 = push-pull; four channels
110 = DPD4; DPD = phase (A,D) + phase (C,B)
X11 = TBPP channels E and F
0
2003 Jun 03
RFSUM
RF channel selection. 0 = diode inputs selected; 1 = RFSUM input selected.
18
Philips Semiconductors
Preliminary specification
High speed advanced analog DVD signal
processor and laser supply
7.3.3
TZA1035HL
REGISTER 2: FOCUS OFFSET DAC
Table 6
Register address 2H
BIT
15
14
13
12
11
10
9
8
SYMBOL
AD3
AD2
AD1
AD0
K2_Mode
FOFFSEN
β4
β3
BIT
7
6
5
4
3
2
1
0
SYMBOL
β2
β1
β0
−
−
−
−
−
Table 7
Description of register bits (address 2H)
BIT
SYMBOL
15 to 12
11
FUNCTION
AD[3:0]
0010 = address 2H
K2_Mode
K2 mode. 0 = disable; 1 = enable.
FOFFSEN
Focus offset enable. 0 = enable; 1 = disable.
9 to 5
β[4:0]
Focus offset compensation. 00000 to 11111: β = 0 to β = 31⁄32.
4 to 0
−
not used
10
7.3.4
REGISTER 3: RF PATH GAIN
Table 8
Register address 3H
BIT
15
14
13
12
11
10
9
8
SYMBOL
AD3
AD2
AD1
AD0
G11
G10
G21
G20
BIT
7
6
5
4
3
2
1
0
SYMBOL
G33
G32
G31
G30
−
−
−
−
Table 9
Description of register bits (address 3H)
BIT
15 to 12
SYMBOL
AD[3:0]
11 and 10 G1[1:0]
FUNCTION
0011 = address 3H
First RF amplifier stage gain.
00 = 0 dB
01 = 6 dB
10 = 12 dB
11 = not used
9 and 8
G2[1:0]
Second RF amplifier stage gain.
00 = 6 dB
01 = 12 dB
10 = 18 dB
11 = 24 dB
7 to 4
G3[3:0]
Third RF amplifier stage gain. 0000 to 1111: 0 to 13 dB in 0.8 dB steps.
3 to 0
−
not used
2003 Jun 03
19
Philips Semiconductors
Preliminary specification
High speed advanced analog DVD signal
processor and laser supply
7.3.5
TZA1035HL
REGISTER 4: RF LEFT AND RIGHT, OR SUM OFFSET COMPENSATION
Table 10 Register address 4H
BIT
15
14
13
12
11
10
9
8
SYMBOL
AD3
AD2
AD1
AD0
RFOFFSL5
RFOFFSL4
RFOFFSL3
RFOFFSL2
BIT
7
6
5
4
3
2
1
0
RFOFFSR5/
RFOFFSS5
RFOFFSR4/
RFOFFSS4
RFOFFSR3/
RFOFFSS3
RFOFFSR2/
RFOFFSS2
RFOFFSR1/
RFOFFSS1
RFOFFSR0/
RFOFFSS0
SYMBOL
RFOFFSL1 RFOFFSL0
Table 11 Description of register bits (address 4H)
BIT
SYMBOL
FUNCTION
15 to 12
AD[3:0]
0100 = address 4H
11 to 6
RFOFFSL[5:0]
Left channel RF offset compensation definition.
bit RFSUM = 0: left RF channel offset compensation value
bit RFSUM = 1: not used
5 to 0
RFOFFSR[5:0]
Right channel RF offset compensation definition.
bit RFSUM = 0: right RF channel offset compensation value (symbol is RFOFFSR)
bit RFSUM = 1 and bit DPD_DCC = 1: not used
bit RFSUM = 1 and bit DPD_DCC = 0: the decoder controls DPD and RFSUM
channels automatically, in parallel and with same values (symbol is RFOFFSS).
7.3.6
REGISTER 5: RF SUM OFFSET COMPENSATION
Table 12 Register address 5H
BIT
15
14
13
12
11
10
9
8
SYMBOL
AD3
AD2
AD1
AD0
−
−
−
−
BIT
7
6
5
4
3
2
1
0
SYMBOL
−
−
RFOFFSS5
RFOFFSS4
RFOFFSS3
RFOFFSS2
RFOFFSS1
RFOFFSS0
Table 13 Description of register bits (address 5H)
BIT
SYMBOL
FUNCTION
15 to 12
AD[3:0]
0101 = address 5H
11 to 6
−
not used
5 to 0
RFOFFSS[5:0]
RF offset compensation definition
bit RFSUM = 0: not used
bit RFSUM = 1 and bit DPD_DCC = 0: not used
bit RFSUM = 1 and bit DPD_DCC = 1: the decoder controls RFSUM channels;
the DPD channels can be set independently from the microprocessor.
2003 Jun 03
20
Philips Semiconductors
Preliminary specification
High speed advanced analog DVD signal
processor and laser supply
7.3.7
TZA1035HL
REGISTER 6: SERVO GAIN AND DYNAMIC RADIAL OFFSET COMPENSATION FACTOR
Table 14 Register address 6H
BIT
15
14
13
12
11
10
9
8
SYMBOL
AD3
AD2
AD1
AD0
GLFR3
GLFR2
GLFR1
GLFR0
BIT
7
6
5
4
3
2
1
0
SYMBOL
GLFC3
GLFC2
GLFC1
GLFC0
α3
α2
α1
α0
Table 15 Description of register bits (address 6H)
BIT
SYMBOL
FUNCTION
15 to 12
AD[3:0]
0110 = address 6H
11 to 8
GLFR[3:0]
Low frequency gain, radial path output stage. 0000 to 1000: −15 to +9 dB
in 3 dB steps.
7 to 4
GLFC[3:0]
Low frequency gain, central path output stage. 0000 to 1000: −15 to +9 dB
in 3 dB steps.
3 to 0
α[3:0]
Dynamic radial offset compensation factor. 0000 to 1111: 0.60 to 1.35
in 0.05 steps; 1000 = balanced value (default).
7.3.8
REGISTER 7: SERVO PATH GAIN AND BANDWIDTH AND RF PATH BANDWIDTH AND PRE-EMPHASIS
Definitions in register 7 are intended mainly for software compatibility with the TZA1033HL/V1. New features that require
more bit-space to program are moved to registers 14 and 15. Only DPD stretch remains programmed in register 7. Some
parameters are slightly modified.
Table 16 Register address 7H
BIT
15
14
13
12
11
10
9
8
AD3
AD2
AD1
AD0
DPDLPF1
DPDLPF0
DPD_
stretch2
DPD_
stretch1
BIT
7
6
5
4
3
2
1
0
SYMBOL
DPD_
stretch0
EQRF2
EQRF1
EQRF0
fstart_DPD1
fstart_DPD0
SYMBOL
DPD_
DVDALAS_
testmode
mode
Table 17 Description of register bits (address 7H)
FUNCTION
BIT
SYMBOL
K2_Mode = 0
15 to 12
AD[3:0]
11 and 10 DPDLPF[1:0]
0111 = address 7H
0111 = address 7H
DPD low-pass filter.
not applicable
0X : B−3db = 50 MHz (equivalent to TZA1023)
1X : B−3db = 10 MHz
2003 Jun 03
K2_Mode = 1
21
Philips Semiconductors
Preliminary specification
High speed advanced analog DVD signal
processor and laser supply
TZA1035HL
FUNCTION
BIT
SYMBOL
K2_Mode = 0
9 to 7
DPD_stretch [2:0]
K2_Mode = 1
DPD pulse stretcher (tP).
DPD pulse stretcher (tP).
000 = 1.9 ns
000 = 30 ns
001 = 3.8 ns (equivalent to TZA1023)
001 = 15 ns
010 = 7.5 ns
010 = 7.5 ns
011 = 15 ns
011 = 3.8 ns
100 = 30 ns
100 = 1.9 ns
101 = not used
101 = 1.2 ns
6
DPD_ testmode
For factory test purposes only.
For factory test
purposes only.
5
DVDALAS_ mode
DVDALAS mode bit. 0 = disables control of
bits 11 to 6 and creates behaviour equivalent to
TZA1023; 1 = enables DPD low-pass filter and time
stretcher equivalent to TZA1033HL/V1.
not applicable
EQRF[2:0]
RF channel low-pass filter (BRF). 001 = 10 MHz
not applicable
fstart_DPD[1:0]
Start frequency lead/lag filter, DPD block.
not applicable
4 to 2
1 and 0
00 = 1 MHz
01 = 5 MHz
10 = 10 MHz
11 = not used
7.3.9
REGISTER 8: RF CHANNEL SELECTION
Table 18 Register address 8H
BIT
15
14
13
12
11
10
9
8
SYMBOL
AD3
AD2
AD1
AD0
−
−
−
−
BIT
7
6
5
4
3
2
1
0
SW-Cmute
SW-Cinv
SW-Bmute
SW-Binv
SW-Amute
SW-Ainv
SYMBOL SW-Dmute SW-Dinv
Table 19 Description of register bits (address 8H)
BIT
SYMBOL
FUNCTION
15 to 12
AD[3:0]
1000 = address 8H.
11 to 8
−
not used
7
SW-Dmute
0 = pass D signal; 1 = mute D signal.
6
SW-Dinv
0 = pass D signal with no inversion; 1 = pass D signal with inversion.
5
SW-Cmute
0 = pass C signal; 1 = mute C signal.
4
SW-Cinv
0 = pass C signal with no inversion; 1 = pass C signal with inversion.
3
SW-Bmute
0 = pass B signal; 1 = mute B signal.
2003 Jun 03
22
Philips Semiconductors
Preliminary specification
High speed advanced analog DVD signal
processor and laser supply
BIT
TZA1035HL
SYMBOL
FUNCTION
2
SW-Binv
0 = pass B signal with no inversion; 1 = pass B signal with inversion.
1
SW-Amute
0 = pass A signal; 1 = mute A signal.
0
SW-Ainv
0 = pass A signal with no inversion; 1 = pass A signal with inversion.
7.3.10
REGISTER 11: RADIAL SERVO OFFSET CANCELLATION
Table 20 Register address BH
BIT
15
14
13
12
11
10
9
8
SYMBOL
AD3
AD2
AD1
AD0
LFOFFS1
LFOFFS0
SERVOOS
FTCHBW
BIT
7
6
5
4
3
2
1
0
SYMBOL
ROFFSE3
ROFFSE2
ROFFSE1
ROFFSE0
ROFFSF3
ROFFSF2
ROFFSF1
ROFFSF0
Table 21 Description of register bits (address BH)
BIT
SYMBOL
15 to 12
AD[3:0]
FUNCTION
1011 = address BH
11 and 10 LFOFFS[1:0]
DC offset compensation for LF path (VLFOFFS). Common for all servo inputs:
SERVOOS = 0
SERVOOS = 1
00 = 0 mV
00 = 0 mV
01 = 5 mV
01 = 15 mV
10 = 10 mV
10 = 30 mV
11 = 15 mV
11 = 45 mV
9
SERVOOS
Servo offset scale (DACs ROFFSx, COFFSx and LFOFFS). 0 = normal range;
1 = triple range.
8
FTCHBW
FTC bandwidth. 0 = 600 kHz (approximately); 1 = 1.2 MHz (approximately.)
7 to 4
ROFFSE[3:0]
Programmable DC offset compensation for radial servo path (E input).
SERVOOS = 0: 0 to 20 mV; bit SERVOOS = 1: 0 to 60 mV.
3 to 0
ROFFSF[3:0]
Programmable DC offset compensation for radial servo path (F input).
SERVOOS = 0: 0 to 20 mV; bit SERVOOS = 1: 0 to 60 mV.
7.3.11
REGISTER 12: CENTRAL SERVO OFFSET CANCELLATION INPUTS A AND B
Table 22 Register address CH
BIT
15
14
13
12
D11
D10
D9
D8
SYMBOL
AD3
AD2
AD1
AD0
TSTDPDRF
TSTSRV2
TSTSRV1
TSTSRV0
BIT
D7
D6
D5
D4
D3
D2
D1
D0
SYMBOL
COFFSA3
COFFSA2
COFFSA1
COFFSA0
COFFSB3
COFFSB2
COFFSB1
COFFSB0
2003 Jun 03
23
Philips Semiconductors
Preliminary specification
High speed advanced analog DVD signal
processor and laser supply
TZA1035HL
Table 23 Description of register bits (address CH)
BIT
SYMBOL
15 to 12
FUNCTION
AD[3:0]
1100 = address CH
11
TSTDPDRF
DPD RF test bit. With this bit the DPD filter performance is checked. 0 = normal
operation; 1 = RF signal filtered by the DPD block is connected to the RF output.
10 to 8
TSTSRV[2:0]
Test matrix for servo signals to pin OCENTRAL.
000 = normal operation
001 = filter DAC current for test purposes
011 = CA (sum A to D)
100 = channel A
101 = channel B
110 = channel C
111 = channel D
7 to 4
COFFSA[3:0]
Central servo input A offset cancellation. Bit SERVOOS = 0: 0 to 20 mV;
bit SERVOOS = 1: 0 to 60 mV.
3 to 0
COFFSB[3:0]
Central servo input B offset cancellation. Bit SERVOOS = 0: 0 to 20 mV;
bit SERVOOS = 1: 0 to 60 mV.
7.3.12
REGISTER 13: CENTRAL SERVO OFFSET CANCELLATION INPUTS C AND D
Table 24 Register address DH
BIT
15
14
13
12
11
10
9
8
SYMBOL
AD3
AD2
AD1
AD0
RFonly
−
−
−
BIT
7
6
5
4
3
2
1
0
SYMBOL
COFFSC3
COFFSC2
COFFSC1
COFFSC0
COFFSC3
COFFSC2
COFFSC1
COFFSC0
Table 25 Description of register bits (address DH)
BIT
SYMBOL
FUNCTION
15 to 12
AD[3:0]
1101 = address DH
11
RFonly
Operation mode. 0 = normal operation; 1 = RF only mode (servo outputs
OA to OD, S1 and S2 are 3-state).
10 to 8
−
not used
7 to 4
COFFSC[3:0]
Central servo input C offset cancellation. Bit SERVOOS = 0: 0 to 20 mV;
bit SERVOOS = 1: 0 to 60 mV.
3 to 0
COFFSD[3:0]
Central servo input D offset cancellation. Bit SERVOOS = 0: 0 to 20 mV;
bit SERVOOS = 1: 0 to 60 mV.
2003 Jun 03
24
Philips Semiconductors
Preliminary specification
High speed advanced analog DVD signal
processor and laser supply
7.3.13
TZA1035HL
REGISTER 14: RF FILTER SETTINGS
Table 26 Register address EH
BIT
15
14
13
12
11
10
9
8
SYMBOL
AD3
AD2
AD1
AD0
−
−
RFNFEN
RFEQEN
BIT
7
6
5
4
3
2
1
0
SYMBOL
RFKEQ
BWRF6
BWRF5
BWRF4
BWRF3
BWRF2
BWRF1
BWRF0
Table 27 Description of register bits (address EH); bit K2_Mode = 1
BIT
SYMBOL
15 to 12
FUNCTION
AD[3:0]
1110 = address EH
11 and 10 −
not used
9
RFNFEN
Noise filter enable. 0 = disable; 1 = enable.
8
RFEQEN
Equalizer enable. 0 = disable; 1 = enable.
7
RFKEQ
Boost factor. 0 = boost factor low; 1 = boost factor high.
BWRF[6:0]
Bandwidth limitation in RF path. 000 0000 to 111 1111: f0(RF) = 12 to 145 MHz.
6 to 0
7.3.14
REGISTER 15: DPD FILTER SETTINGS
Table 28 Register address FH
BIT
15
14
13
12
11
10
9
8
SYMBOL
AD3
AD2
AD1
AD0
−
−
−
−
BIT
7
6
5
4
3
2
1
0
SYMBOL
−
−
DPD_LL2
DPD_LL1
DPD_LL0
DPD_LPF2
DPD_LPF1
DPD_LPF0
2003 Jun 03
25
Philips Semiconductors
Preliminary specification
High speed advanced analog DVD signal
processor and laser supply
TZA1035HL
Table 29 Description of register bits (address FH); bit K2_Mode = 1
BIT
SYMBOL
FUNCTION
15 to 12
AD[3:0]
1111 = address FH
11 to 6
−
not used
5 to 3
DPD_LL[2:0]
DPD lead/lag filter start frequency (fstart).
000 = 1 MHz
001 = 5 MHz
010 = 10 MHz
011 = 18 MHz
100 = 24 MHz
2 to 0
DPD_LPF[2:0]
DPD low-pass filter (f−3dB).
000 = 10 MHz
001 = 50 MHz
010 = 100 MHz
011 = 180 MHz
111 = 240 MHz
7.4
Internal digital control, serial bus and external
digital input signal relationships
7.5
The variables A1 to A3, ARFSUM, ALFC and ALFR, are the
linear equivalents of G1 to G3, GRFSUM, GLFC and GLFR.
The settings of all internal switches, DACs and modes of
operation can be programmed via the serial bus. There are
also a few external digital signals which influence the
programmed settings.
7.4.1
Signal descriptions
7.5.1
DATA PATH SIGNALS THROUGH PINS A TO D
With bit RFSUM = 0:
(DVDRFP − DVDRFN) =
A2 × 1/4 × [SW-A {(A − OPUREF) × A1 − RFOFFSL}
+ SW-B {(B − OPUREF) × A1 − RFOFFSL}
+ SW-C {(C − OPUREF) × A1 − RFOFFSR}
+ SW-D {(D − OPUREF) × A1 − RFOFFSR}]
STANDBY MODE
To ensure a safe start-up, the TZA1035HL has an internal
Power-on reset that resets on bit PWRON. During
STANDBY mode, most circuits, including laser supplies,
are switched off.
bit CD_LDON = 1 if CD laser is on and POWERON
RFP = RFREF + 0.5 × A3 × (DVDRFP − DVDRFN)
bit DVD_LDON = 1 if DVD laser is on and POWERON.
RFN = RFREF − 0.5 × A3 × (DVDRFP − DVDRFN)
7.4.2
Thus:
RF ONLY MODE
RFdif =
The servo outputs can be disabled for easy interfacing in
systems where two front-end signal processors are used.
This mode will set the outputs OA to OD, S1 and S2 to
3-state. The RF data path remains active.
2003 Jun 03
A+B+C+D
A3 × A2 × A1 × ----------------------------------- – OPUREF – RF OFFS
4
26
Philips Semiconductors
Preliminary specification
High speed advanced analog DVD signal
processor and laser supply
Switches SW-A to SW-D can be programmed 1, −1 or 0
(respectively pass, invert or not pass the signal) for each
channel. In this way the data can be read by any
combination of diode inputs.
1
1
H n ( s ) = -------------------------------------------- × ---------------------2
s
s
s
1 + --------------2- + ------------ 1 + -----------ω
0RF
ω 0RF
ω
0RF
The corner frequency ω0RF is equal to that of the equalizer
filter. The noise filter is switched on with bit RFNFEN.
The first gain stage also carries the signals for DPD
tracking. Therefore this stage will also be active when
RFSUM input and DPD is selected. The DC offset
cancellation is also active in this situation but left and right
channels are controlled from a single DAC. Also in this
situation, the A to D and RFSUM inputs are used
simultaneously.
7.5.4
FOCUS SIGNALS
Focus servo signals:
1
OA = ------------- × ALFC × (A − OPUREF + LFOFFS − COFFSA)
R LFC
Control of the DC offset DACs can be chosen to be from
the same register or from two independent registers
(registers 4 and 5).
7.5.2
TZA1035HL
+ β × FOFFS
1
OB = ------------- × ALFC × (B − OPUREF + LFOFFS − COFFSB)
R LFC
DATA SIGNAL PATH THROUGH INPUT PINS RFSUMP
AND RFSUMN
+ (1 − β) × FOFFS
With bit RFSUM = 1:
1
OC = ------------- × ALFC × (C − OPUREF + LFOFFS − COFFSC)
R LFC
(DVDRFP − DVDRFN) =
ARFSUM × [RFSUMP − RFSUMN − RFOFFSS]
+ β × FOFFS
RFP = RFREF + 0.5 × A3 × (DVDRFP − DVDRFN)
RFN = RFREF − 0.5 × A3 × (DVDRFP − DVDRFN)
1
OD = ------------- × ALFC × (D − OPUREF + LFOFFS − COFFSD)
R LFC
Thus:
+ (1 − β) × FOFFS
RFdif = ARFSUM × [RFSUMP − RFSUMN − RFOFFSS]
The parameter β can be programmed via the serial bus.
7.5.3
The focus offset DAC can be switched on with the control
bit FOFFSEN.
HF FILTERING
The differential HF signal from the G3 stage is sent to a
filter section that consists of an equalizer and a noise filter,
which are controlled by bits BWRF, RFKEQ, RFEQEN and
RFNFEN. The equalizer has a transfer function H1 (s)
which is modelled after a target transfer function He (s):
7.5.5
7.5.5.1
DPD signals (DVD-ROM mode) with no
drop-out concealment
DPD tracking can be activated with bits RT_mode[2:0] of
register 1. Input signals are taken from the diode inputs
A to D, through the input stage G1 and the DC offset
cancellation DAC. When bit RFSUM = 0, the input stage is
also used for the RF signal. When bit RFSUM = 1, the
setting for G1 and DC offset control can be independent of
the setting for the data signal which goes through RFSUM.
∆t
S1DPD = I(FS)(DPD) × ------ + IREFRAD
TP
∆t
S2DPD = −I(FS)(DPD) × ------ + IREFRAD
TP
2
s
1 + k × --------------2ω 0RF
1
H e ( s ) = ------------------------------------------------------× ------------------------------2
s
s
s
-----------1 + ---------------2- + α × ------------ 1 + τ × ω
0RF
ω 0RF
ω 0RF
This represents a third-order equi-ripple phase filter with a
good delay response. The boost factor k is programmable
via the serial bus control bit RFKEQ. The corner
frequency ω0RF = 2πf0RF is programmable via control
parameter bit BWRF. The equalizer is switched on with
control bit RFEQEN.
∆t
------ is the time difference between the two input signals,
TP
The noise filter has a transfer function H2 (s) which is
modelled after a third-order Butterworth low-pass filter with
target transfer function Hn (s):
2003 Jun 03
RADIAL SIGNALS
relative to the period time TP of the input signal. I(FS)(DPD)
is the full scale range.
27
Philips Semiconductors
Preliminary specification
High speed advanced analog DVD signal
processor and laser supply
TZA1035HL
The bandwidth of the DPD signal is limited by the 100 kHz
phase detector integration filters and the bandwidth of the
output stages (100 kHz for S1 and S2).
For S1 and S2 bit RAD_pol is assumed to be set to logic 1.
Otherwise the signals appearing at S1 and S2 will be
swapped.
The input signals used for DPD depend on the
programmed radial tracking mode (bits RT_mode[2:0]):
The DPD detection can not work properly when the input
signal becomes very small. The output of the DPD may
then show a significant offset. The DOC may not conceal
this offset completely because:
∆t
∆t
DPDmode = DPD2: ------ (A,D) or DPD2: ------ (A + C, B + D)
TP
TP
• DOC is gradually controlled from the CA signal
• The CA signal may not become 0 during disc-defect.
∆t
∆t
DPDmode = DPD4: 0.5[ ------ (A,D) + ------ (C,B)]
TP
TP
7.5.5.3
∆t
Range of ------ is from −0.5 to + 0.5.
TP
When the three-beam system is used, the radial signals
S1 and S2 can be composed from inputs E and F.
∆t
------ > 0 if A,C phase leads with respect to D,B phase.
TP
E – OPUREF + LF OFFS + R OFFSE
S1 PP = A LFR × -----------------------------------------------------------------------------------------
R LFR
FTC = (S1 − S2) × (RFTC + FTCREF)
F – OPUREF + LF OFFS – R OFFSF
S2 PP = A LFR × ----------------------------------------------------------------------------------------
R LFR
For S1 and S2 bit RAD_pol is assumed to be set to logic 1.
Otherwise the signals appearing at S1 and S2 will be
swapped.
7.5.5.2
Three-beam push-pull (CD mode)
FTC = (S1 − S2) × RFTC + FTCREF (bandwidth limited
to 600 kHz).
DPD signals (DVD-ROM mode) with
drop-out concealment
With bit DOCEN = 1, drop-out concealment is activated
and the S1 and S2 outputs change:
For S1 and S2 bit RAD_pol is assumed to be set to logic 1.
Otherwise the signals appearing at S1 and S2 will be
swapped.
• The common mode level (IREFRAD) is now determined by
the CA signal
7.5.5.4
• The scaling changes.
Top hold push-pull method is supported but only in
conjunction with a compatible decoder. The peak hold
function is executed in the decoder, by measuring the
mirror levels of the gap-zones in each header. The
TZA1035HL will compensate for offset errors in two ways:
At low signal levels (SUM < DOCthreshold), the contribution
∆t
of ------ is reduced smoothly.
TP
• The DC offset from the pick-up can be compensated by
means of a DAC (COFFSx) in each channel
∆t
S1DPD = C × I(FS)(DPD)(DOC) × ------ + 0.25 × CA.
TP
• The dynamic offsets can be compensated by means of
the multiplier ratio α.
∆t
S2DPD = −C × I(FS)(DPD)(DOC) × ------ + 0.25 × CA.
TP
The correction values must be calculated in the decoder
and programmed via the serial bus. The method is called
the enhanced push-pull method.
Where:
• I(FS)(DPD)(DOC) is the full scale range
For S1 and S2 bit RAD_pol is assumed to be set to logic 1.
Otherwise the signals appearing at S1 and S2 will be
swapped.
• C = concealment multiplier, C = 0 to 1 when CA is
0 to DOCthreshold
• CA = OA + OB + OC + OD
• DOCthreshold is typically 3 µA.
2003 Jun 03
Enhanced push-pull
28
Philips Semiconductors
Preliminary specification
High speed advanced analog DVD signal
processor and laser supply
TZA1035HL
A + B – 2 × OPUREF + 2 × LF OFFS – ( C OFFSA – C OFFSB )
S1 PP = A LFR × α × ------------------------------------------------------------------------------------------------------------------------------------------------------
R LFPP
C + D – 2 × OPUREF + 2 × LF OFFS – ( C OFFSC – C OFFSD )
S2 PP = A LFR × ( 2 – α ) × -------------------------------------------------------------------------------------------------------------------------------------------------------
R LFPP
or:
A – OPUREF + LF OFFS – C OFFSA
S1 PP = A LFR × α × -----------------------------------------------------------------------------------------
R LFPP
D – OPUREF + LF OFFS – C OFFSD
S2 PP = A LFR × ( 2 – α ) × -----------------------------------------------------------------------------------------
R LFPP
The signals from the B and C channels can be switched off, depending on the photodiode configuration
(bit RT_mode[2:0]).
2003 Jun 03
29
Philips Semiconductors
Preliminary specification
High speed advanced analog DVD signal
processor and laser supply
TZA1035HL
8 LIMITING VALUES
In accordance with the Absolute Maximum Rating System (IEC 60134).
SYMBOLS
PARAMETER
CONDITIONS
MIN.
MAX.
UNIT
VDD
supply voltage
−
5.5
V
Tamb
ambient temperature
0
60
°C
Vesd
electrostatic discharge
voltage
Human Body Model (HBM); note 1 −
−
Machine Model (MM); note 1
2000
V
200
V
Note
1. ESD behaviour is tested in accordance with JEDEC II standard:
HBM is equivalent to discharging a 100 pF capacitor through a 1.5 kΩ series resistor.
MM is equivalent to discharging a 200 pF capacitor through a 0.75 µH series inductor.
9
THERMAL CHARACTERISTICS
SYMBOL
Rth(j-a)
PARAMETER
CONDITIONS
thermal resistance from
junction to ambient
VALUE
UNIT
76
K/W
in free air
10 CHARACTERISTICS
VDDA = 5 V; VDDD3 = 3.3 V; VDDD5 = 5 V; VRFREF = 1.2 V; Tamb = 25 °C; RF inputs A to D are referred to pin OPUREF;
f0(RF) = 50 MHz; Rext = 12.1 kΩ (pin REXT); RF output max. load on pins RFP and RFN is ZO(max): 5 pF parallel with
10 kΩ to VSS; unless otherwise specified.
SYMBOL
Tamb
PARAMETER
CONDITIONS
MIN.
ambient
temperature
TYP.
MAX.
UNIT
0
−
60
°C
4.5
5.0
5.5
V
Supplies
VDDA1, VDDA2, analog supply
VDDA3, VDDA4 voltage
VDDD3
3 V digital supply
voltage
2.7
3.3
5.5
V
VDDD5
5 V digital supply
voltage
4.5
5.0
5.5
V
VI(logic)
logic input
compatibility
2.7
3.3
5.5
V
VPOR
Power-on reset
voltage
3.3
3.5
3.7
V
IDD
supply current
without laser supply
−
98
120
mA
STANDBY mode
−
−
1
mA
2003 Jun 03
note 1
30
Philips Semiconductors
Preliminary specification
High speed advanced analog DVD signal
processor and laser supply
SYMBOL
PARAMETER
CONDITIONS
TZA1035HL
MIN.
TYP.
MAX.
UNIT
RF data path, input: pins A to D and OPUREF
1.5
0.5VDDA
VDDA − 2
V
G1 = 0 dB
−
−
600
mV
G1 = 6 dB
−
−
300
mV
G1 = 12 dB
−
−
150
mV
1.8
0.5VDDA
VDDA − 1.4
V
Vi(OPUREF)
input voltage on
pin OPUREF
note 2
Vi(RF)(FS)
input voltage on
pins A to D for
full-scale at output
referred to VOPUREF
VI(DC)
DC component of
input voltage
VRFOFFSL,
VRFOFFSR
DC offset
compensation
voltage
G1 = 0 dB
350
450
550
mV
G1 = 6 dB
175
225
275
mV
G1 = 12 dB
90
120
160
mV
DC offset
compensation
voltage resolution
G1 = 0 dB
−
7.1
−
mV
G1 = 6 dB
−
3.6
−
mV
G1 = 12 dB
−
1.9
−
mV
∆VRFOFFSL,
∆VRFOFFSR
II(bias)
input bias current
on pins A to D
−
−
5
µA
Zi
input impedance of
pins A to D
100
−
−
kΩ
ARF(min)
minimum gain
G1 = 0 dB, G2 = 6 dB,
G3 = 0 dB; note 3
4
6
8
dB
ARF(max)
maximum gain
G1 = 12 dB,
G2 = 24 dB,
G3 = 13 dB; note 3
48
49
52
dB
TCgain
gain temperature
coefficient
−
−0.025
−
dB/°C
∆G1
first RF amplifier
stage gain step size
5
6
7
dB
∆G2
second RF amplifier
stage gain step size
5
6
7
dB
RF data path, input: pins RFSUMP and RFSUMN
VI(DC)
DC input voltage
with respect to VSS
1.3
−
VDDA − 1.0
V
VI(SUM)(dif)
differential input
voltage
GRFSUM = −6 dB
−
−
1800
mV
GRFSUM = 0 dB
−
−
1400
mV
GRFSUM = 6 dB
−
−
700
mV
GRFSUM = 12 dB
−
−
350
mV
GRFSUM = 18 dB
−
−
175
mV
II(bias)
input bias current
ZI
input impedance
2003 Jun 03
note 4
31
−
5
−
µA
50
−
600
kΩ
Philips Semiconductors
Preliminary specification
High speed advanced analog DVD signal
processor and laser supply
SYMBOL
VRFOFFSS
∆VRFOFFSS
PARAMETER
DC offset
compensation
voltage
DC offset
compensation
voltage resolution
CONDITIONS
TZA1035HL
MIN.
TYP.
MAX.
UNIT
GRFSUM = −6 dB
−
1700
−
mV
GRFSUM = 0 dB
−
850
−
mV
GRFSUM = 6 dB
−
425
−
mV
GRFSUM = 12 dB
−
210
−
mV
GRFSUM = 18 dB
−
105
−
mV
GRFSUM = −6 dB
−
27
−
mV
GRFSUM = 0 dB
−
13.5
−
mV
GRFSUM = 6 dB
−
6.7
−
mV
GRFSUM = 12 dB
−
3.4
−
mV
GRFSUM = 18 dB
−
1.7
−
mV
−8
−6
−4
dB
ARFSUM(min)
minimum gain
note 3
note 3
ARFSUM(max)
maximum gain
29
31
33
dB
TCgain
gain temperature
coefficient
−
−0.02
−
dB/°C
∆GRFSUM
RFSUM amplifier
stage gain step size
5
6
7.5
dB
A = 12 + 24 + 6 dB;
RFEQEN = 0
−
7
-
mV
A = 12 + 6 + 6 dB;
RFEQEN = 0
−
6
−
mV
A = 12 + 6 + 6 dB;
RFEQEN = 1;
RFKEQ = 0
−
9
−
mV
A = 12 + 6 + 6 dB;
RFEQEN = 1;
RFKEQ = 1
−
11
−
mV
−
12
−
mV
−
−
60
mV
VRFREF = 0.8 to 2.1 V −
−
100
mV
RF data path, filter and output
Vn(o)(dif)(rms)
differential
RF output noise
voltage (RMS
value)
diode input:
BWRF = 127;
f = 0 to 500 MHz;
RFNFEN = 1; note 5
SUM input:
BWRF = 127;
f = 0 to 500 MHz;
RFNFEN = 1; note 5
A = 12 + 6 + 6 dB;
RFEQEN = 0
VOO(ref)
2003 Jun 03
DC output offset
VI(RF) = 0 V;
voltage with respect DVDOFFS = 0; note 6
to VRFREF
VRFREF = 1.2 V
32
Philips Semiconductors
Preliminary specification
High speed advanced analog DVD signal
processor and laser supply
SYMBOL
PARAMETER
CONDITIONS
TZA1035HL
MIN.
TYP.
MAX.
UNIT
Vo(dif)(p-p)
differential output
voltage on
pins RFP and RFN
(peak-to-peak
value)
−
−
1.4
V
VO(RF)(DC)
DC output voltage
on pins RFP and
RFN
0.35
−
VDDA − 1.9
V
Vi(RFREF)(CM)
input reference
voltage for common
mode output on
pin RFREF
0.8
1.2
2.1
V
Ro
output impedance
on pins RFP and
RFN
−
100
−
Ω
∆G3
third RF amplifier
note 7
stage gain step size
−
0.85
1.3
dB
||h1| − |he||
equalizer amplitude flatness between
error
f0 and 100 kHz
−
−
1.5
dB
||h1| − |hn||
noise filter
amplitude error
flatness between
f0 and 100 kHz
−
−
1.5
dB
BRF(−3dB)
−3 dB bandwidth of
RFP and RFN
signal path
RFEQEN = 0;
RFNFEN = 0
200
300
−
MHz
f0(RF)
noise filter and
equalizer corner
frequency
BWRF = 0
8
12.0
14.5
MHz
BWRF = 127
100
145
182
MHz
∆f0(RF)
noise filter and
equalizer corner
frequency step size
∆BWRF = 1; note 8
0.73
1.06
1.32
MHz
td(RF)
flatness delay in
RF data path
equalizer off;
f = 0 to 150 MHz
−
−
0.1
ns
equalizer on;
f = 0 to 100 MHz;
BWRF = 127
−
−
0.5
ns
BWRF = 0
−
−
3.5
ns
BWRF = 127
−
−
0.6
ns
µs
equalizer and noise
filter on;
f = 0 to 0.7f0(RF)
tst(G3)
amplifier G3 gain
note 9
change settling time
−
−
0.5
α
equalizer parameter see Section 7.5.3
1.125
1.25
1.375
τ
equalizer parameter see Section 7.5.3
1.18
1.31
1.44
2003 Jun 03
33
Philips Semiconductors
Preliminary specification
High speed advanced analog DVD signal
processor and laser supply
SYMBOL
k
PARAMETER
CONDITIONS
TZA1035HL
MIN.
TYP.
MAX.
UNIT
equalizer parameter see Section 7.5.3
RFKEQ = 0
3.2
4.0
4.8
RFKEQ = 1
4.8
6.0
7.2
path to focus servo
outputs referred to
VOPUREF
700
−
−
mV
path to radial servo
outputs referred to
VOPUREF
500
−
−
mv
−0.2
−
VDD − 2.5
V
SERVOOS = 0
−
15
−
mV
SERVOOS = 1
−
45
−
mV
4.25
5
5.75
mV
LF servo path
VI(LF)
input voltage range
VO(LF)
servo output
voltage
VLFOFFS(CM)
common mode
offset
compensation
voltage
∆VLFOFFS
DC offset voltage
resolution
SERVOOS = 0
SERVOOS = 1
13
15
17
mV
VROFFS,
VCOFFS
offset voltage
compensation
SERVOOS = 0
−
20
−
mV
SERVOOS = 1
−
60
−
mV
∆VROFFS,
∆VCOFFS
DC offset voltage
resolution
SERVOOS = 0
1.0
1.3
1.6
mV
SERVOOS = 1
3.0
4
4.8
mV
VI(FTCREF)
FTC reference input
reference voltage
1.25
−
2.75
V
VO(FTC)(p-p)
FTC output voltage
(peak-to-peak
value)
2.0
−
−
V
IO(LF)
output current
focus servo outputs
0
−
12
µA
radial servo outputs
0
−
12
µA
IFOFFS
focus compensation from FOFFS DAC
current
310
390
480
nA
∆IFOFFS
compensation
current resolution
−
12
−
nA
I(FS)(DPD)
DPD full scale
current
DOCEN = 0
17
20
23
µA
DOCEN = 1
4.5
6.6
8
µA
f = 3 MHz;
Vi = 100 mV (p-p)
Ith(DOC)
DOCEN threshold
current
SUM value
2.5
3
3.5
µA
IREFRAD(CM)
common mode DC
current in DPD
mode
DOCEN = 0
−
3.5
−
µA
2003 Jun 03
34
Philips Semiconductors
Preliminary specification
High speed advanced analog DVD signal
processor and laser supply
SYMBOL
PARAMETER
CONDITIONS
TZA1035HL
MIN.
TYP.
MAX.
UNIT
RLFC
LF path input
transresistance
GLFC = 0 dB
10.5
14
16.5
kΩ
RLFR
CD satellite path
input
transresistance
GLFR = 0 dB; α = 1
11
15
18
kΩ
RLFPP
DVD push-pull
transresistance
GLFR = 0 dB; α = 1
23
30
36
kΩ
RFTC
fast track count
transimpedance
note 10
510
650
800
kΩ
GLFC
gain range central
channels
−15.5
−
+8.5
dB
∆GLFC
gain resolution
−
3
−
dB
GLFR
gain range radial
channels
−15.5
−
+8.5
dB
∆GLFR
gain resolution
−
3
−
dB
BLF(−3dB)
−3 dB bandwidth of
LF path
60
75
100
kHz
BFTC
FTC bandwidth
FTCHBW = 0
−
600
−
kHz
FTCHBW = 1; note 11
−
1200
−
kHz
LRM
dynamic radial left
right matching
α=1
−7
−
+7
%
CPM
channel pair
matching
GLF = 0 dB; note 12
VI(LF) = 96 mV; pairs
OA, OD or OC, OB
−2
−
+2
%FS
VI(LF) = 48 mV; pair
S1 and S2
−7
−
+7
%FS
α
dynamic radial
offset
compensation
factor
0.6
−
1.35
∆α
dynamic radial
offset
compensation
factor resolution
−
0.05
−
ALPC Automatic Laser Power Control
Vi(mon)
input voltage from
laser monitor diode
P-type monitor diode
LOW level voltage
VDDA4 − 0.140 VDDA4 − 0.155 VDDA4 − 0.170 V
HIGH level voltage
VDDA4 − 0.215 VDDA4 − 0.190 VDDA4 − 0.180 V
N-type monitor diode
LOW level voltage
0.145
0.155
0.17
V
HIGH level voltage
0.175
0.185
0.2
V
VO(laser)
laser output voltage
−
−
VDDL − 0.5
V
Vprot
low supply voltage
protection level
3.6
3.8
4.0
V
2003 Jun 03
35
Philips Semiconductors
Preliminary specification
High speed advanced analog DVD signal
processor and laser supply
SYMBOL
PARAMETER
CONDITIONS
TZA1035HL
MIN.
TYP.
MAX.
UNIT
∆Vprot
low supply voltage
protection
hysteresis
−
200
−
mV
II(mon)
laser monitor diode
input current
−
−
200
nA
Io(laser)(max)
maximum current
output to laser
−120
−
−
mA
ton(laser)
laser switch on time
−
3
−
ms
FTC comparator
VI(CM)
common mode
input voltage
0
−
2.5
V
VOL
LOW-level output
voltage
0
−
0.5
V
VOH
HIGH-level output
voltage
VDDD3 − 0.5
−
VDDD3
V
VIO
input offset voltage
−
−
10
mV
ILI
input leakage
current
−
−
100
nA
AV
voltage gain
−
200
−
V/mV
tr, tf
rise and fall time
CL = 15 pF
−
250
−
ns
tres
response time
VI(dif) = 200 mV (p-p)
−
200
−
ns
Serial bus interface (see Fig.8)
VIH
HIGH-level input
voltage
0.7VDDD3
−
−
V
VIL
LOW-level input
voltage
−
−
0.3VDDD3
V
IIH
HIGH-level input
current on pin TM,
input incorporates
internal pull-down
resistor
−
−
100
µA
II
input current
pins SIDA, SICL and
SILD
−
−
100
nA
tsu(strt)
start set-up time
0
−
−
ns
tsu(D)
data set-up time
5
−
−
ns
th(D)
data hold time
20
−
−
ns
tclk(H)
clock HIGH time
10
−
−
ns
tclk(L)
clock LOW time
10
−
−
ns
Tclk
clock period
30
−
−
ns
tsu(load)
load pulse set-up
time
30
−
−
ns
tload(H)
load pulse HIGH
time
10
−
−
ns
Notes
1. Level follows the applied supply voltage at pin VDDD3.
2003 Jun 03
36
Philips Semiconductors
Preliminary specification
High speed advanced analog DVD signal
processor and laser supply
TZA1035HL
2. This range for the servo path is designed to be larger than for the data path so that the servo path can handle
out-of-focus situations.
( G1 + G2 + G3 )
----------------------------------------20
3. A = 10
( Gsum + G3 )
----------------------------------20
[dB] or A = 10
[dB] (see Section 7.5).
4. Input impedance depends on gain setting. Highest gain has lowest input impedance.
5. Noise figures depend on gain and filter settings, examples given here.
V RFP + V RFN
6. VOO(ref) = --------------------------------- – V RFREF
2
7. Integral range for G3 from minimum to maximum gain is 13 dB (typical).
8. At the transition BWRF = 63 to 64 the ∆f may be between −0.2 and +1.7 MHz
9. Faster for small steps.
10. Overall gain from input to output is determined by RFTC/RLFR or RFTC/RLFPP, depending on radial tracking mode,
three-beam push-pull (CD) or DVD push-pull. Gain FTC scales with GFRR. When DPD tracking is selected the FTC
gain is fixed.
11. High FTC bandwidth is achieved when IS1 and IS2 > 1.5 µA.
12. Channel pair matching is defined in % of full scale (FS) output at half of the full scale level.
handbook, full pagewidth
SICL
t clk(L)
t clk(H)
t su(strt)
t h(D)
T clk
t su(D)
SIDA
D0
A3
SILD
t su(load)
MGW495
Fig.8 Single word transmission.
2003 Jun 03
37
Philips Semiconductors
Preliminary specification
High speed advanced analog DVD signal
processor and laser supply
TZA1035HL
11 APPLICATION INFORMATION
11.1.2
11.1
The current through output pins OA to OD represents the
low-pass filtered input voltage of each individual pick-up
segment. The gain from input to output can be
programmed to adapt to different disc types or pick-ups
(offset cancellation is omitted for simplicity):
Signal relationships
Simplified relationships between signals are described in
this section. In the simplification, all built-in options for
DVD-ROM are omitted. The variables A1 to A3, ALFC and
ALFR, are the linear equivalents of bits G1 to G3, GLFC and
GLFR.
11.1.1
V Ix × A LFC
I Ox = -------------------------14 kΩ
DATA PATH
( V I(A) + V I(B) ) × A LFR
I S1 = ---------------------------------------------------- (in DVD push-pull mode)
30 kΩ
Pins RFP and RFN carry the RF data signals in opposite
phases with respect to each other. This allows an ADC
with a balanced or differential input to be used in the
decoder. Depending on the DC input ranges of the ADC,
in many cases the connection between TZA1035HL and
the decoder can be a DC pin to pin connection. The
common mode DC level of pins RFP and RFN can be
chosen independently by means of input pin RFREF.
( V I(C) + V I(D) ) × A LFR
I S2 = ---------------------------------------------------- (in DVD push-pull mode)
30 kΩ
or:
V I(E) × A LFR
I S1 = ----------------------------- (in CD three-beam push-pull mode)
15 kΩ
If bit RFSUM = 0
V I(F) × A LFR
I S2 = ----------------------------- (in CD three-beam push-pull mode)
15 kΩ
• VRFP = VRFREF + 0.5 × A3 × A2 × A1 × (VI − VRFOFFS)
• VRFN = VRFREF − 0.5 × A3 × A2 × A1 × (VI − VRFOFFS)
or
• VRFDIF = A3 × A2 × A1 × (VI − VRFOFFS).
I S1 = I DC + I FS × phase difference (in DPD mode)
If bit RFSUM = 1
I S2 = I DC – I FS × phase difference (in DPD mode)
• VRFP = VRFREF + 0.5 × ARFSUM × A3 × (VRFSUMP − VRFSU
MN − VRFOFFSS)
Where:
• VRFN = VRFREF − 0.5 × ARFSUM × A3 × (VRFSUMP − VRFSU
MN − VRFOFFSS)
• ALFC and ALFR are the programmable gains in central
and radial paths
• VRFDIF = ARFSUM × A3 (VRFSUMP − VRFSUMN − VRFOFFSS).
• Gain should be programmed such that maximum signal
levels fit into the range of the servo processor ADC
Where:
• A1, A2, A3 and ARFSUM are programmed gain values
• VI(A); VI(B); VI(C) and VI(D) are defined as input voltages
at pins A to D with respect to pin OPUREF
• VI = average input voltage at pins A to D, with respect to
the voltage at pin OPUREF
• IDC is a DC current that keeps IS1 and IS2 unipolar
• VRFOFFS is the programmed RFOFFS DAC voltage
(register 4 and register 5)
• IFS is the sensitivity to relative phase difference.
∆φ [ degrees ]
∆t
Phase difference = ------ = ---------------------------------- ;
360
Tp
• VRFREF is the input voltage at pin RFREF.
Correct settings for VRFREF and VRFOFFS are required to
keep both VRFP and VRFN at the DC voltage levels
specified for the TZA1035HL and the decoder.
2003 Jun 03
SERVO PATH
−180° < φ < + 180°.
38
Philips Semiconductors
Preliminary specification
High speed advanced analog DVD signal
processor and laser supply
11.2
TZA1035HL
Programming examples
Table 30 Sample of register values and mode settings.
REGISTER VALUE (HEX)
REGISTER
DVD; LOW
GAIN
DVD; HIGH
GAIN(1)
CD; HIGH
GAIN(1)
MODE SETTINGS
0
005
045
043
switch on the laser power; Vmon = 150 mV; set GRFSUM
1
01D
01D
007
select diode or SUM inputs and corresponding tracking
method
2
800
800
800
set K2 mode
3
800
−
800
set low RF gain = 18 dB + G3
−
800
−
4
820
410
410
approximation for DVDOFFS DAC
5
000
000
000
optional second RF offset setting
6
338
778
778
GLFC = GLFR = −6 dB (low gain) or +6 dB (high gain);
α=1
7
200
200
000
set bits DPD_stretch to 1.9 ns
8
000
000
000
enable inputs A to D for RF
9
000
000
000
not used
10
000
000
000
not used
11
000
000
000
12
000
000
000
set for electrical offset compensation from pick-up (see
Section 11.4)
13
000
000
000
14
335
335
335
set bits BWRF to 80 MHz; RFEQEN = 1; RFNFEN = 1
15
022
022
000
set bits DPD_LL to 24 MHz; set bits DPD_LPF
to 100 MHz
set G1 for DPD (G3 = 0 dB in this example)
Note
1. Use RFSUM input.
2003 Jun 03
39
Philips Semiconductors
Preliminary specification
High speed advanced analog DVD signal
processor and laser supply
11.3
The test pin OCENTRAL can be useful to follow this
procedure. This pin can be programmed to output a copy
of the signal OA to OD (see register 12).
Energy saving
Bit PWRON can be used to bring the TZA1035HL into
STANDBY mode reducing the supply current to
approximately 0.5 mA.
11.4
11.4.1
11.4.2
Initial DC and gain setting strategy
GAIN SETTING SERVO
The servo gain has to be chosen dependant on the
reflectivity of the disc. So this needs to be done each time
when a new disc is inserted in the mechanism. A trial and
error procedure should find the optimal setting. Gain can
be set in 3 dB steps.
ELECTRICAL OFFSET FROM PICK-UP
It is useful to compensate for electrical offset, especially
with pick-ups that give a low output signal. It is possible to
compensate for each individual servo channel. Due to
internal circuitry, the TZA1035HL servo channels can
handle only signals positive with respect to the reference
input OPUREF. Therefore the potentially negative offset
from the pick-up must first be cancelled. The LFOFFS DAC
can be programmed to do this, and will apply this to all six
channels at the same time. The LFOFFS DAC can be set
to 0, 5, 10 or 15 mV.
11.4.3
DC LEVEL IN RF PATH
Once the gains in the servo path have been set, the
average DC level at the inputs can be calculated from the
value of the servo output signals:
I Ox × 14 kΩ
V I = -----------------------------------------------------------------------A LFC – ( V LFOFFS + V COFFSx )
As a second step, the offset between each channel can be
compensated by connecting the DACs to each individual
DAC (COFFSA to COFFSD, ROFFSE and ROFFSF). These
DACs can be programmed between 0 and 20 mV with
approximately 1.25 mV resolution. Where the LFOFFS DAC
increases the outputs signal level, the individual DACs
decrease the output signal. In this way the output signal
can be set very close to zero. The range of DACs, LFOFFS,
COFFS and ROFFS can be tripled with control
bit SERVOOS.
Where IOx is the average value of the output currents at
pins OA to OD.
This value is a good estimate to use initially to set the
RF DC compensation, VRFOFFS. The range and resolution
of the RFOFFS DACs are scaled with the programmed gain
of G1.
In cases where a DC coupling between TZA1035HL and
the decoder is made, a fine tuning of the RF DC
compensation can be done during play. The zero-crossing
level of the data-eye pattern can be used to judge the
correct DC compensation level.
The output current of servo channel A is calculated by:
[ ( V A – V OPUREF ) + V FLOFFS – V COFFSA ] × A LFC
I OA = -----------------------------------------------------------------------------------------------------------------------14 kΩ
11.4.4
In case the laser is switched off, the term (VA − VOPUREF)
represents the electrical offset from the pick-up.
GAIN SETTING RF PATH
The choice of RF gain is determined by the modulation of
the disc, therefore the modulation needs to be checked
each time a new disc is inserted in the mechanism. A trial
and error procedure should be sufficient to find the
optimum setting. For optimum use of the dynamic range:
The procedure to cancel the offset is:
1. Activate the pick-up and switch off the laser.
2. Set LFOFFS to its maximum value.
• Use G3 for fine tuning and AGC, so initially this should
be set in the range 0 to 6 dB to leave an additional gain
of 6 dB free to use during disc defects
3. Measure the output currents off all relevant servo
outputs.
• Use G1 and G2 to set the gain, increase G1 first,
when G1 has reached its maximum then G2 should be
increased
4. If all outputs represent a signal >5 mV equivalent input
voltage, decrease VLFOFFS then repeat step 3; if all
outputs represent a signal <5 mV equivalent input
voltage, go to step 5.
• G2 shows better noise performance in 12 and 24 dB
settings than in 6 and 18 dB setting
5. Measure each output and increase COFFS until the
output current is close enough to zero.
• A similar procedure can be followed for RFSUM.
This procedure needs only to be done once, or after a
longer time when temperature may have changed the
pick-up offset.
2003 Jun 03
TZA1035HL
40
Philips Semiconductors
Preliminary specification
High speed advanced analog DVD signal
processor and laser supply
TZA1035HL
12 PACKAGE OUTLINE
LQFP48: plastic low profile quad flat package; 48 leads; body 7 x 7 x 1.4 mm
SOT313-2
c
y
X
36
25
A
37
24
ZE
e
E HE
A A2
(A 3)
A1
w M
θ
bp
pin 1 index
Lp
L
13
48
detail X
12
1
ZD
e
v M A
w M
bp
D
B
HD
v M B
0
2.5
5 mm
scale
DIMENSIONS (mm are the original dimensions)
UNIT
A
max.
A1
A2
A3
bp
c
D (1)
E (1)
e
HD
HE
L
Lp
v
w
y
mm
1.6
0.20
0.05
1.45
1.35
0.25
0.27
0.17
0.18
0.12
7.1
6.9
7.1
6.9
0.5
9.15
8.85
9.15
8.85
1
0.75
0.45
0.2
0.12
0.1
Z D (1) Z E (1)
θ
0.95
0.55
7
0o
0.95
0.55
o
Note
1. Plastic or metal protrusions of 0.25 mm maximum per side are not included.
REFERENCES
OUTLINE
VERSION
IEC
JEDEC
SOT313-2
136E05
MS-026
2003 Jun 03
JEITA
EUROPEAN
PROJECTION
ISSUE DATE
00-01-19
03-02-25
41
Philips Semiconductors
Preliminary specification
High speed advanced analog DVD signal
processor and laser supply
To overcome these problems the double-wave soldering
method was specifically developed.
13 SOLDERING
13.1
Introduction to soldering surface mount
packages
If wave soldering is used the following conditions must be
observed for optimal results:
This text gives a very brief insight to a complex technology.
A more in-depth account of soldering ICs can be found in
our “Data Handbook IC26; Integrated Circuit Packages”
(document order number 9398 652 90011).
• Use a double-wave soldering method comprising a
turbulent wave with high upward pressure followed by a
smooth laminar wave.
• For packages with leads on two sides and a pitch (e):
There is no soldering method that is ideal for all surface
mount IC packages. Wave soldering can still be used for
certain surface mount ICs, but it is not suitable for fine pitch
SMDs. In these situations reflow soldering is
recommended.
13.2
TZA1035HL
– larger than or equal to 1.27 mm, the footprint
longitudinal axis is preferred to be parallel to the
transport direction of the printed-circuit board;
– smaller than 1.27 mm, the footprint longitudinal axis
must be parallel to the transport direction of the
printed-circuit board.
Reflow soldering
The footprint must incorporate solder thieves at the
downstream end.
Reflow soldering requires solder paste (a suspension of
fine solder particles, flux and binding agent) to be applied
to the printed-circuit board by screen printing, stencilling or
pressure-syringe dispensing before package placement.
Driven by legislation and environmental forces the
worldwide use of lead-free solder pastes is increasing.
• For packages with leads on four sides, the footprint must
be placed at a 45° angle to the transport direction of the
printed-circuit board. The footprint must incorporate
solder thieves downstream and at the side corners.
Several methods exist for reflowing; for example,
convection or convection/infrared heating in a conveyor
type oven. Throughput times (preheating, soldering and
cooling) vary between 100 and 200 seconds depending
on heating method.
During placement and before soldering, the package must
be fixed with a droplet of adhesive. The adhesive can be
applied by screen printing, pin transfer or syringe
dispensing. The package can be soldered after the
adhesive is cured.
Typical reflow peak temperatures range from
215 to 270 °C depending on solder paste material. The
top-surface temperature of the packages should
preferably be kept:
Typical dwell time of the leads in the wave ranges from
3 to 4 seconds at 250 °C or 265 °C, depending on solder
material applied, SnPb or Pb-free respectively.
• below 220 °C (SnPb process) or below 245 °C (Pb-free
process)
A mildly-activated flux will eliminate the need for removal
of corrosive residues in most applications.
– for all BGA and SSOP-T packages
13.4
– for packages with a thickness ≥ 2.5 mm
Fix the component by first soldering two
diagonally-opposite end leads. Use a low voltage (24 V or
less) soldering iron applied to the flat part of the lead.
Contact time must be limited to 10 seconds at up to
300 °C.
– for packages with a thickness < 2.5 mm and a
volume ≥ 350 mm3 so called thick/large packages.
• below 235 °C (SnPb process) or below 260 °C (Pb-free
process) for packages with a thickness < 2.5 mm and a
volume < 350 mm3 so called small/thin packages.
When using a dedicated tool, all other leads can be
soldered in one operation within 2 to 5 seconds between
270 and 320 °C.
Moisture sensitivity precautions, as indicated on packing,
must be respected at all times.
13.3
Wave soldering
Conventional single wave soldering is not recommended
for surface mount devices (SMDs) or printed-circuit boards
with a high component density, as solder bridging and
non-wetting can present major problems.
2003 Jun 03
Manual soldering
42
Philips Semiconductors
Preliminary specification
High speed advanced analog DVD signal
processor and laser supply
13.5
TZA1035HL
Suitability of surface mount IC packages for wave and reflow soldering methods
SOLDERING METHOD
PACKAGE(1)
WAVE
BGA, LBGA, LFBGA, SQFP, SSOP-T(3), TFBGA, VFBGA
not suitable
suitable(4)
DHVQFN, HBCC, HBGA, HLQFP, HSQFP, HSOP, HTQFP,
HTSSOP, HVQFN, HVSON, SMS
not
PLCC(5), SO, SOJ
suitable
LQFP, QFP, TQFP
SSOP, TSSOP, VSO, VSSOP
REFLOW(2)
suitable
suitable
suitable
not
recommended(5)(6)
suitable
not
recommended(7)
suitable
Notes
1. For more detailed information on the BGA packages refer to the “(LF)BGA Application Note” (AN01026); order a copy
from your Philips Semiconductors sales office.
2. All surface mount (SMD) packages are moisture sensitive. Depending upon the moisture content, the maximum
temperature (with respect to time) and body size of the package, there is a risk that internal or external package
cracks may occur due to vaporization of the moisture in them (the so called popcorn effect). For details, refer to the
Drypack information in the “Data Handbook IC26; Integrated Circuit Packages; Section: Packing Methods”.
3. These transparent plastic packages are extremely sensitive to reflow soldering conditions and must on no account
be processed through more than one soldering cycle or subjected to infrared reflow soldering with peak temperature
exceeding 217 °C ± 10 °C measured in the atmosphere of the reflow oven. The package body peak temperature
must be kept as low as possible.
4. These packages are not suitable for wave soldering. On versions with the heatsink on the bottom side, the solder
cannot penetrate between the printed-circuit board and the heatsink. On versions with the heatsink on the top side,
the solder might be deposited on the heatsink surface.
5. If wave soldering is considered, then the package must be placed at a 45° angle to the solder wave direction.
The package footprint must incorporate solder thieves downstream and at the side corners.
6. Wave soldering is suitable for LQFP, TQFP and QFP packages with a pitch (e) larger than 0.8 mm; it is definitely not
suitable for packages with a pitch (e) equal to or smaller than 0.65 mm.
7. Wave soldering is suitable for SSOP, TSSOP, VSO and VSSOP packages with a pitch (e) equal to or larger than
0.65 mm; it is definitely not suitable for packages with a pitch (e) equal to or smaller than 0.5 mm.
2003 Jun 03
43
Philips Semiconductors
Preliminary specification
High speed advanced analog DVD signal
processor and laser supply
TZA1035HL
14 DATA SHEET STATUS
LEVEL
DATA SHEET
STATUS(1)
PRODUCT
STATUS(2)(3)
Development
DEFINITION
I
Objective data
II
Preliminary data Qualification
This data sheet contains data from the preliminary specification.
Supplementary data will be published at a later date. Philips
Semiconductors reserves the right to change the specification without
notice, in order to improve the design and supply the best possible
product.
III
Product data
This data sheet contains data from the product specification. Philips
Semiconductors reserves the right to make changes at any time in order
to improve the design, manufacturing and supply. Relevant changes will
be communicated via a Customer Product/Process Change Notification
(CPCN).
Production
This data sheet contains data from the objective specification for product
development. Philips Semiconductors reserves the right to change the
specification in any manner without notice.
Notes
1. Please consult the most recently issued data sheet before initiating or completing a design.
2. The product status of the device(s) described in this data sheet may have changed since this data sheet was
published. The latest information is available on the Internet at URL http://www.semiconductors.philips.com.
3. For data sheets describing multiple type numbers, the highest-level product status determines the data sheet status.
15 DEFINITIONS
16 DISCLAIMERS
Short-form specification The data in a short-form
specification is extracted from a full data sheet with the
same type number and title. For detailed information see
the relevant data sheet or data handbook.
Life support applications These products are not
designed for use in life support appliances, devices, or
systems where malfunction of these products can
reasonably be expected to result in personal injury. Philips
Semiconductors customers using or selling these products
for use in such applications do so at their own risk and
agree to fully indemnify Philips Semiconductors for any
damages resulting from such application.
Limiting values definition Limiting values given are in
accordance with the Absolute Maximum Rating System
(IEC 60134). Stress above one or more of the limiting
values may cause permanent damage to the device.
These are stress ratings only and operation of the device
at these or at any other conditions above those given in the
Characteristics sections of the specification is not implied.
Exposure to limiting values for extended periods may
affect device reliability.
Right to make changes Philips Semiconductors
reserves the right to make changes in the products including circuits, standard cells, and/or software described or contained herein in order to improve design
and/or performance. When the product is in full production
(status ‘Production’), relevant changes will be
communicated via a Customer Product/Process Change
Notification (CPCN). Philips Semiconductors assumes no
responsibility or liability for the use of any of these
products, conveys no licence or title under any patent,
copyright, or mask work right to these products, and
makes no representations or warranties that these
products are free from patent, copyright, or mask work
right infringement, unless otherwise specified.
Application information Applications that are
described herein for any of these products are for
illustrative purposes only. Philips Semiconductors make
no representation or warranty that such applications will be
suitable for the specified use without further testing or
modification.
2003 Jun 03
44
Philips Semiconductors
Preliminary specification
High speed advanced analog DVD signal
processor and laser supply
NOTES
2003 Jun 03
45
TZA1035HL
Philips Semiconductors
Preliminary specification
High speed advanced analog DVD signal
processor and laser supply
NOTES
2003 Jun 03
46
TZA1035HL
Philips Semiconductors
Preliminary specification
High speed advanced analog DVD signal
processor and laser supply
NOTES
2003 Jun 03
47
TZA1035HL
Philips Semiconductors – a worldwide company
Contact information
For additional information please visit http://www.semiconductors.philips.com.
Fax: +31 40 27 24825
For sales offices addresses send e-mail to: [email protected].
SCA75
© Koninklijke Philips Electronics N.V. 2003
All rights are reserved. Reproduction in whole or in part is prohibited without the prior written consent of the copyright owner.
The information presented in this document does not form part of any quotation or contract, is believed to be accurate and reliable and may be changed
without notice. No liability will be accepted by the publisher for any consequence of its use. Publication thereof does not convey nor imply any license
under patent- or other industrial or intellectual property rights.
Printed in The Netherlands
753503/01/pp48
Date of release: 2003
Jun 03
Document order number:
9397 750 10296