TI THS5661AIPW

THS5661A
12-BIT, 125 MSPS, CommsDAC
DIGITAL-TO-ANALOG CONVERTER
SLAS247 – NOVEMBER 1999
D
D
D
D
D
D
D
D
D
D
D
Member of the Pin-Compatible
CommsDAC Product Family
125 MSPS Update Rate
12-Bit Resolution
Spurious Free Dynamic Range (SFDR) to
Nyquist at 40 MHz Output: 60 dBc
1 ns Setup/Hold Time
Differential Scalable Current Outputs: 2 mA
to 20 mA
On-Chip 1.2 V Reference
3 V and 5 V CMOS-Compatible Digital
Interface
Straight Binary or Twos Complement Input
Power Dissipation: 175 mW at 5 V, Sleep
Mode: 25 mW at 5 V
Package: 28-Pin SOIC and TSSOP
SOIC (DW) OR TSSOP (PW) PACKAGE
(TOP VIEW)
D11
D10
D9
D8
D7
D6
D5
D4
D3
D2
D1
D0
NC
NC
1
2
3
4
5
6
7
8
9
10
11
12
13
14
28
27
26
25
24
23
22
21
20
19
18
17
16
15
CLK
DVDD
DGND
MODE
AVDD
COMP2
IOUT1
IOUT2
AGND
COMP1
BIASJ
EXTIO
EXTLO
SLEEP
NC – No internal connection
description
The THS5661A is a 12-bit resolution digital-to-analog converter (DAC) specifically optimized for digital data
transmission in wired and wireless communication systems. The 12-bit DAC is a member of the CommsDAC
series of high-speed, low-power CMOS digital-to-analog converters. The CommsDAC family consists of pin
compatible 14-, 12-, 10-, and 8-bit DACs. All devices offer identical interface options, small outline package, and
pinout. The THS5661A offers superior ac and dc performance while supporting update rates up to 125 MSPS.
The THS5661A operates from an analog supply of 4.5 V to 5.5 V. Its inherent low power dissipation of 175 mW
ensures that the device is well-suited for portable and low-power applications. Lowering the full-scale current
output reduces the power dissipation without significantly degrading performance. The device features a
SLEEP mode, which reduces the standby power to approximately 25 mW, thereby optimizing the power
consumption for system needs.
The THS5661A is manufactured in Texas Instruments advanced high-speed mixed-signal CMOS process. A
current-source-array architecture combined with simultaneous switching shows excellent dynamic
performance. On-chip edge-triggered input latches and a 1.2 V temperature-compensated bandgap reference
provide a complete monolithic DAC solution. The digital supply range of 3 V to 5.5 V supports 3 V and 5 V CMOS
logic families. Minimum data input setup and hold times allow for easy interfacing with external logic. The
THS5661A supports both a straight binary and twos complement input word format, enabling flexible interfacing
with digital signal processors.
The THS5661A provides a nominal full-scale differential output current of 20 mA and >300 kΩ output
impedance, supporting both single-ended and differential applications. The output current can be directly fed
to the load (e.g., external resistor load or transformer), with no additional external output buffer required. An
accurate on-chip reference and control amplifier allows the user to adjust this output current from 20 mA down
to 2 mA, with no significant degradation of performance. This reduces power consumption and provides 20 dB
gain range control capabilities. Alternatively, an external reference voltage and control amplifier may be applied
in applications using a multiplying DAC. The output voltage compliance range is 1.25 V.
Please be aware that an important notice concerning availability, standard warranty, and use in critical applications of
Texas Instruments semiconductor products and disclaimers thereto appears at the end of this data sheet.
CommsDAC is a trademark of Texas Instruments Incorporated.
Copyright  1999, Texas Instruments Incorporated
PRODUCTION DATA information is current as of publication date.
Products conform to specifications per the terms of Texas Instruments
standard warranty. Production processing does not necessarily include
testing of all parameters.
POST OFFICE BOX 655303
• DALLAS, TEXAS 75265
1
THS5661A
12-BIT, 125 MSPS, CommsDAC
DIGITAL-TO-ANALOG CONVERTER
SLAS247 – NOVEMBER 1999
description (continued)
The THS5661A is available in both a 28-pin SOIC and TSSOP package. The device is characterized for
operation over the industrial temperature range of –40°C to 85°C.
AVAILABLE OPTIONS
PACKAGE
TA
28-TSSOP
(PW)
– 40°C to 85°C
28-SOIC
(DW)
THS5661AIPW
THS5661AIDW
functional block diagram
AVDD
C1
SLEEP
EXTLO
COMP1
0.1 µF
COMP2
0.1 µF
1.2 V
REF
IOUT1
1 nF
EXTIO
–
CEXT
BIASJ
0.1 µF
+
I BIAS
2 kΩ
Control
AMP
Current
Source
Array
50 Ω
Output
Current
Switches
IOUT2
RBIAS
DVDD
50 Ω
Logic
D[11:0]
Control
MODE
CLK
DGND
2
RLOAD
AGND
POST OFFICE BOX 655303
• DALLAS, TEXAS 75265
RLOAD
THS5661A
12-BIT, 125 MSPS, CommsDAC
DIGITAL-TO-ANALOG CONVERTER
SLAS247 – NOVEMBER 1999
Terminal Functions
TERMINAL
NAME
NO.
AGND
20
AVDD
BIASJ
I/O
DESCRIPTION
I
Analog ground return for the internal analog circuitry
24
I
Positive analog supply voltage (4.5 V to 5.5 V)
18
O
Full-scale output current bias
CLK
28
I
External clock input. Input data latched on rising edge of the clock.
COMP1
19
I
Compensation and decoupling node, requires a 0.1 µF capacitor to AVDD.
COMP2
23
I
Internal bias node, requires a 0.1 µF decoupling capacitor to AGND.
D[11:0]
[1:12]
I
Data bits 0 through 11.
D11 is most significant data bit (MSB), D0 is least significant data bit (LSB).
DGND
26
I
Digital ground return for the internal digital logic circuitry
DVDD
27
I
Positive digital supply voltage (3 V to 5.5 V)
EXTIO
17
I/O
Used as external reference input when internal reference is disabled (i.e., EXTLO = AVDD). Used as internal
reference output when EXTLO = AGND, requires a 0.1 µF decoupling capacitor to AGND when used as reference
output.
EXTLO
16
O
Internal reference ground. Connect to AVDD to disable the internal reference source.
IOUT1
22
O
DAC current output. Full scale when all input bits are set 1
IOUT2
21
O
Complementary DAC current output. Full scale when all input bits are 0
MODE
25
I
Mode select. Internal pulldown. Mode 0 is selected if this pin is left floating or connected to DGND. See
timing diagram.
[13:14]
N
No connection
15
I
Asynchronous hardware power down input. Active high. Internal pulldown. Requires 5 µs to power down but 3 ms
to power up.
NC
SLEEP
absolute maximum ratings over operating free-air temperature (unless otherwise noted)†
Supply voltage range, AVDD (see Note 1) . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . –0.3 V to 6.5 V
DVDD (see Note 2) . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . –0.3 V to 6.5 V
Voltage between AGND and DGND . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . –0.3 V to 0.5 V
Supply voltage range, AVDD to DVDD . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . –6.5 V to 6.5 V
CLK, SLEEP, MODE (see Note 2) . . . . . . . . . . . . . . . . . . . . . . –0.3 V to DVDD + 0.3 V
Digital input D11–D0 (see Note 2) . . . . . . . . . . . . . . . . . . . . . –0.3 V to DVDD + 0.3 V
IOUT1, IOUT2 (see Note 1) . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . –1 V to AVDD + 0.3 V
COMP1, COMP2 (see Note 1) . . . . . . . . . . . . . . . . . . . . . . . . . –0.3 V to AVDD + 0.3 V
EXTIO, BIASJ (see Note 1) . . . . . . . . . . . . . . . . . . . . . . . . . . . . –0.3 V to AVDD + 0.3 V
EXTLO (see Note 1) . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . –0.3 V to 0.3 V
Peak input current (any input) . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 20 mA
Peak total input current (all inputs) . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . –30 mA
Operating free-air temperature range, TA: THS5661AI . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . –40°C to 85°C
Storage temperature range . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . – 65°C to 150°C
Lead temperature 1,6 mm (1/16 inch) from the case for 10 seconds . . . . . . . . . . . . . . . . . . . . . . . . . . . . 260°C
† Stresses beyond those listed under “absolute maximum ratings” may cause permanent damage to the device. These are stress ratings only, and
functional operation of the device at these or any other conditions beyond those indicated under “recommended operating conditions” is not
implied. Exposure to absolute-maximum-rated conditions for extended periods may affect device reliability.
NOTES: 1. Measured with respect to AGND.
2. Measured with respect to DGND.
POST OFFICE BOX 655303
• DALLAS, TEXAS 75265
3
THS5661A
12-BIT, 125 MSPS, CommsDAC
DIGITAL-TO-ANALOG CONVERTER
SLAS247 – NOVEMBER 1999
electrical characteristics over recommended operating free-air temperature range, AVDD = 5 V,
DVDD = 5 V, IOUTFS = 20 mA (unless otherwise noted)
dc specifications
PARAMETER
TEST CONDITIONS
Resolution
MIN
TYP
MAX
12
UNIT
Bits
DC accuracy†
INL
Integral nonlinearity
DNL
Differential nonlinearity
Monotonicity
–4
TA = –40°C
40°C to 85°C
–2
At 11-bit level
±0.75
4
LSB
±0.5
2
LSB
Monotonic
Analog output
Offset error
Gain error
0.02
Without internal reference
2.3
With internal reference
1.3
Full scale output current‡
Output compliance range
AVDD = 5 V,
IOUTFS = 20 mA
%FSR
%FSR
2
20
–1
1.25
Output resistance
Output capacitance
mA
V
300
kΩ
5
pF
Reference output
Reference voltage
1.18
Reference output current§
1.22
1.32
100
V
nA
Reference input
VEXTIO
Input voltage range
0.1
Input resistance
Small signal bandwidth¶
Without CCOMP1
Input capacitance
1.25
V
1
MΩ
1.3
MHz
100
pF
Temperature coefficients
Offset drift
Gain drift
0
±40
Without internal reference
ppm
m of
FSR/°C
±120
With internal reference
±35
Reference voltage drift
Power supply
AVDD
DVDD
IAVDD
IDVDD
AVDD
DVDD
Analog supply voltage
4.5
Digital supply voltage
Analog supply current
Sleep mode supply current
Digital supply current#
Sleep mode
Power dissipation||
AVDD = 5 V, DVDD = 5 V,
IOUTFS = 20 mA
5.5
V
5.5
V
25
30
mA
3
5
mA
5
6
mA
175
mW
±0.4
Power supply rejection ratio
%FSR/V
±0.025
Operating range
† Measured at IOUT1 in virtual ground configuration.
‡ Nominal full-scale current IOUTFS equals 32X the IBIAS current.
§ Use an external buffer amplifier with high impedance input to drive any external load.
¶ Reference bandwidth is a function of external cap at COMP1 pin and signal level.
# Measured at fCLK = 50 MSPS and fOUT= 1 MHz.
|| Measured for 50 Ω RLOAD at IOUT1 and IOUT2, fCLK = 50 MSPS and fOUT = 20 MHz.
Specifications subject to change
4
5
3
POST OFFICE BOX 655303
• DALLAS, TEXAS 75265
–40
85
°C
THS5661A
12-BIT, 125 MSPS, CommsDAC
DIGITAL-TO-ANALOG CONVERTER
SLAS247 – NOVEMBER 1999
electrical characteristics over recommended operating free-air temperature range, AVDD = 5 V,
DVDD = 5 V, IOUTFS = 20 mA, differential transformer coupled output, 50 Ω doubly terminated load
(unless otherwise noted)
ac specifications
PARAMETER
TEST CONDITIONS
MIN
TYP
100
125
70
100
MAX
UNIT
Analog output
fCLK
Maximum output update rate
ts(DAC)
tpd
Output settling time to 0.1%†
GE
Output propagation delay
Glitch energy‡
tr(IOUT)
tf(IOUT)
Output rise time 10% to 90%†
Output fall time 90% to 10%†
Output noise
DVDD = 4.5 V to 5.5 V
DVDD = 3 V to 3.6 V
Worst case LSB transition (code 2047 – code 2048)
IOUTFS = 20 mA
IOUTFS = 2 mA
MSPS
35
ns
1
ns
5
pV-s
1
ns
1
ns
15
pA/√HZ
10
AC linearity
THD
Total harmonic distortion
fCLK = 25 MSPS, fOUT = 1 MHz, TA = 25°C
fCLK = 50 MSPS, fOUT = 1 MHz, TA = –40°C to 85°C
–78
fCLK = 50 MSPS, fOUT = 2 MHz, TA = 25°C
fCLK = 100 MSPS, fOUT = 2 MHz, TA = 25°C
–75
fCLK = 25 MSPS, fOUT = 1 MHz, TA = 25°C
fCLK = 50 MSPS, fOUT= 1 MHz, TA = –40°C to 85°C
Spurious free dynamic range to
Nyquist
SFDR
Spurious free dynamic range
within a window
–77
–66
dBc
–75
82
68
fCLK = 50 MSPS, fOUT = 1 MHz, TA = 25°C
fCLK = 50 MSPS, fOUT = 2.51 MHz, TA = 25°C
79
fCLK = 50 MSPS, fOUT = 5.02 MHz, TA = 25°C
fCLK = 50 MSPS, fOUT = 20.2 MHz, TA = 25°C
69
fCLK = 100 MSPS, fOUT = 5.04 MHz, TA = 25°C
fCLK = 100 MSPS, fOUT = 20.2 MHz, TA = 25°C
68
dBc
59
dBc
fCLK = 100 MSPS, fOUT = 40.4 MHz, TA = 25°C
fCLK = 50 MSPS, fOUT = 1 MHz, TA= 25°C,1 MHz span
60
dBc
fCLK = 50 MSPS, fOUT = 5.02 MHz, 2 MHz span
fCLK = 100 MSPS, fOUT= 5.04 MHz, 4 MHz span
88
75
dBc
61
89
dBc
89
† Measured single ended into 50 Ω load at IOUT1.
‡ Single-ended output IOUT1, 50 Ω doubly terminated load.
POST OFFICE BOX 655303
• DALLAS, TEXAS 75265
5
THS5661A
12-BIT, 125 MSPS, CommsDAC
DIGITAL-TO-ANALOG CONVERTER
SLAS247 – NOVEMBER 1999
electrical characteristics over recommended operating free-air temperature range, AVDD = 5 V,
DVDD = 5 V, IOUTFS = 20 mA (unless otherwise noted)
digital specifications
PARAMETER
TEST CONDITIONS
MIN
TYP
MAX
UNIT
Interface
DVDD = 5 V
3.5
5
DVDD = 3.3 V
2.1
3.3
VIH
High level input voltage
High-level
V
VIL
Low level input voltage
Low-level
IIH
IIL
High-level input current
DVDD = 3 V to 5.5 V
–10
10
µA
Low-level input current
DVDD = 3 V to 5.5 V
–10
10
µA
Input capacitance
1
5
pF
tsu(D)
th(D)
Input setup time
1
ns
Input hold time
1
ns
tw(LPH)
td(D)
Input latch pulse high time
4
DVDD = 5 V
0
1.3
DVDD = 3.3 V
0
0.9
V
Timing
Digital delay time
Specifications subject to change
6
ns
1
POST OFFICE BOX 655303
• DALLAS, TEXAS 75265
clk
THS5661A
12-BIT, 125 MSPS, CommsDAC
DIGITAL-TO-ANALOG CONVERTER
SLAS247 – NOVEMBER 1999
TYPICAL CHARACTERISTICS†
SPURIOUS FREE DYNAMIC RANGE
vs
OUTPUT FREQUENCY AT 0 dBFS
SPURIOUS FREE DYNAMIC RANGE
vs
OUTPUT FREQUENCY AT 5 MSPS
90
90
DVDD = 5 V
84
84
fCLK = 25 MSPS
78
0 dBFS
fCLK = 50 MSPS
72
SFDR – dBc
SFDR – dBc
DVDD = 5 V
fCLK = 5 MSPS
fCLK = 70 MSPS
66
fCLK = 100 MSPS
– 6 dBFS
78
72
– 12 dBFS
60
66
fCLK = 125 MSPS
54
48
0
10
20
30
40
60
50
0
0.5
Fout – Output Frequency – MHz
1.0
1.5
2.0
2.5
Fout – Output Frequency – MHz
Figure 1
Figure 2
SPURIOUS FREE DYNAMIC RANGE
vs
OUTPUT FREQUENCY AT 25 MSPS
SPURIOUS FREE DYNAMIC RANGE
vs
OUTPUT FREQUENCY AT 50 MSPS
90
78
DVDD = 5 V
DVDD = 5 V
– 6 dBFS
84
72
78
72
SFDR – dBc
SFDR – dBc
0 dBFS
– 6 dBFS
– 12 dBFS
66
66
– 12 dBFS
60
0 dBFS
54
60
0
2
4
6
8
10
12
48
0
Fout – Output Frequency – MHz
5
10
15
20
25
Fout – Output Frequency – MHz
Figure 3
Figure 4
† AVDD = 5 V, IOUTFS = 20 mA, differential transformer coupled output, 50 Ω doubly terminated load, TA = 25°C (unless otherwise
noted.)
POST OFFICE BOX 655303
• DALLAS, TEXAS 75265
7
THS5661A
12-BIT, 125 MSPS, CommsDAC
DIGITAL-TO-ANALOG CONVERTER
SLAS247 – NOVEMBER 1999
TYPICAL CHARACTERISTICS†
SPURIOUS FREE DYNAMIC RANGE
vs
OUTPUT FREQUENCY AT 70 MSPS
SPURIOUS FREE DYNAMIC RANGE
vs
OUTPUT FREQUENCY AT 100 MSPS
78
78
DVDD = 5 V
DVDD = 5 V
– 6 dBFS
72
72
SFDR – dBc
– 6 dBFS
SFDR – dBc
66
– 12 dBFS
60
0 dBFS
66
– 12 dBFS
60
0 dBFS
54
54
48
0
10
20
30
48
40
0
10
Fout – Output Frequency – MHz
20
30
40
50
Fout – Output Frequency – MHz
Figure 5
Figure 6
SPURIOUS FREE DYNAMIC RANGE
vs
OUTPUT FREQUENCY AT 0 dBFS
SPURIOUS FREE DYNAMIC RANGE
vs
OUTPUT FREQUENCY AT 125 MSPS
90
78
DVDD = 3.3 V
DVDD = 5 V
84
fCLK = 5 MSPS
– 6 dBFS
72
78
SFDR – dBc
SFDR – dBc
– 12 dBFS
66
0 dBFS
60
fCLK = 25 MSPS
72
fCLK = 50 MSPS
66
fCLK = 70 MSPS
60
54
54
fCLK = 100 MSPS
48
42
48
0
10
20
30
40
50
0
10
20
30
Fout – Output Frequency – MHz
Fout – Output Frequency – MHz
Figure 7
Figure 8
† AVDD = 5 V, IOUTFS = 20 mA, differential transformer coupled output, 50 Ω doubly terminated load, TA = 25°C (unless otherwise
noted.)
8
POST OFFICE BOX 655303
• DALLAS, TEXAS 75265
40
THS5661A
12-BIT, 125 MSPS, CommsDAC
DIGITAL-TO-ANALOG CONVERTER
SLAS247 – NOVEMBER 1999
TYPICAL CHARACTERISTICS†
SPURIOUS FREE DYNAMIC RANGE
vs
OUTPUT FREQUENCY AT 5 MSPS
SPURIOUS FREE DYNAMIC RANGE
vs
OUTPUT FREQUENCY AT 25 MSPS
90
90
DVDD = 3.3 V
DVDD = 3.3 V
84
84
0 dBFS
SFDR – dBc
SFDR – dBc
0 dBFS
78
– 6 dBFS
72
– 12 dBFS
78
72
– 12 dBFS
66
– 6 dBFS
66
60
0
0.5
1.0
1.5
2.0
60
2.5
0
2
Fout – Output Frequency – MHz
4
6
8
10
12
Fout – Output Frequency – MHz
Figure 9
Figure 10
SPURIOUS FREE DYNAMIC RANGE
vs
OUTPUT FREQUENCY AT 50 MSPS
SPURIOUS FREE DYNAMIC RANGE
vs
OUTPUT FREQUENCY AT 70 MSPS
78
78
DVDD = 3.3 V
DVDD = 3.3 V
0 dBFS
72
72
– 6 dBFS
– 12 dBFS
SFDR – dBc
SFDR – dBc
– 6 dBFS
66
60
66
0 dBFS
60
– 12 dBFS
54
54
48
0
5
10
15
20
25
48
0
Fout – Output Frequency – MHz
10
20
30
40
Fout – Output Frequency – MHz
Figure 11
Figure 12
† AVDD = 5 V, IOUTFS = 20 mA, differential transformer coupled output, 50 Ω doubly terminated load, TA = 25°C (unless otherwise
noted.)
POST OFFICE BOX 655303
• DALLAS, TEXAS 75265
9
THS5661A
12-BIT, 125 MSPS, CommsDAC
DIGITAL-TO-ANALOG CONVERTER
SLAS247 – NOVEMBER 1999
TYPICAL CHARACTERISTICS†
SPURIOUS FREE DYNAMIC RANGE
vs
AOUT AT FOUT = FCLOCK/5
SPURIOUS FREE DYNAMIC RANGE
vs
AOUT AT FOUT = FCLOCK/11
78
78
DVDD = 5 V
DVDD = 5 V
4.55 MHz @ 50 MSPS
72
72
5 MHz @ 25 MSPS
SFDR – dBc
SFDR – dBc
66
66
6.36 MHz @ 70 MSPS
60
10 MHz @ 50 MSPS
60
54
9.1 MHz @ 100 MSPS
54
48
14 MHz @ 70 MSPS
48
–27 –24 –21 –18 –15 –12
20 MHz @ 100 MSPS
–9
–6
–3
42
–27 –24 –21 –18 –15 –12
0
–9
0
Figure 14
Figure 13
TOTAL HARMONIC DISTORTION
vs
CLOCK FREQUENCY AT FOUT = 2 MHz
DUAL TONE SPURIOUS FREE DYNAMIC RANGE
vs
AOUT AT FOUT = FCLOCK/7
–66
78
DVDD = 5 V
DVDD = 5 V
0.675/0.725 MHz @ 5 MSPS
–72
3.38/3.63 MHz @ 25 MSPS
2nd Harmonic
66
THD – dBc
SFDR – dBc
–3
Aout – dBFS
Aout – dBFS
72
–6
60
13.5/14.5 MHz
@ 100 MSPS
54
–78
3rd Harmonic
–84
4th Harmonic
6.75/7.25 MHz @ 50 MSPS
9.67/10.43 MHz @ 70 MSPS
48
–27 –24 –21 –18 –15 –12
–9
–6
–90
–3
0
0
20
40
60
80
100
Fclock –Clock Frequency – MSPS
Aout – dBFS
Figure 16
Figure 15
† AVDD = 5 V, IOUTFS = 20 mA, differential transformer coupled output, 50 Ω doubly terminated load, TA = 25°C (unless otherwise
noted.)
10
POST OFFICE BOX 655303
• DALLAS, TEXAS 75265
120
THS5661A
12-BIT, 125 MSPS, CommsDAC
DIGITAL-TO-ANALOG CONVERTER
SLAS247 – NOVEMBER 1999
TYPICAL CHARACTERISTICS†
SPURIOUS FREE DYNAMIC RANGE
vs
OUTPUT FREQUENCY AT 100 MSPS
SPURIOUS FREE DYNAMIC RANGE
vs
FULL-SCALE OUTPUT CURRENT AT 100 MSPS
84
78
DVDD = 5 V
DVDD = 5 V
78
Differential @ –6 dBFS
72
72
Differential @ 0 dBFS
SFDR – dBc
SFDR – dBc
Fout = 2.5 MHz
66
Fout = 10 MHz
60
66
60
Single-ended @ 0 dBFS
54
48
54
Fout = 28.6 MHz
Fout = 40 MHz
Single-ended
@ –6 dBFS
42
36
48
2
4
6
8
10
12
14
16
18
0
20
5
10
15
20
25
30
35
40
45
50
Fout Output Frequency– MHz
IOUTFS –Full Scale Output Current – mA
Figure 18
Figure 17
SPURIOUS FREE DYNAMIC RANGE
vs
TEMPERATURE AT 70 MSPS
78
DVDD = 5 V
Fout = 2 MHz
SFDR – dBc
72
Fout = 10 MHz
66
60
Fout = 25 MHz
54
48
–40
–20
0
20
40
60
80
TA Temperature– °C
Figure 19
† AVDD = 5 V, IOUTFS = 20 mA, differential transformer coupled output, 50 Ω doubly terminated load, TA = 25°C (unless otherwise
noted.)
POST OFFICE BOX 655303
• DALLAS, TEXAS 75265
11
THS5661A
12-BIT, 125 MSPS, CommsDAC
DIGITAL-TO-ANALOG CONVERTER
SLAS247 – NOVEMBER 1999
TYPICAL CHARACTERISTICS†
INL – Integral Nonlinearity – LSB
INTEGRAL NONLINEARITY
1.0
0.5
0.0
–0.5
–1
0
512
1024
1536
2048
2560
3072
3584
4096
3072
3584
4096
Code
DNL – Differential Nonlinearity – LSB
Figure 20
DIFFERENTIAL NONLINEARITY
0.50
0.25
0.00
–0.25
–0.5
0
512
1024
1536
2048
2560
Code
Figure 21
† AVDD = 5 V, IOUTFS = 20 mA, differential transformer coupled output, 50 Ω doubly terminated load, TA = 25°C (unless otherwise
noted.)
12
POST OFFICE BOX 655303
• DALLAS, TEXAS 75265
THS5661A
12-BIT, 125 MSPS, CommsDAC
DIGITAL-TO-ANALOG CONVERTER
SLAS247 – NOVEMBER 1999
TYPICAL CHARACTERISTICS†
SINGLE-TONE OUTPUT SPECTRUM
0
Amplitude – dBm
–10
Fout = 5 MHz at
Fclock = 50 MSPS,
DVDD = 5 V
–20
–30
–40
–50
–60
–70
–80
–90
–100
0
5
10
15
20
25
Frequency – MHz
Figure 22
SINGLE-TONE OUTPUT SPECTRUM
0
Amplitude – dBm
–10
Fout = 10 MHz at
Fclock = 100 MSPS,
DVDD = 5 V
–20
–30
–40
–50
–60
–70
–80
–90
–100
0
10
20
30
40
50
40
50
Frequency – MHz
Figure 23
DUAL-TONE OUTPUT SPECTRUM
0
Fclock = 100 MSPS
Fout1 = 13.2 MHz,
Fout2 = 14.2 MHz,
DVDD = 5 V
–10
Amplitude – dBm
–20
–30
–40
–50
–60
–70
–80
–90
–100
0
10
20
30
Frequency – MHz
Figure 24
† AVDD = 5 V, IOUTFS = 20 mA, differential transformer coupled output, 50 Ω doubly terminated load, TA = 25°C (unless otherwise
noted.)
POST OFFICE BOX 655303
• DALLAS, TEXAS 75265
13
THS5661A
12-BIT, 125 MSPS, CommsDAC
DIGITAL-TO-ANALOG CONVERTER
SLAS247 – NOVEMBER 1999
TYPICAL CHARACTERISTICS†
FOUR-TONE OUTPUT SPECTRUM
0
Fclock = 50 MSPS
Fout1 = 6.25 MHz,
Fout2 = 6.75 MHz,
Fout3 = 7.25 MHz,
Fout4 = 7.75 MHz,
DVDD = 5 V
–10
Amplitude – dBm
–20
–30
–40
–50
–60
–70
–80
–90
–100
0
5
10
15
20
25
Frequency – MHz
Figure 25
† AVDD = 5 V, IOUTFS = 20 mA, differential transformer coupled output, 50 Ω doubly terminated load, TA = 25°C (unless otherwise
noted.)
14
POST OFFICE BOX 655303
• DALLAS, TEXAS 75265
THS5661A
12-BIT, 125 MSPS, CommsDAC
DIGITAL-TO-ANALOG CONVERTER
SLAS247 – NOVEMBER 1999
TYPICAL CHARACTERISTICS†
ANALOG SUPPLY CURRENT
vs
FULL-SCALE OUTPUT CURRENT
DIGITAL SUPPLY CURRENT
vs
RATIO (Fclock/Fout) AT DVDD = 5 V
30
25
I(DVDD) – Supply Current – mA
I(AVDD) – Supply Current – mA
100 MSPS
25
20
15
10
5
0
2
4
6
8
10
12
14
16
18
20
70 MSPS
15
50 MSPS
10
25 MSPS
5
5 MSPS
0
20
0
0.1
IOUTFS – Full-Scale Output Current – mA
0.2
0.3
0.4
0.5
Ratio – (Fclock/Fout)
Figure 26
Figure 27
DIGITAL SUPPLY CURRENT
vs
RATIO (Fclock/Fout) AT DVDD = 3.3 V
I(DV ) – Supply Current – mA
DD
10
8
70 MSPS
6
50 MSPS
4
25 MSPS
2
5 MSPS
0
0
0.1
0.2
0.3
0.4
0.5
Ratio – (Fclock/Fout)
Figure 28
† AVDD = 5 V, IOUTFS = 20 mA, differential transformer coupled output, 50 Ω doubly terminated load, TA = 25°C (unless otherwise
noted.)
POST OFFICE BOX 655303
• DALLAS, TEXAS 75265
15
THS5661A
12-BIT, 125 MSPS, CommsDAC
DIGITAL-TO-ANALOG CONVERTER
SLAS247 – NOVEMBER 1999
APPLICATION INFORMATION
The THS5661A architecture is based on current steering, combining high update rates with low power
consumption. The CMOS device consists of a segmented array of PMOS transistor current sources, which are
capable of delivering a full-scale current up to 20 mA. High-speed differential current switches direct the current
of each current source to either one of the output nodes, IOUT1 or IOUT2. The complementary output currents
thus enable differential operation, canceling out common mode noise sources (on-chip and PCB noise), dc
offsets, even order distortion components, and increasing signal output power by a factor of two. Major
advantages of the segmented architecture are minimum glitch energy, excellent DNL, and very good dynamic
performance. The DAC’s high output impedance of >300 kΩ and fast switching result in excellent dynamic
linearity (spurious free dynamic range SFDR).
The full-scale output current is set using an external resistor RBIAS in combination with an on-chip bandgap
voltage reference source (1.2 V) and control amplifier. The current IBIAS through resistor RBIAS is mirrored
internally to provide a full-scale output current equal to 32 times IBIAS. The full-scale current can be adjusted
from 20 mA down to 2 mA.
data interface and timing
The THS5661A comprises separate analog and digital supplies, i.e. AVDD and DVDD. The digital supply voltage
can be set from 5.5 V down to 3 V, thus enabling flexible interfacing with external logic. The THS5661A provides
two operating modes, as shown in Table 1. Mode 0 (mode pin connected to DGND) supports a straight binary
input data word format, whereas mode 1 (mode pin connected to DVDD) sets a twos complement input
configuration.
Figure 29 shows the timing diagram. Internal edge-triggered flip-flops latch the input word on the rising edge
of the input clock. The THS5661A provides for minimum setup and hold times (> 1 ns), allowing for noncritical
external interface timing. Conversion latency is one clock cycle for both modes. The clock duty cycle can be
chosen arbitrarily under the timing constraints listed in the digital specifications table. However, a 50% duty cycle
will give optimum dynamic performance. Figure 30 shows a schematic of the equivalent digital inputs of the
THS5661A, valid for pins D11–D0, SLEEP, and CLK. The digital inputs are CMOS-compatible with logic
thresholds of DVDD/2 ±20%. Since the THS5661A is capable of being updated up to 125 MSPS, the quality of
the clock and data input signals are important in achieving the optimum performance. The drivers of the digital
data interface circuitry should be specified to meet the minimum setup and hold times of the THS5661A, as well
as its required min/max input logic level thresholds. Typically, the selection of the slowest logic family that
satisfies the above conditions will result in the lowest data feed-through and noise. Additionally, operating the
THS5661A with reduced logic swings and a corresponding digital supply (DVDD) will reduce data feed-through.
Note that the update rate is limited to 70 MSPS for a digital supply voltage DVDD of 3 V to 3.6 V.
16
POST OFFICE BOX 655303
• DALLAS, TEXAS 75265
THS5661A
12-BIT, 125 MSPS, CommsDAC
DIGITAL-TO-ANALOG CONVERTER
SLAS247 – NOVEMBER 1999
APPLICATION INFORMATION
D[11:0]
Valid Data
ts(DAC)
tpd
0.1%
DAC
90%
50%
Output
10%
(IOUT1 or
IOUT2)
0.1%
tr(IOUT)
th(D)
tsu(D)
td(D)
1/fCLK
CLK
50%
50%
50%
50%
50%
50%
tw(LPH)
Figure 29. Timing Diagram
Table 1. Input Interface Modes
MODE 0
MODE 1
FUNCTION/MODE
MODE PIN CONNECTED TO
DGND
MODE PIN CONNECTED TO
DVDD
Input code format
Binary
Twos complement
DVDD
External
Digital in
Internal
Digital in
Figure 30. Digital Equivalent Input
POST OFFICE BOX 655303
• DALLAS, TEXAS 75265
17
THS5661A
12-BIT, 125 MSPS, CommsDAC
DIGITAL-TO-ANALOG CONVERTER
SLAS247 – NOVEMBER 1999
APPLICATION INFORMATION
DAC transfer function
The THS5661A delivers complementary output currents IOUT1 and IOUT2. Output current IOUT1 equals the
approximate full-scale output current when all input bits are set high in mode 0 (straight binary input), i.e. the
binary input word has the decimal representation 4095. For mode 1, the MSB is inverted (twos complement input
format). Full-scale output current will flow through terminal IOUT2 when all input bits are set low (mode 0,
straight binary input). The relation between IOUT1 and IOUT2 can thus be expressed as:
IOUT1
+ IOUT * IOUT2
FS
where IOUTFS is the full-scale output current. The output currents can be expressed as:
IOUT1
+ IOUT
FS
CODE
4096
IOUT2
+ IOUT
FS
(4095 CODE)
4096
*
where CODE is the decimal representation of the DAC data input word. Output currents IOUT1 and IOUT2 drive
resistor loads RLOAD or a transformer with equivalent input load resistance RLOAD. This would translate into
single-ended voltages VOUT1 and VOUT2 at terminal IOUT1 and IOUT2, respectively, of:
VOUT1
+ IOUT1
R LOAD
+ CODE
4096
VOUT2
+ IOUT2
R LOAD
+ (4095–CODE)
4096
IOUT FS
R LOAD
IOUT FS
R LOAD
The differential output voltage VOUTDIFF can thus be expressed as:
VOUT DIFF
+ VOUT1–VOUT2 + (2CODE–4095)
4096
IOUT FS
R LOAD
The latter equation shows that applying the differential output will result in doubling of the signal power delivered
to the load. Since the output currents of IOUT1 and IOUT2 are complementary, they become additive when
processed differentially. Care should be taken not to exceed the compliance voltages at node IOUT1 and
IOUT2, which would lead to increased signal distortion.
18
POST OFFICE BOX 655303
• DALLAS, TEXAS 75265
THS5661A
12-BIT, 125 MSPS, CommsDAC
DIGITAL-TO-ANALOG CONVERTER
SLAS247 – NOVEMBER 1999
APPLICATION INFORMATION
reference operation
The THS5661A comprises a bandgap reference and control amplifier for biasing the full-scale output current.
The full-scale output current is set by applying an external resistor RBIAS. The bias current IBIAS through resistor
RBIAS is defined by the on-chip bandgap reference voltage and control amplifier. The full-scale output current
equals 32 times this bias current. The full-scale output current IOUTFS can thus be expressed as:
IOUT FS
+ 32
I BIAS
+ 32 R V
EXTIO
BIAS
where VEXTIO is the voltage at terminal EXTIO. The bandgap reference voltage delivers an accurate voltage
of 1.2 V. This reference is active when terminal EXTLO is connected to AGND. An external decoupling capacitor
CEXT of 0.1 µF should be connected externally to terminal EXTIO for compensation. The bandgap reference
can additionally be used for external reference operation. In that case, an external buffer with high impedance
input should be applied in order to limit the bandgap load current to a maximum of 100 nA. The internal reference
can be disabled and overridden by an external reference by connecting EXTLO to AVDD. Capacitor CEXT may
hence be omitted. Terminal EXTIO thus serves as either input or output node.
The full-scale output current can be adjusted from 20 mA down to 2 mA by varying resistor RBIAS or changing
the externally applied reference voltage. The internal control amplifier has a wide input range, supporting the
full-scale output current range of 20 dB. The bandwidth of the internal control amplifier is defined by the internal
1 nF compensation capacitor at pin COMP1 and the external compensation capacitor C1. The relatively weak
internal control amplifier may be overridden by an externally applied amplifier with sufficient drive for the internal
1 nF load, as shown in Figure 31. This provides the user with more flexibility and higher bandwidths, which are
specifically attractive for gain control and multiplying DAC applications. Pin SLEEP should be connected to
AGND or left disconnected when an external control amplifier is used.
EXT Reference
Voltage
–
External
Control AMP
THS4041
+
AGND
AVDD
SLEEP
AVDD
EXTLO
EXTIO
BIASJ
1.2 V
REF
COMP1
1 nF
AVDD
Current Source Array
–
REF AMP
+
Internal
Control AMP
R EXT
IOUT1 or IOUT2
Figure 31. Bypassing the Internal Reference and Control Amplifier
POST OFFICE BOX 655303
• DALLAS, TEXAS 75265
19
THS5661A
12-BIT, 125 MSPS, CommsDAC
DIGITAL-TO-ANALOG CONVERTER
SLAS247 – NOVEMBER 1999
APPLICATION INFORMATION
analog current outputs
Figure 32 shows a simplified schematic of the current source array output with corresponding switches.
Differential PMOS switches direct the current of each individual PMOS current source to either the positive
output node IOUT1 or its complementary negative output node IOUT2. The output impedance is determined
by the stack of the current sources and differential switches, and is typically >300 kΩ in parallel with an output
capacitance of 5 pF.
Output nodes IOUT1 and IOUT2 have a negative compliance voltage of –1 V, determined by the CMOS process.
Beyond this value, transistor breakdown may occur, resulting in reduced reliability of the THS5661A device. The
positive output compliance depends on the full-scale output current IOUTFS and positive supply voltage AVDD.
The positive output compliance equals 1.25 V for AVDD = 5 V and IOUTFS = 20 mA. Exceeding the positive
compliance voltage adversely affects distortion performance and integral nonlinearity. The optimum distortion
performance for a single-ended or differential output is achieved when the maximum full-scale signal at IOUT1
and IOUT2 does not exceed 0.5 V (e.g. when applying a 50 Ω doubly terminated load for 20 mA full-scale output
current). Applications requiring the THS5661A output (i.e., OUT1 and/or OUT2) to extend its output compliance
should size RLOAD accordingly.
AVDD
Current
Sources
Switches
IOUT1
IOUT2
RL
Current Source Array
RL
Figure 32. Equivalent Analog Current Output
Figure 33(a) shows the typical differential output configuration with two external matched resistor loads. The
nominal resistor load of 50 Ω will give a differential output swing of 2 VPP when applying a 20 mA full-scale output
current. The output impedance of the THS5661A depends slightly on the output voltage at nodes IOUT1 and
IOUT2. Consequently, for optimum dc integral nonlinearity, the configuration of Figure 33(b) should be chosen.
In this I–V configuration, terminal IOUT1 is kept at virtual ground by the inverting operational amplifier. The
complementary output should be connected to ground to provide a dc current path for the current sources
switched to IOUT2. Note that the INL/DNL specifications for the THS5661A are measured with IOUT1
maintained at virtual ground. The amplifier’s maximum output swing and the DAC’s full-scale output current
determine the value of the feedback resistor RFB. Capacitor CFB filters the steep edges of the THS5661A current
output, thereby reducing the operational amplifier slew-rate requirements. In this configuration, the op amp
should operate on a dual supply voltage due to its positive and negative output swing. Node IOUT1 should be
selected if a single-ended unipolar output is desirable.
20
POST OFFICE BOX 655303
• DALLAS, TEXAS 75265
THS5661A
12-BIT, 125 MSPS, CommsDAC
DIGITAL-TO-ANALOG CONVERTER
SLAS247 – NOVEMBER 1999
APPLICATION INFORMATION
CFB
RFB
50 Ω
IOUT1
100 Ω
–
IOUT1
+)
+)
VO
+
VO
–)
IOUT2
IOUT2
THS4001
THS4011
50 Ω
(a)
–)
(b)
Figure 33. Differential and Single-Ended Output Configuration
The THS5661A can be easily configured to drive a doubly terminated 50 Ω cable. Figure 34(a) shows the
single-ended output configuration, where the output current IOUT1 flows into an equivalent load resistance of
25 Ω. Node IOUT2 should be connected to ground or terminated with a resistor of 25 Ω. Differential-to-single
conversion (e.g., for measurement purposes) can be performed using a properly selected RF transformer, as
shown in Figure 34(b). This configuration provides maximum rejection of common-mode noise sources and
even order distortion components, thereby doubling the power to the output. The center tap on the primary side
of the transformer is connected to AGND, enabling a dc current flow for both IOUT1 and IOUT2. Note that the
ac performance of the THS5661A is optimum and specified using this differential transformer coupled output,
limiting the voltage swing at IOUT1 and IOUT2 to ±0.5 V.
50 Ω
50 Ω
1:1
VO
VO
IOUT1
IOUT1
100 Ω
50 Ω
50 Ω
IOUT2
IOUT2
25 Ω
50 Ω
(a)
(b)
Figure 34. Driving a Doubly Terminated 50 Ω Cable
POST OFFICE BOX 655303
• DALLAS, TEXAS 75265
21
THS5661A
12-BIT, 125 MSPS, CommsDAC
DIGITAL-TO-ANALOG CONVERTER
SLAS247 – NOVEMBER 1999
APPLICATION INFORMATION
sleep mode
The THS5661A features a power-down mode that turns off the output current and reduces the supply current
to less than 5 mA over the analog supply range of 4.5 V to 5.5 V and temperature range. The power-down mode
is activated by applying a logic level 1 to the SLEEP pin (e.g., by connecting pin SLEEP to AVDD). An internal
pulldown circuit at node SLEEP ensures that the THS5661A is enabled if the input is left disconnected.
Power-up and power-down activation times depend on the value of external capacitor at node SLEEP. For a
nominal capacitor value of 0.1 µF power down takes less than 5 µs, and approximately 3 ms to power backup.
The SLEEP mode should not be used when an external control amplifier is used, as shown in Figure 25.
definitions of specifications and terminology
integral nonlinearity (INL)
The relative accuracy or integral nonlinearity (INL), sometimes referred to as linearity error, is the maximum
deviation of the output from the line between zero and full scale excluding the effects of zero code and full-scale
errors.
differential nonlinearity (DNL)
The differential nonlinearity (DNL), sometimes referred to as differential error, is the difference between the
measured and ideal 1 LSB amplitude change of any two adjacent codes. Monotonic means the output voltage
changes in the same direction (or remains constant) as a change in the digital input code.
offset error
Offset error is defined as the deviation of the output current from the ideal of zero at a digital input value of 0.
gain error
Gain error is the error in slope of the DAC transfer function.
signal-to-noise ratio + distortion (S/N+D or SINAD)
S/N+D or SINAD is the ratio of the rms value of the output signal to the rms sum of all other spectral components
below the Nyquist frequency, including harmonics but excluding dc. The value for S/N+D is expressed in
decibels.
spurious free dynamic range (SFDR)
SFDR is the difference between the rms value of the output signal and the rms value of the largest spurious
signal within a specified bandwidth. The value for SFDR is expressed in decibels.
total harmonic distortion (THD)
THD is the ratio of the rms sum of the first six harmonic components to the rms value of the fundamental signal
and is expressed in decibels.
output compliance range
The maximum and minimum allowable voltage of the output of the DAC, beyond which either saturation of the
output stage or breakdown may occur.
settling time
The time required for the output to settle within a specified error band.
glitch energy
The time integral of the analog value of the glitch transient.
22
POST OFFICE BOX 655303
• DALLAS, TEXAS 75265
THS5661A
12-BIT, 125 MSPS, CommsDAC
DIGITAL-TO-ANALOG CONVERTER
SLAS247 – NOVEMBER 1999
APPLICATION INFORMATION
definitions of specifications and terminology (continued)
offset drift
The change in offset error versus temperature from the ambient temperature (TA = 25°C) in ppm of full-scale
range per °C.
gain drift
The change in gain error versus temperature from the ambient temperature (TA = 25°C) in ppm of full-scale
range per °C.
reference voltage drift
The change in reference voltage error versus temperature from the ambient temperature (TA = 25°C) in ppm
of full-scale range per °C.
THS5661A evaluation board
An evaluation module (EVM) board for the THS5661A digital-to-analog converter is available for evaluation.
This board allows the user the flexibility to operate the THS5661A in various configurations. Possible output
configurations include transformer coupled, resistor terminated, and inverting/noninverting amplifier outputs.
The digital inputs are designed to interface with the TMS320 C5000 or C6000 family of DSPs or to be driven
directly from various pattern generators with the onboard option to add a resistor network for proper load
termination.
See the THS56x1 Evaluation Module User’s Guide for more details (SLAU032).
POST OFFICE BOX 655303
• DALLAS, TEXAS 75265
23
24
J4
0.1 µF
4.7 µF
J6
C34
6
U9
POST OFFICE BOX 655303 • DALLAS, TEXAS 75265
3
2
1
R25
TDB
0.01 µF
T1
4.7 µF
C28
2
3
L2
L3
3
1
R24
49.9
C9
0.1 µF
C23
0.1 µF
R23
100
0.1 µF 0.01 µF
C26
–5VA
W8
C25
C27
750
R28
750
R30
W9
T1–1T–KK81
+
750
THS3001
4
–5VA
R26
C33
+5VA
10
R22
+ C35
J7
7
+5VA
750
R27
J8
D
E
F
A
B
C
FB2
+
10 µF
C15
+
C32
C24
10 µF
4.7 µH
R16
3.0 K
D2
4.7 µH
FB4
W7
W6
J9
1 µF
C22
1 µF
C31
R29
49.9
0.01 µF
0.01 µF
C20
–5VA
0.1 µF
C21
R19
C18
4.7 µF
+
J2
W4
C14
0.01 µF
2
1
R15
2.94 K
C12
0.1 µF
FB3
+5VA
33
+ C19
U7
4.7 µF
LT1004D
C29
+5VA
0.1 µF
C30
1
+5VA
3
W3
20
23
19
24
R14
5K
18
2
1
10 µF
26
27
25
15
28
14
13
12
11
10
9
8
7
6
5
4
3
2
1
C3
C7
C6
C10
0.1 µF 0.1 µF 0.1 µF
0.1 µF
C8
W5
0.01 µF
C2
DVDCC
1 µF 0.1 µF
C1
C11
0.1 µF
DVDCC
R20
10 K
DVDCC
DAC2
DAC3
DAC4
DAC5
DAC6
DAC7
DAC8
DAC9
DAC10
DAC11
DAC12
DAC13
DAC14
DAC15
DVDCC
MiscellaniousDigital Bypass Caps
C5
0.1 µF
FB1
+ C4
DGND
DVDD
MODE
SLEEP
CLK
NC4
NC3
D0
D1
D2
D3
D4
D5
D6
D7
D8
D9
D10
D11
Figure 35. Schematic
R1
1.5 K
D1
4.7 µH
L1
U8
AD1580BRT
3
U5
THS5661A
AGND
COMP2
COMP1
AVDD
BIASJ
EXTIO
EXTLO
IOUT2
IOUT1
ALTERNATECONFIGURATION
C13
0.1 µF
C16
0.1 µF
C17
0.1 µF
17
16
21
22
SN74ALVC08
U6A
11
12
13
14
15
16
17
18
R11A
R11B
R11C
R11D
R11E
R11F
R11G
R11H
U6D
B8
B7
B6
B5
B4
B3
B2
B1
A8
A7
A6
A5
A4
A3
A2
A1
9
8
7
6
5
4
3
2
B1
B2
B3
B4
B5
B6
B7
B8
A1
A2
A3
A4
A5
A6
A7
A8
DIR
19
W2
3
R18
49.9
3
1
W1
R6
10 K
R3
DSP7
DSP6
DSP5
DSP4
DSP3
DSP2
DSP1
DSP0
J5
CLKOUT
PDAC
CLKOUT
3
5
0Ω
0Ω
R8
0Ω
R13
0Ω
R17
R21
U3
SN74AHC1G00
A0
A1
I/OSTROBE
DVDCC
DSP[2..15]
R5A
R5B
R5C
R5D
R5E
R5F
R5G
R5H
~OE
10K
R4H DSP8
R4G DSP9
R4F DSP10
R4E DSP11
R4D DSP12
R4C DSP13
R4B DSP14
R4A DSP15
DVDCC
DVDCC
U4
SN74HC1G32
5
2
3
4
5
6
7
8
9
1
SN74LVT245B
10 GND
18
17
16
15
14
13
12
11
U2
20 VCC OE
1
DIR
20 VCC OE 19
SN74LVT245B
DVDCC
R10H
R10G
R10F
R10E
R10D
R10C
R10B
R10A
~OE
DAC[2..15]
DAC7
DAC6
DAC5
DAC4
DAC3
DAC2
DAC1
DAC0
DAC8
DAC9
DAC10
DAC11
DAC12
DAC13
DAC14
DAC15
U1
10 GND
U6C
U6B
33
R7
33
R9
33
R12
0 Ω
R2
DSP15
DSP14
DSP13
DSP12
DSP11
DSP10
DSP9
DSP8
DSP7
DSP6
DSP5
DSP4
DSP3
DSP2
DSP1
DSP0
J3
12
11
10
9
8
7
6
5
4
3
2
1
2
4
6
8
10
12
14
16
18
20
22
24
26
28
30
32
34
J1
1
3
5
7
9
11
13
15
17
19
21
23
25
27
29
31
33
THS5661A
12-BIT, 125 MSPS, CommsDAC
DIGITAL-TO-ANALOG
CONVERTER
SLAS247 – NOVEMBER 1999
APPLICATION INFORMATION
THS5661A
12-BIT, 125 MSPS, CommsDAC
DIGITAL-TO-ANALOG CONVERTER
SLAS200A – NOVEMBER 1999
APPLICATION INFORMATION
Figure 36. Board Layout, Layer 1
Figure 37. Board Layout, Layer 2
POST OFFICE BOX 655303
• DALLAS, TEXAS 75265
23
THS5661A
12-BIT, 125 MSPS, CommsDAC
DIGITAL-TO-ANALOG CONVERTER
SLAS200A – NOVEMBER 1999
APPLICATION INFORMATION
Figure 38. Board Layout, Layer 3
Figure 39. Board Layout, Layer 4
24
POST OFFICE BOX 655303
• DALLAS, TEXAS 75265
THS5661A
12-BIT, 125 MSPS, CommsDAC
DIGITAL-TO-ANALOG CONVERTER
SLAS200A – NOVEMBER 1999
APPLICATION INFORMATION
Figure 40. Board Layout, Layer 5
Table 2. Bill of Materials
QTY
REF. DES
PART NUMBER
DESCRIPTION
MFG.
3
C1, C22, C31
1206ZC105KAT2A
Ceranucm 1 µF, 10 V, X7R, 10%
AVX
4
C18, C19, C28, C35
ECSTOJY475
6.3 V, 4.7 µF, tantalum
Panasonic
3
C15, C24, C4
ECSTOJY106
6.3 V, 10 µF, tantalum
Panasonic
0
C25, C32
6
C14, C2, C20, C26, C29, C33
12065C103KAT2A
Ceramic, 0.01 µF, 50 V, X7R, 10%
AVX
17
C10, C11, C12, C13, C16,
C17, C21, C23, C27, C3, C30,
C34, C5, C6, C7, C8, C9
12065C104KAT2A
Ceramic, 0.1 µF, 50 V, X7R, 10%
AVX
2
D1, D2
AND/AND5GA or equivalent
GREEN LED, 1206 size SM chip LED
4
FB1, FB2, FB3, FB4
27-43-037447
Fair-Rite SM beads #27-037447
FairRite
1
J1
TSW-117-07-L-D or equivalent
34-Pin header for IDC
Samtec
1
J2
KRMZ2 or equivalent
2 Terminal screw connector,
2TERM_CON
Lumberg
1
J3
TSW-112-07-L-S or equivalent
Single row 12-pin header
Samtec
1
J4
KRMZ3 or equivalent
3 Terminal screw connector
Lumberg
3
J5, J6, J7
142-0701-206 or equivalent
PCB Mount SMA jack, SMA_PCB_MT
Johnson Components
0
J8, J9
142-0701-206 or equivalent
PCB Mount SMA jack, not installed
Johnson Components
3
L1, L2, L3
DO1608C-472
DO1608C-series, DS1608C-472
Coil Craft
1
R1
1206
1206 Chip resistor, 1.5K, 1/4 W, 1%
4
R10, R11, R4, R5
CTS/CTS766-163-(R)330-G-TR
8 Element isolated resistor pack, 33 Ω
Ceramic, not installed, 50 V, X7R, 10%
POST OFFICE BOX 655303
• DALLAS, TEXAS 75265
25
THS5661A
12-BIT, 125 MSPS, CommsDAC
DIGITAL-TO-ANALOG CONVERTER
SLAS200A – NOVEMBER 1999
APPLICATION INFORMATION
Table 2. Bill of Materials (Continued)
QTY
26
REF. DES
PART NUMBER
DESCRIPTION
MFG.
4
R12, R19, R7, R9
1206
1206 Chip resistor, 33 Ω, 1/4 W, 1%
5
R13, R17. R2, R21, R8
1206
1206 Chip resistor, 0 Ω, 1/4 W, 1%
1
R14
3214W-1-502 E or equivalent
4 mm SM Pot, 5K
1
R15
1206
1206 Chip resistor, 2.94K, 1/4 W, 1%
1
R16
1206
1206 Chip resistor, 3K, 1/4 W, 1%
3
R18, R24, R29
1206
1206 Chip resistor, 49.94K, 1/4 W, 1%
3
R20, R3, R6
1206
1206 Chip resistor, 10K, 1/4 W, 1%
1
R22
1206
1206 Chip resistor, 10K, 1/4 W, 1%
1
R23
1206
1206 Chip resistor, 100K, 1/4 W, 1%
1
R25
1206
1206 Chip resistor, TBD, 1/4 W, 1%
4
R26, R27, R28, R30
1206
1206 Chip resistor, 750K, 1/4 W, 1%
1
T1
T1-1T-KK81
RF Transformer, T1-1T-KK81
MiniCircuits
2
U1, U2
SN74LVT245BDW
Octal bus transceiver, 3-state,
SN74LVT245B
TI
1
U3
SN74AHCT1G00DBVR/
SN74AHC1G00DBVR
Single gate NAND, SN74AHC1G00
TI
1
U4
SN74AHCT1G32DBVR/
SN74AHCC1G32DBVR
Single 2 input positive or gate,
SN74AHC1G32
TI
THS5641
THS5641IDW
DAC, 2.7–5.5 V, 8 Bit, 125 MHz
TI
THS5651
THS5651IDW
DAC, 2.7–5.5 V, 10 Bit, 125 MHz
TI
THS5661
THS5661IDW
DAC, 2.7–5.5 V, 12 Bit, 125 MHz
TI
THS5671
THS5647IDW
DAC, 2.7–5.5 V, 14 Bit, 125 MHz
TI
1
SN74ALVC08
SN74ALVC08D
Quad AND gate
TI
1
LT1004D
LT1004CD-1-2/LT1004ID-1-2
Precision 1.2 V reference
TI
0
NOT INSTALLED
AD1580BRT
Precision voltage reference, not
installed
1
THS3001
THS3001CD/THS2001ID
THS3001 high-speed op amp
TI
4
W2
TSW-102-07-L-S or equivalent
2 position jumper_.1’’ spacing, W2
Samtec
3
W3
TSW-102-07-L-S or equivalent
3 position jumper_.1’’ spacing, W3
Samtec
2
2X3_JUMPER
TSW-102-07-L-S or equivalent
6-Pin header dual row, 0.025×0.1,
2X3_JUMPER
Samtec
POST OFFICE BOX 655303
• DALLAS, TEXAS 75265
Bourns
THS5661A
12-BIT, 125 MSPS, CommsDAC
DIGITAL-TO-ANALOG CONVERTER
SLAS200A – NOVEMBER 1999
MECHANICAL DATA
DW (R-PDSO-G**)
PLASTIC SMALL-OUTLINE PACKAGE
16 PINS SHOWN
0.050 (1,27)
0.020 (0,51)
0.014 (0,35)
16
0.010 (0,25) M
9
0.419 (10,65)
0.400 (10,15)
0.010 (0,25) NOM
0.299 (7,59)
0.293 (7,45)
Gage Plane
0.010 (0,25)
1
8
0°– 8°
A
0.050 (1,27)
0.016 (0,40)
Seating Plane
0.104 (2,65) MAX
0.012 (0,30)
0.004 (0,10)
PINS **
0.004 (0,10)
16
20
24
28
A MAX
0.410
(10,41)
0.510
(12,95)
0.610
(15,49)
0.710
(18,03)
A MIN
0.400
(10,16)
0.500
(12,70)
0.600
(15,24)
0.700
(17,78)
DIM
4040000 / C 07/96
NOTES: A.
B.
C.
D.
All linear dimensions are in inches (millimeters).
This drawing is subject to change without notice.
Body dimensions do not include mold flash or protrusion not to exceed 0.006 (0,15).
Falls within JEDEC MS-013
POST OFFICE BOX 655303
• DALLAS, TEXAS 75265
27
THS5661A
12-BIT, 125 MSPS, CommsDAC
DIGITAL-TO-ANALOG CONVERTER
SLAS200A – NOVEMBER 1999
MECHANICAL DATA
PW (R-PDSO-G**)
PLASTIC SMALL-OUTLINE PACKAGE
14 PINS SHOWN
0,30
0,19
0,65
14
0,10 M
8
0,15 NOM
4,50
4,30
6,60
6,20
Gage Plane
0,25
1
7
0°– 8°
A
0,75
0,50
Seating Plane
0,15
0,05
1,20 MAX
PINS **
0,10
8
14
16
20
24
28
A MAX
3,10
5,10
5,10
6,60
7,90
9,80
A MIN
2,90
4,90
4,90
6,40
7,70
9,60
DIM
4040064/F 01/97
NOTES: A.
B.
C.
D.
28
All linear dimensions are in millimeters.
This drawing is subject to change without notice.
Body dimensions do not include mold flash or protrusion not to exceed 0,15.
Falls within JEDEC MO-153
POST OFFICE BOX 655303
• DALLAS, TEXAS 75265
IMPORTANT NOTICE
Texas Instruments and its subsidiaries (TI) reserve the right to make changes to their products or to discontinue
any product or service without notice, and advise customers to obtain the latest version of relevant information
to verify, before placing orders, that information being relied on is current and complete. All products are sold
subject to the terms and conditions of sale supplied at the time of order acknowledgement, including those
pertaining to warranty, patent infringement, and limitation of liability.
TI warrants performance of its semiconductor products to the specifications applicable at the time of sale in
accordance with TI’s standard warranty. Testing and other quality control techniques are utilized to the extent
TI deems necessary to support this warranty. Specific testing of all parameters of each device is not necessarily
performed, except those mandated by government requirements.
CERTAIN APPLICATIONS USING SEMICONDUCTOR PRODUCTS MAY INVOLVE POTENTIAL RISKS OF
DEATH, PERSONAL INJURY, OR SEVERE PROPERTY OR ENVIRONMENTAL DAMAGE (“CRITICAL
APPLICATIONS”). TI SEMICONDUCTOR PRODUCTS ARE NOT DESIGNED, AUTHORIZED, OR
WARRANTED TO BE SUITABLE FOR USE IN LIFE-SUPPORT DEVICES OR SYSTEMS OR OTHER
CRITICAL APPLICATIONS. INCLUSION OF TI PRODUCTS IN SUCH APPLICATIONS IS UNDERSTOOD TO
BE FULLY AT THE CUSTOMER’S RISK.
In order to minimize risks associated with the customer’s applications, adequate design and operating
safeguards must be provided by the customer to minimize inherent or procedural hazards.
TI assumes no liability for applications assistance or customer product design. TI does not warrant or represent
that any license, either express or implied, is granted under any patent right, copyright, mask work right, or other
intellectual property right of TI covering or relating to any combination, machine, or process in which such
semiconductor products or services might be or are used. TI’s publication of information regarding any third
party’s products or services does not constitute TI’s approval, warranty or endorsement thereof.
Copyright  1999, Texas Instruments Incorporated