FREESCALE MC12149

Freescale Semiconductor, Inc.Order this document by MC12149/D
LOW POWER
VOLTAGE CONTROLLED
OSCILLATOR BUFFER
SEMICONDUCTOR
TECHNICAL DATA
NOTE: The MC12149 is NOT suitable as a crystal oscillator.
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The MC12149 is intended for applications requiring high frequency signal
generation up to 1300 MHz. An external tank circuit is used to determine the
desired frequency of operation. The VCO is realized using an
emitter–coupled pair topology. The MC12149 can be used with an integrated
PLL IC such as the MC12202 1.1 GHz Frequency Synthesizer to realize a
complete PLL sub–system. The device is specified to operate over a voltage
supply range of 2.7 to 5.5 V. It has a typical current consumption of 15 mA at
3.0 V which makes it attractive for battery operated handheld systems.
8
Operates Up to 1.3 GHz
1
Space–Efficient 8–Pin SOIC or SSOP Package
Low Power 15 mA Typical @ 3.0 V Operation
D SUFFIX
PLASTIC PACKAGE
CASE 751
(SO–8)
Supply Voltage of 2.7 to 5.5 V
Typical 900 MHz Performance
– Phase Noise –105 dBc/Hz @ 100 kHz Offset
– Tuning Voltage Sensitivity of 20 MHz/V
Output Amplitude Adjustment Capability
PIN CONNECTIONS
Two High Drive Outputs With a Typical Range from –8.0 to –2.0 dBm
One Low–Drive Output for Interfacing to a Prescaler
The device has three high frequency outputs which make it attractive for
transceiver applications which require both a transmit and receive local
oscillator (LO) signal as well as a lower amplitude signal to drive the
prescaler input of the frequency synthesizer. The outputs Q and QB are
available for servicing the receiver IF and transmitter up–converter
single–ended. In receiver applications, the outputs can be used together if it
is necessary to generate a differential signal for the receiver IF. Because the
Q and QB outputs are open collector, terminations to the VCC supply are
required for proper operation. Since the outputs are complementary, BOTH
outputs must be terminated even if only one is needed. The Q and QB
outputs have a nominal drive level of –8dBm to conserve power. If addition
signal amplitude is needed, a level adjustment pin (CNTL) is available, which
when tied to ground, boosts the nominal output levels to –2.0 dBm. A low
power VCO output (Q2) is also provided to drive the prescaler input of the
PLL. The amplitude of this signal is nominally 500 mV which is suitable for
most prescalers.
External components required for the MC12149 are: (1) tank circuit (LC
network); (2) Inductor/capacitor to provide the termination for the open
collector outputs; and (3) adequate supply voltage bypassing. The tank
circuit consists of a high–Q inductor and varactor components. The
preferred tank configuration allows the user to tune the VCO across the full
supply range. VCO performance such as center frequency, tuning voltage
sensitivity, and noise characteristics are dependent on the particular
components and configuration of the VCO tank circuit.
Q2
Q
GND
QB
8
7
6
5
1
2
3
4
VCC
CNTL TANK
VREF
(Top View)
ORDERING INFORMATION
Device
Operating
Temperature Range
Package
MC12149D
TA = –40 to 85°C
SO–8
 Motorola, Inc. 1998
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Rev 4
1
Freescale Semiconductor,
Inc.
MC12149
PIN NAMES
Pin
VCC
CNTL
TANK
VREF
QB
GND
Q
Q2
Function
Power Supply
Amplitude Control for Q, QB Output Pair
Tank Circuit Input
Bias Voltage Output
Open Collector Output
Ground
Open Collector Output
Low Power Output
Symbol
Value
Unit
VCC
-0.5 to 7.0
V
TA
–40 to 85
°C
TSTG
-65 to 150
°C
Maximum Output Current, Pin 8
IO
7.5
mA
Maximum Output Current, Pin 5,7
IO
12
mA
Parameter
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Power Supply Voltage, Pin 1
Operating Temperature Range
Storage Temperature Range
NOTES: 1. Maximum Ratings are those values beyond which damage to the device may occur.
Functional operation should be restricted to the Recommended Operating Conditions.
2. ESD data available upon request.
ELECTRICAL CHARACTERISTICS (VCC = 2.7 to 5.5 VDC, TA = -40 to 85°C, unless otherwise noted.)
Symbol
Min
Typ
Max
Unit
Supply Current (CNTL=GND)VCC = 3.3 V
VCC = 5.5 V
ICC
–
–
16
23.5
20
30
mA
Supply Current (CNTL=OPEN)VCC = 3.3 V
VCC = 5.5 V
ICC
–
–
10
15
15.0
24.5
mA
Output Amplitude (Pin 8)VCC = 2.7 V
High Impedance LoadVCC = 2.7 V
VOH,
VOL
1.75
1.20
1.85
1.35
1.95
1.50
V
Output Amplitude (Pin 8)VCC = 5.5 V
High Impedance LoadVCC = 5.5 V
VOH,
VOL
4.50
3.85
4.6
4.0
4.70
4.15
V
Output Amplitude (Pin 5 & 7) [Note 1] VCC = 2.7 V
50 Ω to VCC
VCC = 2.7 V
VOH,
VOL
2.6
2.1
2.7
2.3
–
2.4
V
Output Amplitude (Pin 5 & 7) [Note 1] VCC = 5.5 V
50Ω to VCC
VCC = 5.5V
VOH,
VOL
5.4
4.8
5.5
5.0
–
5.1
V
Tstg
FC
–
20
–
MHz/V
100
–
1300
MHz
–
–85
–
dBc/Hz
–
–105
–
dBc/Hz
–
–
0.8
50
–
–
MHz/V
KHz/°C
Characteristic
Tuning Voltage Sensitivity [Notes 2 and 3]
Frequency of Operation
CSR at 10 kHz Offset, 1Hz BW [Notes 2 and 3]
CSR at 100 kHz Offset, 1Hz BW [Notes 2 and 3]
Frequency Stability [Notes 3 and 4]
Supply Drift
Thermal Drift
L(f)
L(f)
Fsts
fstt
NOTES: 1. CNTL pin tied to ground.
2. Actual performance depends on tank components selected.
3. See Figure 12, 750 MHz tank.
4. T = 25°C, VCC = 5.0 V ±10%
2
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MAXIMUM RATINGS (Note 1)
Freescale Semiconductor,
Inc.
MC12149
A simplified schematic of the MC12149 is found in
Figure 1. The oscillator incorporates positive feedback by
coupling the base of transistor Q2 to the collector of transistor
Q1. In order to minimize interaction between the VCO
outputs and the oscillator tank transistor pair, a buffer is
incorporated into the circuit. This differential buffer is realized
by the Q3 and Q4 transistor pair. The differential buffer drives
the gate which contains the primary open collector outputs, Q
and QB. The output is actually a current which has been set
by an internal bias driver to a nominal current of 4mA.
Additional circuitry is incorporated into the tail of the current
source which allows the current source to be increased to
approximately 10 mA. This is accommodated by the addition
of a resistor which is brought out to the CNTL pin. When this
pin is tied to ground, the additional current is sourced through
the current source thus increasing the output amplitude of the
Q/QB output pair. If less than 10mA of current is needed, a
resistor can be added to ground which reduces the amount of
current.
The Q/QB outputs drive an additional differential buffer
which generate the Q2 output signal. To minimize current, the
circuit is realized as an emitter–follower buffer with an on chip
pull down resistor. This output is intended to drive the
prescaler input of the PLL synthesizer block.
APPLICATION INFORMATION
Figure 2 illustrates the external components necessary for
the proper operation of the VCO buffer. The tank circuit
configuration in this figure allows the VCO to be tuned across
the full operating voltage of the power supply. This is very
important in 3.0 V applications where it is desirable to utilize
as much of the operating supply range as possible so as to
minimize the VCO sensitivity (MHz/V). In most situations, it is
desirable to keep the sensitivity low so the circuit will be less
susceptible to external noise influences. An additional benefit
to this configuration is that additional regulation/ filtering can
be incorporated into the VCC line without compromising the
tuning range of the VCO. With the ac–coupled tank
configuration, the Vtune voltage can be greater than the VCC
voltage supplied to the device.
There are four main areas that the user directly influences
the performance of the VCO. These include Tank Design,
Output Termination Selection, Power Supply Decoupling,
and Circuit Board Layout/Grounding.
The design of the tank circuit is critical to the proper
operation of the VCO. This tank circuit directly impacts the
main VCO operating characteristics:
1)
2)
3)
4)
Frequency of Operation
Tuning Sensitivity
Voltage Supply Pushing
Phase Noise Performance
The tank circuit, in its simplest form, is realized as an LC
circuit which determines the VCO operating frequency. This
is described in Equation 1.
fo
+ Ǹ1
2p LC
Equation 1
In the practical case, the capacitor is replaced with a
varactor diode whose capacitance changes with the voltage
applied, thus changing the resonant frequency at which the
VCO tank operates. The capacitive component in Equation 1
also needs to include the input capacitance of the device and
other circuit and parasitic elements. Typically, the inductor is
realized as a surface mount chip or a wound–coil. In addition,
the lead inductance and board inductance and capacitance
also have an impact on the final operating point.
Figure 1. Simplified Schematic
VCC
Q3
Q4
TANK
VREF
Q
QB
Q5
Q6
VCC
Q2
Q1
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OPERATIONAL CHARACTERISTICS
Q2
VREF
136Ω
CNTL
1000Ω
200Ω
GND
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MC12149
Figure 2. MC12149 Typical External Component Connections
VCC Supply
C3a
VCC
1
Q2
8
C7
CNTL
Q
L2a
2
7
Note 1
R1
TANK
C1
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LT
CV
Cb
VREF
4
C6a
VCO Output
GND
3
Vin
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To Prescaler
C2a
6
VCO
QB
L2b
C6b
5
VCO Output
1. This input can be left open, tied to ground, or tied with a resistor to ground, depending
on the desired output amplitude needed at the Q and QB output pair.
2. Typical values for R1 range from 5.0 kΩ to 10 kΩ.
A simplified linear approximation of the device, package,
and typical board parasitics has been developed to aid the
designer in selecting the proper tank circuit values. All the
parasitic contributions have been lumped into a parasitic
capacitive component and a parasitic inductive component.
While this is not entirely accurate, it gives the designer a solid
starting point for selecting the tank components.
Below are the parameters used in the model.
Cp
Lp
LT
C1
Cb
CV
Parasitic Capacitance
Parasitic Inductance
Inductance of Coil
Coupling Capacitor Value
Capacitor for decoupling the Bias Pin
Varactor Diode Capacitance (Variable)
The values for these components are substituted into the
following equations:
Ci
C1 CV ) Cp
+ C1
) CV
Equation 2
C
Cb
+ CiCi ) Cb
Equation 3
L=
Lp + LT
Equation 4
From Figure 2, it can be seen that the varactor
capacitance (CV) is in series with the coupling capacitor
(C1). This is calculated in Equation 2. For analysis purposes,
the parasitic capacitances (CP) are treated as a lumped
element and placed in parallel with the series combination of
C1 and CV. This compound capacitance (Ci) is in series with
the bias capacitor (Cb) which is calculated in Equation 3. The
influences of the various capacitances; C1, CP, and Cb,
impact the design by reducing the variable capacitance
effects of the varactor which controls the tank resonant
frequency and tuning range.
4
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C3a
C2a
Now the results calculated from Equation 2, Equation 3
and Equation 4 can be substituted into Equation 1 to
calculate the actual frequency of the tank.
To aid in analysis, it is recommended that the designer use
a simple spreadsheet based on Equation 1 through
Equation 4 to calculate the frequency of operation for various
varactor/inductor selections before determining the initial
starting condition for the tank.
The two main components at the heart of the tank are the
inductor (LT) and the varactor diode (CV). The capacitance of
a varactor diode junction changes with the amount of reverse
bias voltage applied across the two terminals. This is the
element which actually “tunes” the VCO. One characteristic
of the varactor is the tuning ratio which is the ratio of the
capacitance at specified minimum and maximum voltage
points. For characterizing the MC12149, a Matsushita
(Panasonic) varactor – MA393 was selected. This device has
a typical capacitance of 11 pF at 1.0 V and 3.7 pF at 4.0 V and
the C–V characteristic is fairly linear over that range. Similar
performance was also acheived with Loral varactors. A
multi–layer chip inductor was used to realize the LT
component. These inductors had typical Q values in the 35 to
50 range for frequencies between 500 and 1000 MHz.
Note: There are many suppliers of high performance
varactors and inductors and Motorola can not recommend
one vendor over another.
The Q (quality factor) of the components in the tank circuit
has a direct impact on the resulting phase noise of the
oscillator. In general, the higher the Q, the lower the phase
noise of the resulting oscillator. In addition to the LT and CV
components, only high quality surface–mount RF chip
capacitors should be used in the tank circuit. These
capacitors should have very low dielectric loss (high–Q). At a
minimum, the capacitors selected should be operating
100 MHz below their series resonance point. As the desired
frequency of operation increases, the values of the C1 and
Cb capacitors will decrease since the series resonance point
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MC12149
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Frequency
C1
Cb
200 – 500 MHz
47 pF
47 pF
500 – 900 MHz
5.1 pF
15 pF
900 – 1200 MHz
2.7 pF
15 pF
The value of the Cb capacitor influences the VCO supply
pushing. To minimize pushing, the Cb capacitor should be
kept small. Since C1 is in series with the varactor, there is a
strong relationship between these two components which
influences the VCO sensitivity. Increasing the value of C1
tends to increase the sensitivity of the VCO.
The parasitic contributions Lp and Cp are related to the
MC12149 as well as parasitics associated with the layout,
tank components, and board material selected. The input
capacitance of the device, bond pad, the wire bond,
package/lead capacitance, wire bond inductance, lead
inductance, printed circuit board layout, board dielectric, and
proximity to the ground plane all have an impact on these
parasitics. For example, if the ground plane is located directly
below the tank components, a parasitic capacitor will be
formed consisting of the solder pad, metal traces, board
dielectric material, and the ground plane. The test fixture
used for characterizing the device consisted of a two sided
copper clad board with ground plane on the back. Nominal
values where determined by selecting a varactor and
characterizing the device with a number of different tank/
frequency combinations and then performing a curve fit with
the data to determine values for Lp and Cp. The nominal
values for the parasitic effects are seen below:
Parasitic Capacitance
Parasitic Inductance
Cp
Lp
4.2 pF
2.2 nH
10. Perform worst case analysis of tank component
variation to insure proper VCO operation over full
temperature and voltage range and make any
adjustments as needed.
Outputs Q and QB are open collector outputs and need a
inductor to VCC to provide the voltage bias to the output
transistor. In most applications, DC–blocking capacitors are
placed in series with the output to remove the DC component
before interfacing to other circuitry. These outputs are
complementary and should have identical inductor values for
each output. This will minimize switching noise on the VCC
supply caused by the outputs switching. It is important that
both outputs be terminated, even if only one of the outputs is
used in the application.
Referring to Figure 2, the recommended value for L2a and
L2b should be 47 nH and the inductor components
resonance should be at least 300 MHz greater than the
maximum operating frequency. For operation above 1100
MHz, it may be necessary to reduce that inductor value to 33
nH. The recommended value for the coupling capacitors
C6a, C6b, and C7 is 47 pF. Figure 2 also includes decoupling
capacitors for the supply line as well as decoupling for the
output inductors. Good RF decoupling practices should be
used with a series of capacitors starting with high quality 100
pF chip capacitors close to the device. A typical layout is
shown below in Figure 3.
The output amplitude of the Q and QB can be adjusted
using the CNTL pin. Refering to Figure 1, if the CNTL pin is
connected to ground, additional current will flow through the
current source. When the pin is left open, the nominal current
flowing through the outputs is 4 mA. When the pin is
grounded, the current increases to a nominal value of 10 mA.
So if a 50 ohm resistor was connected between the outputs
and VCC, the output amplitude would change from 200 mV
pp to 500 mV pp with an additional current drain for the
device of 6 mA. To select a value between 4 and 10 mA, an
external resistor can be added to ground. The equation below
is used to calculate the current.
Iout(nom)
These values will vary based on the users unique circuit
board configuration.
Basic Guidelines:
1. Select a varactor with high Q and a reasonable
capacitance versus voltage slope for the desired
frequency range.
2. Select the value of Cb and C1 from the table above .
3. Calculate a value of inductance (L) which will result in
achieving the desired center frequency. Note that L
includes both LT and Lp.
4. Adjust the value of C1 to achieve the proper VCO
sensitivity.
5. Re–adjust value of L to center VCO.
6. Prototype VCO design using selected components. It
is important to use similar construction techniques and
materials, board thickness, layout, ground plane
spacing as intended for the final product.
7. Characterize tuning curve over the voltage operation
conditions.
8. Adjust, as necessary, component values – L,C1, and
Cb to compensate for parasitic board effects.
9. Evaluate over temperature and voltage limits.
+
) 136 ) Rext) 0.8V
200 (136 ) Rext)
(200
Figure 4 through Figure 13 illustrate typical performance
achieved with the MC12149. The curves illustrate the tuning
curve, supply pushing characteristics, output power, current
drain, output spectrum, and phase noise performance. In
most cases, data is present for both a 750 MHz and
1200 MHz tank design. The table below illustrates the
component values used in the designs.
Component
750MHz Tank
1200MHz Tank
R1
5000
5000
Ω
C1
5.1
2.7
pF
LT
4.7
1.8
nH
CV
3.7 @ 1.0 V
11 @ 4.0 V
3.7 @ 1.0 V
11 @ 4.0 V
pF
Cb
100*
15
pF
C6, C7
47
33
pF
L2
47
47
nH
NOTE:
Units
* The value of Cb should be reduced to minimize pushing.
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is a function of the capacitance value. To simplify the
selection of C1 and Cb, a table has been constructed based
on t he int ende d o p e ra ti n g fre q u e n c y to prov i de
recommended starting points. These may need to be altered
depending on the value of the varactor selected.
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MC12149
Figure 3. MC12149 Typical Layout
(Not to Scale)
To Prescaler
C7
C2a
VCO Output 1
1
R2
R1
ÇÇÇÇÇ
ÇÇÇÇÇ
ÇÇÇÇÇ
C1
Vtune
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LT
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Varactor
C6a
L2a
C3b
L2b
C2b
Cb
VCO Output 2
C6b
ÇÇÇ
ÇÇÇ
ÇÇÇ
= Via to/or Ground Plane
= Via to/or Power Plane
6
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ÇÇ
ÇÇ
ÇÇ
C3a
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MC12149
Figure 4. Typical VCO Tuning Curve, 750 MHz Tank
850
825
775
750
725
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700
–40°C
+25°C
+85°C
675
650
0
0.5
1.0
1.5
2.0
2.5
3.0
3.5
4.0
4.5
5.0
Tuning Voltage (V)
Figure 5. Typical Supply Pushing, 750 MHz Tank
750
748
746
Frequency of Operation (MHz)
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Frequency of Operation (MHz)
800
744
742
740
738
736
734
–40°C
+25°C
+85°C
732
730
2.7
3.0
3.3
3.6
3.9
4.2
4.5
4.8
5.1
5.4
VCC Supply Voltage (V)
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Figure 6. Typical Q/QB Output Power versus Supply, 750 MHz Tank
0
–1
–2
Output Power (dBm)
–3
–4
–40°C
+25°C
+85°C
+25°C (LP)
CNTL to GND
–5
–6
–7
–9
CNTL–N/C
–10
2.7
3.0
3.3
3.6
3.9
4.2
4.5
4.8
5.0
VCC Supply Voltage (V)
Figure 7. Typical Current Drain versus Supply, 750 MHz Tank
25
Current Drain (mA)
20
15
CNTL to GND
–40°C
+25°C
+85°C
+25°C (LP)
10
CNTL–N/C
5
2.7
3.0
3.3
3.6
3.9
4.2
4.5
4.8
5.1
5.4
VCC Supply Voltage (V)
8
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–8
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Inc.
MC12149
Figure 8. Typical VCO Tuning Curve, 1200 MHz Tank
(VCC = 5.0 V)
1300
1250
1225
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1200
1175
–40°C
+25°C
+85°C
1150
0
0.6
1.2
1.8
2.4
3.0
3.6
4.2
4.8
Tuning Voltage (V)
Figure 9. Typical Supply Pushing, 1200 MHz Tank
1210
1208
1206
Frequency of Operation (MHz)
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Frequency of Operation (MHz)
1275
1204
1202
1200
1198
1196
1194
–40°C
+25°C
+85°C
1192
1190
2.7
3.0
3.3
3.6
3.9
4.2
4.5
4.8
5.1
5.4
VCC Supply Voltage (V)
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MC12149
Figure 10. Q/QB Output Power versus Supply, 1200 MHz Tank
2
1
Output Power (dBm)
0
–1
–3
–40°C
+25°C
+85°C
–4
2.7
3.0
3.3
3.6
3.9
4.2
4.5
4.8
5.0
VCC Supply Voltage (V)
Figure 11. Typical VCO Output Spectrum
ATTEN 10
RL 0dBm
MARKER
909MHz –7.1dBm
10dB/
0
–10
–20
AMPLITUDE (dBm)
–30
–40
–50
–60
–70
–80
–90
–100
START 10MHz
RBW 1.0MHz
10
VBW 1.0MHz
STOP 10.0GHz
SWP 200ms
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–2
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MC12149
Figure 12. Typical Phase Noise Plot, 750 MHz Tank
HP 3048A
CARRIER
784.2MHz
0
–25
–50
dBc/Hz
–75
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–125
–150
–170
100
1K
10K
100K
1M
10M
40M
10M
40M
L(f) [dBc/Hz] vs f[Hz]
Figure 13. Typical Phase Noise Plot, 1200 MHz Tank
HP 3048A
CARRIER
1220MHz
0
dBc/Hz
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–100
–25
–50
–75
–100
–125
–150
–170
100
1K
10K
100K
1M
L(f) [dBc/Hz] vs f[Hz]
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MC12149
OUTLINE DIMENSIONS
D SUFFIX
PLASTIC PACKAGE
CASE 751–06
(SO–8)
ISSUE T
8
NOTES:
1. DIMENSIONING AND TOLERANCING PER ASME
Y14.5M, 1994.
2. DIMENSIONS ARE IN MILLIMETER.
3. DIMENSION D AND E DO NOT INCLUDE MOLD
PROTRUSION.
4. MAXIMUM MOLD PROTRUSION 0.15 PER SIDE.
5. DIMENSION B DOES NOT INCLUDE DAMBAR
PROTRUSION. ALLOWABLE DAMBAR
PROTRUSION SHALL BE 0.127 TOTAL IN EXCESS
OF THE B DIMENSION AT MAXIMUM MATERIAL
CONDITION.
C
5
0.25
H
E
M
B
M
1
4
h
ARCHIVE INFORMATION
Freescale Semiconductor, Inc...
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e
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A
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SEATING
PLANE
L
0.10
A1
B
0.25
M
C B
S
A
S
DIM
A
A1
B
C
D
E
e
H
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L
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MILLIMETERS
MIN
MAX
1.35
1.75
0.10
0.25
0.35
0.49
0.19
0.25
4.80
5.00
3.80
4.00
1.27 BSC
5.80
6.20
0.25
0.50
0.40
1.25
0_
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the suitability of its products for any particular purpose, nor does Motorola assume any liability arising out of the application or use of any product or circuit, and
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D
A
Mfax is a trademark of Motorola, Inc.
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MC12149/D
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Go to: www.freescale.com