MCP6S91/2/3 Single-Ended, Rail-to-Rail I/O, Low-Gain PGA Features Description • Multiplexed Inputs: 1 or 2 channels • 8 Gain Selections: - +1, +2, +4, +5, +8, +10, +16 or +32 V/V • Serial Peripheral Interface (SPI™) • Rail-to-Rail Input and Output • Low Gain Error: ±1% (max.) • Offset Mismatch Between Channels: 0 µV • High Bandwidth: 1 to 18 MHz (typ.) • Low Noise: 10 nV/√Hz @ 10 kHz (typ.) • Low Supply Current: 1.0 mA (typ.) • Single Supply: 2.5V to 5.5V • Extended Temperature Range: -40°C to +125°C The Microchip Technology Inc. MCP6S91/2/3 are analog Programmable Gain Amplifiers (PGAs). They can be configured for gains from +1 V/V to +32 V/V and the input multiplexer can select one of up to two channels through a SPI port. The serial interface can also put the PGA into shutdown to conserve power. These PGAs are optimized for high-speed, low offset voltage and single-supply operation with rail-to-rail input and output capability. These specifications support singlesupply applications needing flexible performance or multiple inputs. Typical Applications • • • • • • A/D Converter Driver Multiplexed Analog Applications Data Acquisition Industrial Instrumentation Test Equipment Medical Instrumentation Package Types MCP6S91 PDIP, SOIC, MSOP Block Diagram VDD CH0 CH1 MUX VOUT SPI™ Logic RF 8 Gain Switches RG VSS 2004 Microchip Technology Inc. MCP6S93 MSOP VOUT 1 8 VDD VOUT 1 10 VDD CH0 2 7 SCK CH0 2 9 SCK VREF 3 VSS 4 6 SI CH1 3 8 SO 5 CS VREF 4 7 SI VSS 5 6 CS MCP6S92 PDIP, SOIC, MSOP Resistor Ladder (RLAD) CS SI SO SCK The one-channel MCP6S91 and the two-channel MCP6S92 are available in 8-pin PDIP, SOIC and MSOP packages. The two-channel MCP6S93 is available in a 10-pin MSOP package. All parts are fully specified from -40°C to +125°C. VOUT 1 8 VDD CH0 2 7 SCK CH1 3 VSS 4 6 SI 5 CS VREF DS21908A-page 1 MCP6S91/2/3 1.0 ELECTRICAL CHARACTERISTICS PIN FUNCTION TABLE Name VOUT Absolute Maximum Ratings † Function Analog Output CH0, CH1 Analog Inputs VDD – VSS ........................................................................7.0V VREF External Reference Pin VSS Negative Power Supply Output Short Circuit Current ..................................continuous CS SPI Chip Select Current at Input Pin .............................................................±2 mA SI SPI Serial Data Input All inputs and outputs..................... VSS – 0.3V to VDD + 0.3V Difference Input voltage ....................................... |VDD – VSS| Current at Output and Supply Pins ................................ ±30 mA SO Storage temperature .....................................-65°C to +150°C SCK SPI Clock Input Junction temperature .................................................. +150°C VDD Positive Power Supply SPI Serial Data Output ESD protection on all pins (HBM; MM) ................ ≥ 4 kV; 200V † Notice: Stresses above those listed under “Maximum Ratings” may cause permanent damage to the device. This is a stress rating only and functional operation of the device at those or any other conditions above those indicated in the operational listings of this specification is not implied. Exposure to maximum rating conditions for extended periods may affect device reliability. DC CHARACTERISTICS Electrical Specifications: Unless otherwise indicated, TA = +25°C, VDD = +2.5V to +5.5V, VSS = GND, VREF = VSS, G = +1 V/V, Input = CH0 = (0.3V)/G, CH1 = 0.3V, RL = 10 kΩ to VDD/2, SI and SCK are tied low and CS is tied high. Parameters Sym Min Typ Max Units VOS -4 — +4 mV Conditions Amplifier Inputs (CH0, CH1) Input Offset Voltage Input Offset Voltage Mismatch Input Offset Voltage Drift Power Supply Rejection Ratio ∆VOS — 0 — µV ∆VOS/∆TA — ±1.8 — µV/°C G = +1 Between inputs (CH0, CH1) TA = -40°C to +125°C PSRR 70 90 — dB G = +1 (Note 1) Input Bias Current IB — ±1 — pA CHx = VDD/2 Input Bias Current at Temperature IB — 30 — pA CHx = VDD/2, TA = +85°C IB — 600 — pA CHx = VDD/2, TA = +125°C ZIN — 1013||7 — Ω||pF VIVR VSS − 0.3 — VDD + 0.3 V Input Impedance Input Voltage Range (Note 2) Reference Input (VREF) Input Impedance ZIN_REF — (5/G)||6 — kΩ||pF Voltage Range VIVR_REF VSS — VDD V (Note 2) Amplifier Gain Nominal Gains G — 1 to 32 — V/V gE -0.2 — +0.2 % G ≥ +2 gE -1.0 — +1.0 % G = +1 ∆G/∆TA — ±0.0002 — %/°C TA = -40°C to +125°C ∆G/∆TA — ±0.0004 — %/°C TA = -40°C to +125°C DC Gain Error G = +1 DC Gain Drift G ≥ +2 Note 1: 2: 3: +1, +2, +4, +5, +8, +10, +16 or +32 VOUT ≈ 0.3V to VDD − 0.3V VOUT ≈ 0.3V to VDD − 0.3V RLAD (RF+RG in Figure 4-1) connects VREF, VOUT and the inverting input of the internal amplifier. The MCP6S92 has VREF tied internally to VSS, so VSS is coupled to the internal amplifier and the PSRR spec describes PSRR+ only. It is recommended that the MCP6S92’s VSS pin be tied directly to ground to avoid noise problems. The MCP6S92’s VIVR and VIVR_REF are not tested in production; they are set by design and characterization. IQ includes current in RLAD (typically 60 µA at VOUT = 0.3V). Both IQ and IQ_SHDN exclude digital switching currents. 2004 Microchip Technology Inc. DS21908A-page 2 MCP6S91/2/3 DC CHARACTERISTICS (CONTINUED) Electrical Specifications: Unless otherwise indicated, TA = +25°C, VDD = +2.5V to +5.5V, VSS = GND, VREF = VSS, G = +1 V/V, Input = CH0 = (0.3V)/G, CH1 = 0.3V, RL = 10 kΩ to VDD/2, SI and SCK are tied low and CS is tied high. Parameters Sym Min Typ Max Units Conditions Ladder Resistance Ladder Resistance RLAD 3.4 4.9 6.4 kΩ ∆RLAD/∆TA — +0.028 — %/°C DC Output Non-linearity G = +1 VONL — ±0.18 G ≥ +2 VONL — ±0.050 VOH_ANA, VOL_ANA VSS + 20 — % of FSR VOUT ≈ 0.3V to VDD − 0.3V, VDD = 5.0V VDD – 100 mV G ≥ +2; 0.5V output overdrive VSS + 60 — VDD – 60 ISC — ±25 — Ladder Resistance across Temperature (Note 1) TA = -40°C to +125°C (Note 1) Amplifier Output Maximum Output Voltage Swing Short Circuit Current — % of FSR VOUT ≈ 0.3V to VDD − 0.3V, VDD = 5.0V — G ≥ +2; 0.5V output overdrive, VREF = VDD/2 mA Power Supply Supply Voltage Minimum Valid Supply Voltage Quiescent Current Quiescent Current, Shutdown Mode Note 1: 2: 3: VDD 2.5 — 5.5 V VDD_VAL — 0.4 2.0 V IQ 0.4 1.0 1.6 mA IO = 0 (Note 3) IQ_SHDN — 30 — pA IO = 0 (Note 3) Register data still valid RLAD (RF+RG in Figure 4-1) connects VREF, VOUT and the inverting input of the internal amplifier. The MCP6S92 has VREF tied internally to VSS, so VSS is coupled to the internal amplifier and the PSRR spec describes PSRR+ only. It is recommended that the MCP6S92’s VSS pin be tied directly to ground to avoid noise problems. The MCP6S92’s VIVR and VIVR_REF are not tested in production; they are set by design and characterization. IQ includes current in RLAD (typically 60 µA at VOUT = 0.3V). Both IQ and IQ_SHDN exclude digital switching currents. 2004 Microchip Technology Inc. DS21908A-page 3 MCP6S91/2/3 AC CHARACTERISTICS Electrical Specifications: Unless otherwise indicated, TA = +25°C, VDD = +2.5V to +5.5V, VSS = GND, VREF = VSS, G = +1 V/V, Input = CH0 = (0.3V)/G, CH1 = 0.3V, RL = 10 kΩ to VDD/2, CL = 60 pF, SI and SCK are tied low and CS is tied high. Parameters Sym Min Typ Max Units Conditions Frequency Response All gains; VOUT < 100 mVP-P (Note 1) -3 dB Bandwidth BW — 1 to 18 — MHz Gain Peaking GPK — 0 — dB All gains; VOUT < 100 mVP-P f = 20 kHz, G = +1 V/V THD+N — 0.0011 — % VOUT = 1.5V ± 1.0 VPK, VDD = 5.0V, BW = 80 kHz, RL = 10 kΩ to 1.5V f = 20 kHz, G = +1 V/V THD+N — 0.0089 — % VOUT = 2.5V ± 1.0 VPK, VDD = 5.0V, BW = 80 kHz f = 20 kHz, G = +4 V/V THD+N — 0.0045 — % VOUT = 2.5V ± 1.0 VPK, VDD = 5.0V, BW = 80 kHz f = 20 kHz, G = +16 V/V THD+N — 0.028 — % VOUT = 2.5V ± 1.0 VPK, VDD = 5.0V, BW = 80 kHz SR — 4.0 — V/µs — 11 — V/µs G = 4, 5, 8, 10 — 22 — V/µs G = 16, 32 — 4.5 — µVP-P f = 0.1 Hz to 10 Hz (Note 2) — 30 — Total Harmonic Distortion plus Noise Step Response Slew Rate G = 1, 2 Noise Input Noise Voltage Eni f = 0.1 Hz to 200 kHz (Note 2) Input Noise Voltage Density eni — 10 — nV/√Hz f = 10 kHz (Note 2) Input Noise Current Density ini — 4 — fA/√Hz f = 10 kHz Note 1: 2: See Table 4-1 for a list of typical numbers and Figure 2-25 for the frequency response versus gain. Eni and eni include ladder resistance noise. See Figure 2-12 for eni versus G data. 2004 Microchip Technology Inc. DS21908A-page 4 MCP6S91/2/3 DIGITAL CHARACTERISTICS Electrical Specifications: Unless otherwise indicated, TA = 25°C, VDD = +2.5V to +5.5V, VSS = GND, VREF = VSS, G = +1 V/V, Input = CH0 = (0.3V)/G, CH1 = 0.3V, RL = 10 kΩ to VDD/2, CL = 60 pF, SI and SCK are tied low and CS is tied high. Parameters Sym Min Typ Max Units Conditions SPI Inputs (CS, SI, SCK) Logic Threshold, Low VIL 0 — 0.3VDD V Input Leakage Current IIL -1.0 — +1.0 µA Logic Threshold, High VIH 0.7 VDD — VDD V Amplifier Output Leakage Current — -1.0 — 1.0 µA In Shutdown mode Logic Threshold, Low VOL_DIG VSS — VSS+0.4 V IOL = 2.1 mA, VDD = 5V Logic Threshold, High VOH_DIG VDD – 0.5 — VDD V IOH = -400 µA SPI Output (SO, for MCP6S93) SPI Timing Pin Capacitance CPIN — 10 — pF All digital I/O pins Input Rise/Fall Times (CS, SI, SCK) tRFI — — 2 µs (Note 1) Output Rise/Fall Times (SO) tRFO — 5 — ns MCP6S93 CS High Time tCSH 40 — — ns SCK Edge to CS Fall Setup Time tCS0 10 — — ns CS Fall to First SCK Edge Setup Time tCSSC 40 — — ns SCK Frequency fSCK — — 10 MHz SCK High Time tHI 40 — — ns SCK edge when CS is high VDD = 5V (Note 2) tLO 40 — — ns tSCCS 30 — — ns CS Rise to SCK Edge Setup Time tCS1 100 — — ns SI Setup Time tSU 40 — — ns SI Hold Time tHD 10 — — ns SCK to SO Valid Propagation Delay tDO — — 80 ns MCP6S93 CS Rise to SO Forced to Zero tSOZ — — 80 ns MCP6S93 Channel Select Time tCH — 1.5 — µs CHx = 0.6V, CHy = 0.3V, G = 1, CHx to CHy select, CS = 0.7 VDD to VOUT 90% point Gain Select Time tG — 1 — µs CHx = CHy = 0.3V, G = 5 to G = 1 select, CS = 0.7 VDD to VOUT 90% point Out of Shutdown mode (CS goes high) to Amplifier Output Turn-on Time tON — 3.5 10 µs CS = 0.7 VDD to VOUT 90% point Into Shutdown mode (CS goes high) to Amplifier Output High-Z Turn-off Time tOFF — 1.5 — µs CS = 0.7 VDD to VOUT 90% point SCK Low Time SCK Last Edge to CS Rise Setup Time SCK edge when CS is high Channel and Gain Select Timing Shutdown Mode Timing Note 1: 2: Not tested in production. Set by design and characterization. When using the device in the daisy-chain configuration, maximum clock frequency is determined by a combination of propagation delay time (tDO ≤ 80 ns), data input set-up time (tSU ≥ 40 ns), SCK high time (tHI ≥ 40 ns) and SCK rise and fall times of 5 ns. Maximum fSCK is therefore ≈ 5.8 MHz. 2004 Microchip Technology Inc. DS21908A-page 5 MCP6S91/2/3 TEMPERATURE CHARACTERISTICS Electrical Specifications: Unless otherwise indicated, VDD = +2.5V to +5.5V, VSS = GND. Parameters Sym Min Typ Max Units Specified Temperature Range TA -40 — +125 °C Operating Temperature Range TA -40 — +125 °C Storage Temperature Range TA -65 — +150 °C Conditions Temperature Ranges (Note 1) Thermal Package Resistances Thermal Resistance, 8L-PDIP θJA — 85 — °C/W Thermal Resistance, 8L-SOIC θJA — 163 — °C/W Thermal Resistance, 8L-MSOP θJA — 206 — °C/W Thermal Resistance, 10L-MSOP θJA — 143 — °C/W Note 1: Operation in this range must not cause TJ to exceed Maximum Junction Temperature (+150°C). 2004 Microchip Technology Inc. DS21908A-page 6 MCP6S91/2/3 CS CS tCH VOUT tG 0.6V FIGURE 1-1: Diagram. 1.5V VOUT 0.3V 0.3V FIGURE 1-3: Diagram. Channel Select Timing Gain Select Timing CS tON tOFF Hi-Z VOUT Hi-Z 0.3V 1.0 mA (typ.) ISS 30 pA (typ.) FIGURE 1-2: PGA Shutdown Timing Diagram (must enter correct commands before CS goes high). tCSH CS tCSSC tSCCS tCS1 tLO tCS0 tHI SCK tSU tHD 1/fSCK SI tDO tSOZ SO (first 16 bits out are always zeros) FIGURE 1-4: Detailed SPI™ Serial Interface Timing; SPI 0,0 Mode. 2004 Microchip Technology Inc. DS21908A-page 7 MCP6S91/2/3 tCSH CS tCSSC tSCCS tCS1 tHI tCS0 tLO SCK tSU tHD 1/fSCK SI tSOZ tDO SO (first 16 bits out are always zeros) FIGURE 1-5: 1.1 Detailed SPI™ Serial Interface Timing; SPI 1,1 Mode. DC Output Voltage Specs / Model 1.1.1 IDEAL MODEL The ideal PGA output voltage (VOUT) is: EQUATION 1-3: EQUATION 1-1: VO_ID = G VIN The end points of this line are at VO_ID = 0.3V and VDD – 0.3V. Figure 1-6 shows the relationship between the gain and offset specifications referred to in the electrical specifications as follows: V REF = V SS = 0V Where: G is the nominal gain V2 – V1 g E = 100% -------------------------------------G ( VDD – 0.6V ) V1 VOS = ------------------------G ( 1 + gE ) G = +1 (see Figure 1-6). This equation holds when there are no gain or offset errors and when the VREF pin is tied to a low-impedance source (<< 0.1Ω) at ground potential (VSS = 0V). The DC Gain Drift (∆G/∆TA) can be calculated from the change in gE across temperature. This is shown in the following equation: 1.1.2 EQUATION 1-4: LINEAR MODEL The PGA’s linear region of operation, including offset and gain errors, is modeled by the line VO_LIN shown in Figure 1-6. ∆g E ∆G ⁄ ∆T A = ---------∆T A EQUATION 1-2: 0.3V V O_LIN = G ( 1 + g E ) VIN – ----------- + V OS + 0.3V G VREF = V SS = 0V 2004 Microchip Technology Inc. DS21908A-page 8 MCP6S91/2/3 1.1.4 VOUT (V) VDD V2 VDD – 0.3 DIFFERENT VREF CONDITIONS Some of the plots in Section 2.0 “Typical Performance Curves”, have the conditions VREF = VDD/2 or VREF = VDD. The equations and figures above are easily modified for these conditions. The ideal VOUT equation becomes: O V _LIN O _I D V O_ID = VREF + G ( VIN – VREF ) V DD ≥ V REF > V SS = 0V V V O UT EQUATION 1-7: V1 0.3 0 VIN (V) 0.3 G 0 VDD – 0.3 VDD G G FIGURE 1-6: Output Voltage Model with the standard condition VREF = VSS = 0V. 1.1.3 The complete linear model is: EQUATION 1-8: V ON_LIN = G ( 1 + g E ) ( V IN – VIN_L + VOS ) + 0.3V V REF = VSS = 0V where the new VIN end points are: OUTPUT NON-LINEARITY Figure 1-7 shows the Integral Non-Linearity (INL) of the output voltage. EQUATION 1-5: EQUATION 1-9: 0.3V – VREF V IN_L = ------------------------------ + V REF G INL = V OUT – V O_LIN VDD – 0.3V – VREF V IN_H = ----------------------------------------------- + V REF G The output non-linearity specification in the Electrical Specifications (with units of: % of FSR) is related to Figure 1-7 by: The equations for extracting the specifications do not change. EQUATION 1-6: max ( V3, V4 ) V ONL = ------------------------------- ⋅ 100% V DD – 0.6V The Full-Scale Range (FSR) is VDD – 0.6V (0.3V to VDD – 0.3V). INL (V) V4 0 V3 0 0.3 G VDD – 0.3 VDD G G VIN (V) FIGURE 1-7: Output Voltage INL with the standard condition VREF = VSS = 0 V. 2004 Microchip Technology Inc. DS21908A-page 9 MCP6S91/2/3 2.0 TYPICAL PERFORMANCE CURVES Note: The graphs and tables provided following this note are a statistical summary based on a limited number of samples and are provided for informational purposes only. The performance characteristics listed herein are not tested or guaranteed. In some graphs or tables, the data presented may be outside the specified operating range (e.g., outside specified power supply range) and therefore outside the warranted range. 600 Samples G = +1 TA = -40 to +125°C 30% 25% 20% 15% 10% 5% DC Gain Error (%) DC Gain Error, G ≥ +2. 10% 8% 6% 4% 2% Ladder Resistance Drift (%/°C) Ladder Resistance Drift. 2004 Microchip Technology Inc. 0.030 0.029 0.028 0.027 0.026 0.025 0.024 0.023 0.022 0.021 0.020 0% Crosstalk, Input Referred (dB) FIGURE 2-5: 12% FIGURE 2-3: 0.0006 0.0005 0.0004 0.0003 0.0002 0.0000 0.0001 0.0020 0.0016 0.0012 0.0008 0.0004 0.0000 -0.0004 DC Gain Drift (%/°C) 597 Samples TA = -40 to +125°C 0.019 Percentage of Occurrences 14% -0.0008 -0.0012 600 Samples G ≥ +2 TA = -40 to +125°C DC Gain Error (%) 16% -0.0001 DC Gain Drift, G = +1. -0.0016 0.6 0.5 0.4 0.3 0.2 0.1 0.0 -0.1 -0.2 -0.3 -0.4 26% 24% 22% 20% 18% 16% 14% 12% 10% 8% 6% 4% 2% 0% -0.0020 Percentage of Occurrences FIGURE 2-4: 600 Samples G ≥ +2 FIGURE 2-2: -0.0002 DC Gain Drift (%/°C) DC Gain Error, G = +1. -0.5 18% 16% 14% 12% 10% 8% 6% 4% 2% 0% -0.6 Percentage of Occurrences FIGURE 2-1: -0.0003 -0.0004 -0.0005 0% -0.0006 Percentage of Occurrences 35% 0.10 0.08 0.06 0.04 0.02 0.00 -0.02 -0.04 -0.06 600 Samples G = +1 -0.08 24% 22% 20% 18% 16% 14% 12% 10% 8% 6% 4% 2% 0% -0.10 Percentage of Occurrences Note: Unless otherwise indicated, TA = +25°C, VDD = +2.5V to +5.5V, VSS = GND, VREF = VSS, G = +1 V/V, Input = CH0 = (0.3V)/G, CH1 = 0.3V, RL = 10 kΩ to VDD/2 and CL = 60 pF. -10 DC Gain Drift, G ≥ +2. VDD = 5.0V G = +32 V/V CH0 selected RS = 10 kΩ -20 -30 -40 -50 RS = 1 kΩ -60 RS = 100 Ω -70 -80 -90 -100 100k 1.E+05 RS = 0 Ω 1.E+06 1.E+07 1M 10M Frequency (Hz) 1.E+08 100M FIGURE 2-6: Crosstalk vs. Frequency (circuit in Figure 6-4). DS21908A-page 10 MCP6S91/2/3 Note: Unless otherwise indicated, TA = +25°C, VDD = +2.5V to +5.5V, VSS = GND, VREF = VSS, G = +1 V/V, Input = CH0 = (0.3V)/G, CH1 = 0.3V, RL = 10 kΩ to VDD/2 and CL = 60 pF. -1 0 1 2 Input Offset Voltage (mV) 35% 25% FIGURE 2-10: σ = 10.0 µVRMS Measurement Repeatability: 10.4 µVRMS 20% 15% 10% 5% 30 20 10 0 -10 -20 0% 3.0 2.5 2.0 1.5 1.0 0.5 0.0 -0.5 -1.0 -1.5 -2.0 -2.5 -3.0 Input Offset Voltage Input Noise Voltage Density (nV/Hz) Input Noise Voltage Density (nV/Hz) 100 10 0.1 0.1 FIGURE 2-9: vs. Frequency. 1 1 10 100 1000 10 100 1k Frequency (Hz) 10000 10k 8 6 4 VDD = 5.5V VDD = 2.5V Input Offset Voltage vs. 13 12 11 10 9 8 7 6 5 4 3 2 1 0 f = 10 kHz 100000 100k Input Noise Voltage Density 2004 Microchip Technology Inc. G = +1 VIN = VREF FIGURE 2-11: VREF Voltage. 1000 1 Input Offset Voltage Drift. 0.0 0.5 1.0 1.5 2.0 2.5 3.0 3.5 4.0 4.5 5.0 5.5 VREF Voltage (V) Input Offset Voltage Mismatch (µV) FIGURE 2-8: Mismatch. 2 Input Offset Voltage Drift (µV/°C) Input Offset Voltage, 32 Samples VDD = 5.5V VIN = 0.3V 30% -30 Percentage of Occurrences FIGURE 2-7: VDD = 4.0V. 3 10 -2 Input Offset Voltage (mV) -3 -10 0% 0 5% -2 10% -4 15% -6 20% 600 Samples TA = -40 to +125°C G = +1 -8 600 Samples G = +1 VDD = 4.0V 25% 24% 22% 20% 18% 16% 14% 12% 10% 8% 6% 4% 2% 0% Percentage of Occurrences Percentage of Occurrences 30% 1 FIGURE 2-12: vs. Gain. 2 4 5 8 Gain (V/V) 10 16 32 Input Noise Voltage Density DS21908A-page 11 MCP6S91/2/3 120 Power Supply Rejection Ratio (dB) 110 100 90 80 70 -50 -25 0 25 50 75 100 125 100 VDD = 2.5V 90 70 60 50 40 30 20 10 100 10 1000 100 PSRR vs. Ambient FIGURE 2-16: 10,000 VDD = 5.5V CH0 = 5.0V 100 MCP6S91 1000000 100k 1M MCP6S92/3 10 PSRR vs. Frequency. MCP6S92/3 VDD = 5.5V 1,000 TA = +125°C 100 TA = +85°C 10 1 1 50 75 100 0.0 0.5 1.0 1.5 2.0 2.5 3.0 3.5 4.0 4.5 5.0 5.5 125 Ambient Temperature (°C) Input Voltage (V) VDD = 5.5V 1.E-09 1n 100p 1.E-10 VDD = 2.5V 10p 1.E-11 1p 1.E-12 25% 20% Input Bias Current vs. Input 39 Samples VDD = 5.5V CH0 = VDD/2 15% 10% 5% 75 100 Ambient Temperature (°C) FIGURE 2-15: Quiescent Current in Shutdown Mode vs. Ambient Temperature. 2004 Microchip Technology Inc. 125 42 50 38 25 34 0 30 -25 26 -50 18 0% 100f 1.E-13 14 1.E-08 10n In Shutdown Mode CH0 = VDD/2 10 1.E-07 100n FIGURE 2-17: Voltage. Percentage of Occurrences FIGURE 2-14: Input Bias Current vs. Ambient Temperature. Quiescent Current in Shutdown (A) 100000 10k Frequency (Hz) Input Bias Current (pA) Input Bias Current (pA) 1,000 10000 1k Ambient Temperature (°C) FIGURE 2-13: Temperature. Input Referred VDD = 5.5V 80 22 Power Supply Rejection Ratio (dB) Note: Unless otherwise indicated, TA = +25°C, VDD = +2.5V to +5.5V, VSS = GND, VREF = VSS, G = +1 V/V, Input = CH0 = (0.3V)/G, CH1 = 0.3V, RL = 10 kΩ to VDD/2 and CL = 60 pF. Quiescent Current in Shutdown (pA) FIGURE 2-18: Shutdown Mode. Quiescent Current in DS21908A-page 12 MCP6S91/2/3 1.2 1.1 1.0 0.9 0.8 0.7 0.6 0.5 0.4 0.3 0.2 0.1 0.0 35 Output Short Circuit Current Magnitude (mA) Quiescent Current (mA) Note: Unless otherwise indicated, TA = +25°C, VDD = +2.5V to +5.5V, VSS = GND, VREF = VSS, G = +1 V/V, Input = CH0 = (0.3V)/G, CH1 = 0.3V, RL = 10 kΩ to VDD/2 and CL = 60 pF. TA = +125°C TA = +85°C TA = +25°C TA = -40°C 30 25 20 10 5 0 0.0 0.5 1.0 1.5 2.0 2.5 3.0 3.5 4.0 4.5 5.0 5.5 Supply Voltage (V) Quiescent Current vs. DC Output Non-Linearity, Input Referred (% of FSR) 1 0.0 0.5 1.0 1.5 2.0 2.5 3.0 3.5 4.0 4.5 5.0 5.5 Power Supply Voltage (V) FIGURE 2-22: Output Short Circuit Current vs. Supply Voltage. VOUT = 0.3V to VDD - 0.3V 0.1 0.01 VONL/G, G = +1 G = +2 G ≥ +4 1 DC Output Non-Linearity, Input Referred (% of FSR) FIGURE 2-19: Supply Voltage. TA = +125°C TA = +85°C TA = +25°C TA = -40°C 15 0.001 VDD = 5.5V 0.1 VONL/G: G = +1 G = +2 G ≥ +4 0.01 0.001 2.5 3.0 3.5 4.0 4.5 5.0 5.5 1 FIGURE 2-20: Supply Voltage. DC Output Non-Linearity vs. FIGURE 2-23: Output Swing. 10 Output Voltage Swing (V P-P) Output Voltage Headroom; VDD-VOH and VOL-VSS (mV) 1000 VDD = 5.5V 100 VDD = 2.5V 10 1 1 10 VDD = 2.5V 1 G = 1, 2 G = 4 to 10 G = 16, 32 0.1 100k 2004 Microchip Technology Inc. 1.E+06 1.E+07 1M 10M Frequency (Hz) Output Plus Ladder Current Magnitude (mA) FIGURE 2-21: Output Voltage Headroom vs. Output Plus Ladder Current (circuit in Figure 4-2). DC Output Non-Linearity vs. VDD = 5.5V 1.E+05 0.1 10 Output Voltage Swing (VP-P) Power Supply Voltage (V) FIGURE 2-24: Frequency. Output Voltage Swing vs. DS21908A-page 13 MCP6S91/2/3 Note: Unless otherwise indicated, TA = +25°C, VDD = +2.5V to +5.5V, VSS = GND, VREF = VSS, G = +1 V/V, Input = CH0 = (0.3V)/G, CH1 = 0.3V, RL = 10 kΩ to VDD/2 and CL = 60 pF. 40 6 Gain Peaking (dB) 30 Gain (dB) 7 G = +32 G = +16 20 10 0 G = +10 G = +8 G = +5 G = +4 -10 -20 100k 1.E+05 G = +2 G = +1 G = +16 G = +4 G = +1 4 3 2 1 0 1.E+06 1.E+07 1.E+08 1M 10M Frequency (Hz) FIGURE 2-25: 5 10 100M 100 1000 Capacitive Load (pF) FIGURE 2-28: Load. Gain vs. Frequency. 100 Gain Peaking vs. Capacitive 6 Input, Output Voltage (V) Bandwidth (MHz) VIN G = +1 G = +4 G = +16 10 1 10 100 Capacitive Load (pF) FIGURE 2-26: Load. 4 3 2 1 0 0 1 2 3 4 Bandwidth vs. Capacitive THD + Noise (%) Measurement BW = 80 kHz VOUT = 2.0VP-P VDD = 5.0V G = +16 G = +1 0.01 G = +4 0.001 1.E+02 1.E+03 8 9 10 0.1 G = +16 0.01 0.001 G = +4 G = +1 1.E+04 1k 10k Frequency (Hz) FIGURE 2-27: THD plus Noise vs. Frequency, VOUT = 2 VP-P. 2004 Microchip Technology Inc. 7 Measurement BW = 80 kHz VOUT = 4 VP-P VDD = 5.0V G = +1, RL = 10 kΩ to 1.5V 0.0001 100 6 FIGURE 2-29: The MCP6S91/2/3 family shows no phase reversal under overdrive. 1 0.1 5 Time (1 µs/div) 1 THD + Noise (%) VOUT -1 1000 VDD = 5.0V G = +1 V/V 5 1.E+05 100k 0.0001 100 1.E+02 1.E+03 1k 1.E+04 10k 1.E+05 100k Frequency (Hz) FIGURE 2-30: THD plus Noise vs. Frequency, VOUT = 4 VP-P. DS21908A-page 14 MCP6S91/2/3 Note: Unless otherwise indicated, TA = +25°C, VDD = +2.5V to +5.5V, VSS = GND, VREF = VSS, G = +1 V/V, Input = CH0 = (0.3V)/G, CH1 = 0.3V, RL = 10 kΩ to VDD/2 and CL = 60 pF. 60 300 150 20 100 10 50 GVIN 0 0 -10 -50 VOUT G = +1 G = +5 G = +32 -150 -200 -50 0.200 0.400 0.600 0.800 1.000 1.200 1.400 1.600 1.0 0.0 0.5 1.0 1.5 Time (200 ns/div) Small-Signal Pulse FIGURE 2-34: Response. 0.65 10 5 CS CS 0.45 0 0.40 -5 0.35 -10 VOUT (CH1 = 0.3V, G = +1) 0.30 0.25 0.00 0.50 1.00 1.50 2.00 5 0 -15 2.50 3.00 3.50 4.00 -20 5.00 4.50 5 CS 1.5 0 1.0 -5 VOUT is "ON" 0.5 -10 1.E+00 2.E+00 3.E+00 4.E+00 5.E+00 6.E+00 7.E+00 8.E+00 9.E+00 1.E+01 1.E+01 Time (1 µs/div) FIGURE 2-33: Shutdown Mode. Output Voltage vs. 2004 Microchip Technology Inc. -2.5 15 10 1.0 5 CS 0.8 CS 0 0.6 -5 0.4 -10 VOUT (CH0 = 0.3V, G = +1) 0 500 1000 1500 2000 2500 -15 3000 3500 4000 4500 5000 -20 1.E+01 -15 Gain Select Timing. 90% 32 Samples 1st Wafer Lot 80% 70% 60% 50% 40% 30% 20% 10% 0% 0.0 10 CS 0.E+00 5.0 Large-Signal Pulse FIGURE 2-35: Percentage of Occurrences Shutdown 2.0 0.0 4.5 Time (500 ns/div) Chip Select Voltage (V) Output Voltage (mV) 2.5 4.0 1.2 0.0 15 VDD = 5.0V CH0 = 0.3V G = +1 Shutdown 3.5 20 0.2 Channel Select Timing. 3.0 3.0 VOUT (CH0 = 0.3V, G = +5) Time (500 ns/div) FIGURE 2-32: -1.5 2.5 1.4 Output Voltage (V) 0.50 15 Chip Select Voltage (V) Output Voltage (V) 0.55 -0.5 1.6 20 VOUT (CH0 = 0.6V, G = +1) 0.60 2.0 0.5 Time (500 ns/div) 0.5 FIGURE 2-31: Response. 1.5 VOUT G = +1 G = +5 G = +32 1.5 0.0 -300 2.000 1.800 2.5 2.0 Chip Select Voltage (V) -60 0.000 3.5 2.5 0.5 -250 4.5 GVIN 3.0 2.0 -40 -100 5.5 3.5 1.5 -30 4.0 1.0 -20 6.5 Normalized Input Voltage (1V/div) 30 4.5 Output Voltage (V) 200 7.5 VDD = 5.0V 250 40 Normalized Input Voltage (50 mV/div) Output Voltage (10 mV/div) 5.0 VDD = 5.0V 50 Minimum Valid Supply Voltage (V) FIGURE 2-36: Minimum Valid Supply Voltage (register data still valid). DS21908A-page 15 MCP6S91/2/3 1.2 1.1 1.0 0.9 0.8 0.7 0.6 0.5 0.4 0.3 0.2 0.1 0.0 G = 1 V/V VDD = 2.5V 0.0 TA = +125°C TA = +85°C TA = +25°C TA = -40°C 0.5 1.0 Input Offset Voltage (mV) Input Offset Voltage (mV) Note: Unless otherwise indicated, TA = +25°C, VDD = +2.5V to +5.5V, VSS = GND, VREF = VSS, G = +1 V/V, Input = CH0 = (0.3V)/G, CH1 = 0.3V, RL = 10 kΩ to VDD/2 and CL = 60 pF. 1.5 2.0 2.5 Input Voltage (V) Output Voltage Headroom; VDD–VOH and VOL–VSS (mV) G = 1 V/V VDD = 5.5V TA = +125°C TA = +85°C TA = +25°C TA = -40°C 0.0 0.5 1.0 1.5 2.0 2.5 3.0 3.5 4.0 4.5 5.0 5.5 Input Voltage (V) FIGURE 2-37: Input Offset Voltage vs. Input Voltage, VDD = 2.5V. 35 1.2 1.1 1.0 0.9 0.8 0.7 0.6 0.5 0.4 0.3 0.2 0.1 0.0 FIGURE 2-39: Input Offset Voltage vs. Input Voltage, VDD = 5.5V. VREF = VSS 30 VDD = 5.5V: VDD–VOH VOL–VSS VDD = 2.5V: VDD–VOH VOL–VSS 25 20 15 10 5 0 -50 -25 0 25 50 75 100 125 Ambient Temperature (°C) FIGURE 2-38: Output Voltage Headroom vs. Ambient Temperature. 2004 Microchip Technology Inc. DS21908A-page 16 MCP6S91/2/3 3.0 PIN DESCRIPTIONS Descriptions of the pins are listed in Table 3-1. TABLE 3-1: PIN FUNCTION TABLE MCP6S91 MCP6S92 MCP6S93 Symbol 1 1 1 VOUT Analog Output 2 2 2 CH0 Analog Input — 3 3 CH1 Analog Input 3 — 4 VREF External Reference Pin 4 4 5 VSS Negative Power Supply 5 5 6 CS SPI™ Chip Select 6 6 7 SI SPI Serial Data Input — — 8 SO 7 7 9 SCK SPI Clock Input 8 8 10 VDD Positive Power Supply 3.1 Analog Output Description SPI Serial Data Output 3.4 Power Supply (VSS and VDD) The output pin (VOUT) is a low-impedance voltage source. The selected gain (G), selected input (CH0, CH1) and voltage at VREF determine its value. The Positive Power Supply Pin (VDD) is 2.5V to 5.5V higher than the Negative Power Supply Pin (VSS). For normal operation, the other pins are at voltages between VSS and VDD. 3.2 Typically, these parts are used in a single (positive) supply configuration. In this case, VSS is connected to ground and VDD is connected to the supply. VDD will need a local bypass capacitor (typically 0.01 µF to 0.1 µF) within 2 mm of the VDD pin. These parts can share a bulk capacitor with analog parts (typically 2.2 µF to 10 µF) within 100 mm of the VDD pin. Analog Inputs (CH0, CH1) The inputs CH0 and CH1 connect to the signal sources. They are high-impedance CMOS inputs with low bias currents. The internal MUX selects which one is amplified to the output. 3.3 External Reference Voltage (VREF) The VREF pin, which is an analog input, should be at a voltage between VSS and VDD (the MCP6S92 has VREF tied internally to VSS). The voltage at this pin shifts the output voltage. 3.5 Digital Inputs The SPI interface inputs are: Chip Select (CS), Serial Input (SI) and Serial Clock (SCK). These are Schmitttriggered, CMOS logic inputs. 3.6 Digital Output The MCP6S93 device has a SPI interface Serial Output (SO) pin. This is a CMOS push-pull output and does not ever go High-Z. Once the device is deselected (CS goes high), SO is forced low. This feature supports daisy-chaining, as explained in Section 5.3 “DaisyChain Configuration”. 2004 Microchip Technology Inc. DS21908A-page 17 MCP6S91/2/3 4.0 ANALOG FUNCTIONS 4.2 The MCP6S91/2/3 family of Programmable Gain Amplifiers (PGA) is based on simple analog building blocks (see Figure 4-1). Each of these blocks will be explained in more detail in the following subsections. VDD MUX CS SI SO SCK SPI™ Logic VOUT RF 8 Gain Switches RG Resistor Ladder (RLAD) CH0 CH1 VREF VSS MCP6S91 – One input (CH0), no SO pin MCP6S92 – Two inputs (CH0, CH1), VREF tied internally to VSS, no SO pin MCP6S93 – Two inputs (CH0, CH1) FIGURE 4-1: 4.1 PGA Block Diagram. Input MUX Internal Op Amp The internal op amp gives the right combination of bandwidth, accuracy and flexibility. 4.2.1 COMPENSATION CAPACITORS The internal op amp has three compensation capacitors (comp. caps.) connected to a switching network. They are selected to give good small-signal bandwidth at high gains and good slew rates (full-power bandwidth) at low gains. The change in bandwidth as gain changes is between 2 and 12 MHz. Refer to Table 4-1 for more information. TABLE 4-1: Gain (V/V) Internal Comp. Cap. GBWP (MHz) Typ. SR (V/µs) Typ. FPBW (MHz) Typ. BW (MHz) Typ. 1 Large 12 4.0 0.30 12 2 Large 12 4.0 0.30 6 4 Medium 20 11 0.70 10 5 Medium 20 11 0.70 7 8 Medium 20 11 0.70 2.4 10 Medium 20 11 0.70 2.0 16 Small 64 22 1.6 5 32 Small 64 22 1.6 2.0 Note 1: The MCP6S91 has one input, while the MCP6S92 and MCP6S93 have two inputs (see Figure 4-1). 2: For the lowest input current, float unused inputs. Tying these pins to a voltage near the active channel’s bias voltage also works well. For simplicity, they can be tied to VSS or VDD, but the input current may increase. 3: The one-channel MCP6S91 has approximately the same input bias current as the two-channel MCP6S92 and MCP6S93. The input offset voltage mismatch between channels (∆VOS) is, ideally, 0 µV. The input MUX uses CMOS transmission gates that have drain-source (channel) resistance, but no offset voltage. The histogram in Figure 2-8 reflects the measurement repeatability (i.e., noise power bandwidth) rather than the actual mismatch. Reducing the measurement bandwidth will produce a more narrow histogram and give an average closer to 0 µV. 2004 Microchip Technology Inc. GAIN VS. INTERNAL COMPENSATION CAPACITOR 4.2.2 FPBW is the Full-Power Bandwidth. These numbers are based on VDD = 5.0V. No changes in DC performance (e.g., VOS) accompany a change in compensation capacitor. BW is the closed-loop, small signal -3 dB bandwidth. RAIL-TO-RAIL CHANNEL INPUTS The input stage of the internal op amp uses two differential input stages in parallel; one operates at low VIN (input voltage), while the other operates at high VIN. With this topology, the internal inputs can operate to 0.3V past either supply rail. The input offset voltage is measured at both VIN = VSS – 0.3V and VDD + 0.3V to ensure proper operation. The transition between the two input stages occurs when VIN ≈ VDD – 1.5V. For the best distortion and gain linearity, avoid this region of operation. DS21908A-page 18 MCP6S91/2/3 4.2.3 RAIL-TO-RAIL OUTPUT The maximum output voltage swing is the maximum swing possible under a particular amplifier load current. The amplifier load current is the sum of the external load current (IOUT) and the current through the ladder resistance (ILAD); see Figure 4-2. MCP6S9X RIN VIN EQUATION 4-1: RIN ≥ Amplifier Load Current = I OUT + I LAD Where: RIN ≥ ( VOUT – VREF ) I LAD = ------------------------------------RLAD VOUT ILAD RLAD VREF FIGURE 4-2: Amplifier Load Current. See Figure 2-21 for the typical output headroom (VDD – VOH or VOL – VSS) as a function of amplifier load current. The specification table states the output can reach within 60 mV of either supply rail when RL = 10 kΩ and VREF = VDD/2. 4.2.4 (Maximum expected VIN) – VDD 2 mA VSS – (Maximum expected VIN) FIGURE 4-3: into an input pin. 4.3 IOUT VOUT CHx 2 mA RIN limits the current flow Resistor Ladder The resistor ladder shown in Figure 4-1 (RLAD = RF + RG) sets the gain. Placing the gain switches in series with the inverting input reduces the parasitic capacitance, distortion and gain mismatch. RLAD is an additional load on the output of the PGA and causes additional current draw from the supplies. It is also a load (ZIN_REF) on the external circuitry driving the VREF pin. In Shutdown mode, RLAD is still attached to the VOUT and VREF pins. Thus, these pins and the internal amplifier’s inverting input are all connected through RLAD and the output is not High-Z (unlike the internal op amp). While RLAD contributes to the output noise, its effect is small. Refer to Figure 2-12. INPUT VOLTAGE AND PHASE REVERSAL The MCP6S91/2/3 amplifier family is designed with CMOS input devices. It is designed to not exhibit phase inversion when the input pins exceed the supply voltages. Figure 2-29 shows an input voltage exceeding both supplies with no resulting phase inversion. The maximum voltage that can be applied to the input pins (CHx) is VSS – 0.3V to VDD + 0.3V. Voltages on the inputs that exceed this absolute maximum rating can cause excessive current to flow into or out of the input pins. Current beyond ±2 mA can cause possible reliability problems. Applications that exceed this rating must be externally limited with an input resistor, as shown in Figure 4-3. 2004 Microchip Technology Inc. DS21908A-page 19 MCP6S91/2/3 4.4 Rail-to-Rail VREF Input The VREF input is intended to be driven by a lowimpedance voltage source. The source driving the VREF pin should have an output impedance less than 0.1Ω to maintain reasonable gain accuracy. The supply voltage VSS and VDD usually meet this requirement. RLAD presents a load at the VREF pin to the external circuit (ZIN_REF ≈ (5 kΩ/G)||(6 pF)), which depends on the gain. Any source driving the VREF pin must be capable of driving a load as heavy as 0.16 kΩ||6 pF (G = 32). The absolute maximum voltages that can be applied to the reference input pin (VREF) are VSS – 0.3V and VDD + 0.3V. Voltages on the inputs that exceed this absolute maximum rating can cause excessive current to flow into or out of this pin. Current beyond ±2 mA can cause possible reliability problems. Because an external series resistor cannot be used (for low gain error), the external circuit must ensure that VREF is between VSS – 0.3V and VDD + 0.3V. The VIVR_REF spec shows the region of normal operation for the VREF pin (VSS to VDD). Staying within this region ensures proper operation of the PGA and its surrounding circuitry. 4.5 Shutdown Mode These PGAs use a software shutdown command. When the SPI interface sends a shutdown command, the internal op amp is shut down and its output placed in a High-Z state. The resistive ladder is always connected between VREF and VOUT; even in shutdown. This means that the output resistance will be on the order of 5 kΩ, with a path for output signals to appear at the input. 2004 Microchip Technology Inc. DS21908A-page 20 MCP6S91/2/3 5.0 DIGITAL FUNCTIONS Chain Configuration”, covers applications using multiple 16-bit words. SO goes low after CS goes high; it has a push-pull output that does not go into a high-Z state. The MCP6S91/2/3 PGAs use a standard SPI compatible serial interface to receive instructions from a controller. This interface is configured to allow daisychaining with other SPI devices. 5.1 The MCP6S91/2/3 devices operate in SPI modes 0,0 and 1,1. In 0,0 mode, the clock idles in the low state (Figure 5-1). In 1,1 mode, the clock idles in the high state (Figure 5-2). In both modes, SI data is loaded into the PGA on the rising edge of SCK, while SO data is clocked out on the falling edge of SCK. In 0,0 mode, the falling edge of CS also acts as the first falling edge of SCK (see Figure 5-1). There must be multiples of 16 clocks (SCK) while CS is low or commands will abort (see Section 5.3 “Daisy-Chain Configuration”). SPI Timing Chip Select (CS) toggles low to initiate communication with these devices. The first byte of each SI word (two bytes long) is the instruction byte, which goes into the Instruction register. The Instruction register points the second byte to its destination. In a typical application, CS is raised after one word (16 bits) to implement the desired changes. Section 5.3 “Daisy- 2 3 4 5 6 7 8 9 bit 7 1 bit 0 CS 10 11 12 13 14 15 16 SCK bit 0 bit 7 SI Instruction Byte Data Byte SO (first 16 bits out are always zeros) FIGURE 5-1: Serial Bus Sequence for the PGA; SPI™ 0,0 Mode (see Figure 1-4). 2 3 4 5 6 7 8 9 bit 7 1 bit 0 CS 10 11 12 13 14 15 16 SCK Instruction Byte bit 0 bit 7 SI Data Byte SO (first 16 bits out are always zeros) FIGURE 5-2: Serial Bus Sequence for the PGA; SPI™ 1,1 Mode (see Figure 1-5). 2004 Microchip Technology Inc. DS21908A-page 21 MCP6S91/2/3 5.2 Registers The analog functions are programmed through the SPI interface using 16-bit words (see Figure 5-1 and Figure 5-2). This data is sent to two of three 8-bit registers: Instruction register (Register 5-1), Gain register (Register 5-2) and Channel register (Register 5-3). There are no power-up defaults for these three registers. 5.2.1 ENSURING VALID DATA IN THE REGISTERS A 0.1 µF bypass capacitor mounted as close as possible to the VDD pin provides additional transient immunity. 5.2.2 After power up, the registers contain random data that must be initialized. Sending valid gain and channel selection commands to the internal registers puts valid data into those registers. Also, the internal state machine starts in an arbitrary state. Toggling the Chip Select pin (CS) from high to low, then back to high again, puts the internal state machine in a known, valid condition (this can be done by entering any valid command). REGISTER 5-1: After power-up, and when the power supply voltage dips below the minimum valid VDD (VDD_VAL), the internal register data and state machine may need to be reset. This is accomplished as described before. Use an external system supervisor to detect these events so that the microcontroller will reset the PGA state and registers. INSTRUCTION REGISTER The Instruction register has 3 command bits and 1 indirect address bit; see Register 5-1. The command bits include a NOP (000) to support daisy-chaining (see Section 5.3 “Daisy-Chain Configuration”); the other NOP commands shown should not be used (they are reserved for future use). The device is brought out of Shutdown mode when a valid command, other than NOP or Shutdown, is sent and CS is raised. INSTRUCTION REGISTER W-0 W-0 W-0 U-x U-x U-x U-x W-0 M2 M1 M0 — — — — A0 bit 7 bit 0 bit 7-5 M2-M0: Command bits 000 = NOP (Note 1) 001 = PGA enters Shutdown mode as soon as a full 16-bit word is sent and CS is raised. (Notes 1 and 2) 010 = Write to register. 011 = NOP (reserved for future use) (Note 1) 1XX = NOP (reserved for future use) (Note 1) bit 4-1 Unimplemented: Read as ‘0’ (reserved for future use) bit 0 A0: Indirect Address bit 1 = Addresses the Channel register 0 = Addresses the Gain register Note 1: 2: All other bits in the 16-bit word (including A0) are “don’t cares.” The device exits Shutdown mode when a valid command (other than NOP or Shutdown) is sent and CS is raised; that valid command will be executed. Shutdown does not toggle. Legend: R = Readable bit W = Writable bit U = Unimplemented bit, read as ‘0’ -n = Value at POR ‘1’ = Bit is set ‘0’ = Bit is cleared 2004 Microchip Technology Inc. x = Bit is unknown DS21908A-page 22 MCP6S91/2/3 5.2.3 SETTING THE GAIN The amplifier can be programmed to produce binary and decimal gain settings between +1 V/V and +32 V/V. Register 5-2 shows the details. At the same time, different compensation capacitors are selected to optimize the bandwidth vs. slew rate trade-off (see Table 4-1). REGISTER 5-2: GAIN REGISTER U-x U-x U-x U-x U-x W-0 W-0 W-0 — — — — — G2 G1 G0 bit 7 bit 0 bit 7-3 Unimplemented: Read as ‘0’ (reserved for future use) bit 2-0 G2-G0: Gain Select bits 000 = Gain of +1 001 = Gain of +2 010 = Gain of +4 011 = Gain of +5 100 = Gain of +8 101 = Gain of +10 110 = Gain of +16 111 = Gain of +32 Legend: R = Readable bit W = Writable bit U = Unimplemented bit, read as ‘0’ -n = Value at POR ‘1’ = Bit is set ‘0’ = Bit is cleared 2004 Microchip Technology Inc. x = Bit is unknown DS21908A-page 23 MCP6S91/2/3 5.2.4 CHANGING THE CHANNEL If the Instruction register is programmed to address the Channel register, the multiplexed inputs of the MCP6S92 and MCP6S93 can be changed using Register 5-3. REGISTER 5-3: CHANNEL REGISTER U-x U-x U-x U-x U-x U-x U-x W-0 — — — — — — — C0 bit 7 bit 0 bit 7-1 Unimplemented: Read as ‘0’ (reserved for future use) bit 0 C0: Channel Select bit 0= 1= MCP6S91 CH0 CH0 MCP6S92 CH0 CH1 MCP6S93 CH0 CH1 Legend: R = Readable bit W = Writable bit U = Unimplemented bit, read as ‘0’ -n = Value at POR ‘1’ = Bit is set ‘0’ = Bit is cleared 2004 Microchip Technology Inc. x = Bit is unknown DS21908A-page 24 MCP6S91/2/3 5.2.5 SHUTDOWN COMMAND The example in Figure 5-3 shows a daisy-chain configuration with two devices, although any number of devices can be configured this way. The MCP6S91 and MCP6S92 can only be used at the far end of the daisychain, because they do not have a serial data out (SO) pin. As shown in Figure 5-4 and Figure 5-5, both SI and SO data are sent in 16-bit (2 byte) words. These devices abort any command that is not a multiple of 16 bits. The software shutdown command allows the user to put the amplifier into a low-power mode (see Register 5-1). In this Shutdown mode, most pins are high-impedance (Section 4.5 “Shutdown Mode” and Section 5.1 “SPI Timing” cover the exceptions at pins VREF, VOUT and SO). Once the PGA has entered Shutdown mode, it will remain in this mode until either a valid command is sent to the device (other than NOP or Shutdown) or the device is powered down and back up again. The internal registers maintain their values while in shutdown. When using the daisy-chain configuration, the maximum clock speed possible is reduced to ≈ 5.8 MHz due to the SO pin’s propagation delay (see Electrical Specifications). The internal SPI shift register is automatically loaded with zeros whenever CS goes high (a command is executed). Thus, the first 16-bits out of the SO pin after the CS line goes low are always zeros. This means that the first command loaded into the next device in the daisy-chain is a NOP. This feature makes it possible to send shorter command and data byte strings when the farthest devices do not need to change. For example, if there were three devices on the chain, and only the middle device needed changing, then only 32 bytes of data need to be transmitted (for the first and middle devices). The last device on the chain would receive a NOP when the CS pin is raised to execute the command. Once brought out of Shutdown mode, the part returns to its previous state (see Section 5.2.1 “Ensuring Valid Data in the Registers” for exceptions to this rule). This makes it possible to bring the device out of shutdown mode using one command; send a command to select the current channel (or gain) and the device will exit shutdown with the same state that existed before shutdown. 5.3 Daisy-Chain Configuration Multiple MCP6S91/2/3 devices can be connected in a daisy-chain configuration by connecting the SO pin from one device to the SI pin on the next device and using common SCK and CS lines (Figure 5-3). This approach reduces PCB layout complexity and uses fewer PICmicro® microcontroller I/O pins. CS SCK SO PICmicro® Microcontroller CS SCK SO SI Device 1 1. Set CS low. 2. Clock out the instruction and data for device 2 (16 clocks) to Device 1. 3. Device 1 automatically clocks out all zeros (first 16 clocks) to Device 2. 4. Clock out the instruction and data for Device 1 (16 clocks) to Device 1. 5. Device 1 automatically shifts data from Device 1 to Device 2 (16 clocks). 6. Raise CS. FIGURE 5-3: CS SCK SO SI Device 2 Device 1 Device 2 00100000 00000000 00000000 00000000 Device 1 Device 2 01000001 00000111 00100000 00000000 Daisy-Chain Configuration. 2004 Microchip Technology Inc. DS21908A-page 25 MCP6S91/2/3 CS 1 2 3 4 5 6 7 8 9 10111213141516 1 2 3 4 5 6 7 8 9 10111213141516 SCK Instruction Byte for Device 2 Instruction Byte for Device 1 Data Byte for Device 2 bit 0 bit 0 bit 7 bit 0 bit 7 bit 0 bit 7 bit 7 SI Data Byte for Device 1 Instruction Byte for Device 2 FIGURE 5-4: bit 0 bit 0 bit 7 (first 16 bits out are always zeros) bit 7 SO Data Byte for Device 2 Serial Bus Sequence for Daisy-Chain Configuration; SPI™ 0,0 Mode. CS 1 2 3 4 5 6 7 8 9 10111213141516 1 2 3 4 5 6 7 8 9 10111213141516 SCK Instruction Byte for Device 2 Data Byte for Device 2 Instruction Byte for Device 1 bit 0 bit 0 bit 7 bit 0 bit 7 bit 0 bit 7 bit 7 SI Data Byte for Device 1 Instruction Byte for Device 2 FIGURE 5-5: bit 0 bit 0 bit 7 (first 16 bits out are always zeros) bit 7 SO Data Byte for Device 2 Serial Bus Sequence for Daisy-Chain Configuration; SPI™ 1,1 Mode. 2004 Microchip Technology Inc. DS21908A-page 26 MCP6S91/2/3 APPLICATIONS INFORMATION 6.1 Changing External Reference Voltage Figure 6-1 shows a MCP6S91 with the VREF pin at 2.5V and VDD = 5.0V. This allows the PGA to amplify signals centered on 2.5V, instead of ground-referenced signals. The voltage reference MCP1525 is buffered by a MCP6021, which gives a low output impedance reference voltage from DC to high frequencies. The source driving the VREF pin should have an output impedance less than 0.1Ω to maintain reasonable gain accuracy. VDD VIN MCP6S91 VREF VOUT VDD MCP1525 2.5V REF VDD RISO VIN FIGURE 6-2: Capacitive Loads. 1,000 100 10 10p 10 FIGURE 6-3: 6.2 Capacitive Load and Stability Large capacitive loads can cause stability problems and reduced bandwidth for the MCP6S91/2/3 family of PGAs (Figure 2-26 and Figure 2-28). As the load capacitance increases, there is a corresponding increase in frequency response peaking and step response overshoot and ringing. This happens because a large load capacitance decreases the internal amplifier’s phase margin and bandwidth. When driving large capacitive loads with these PGAs (i.e., > 60 pF), a small series resistor at the output (RISO in Figure 6-2) improves the internal amplifier’s stability by making the load resistive at higher frequencies. The bandwidth will be generally lower than the bandwidth with no capacitive load. 2004 Microchip Technology Inc. PGA Circuit for Large Figure 6-3 gives recommended RISO values for different capacitive loads. After selecting RISO for your circuit, double-check the resulting frequency response peaking and step response overshoot on the bench. Modify RISO’s value until the response is reasonable at all gains. 1µF MCP6021 FIGURE 6-1: PGA with Different External Reference Voltage. VOUT MCP6S9X CL Recommended R ISO (Ω) 6.0 6.3 100 1,000 100p 1n Load Capacitance (F) 10,000 10n Recommended RISO. Layout Considerations Good PC board layout techniques will help achieve the performance shown in the Electrical Characteristics and Typical Performance Curves. It will also help minimize Electromagnetic Compatibility (EMC) issues. 6.3.1 COMPONENT PLACEMENT Separate different circuit functions: digital from analog, low-speed from high-speed, and low-power from highpower. This will reduce crosstalk. Keep sensitive traces short and straight. Separate them from interfering components and traces. This is especially important for high-frequency (low rise time) signals. DS21908A-page 27 MCP6S91/2/3 6.3.2 SUPPLY BYPASS 6.3.4 SIGNAL COUPLING Use a local bypass capacitor (0.01 µF to 0.1 µF) within 2 mm of the VDD pin. It must connect directly to the ground plane. A multi-layer ceramic chip capacitor, or high-frequency equivalent, works best. The input pins of the MCP6S91/2/3 family of PGAs are high-impedance. This makes them especially susceptible to capacitively-coupled noise. Using a ground plane helps reduce this problem. Use a bulk bypass capacitor (2.2 µF to 10 µF) within 100 mm of the VDD pin. It needs to connect to the ground plane. A multi-layer ceramic chip capacitor, tantalum or high-frequency equivalent, works best. This capacitor may be shared with other nearby analog parts. When noise is capacitively coupled, the ground plane provides additional shunt capacitance to ground. When noise is magnetically coupled, the ground plane reduces the mutual inductance between traces. Increasing the separation between traces makes a significant difference. 6.3.3 INPUT SOURCE IMPEDANCE The sources driving the inputs of the PGAs need to have reasonably low source impedance at higher frequencies. Figure 6-4 shows how the external source impedance (RS), PGA package pin capacitance (CP1) and PGA package pin-to-pin capacitance (CP2) form a positive feedback voltage divider network. Feedback to the selected channel may cause frequency response peaking and step response overshoot and ringing. Feedback to an unselected channel will produce crosstalk. CP2 RS VIN MCP6S9X VOUT CP1 FIGURE 6-4: Changing the direction of one of the traces can also reduce magnetic coupling. It may help to locate guard traces next to the victim trace. They should be on both sides of, and as close as possible to, the victim trace. Connect the guard traces to the ground plane at both ends. Also connect long guard traces to the ground plane in the middle. 6.3.5 HIGH-FREQUENCY ISSUES Because the MCP6S91/2/3 PGAs’ frequency response reaches unity gain at 64 MHz when G = 16 and 32, it is important to use good PCB layout techniques. Any parasitic-coupling at high-frequency might cause undesired peaking. Filtering high-frequency signals (i.e., fast edge rates) can help. To minimize highfrequency problems: • • • • • Use complete ground and power planes Use HF, surface-mount components Provide clean supply voltages and bypassing Keep traces short and straight Try a linear power supply (e.g., a LDO) Positive Feedback Path. Figure 2-6 shows the crosstalk (referred to input) that results when a hostile signal is connected to CH1, input CH0 is selected and RS is connected from CH0 to GND. A gain of +32 was chosen for this plot because it demonstrates the worst-case behavior. Increasing RS increases the crosstalk as expected. At a source impedance of 10 kΩ, there is noticeable peaking in the response; this is due to positive feedback. Most designs should use a source resistance (RS) no larger than 10 kΩ. Careful attention to layout parasitics and proper component selection will help minimize this effect. When a source impedance larger than 10 kΩ must be used, place a capacitor in parallel to CP1 to reduce the positive feedback. This capacitor needs to be large enough to overcome gain (or crosstalk) peaking, yet small enough to allow a reasonable signal bandwidth. 2004 Microchip Technology Inc. DS21908A-page 28 MCP6S91/2/3 6.4 Typical Applications VIN 6.4.1 GAIN RANGING MCP6291 Figure 6-5 shows a circuit that measures the current IX. The circuit’s performance benefits from changing the gain on the PGA. Just as a hand-held multimeter uses different measurement ranges to obtain the best results, this circuit makes it easy to set a high gain for small signals and a low gain for large signals. As a result, the required dynamic range at the PGA’s output is less than at its input (by up to 30 dB). MCP6S9X IX VOUT RS VOUT MCP6S91 1.11 kΩ FIGURE 6-7: Range. 6.4.3 PGA with Lower Gain EXTENDED GAIN RANGE PGA Figure 6-8 gives a +1 V/V to +1024 V/V gain range, which is much greater than the range for a single PGA (+1 V/V to +32 V/V). The first PGA provides input multiplexing capability, while the second PGA only needs one input. These devices can be daisy-chained (Section 5.3 “Daisy-Chain Configuration”). FIGURE 6-5: Wide Dynamic Range Current Measurement Circuit. 6.4.2 10.0 kΩ SHIFTED GAIN RANGE PGA Figure 6-6 shows a circuit using a MCP6291 at a gain of +10 in front of a MCP6S91. This shifts the overall gain range to +10 V/V to +320 V/V (from +1 V/V to +32 V/V). VIN MCP6S92 MCP6S91 VOUT VIN MCP6291 MCP6S91 VOUT FIGURE 6-8: Range. 6.4.4 MULTIPLE SENSOR AMPLIFIER The multiple-channel PGAs (MCP6S92 and MCP6S93) allow the user to select which sensor appears on the output (see Figure 6-9). These devices can also change the gain to optimize performance for each sensor. 10.0 kΩ 1.11 kΩ FIGURE 6-6: Range. PGA with Extended Gain PGA with Higher Gain It is also easy to shift the gain range to lower gains (see Figure 6-7). The MCP6291 acts as a unity gain buffer, and the resistive voltage divider shifts the gain range down to +0.1 V/V to +3.2 V/V (from +1 V/V to +32 V/V). 2004 Microchip Technology Inc. Sensor # 0 MCP6S93 VOUT Sensor # 1 FIGURE 6-9: Inputs. PGA with Multiple Sensor DS21908A-page 29 MCP6S91/2/3 6.4.5 6.4.7 EXPANDED INPUT PGA Figure 6-10 shows cascaded MCP6S28 and MCP6S92s PGAs that provide up to 9 input channels. Obviously, Sensors #1-8 have a high total gain range available, as explained in Section 6.4.3 “Extended Gain Range PGA”. These devices can be daisychained (Section 5.3 “Daisy-Chain Configuration”). ADC DRIVER This family of PGAs is well suited for driving Analog-toDigital Converters (ADCs). The binary gains (1, 2, 4, 8, 16 and 32) effectively add five more bits to the input range (see Figure 6-12). This works well for applications needing relative accuracy more than absolute accuracy (e.g., power monitoring). Low-pass Filter Sensor #0 MCP6S92 Sensors # 1-8 VOUT VIN MCP6S92 MCP6S28 FIGURE 6-12: FIGURE 6-10: 6.4.6 PGA with Expanded Inputs. PICmicro® MCU WITH EXPANDED INPUT CAPABILITY Figure 6-11 shows a MCP6S93 driving an analog input to a PICmicro microcontroller. This greatly expands the input capacity of the microcontroller, while adding the ability to select the appropriate gain for each source. VIN PICmicro® Microcontroller MCP6S93 MCP3201 3 12-bit ADC OUT PGA as an ADC driver. At low gains, the ADC’s Signal-to-Noise Ratio (SNR) will dominate since the PGA’s input noise voltage density is so low (10 nV/√Hz @ 10 kHz, typ.). At high gains, the PGA’s noise will dominate the SNR, but it is low enough to support most applications. These PGAs add the flexibility of selecting the best gain for an application. The low-pass filter in the block diagram reduces the integrated noise at the MCP6S92’s output and serves as an anti-aliasing filter. This filter may be designed using Microchip’s FilterLab® software, available at www.microchip.com. SPI™ FIGURE 6-11: Expanded Input for a PICmicro® Microcontroller. 2004 Microchip Technology Inc. DS21908A-page 30 MCP6S91/2/3 7.0 PACKAGING INFORMATION 7.1 Package Marking Information 8-Lead PDIP (300 mil) (MCP6S91, MCP6S92) XXXXXXXX XXXXXNNN YYWW MCP6S91 E/P256 0424 8-Lead SOIC (150 mil) (MCP6S91, MCP6S92) XXXXXXXX XXXXYYWW NNN 10-Lead MSOP (MCP6S93) XXXXX YWWNNN Note: * Example: 6S91E 424256 XXXXX YWWNNN XX...X YY WW NNN Example: MCP6S91 E/SN0424 256 8-Lead MSOP (MCP6S91, MCP6S92) Legend: Example: Example: 6S93E 424256 Customer specific information* Year code (last 2 digits of calendar year) Week code (week of January 1 is week ‘01’) Alphanumeric traceability code In the event the full Microchip part number cannot be marked on one line, it will be carried over to the next line thus limiting the number of available characters for customer specific information. Standard marking consists of Microchip part number, year code, week code, traceability code (facility code, mask rev#, and assembly code). For marking beyond this, certain price adders apply. Please check with your Microchip Sales Office. 2004 Microchip Technology Inc. DS21908A-page 31 MCP6S91/2/3 8-Lead Plastic Dual In-line (P) – 300 mil (PDIP) E1 D 2 n 1 α E A2 A L c A1 β B1 p eB B Units Dimension Limits n p Number of Pins Pitch Top to Seating Plane Molded Package Thickness Base to Seating Plane Shoulder to Shoulder Width Molded Package Width Overall Length Tip to Seating Plane Lead Thickness Upper Lead Width Lower Lead Width Overall Row Spacing Mold Draft Angle Top Mold Draft Angle Bottom * Controlling Parameter § Significant Characteristic § A A2 A1 E E1 D L c B1 B eB α β MIN .140 .115 .015 .300 .240 .360 .125 .008 .045 .014 .310 5 5 INCHES* NOM MAX 8 .100 .155 .130 .170 .145 .313 .250 .373 .130 .012 .058 .018 .370 10 10 .325 .260 .385 .135 .015 .070 .022 .430 15 15 MILLIMETERS NOM 8 2.54 3.56 3.94 2.92 3.30 0.38 7.62 7.94 6.10 6.35 9.14 9.46 3.18 3.30 0.20 0.29 1.14 1.46 0.36 0.46 7.87 9.40 5 10 5 10 MIN MAX 4.32 3.68 8.26 6.60 9.78 3.43 0.38 1.78 0.56 10.92 15 15 Notes: Dimensions D and E1 do not include mold flash or protrusions. Mold flash or protrusions shall not exceed .010” (0.254mm) per side. JEDEC Equivalent: MS-001 Drawing No. C04-018 2004 Microchip Technology Inc. DS21908A-page 32 MCP6S91/2/3 8-Lead Plastic Small Outline (SN) – Narrow, 150 mil (SOIC) E E1 p D 2 B n 1 α h 45° c A2 A φ β L Units Dimension Limits n p Number of Pins Pitch Overall Height Molded Package Thickness Standoff § Overall Width Molded Package Width Overall Length Chamfer Distance Foot Length Foot Angle Lead Thickness Lead Width Mold Draft Angle Top Mold Draft Angle Bottom * Controlling Parameter § Significant Characteristic A A2 A1 E E1 D h L φ c B α β MIN .053 .052 .004 .228 .146 .189 .010 .019 0 .008 .013 0 0 A1 INCHES* NOM 8 .050 .061 .056 .007 .237 .154 .193 .015 .025 4 .009 .017 12 12 MAX .069 .061 .010 .244 .157 .197 .020 .030 8 .010 .020 15 15 MILLIMETERS NOM 8 1.27 1.35 1.55 1.32 1.42 0.10 0.18 5.79 6.02 3.71 3.91 4.80 4.90 0.25 0.38 0.48 0.62 0 4 0.20 0.23 0.33 0.42 0 12 0 12 MIN MAX 1.75 1.55 0.25 6.20 3.99 5.00 0.51 0.76 8 0.25 0.51 15 15 Notes: Dimensions D and E1 do not include mold flash or protrusions. Mold flash or protrusions shall not exceed .010” (0.254mm) per side. JEDEC Equivalent: MS-012 Drawing No. C04-057 2004 Microchip Technology Inc. DS21908A-page 33 MCP6S91/2/3 8-Lead Plastic Micro Small Outline Package (MS) (MSOP) E p E1 D 2 B n 1 α A2 A c φ A1 (F) L β Number of Pins Pitch Overall Height MILLIMETERS* INCHES Units Dimension Limits n p MAX NOM MIN MIN NOM 0.65 .026 .044 A 1.18 .038 0.76 0.86 .006 0.05 0.97 .193 .200 4.67 4.90 .5.08 .114 .118 .114 .118 .122 2.90 3.00 3.10 .122 2.90 3.00 L .016 3.10 .022 .028 0.40 0.55 .035 Foot Angle F φ 0.70 .037 .039 0.90 0.95 1.00 Lead Thickness c 6 0 .004 .006 .008 0.10 0.15 0.20 Lead Width Mold Draft Angle Top B α .010 .012 .016 0.25 0.30 0.40 Mold Draft Angle Bottom β Molded Package Thickness A2 .030 Standoff A1 .002 E .184 Molded Package Width E1 Overall Length D Foot Length Footprint (Reference) § Overall Width MAX 8 8 .034 0 0.15 6 7 7 7 7 *Controlling Parameter § Significant Characteristic Notes: Dimensions D and E1 do not include mold flash or protrusions. Mold flash or protrusions shall not exceed .010" (0.254mm) per side. Drawing No. C04-111 2004 Microchip Technology Inc. DS21908A-page 34 MCP6S91/2/3 10-Lead Plastic Micro Small Outline Package (MS) (MSOP) E E1 p D 2 B n 1 α A φ c A2 A1 L (F) β L1 Units Dimension Limits n p MIN INCHES NOM 10 .020 TYP .033 .193 BSC .118 BSC .118 BSC .024 .037 REF .009 - MAX MILLIMETERS* NOM 10 0.50 TYP. 0.85 0.75 0.00 4.90 BSC 3.00 BSC 3.00 BSC 0.60 0.40 0.95 REF 0° 0.08 0.15 0.23 5° 5° MIN Number of Pins Pitch .043 Overall Height A Molded Package Thickness .037 A2 .030 Standoff .006 A1 .000 Overall Width E Molded Package Width E1 Overall Length D Foot Length .031 L .016 Footprint F φ 0° 8° Foot Angle c .009 Lead Thickness .003 .012 Lead Width B .006 α 5° 15° Mold Draft Angle Top β 5° 15° Mold Draft Angle Bottom *Controlling Parameter Notes: Dimensions D and E1 do not include mold flash or protrusions. Mold flash or protrusions shall not exceed .010" (0.254mm) per side. MAX 1.10 0.95 0.15 0.80 8° 0.23 0.30 15° 15° JEDEC Equivalent: MO-187 Drawing No. C04-021 2004 Microchip Technology Inc. DS21908A-page 35 MCP6S91/2/3 NOTES: 2004 Microchip Technology Inc. DS21908A-page 36 MCP6S91/2/3 PRODUCT IDENTIFICATION SYSTEM To order or obtain information, e.g., on pricing or delivery, refer to the factory or the listed sales office. PART NO. -X /XX Device Temperature Range Package Device: MCP6S91: One-channel PGA MCP6S91T: One-channel PGA (Tape and Reel for SOIC and MSOP-8) MCP6S92: Two-channel PGA MCP6S92T: Two-channel PGA (Tape and Reel for SOIC and MSOP-8) MCP6S93: Two-channel PGA MCP6S93T: Two-channel PGA (Tape and Reel for MSOP-10) Examples: a) MCP6S91-E/P: b) MCP6S91-E/SN: c) MCP6S91-E/MS: a) MCP6S92-E/MS: b) Two-channel PGA, MSOP-8 package. MCP6S92T-E/MS: Tape and Reel, Two-channel PGA, MSOP-8 package. a) MCP6S93-E/UN: b) Temperature Range: E = -40°C to +125°C Package: MS P SN UN = = = = One-channel PGA, PDIP package. One-channel PGA, SOIC package. One-channel PGA, MSOP package. Two-channel PGA, MSOP-10 package. MCP6S93T-E/UN: Tape and Reel, Two-channel PGA, MSOP-10 package. Plastic Micro Small Outline (MSOP), 8-lead Plastic DIP (300 mil Body), 8-lead Plastic SOIC (150 mil Body), 8-lead Plastic Micro Small Outline (MSOP), 10-lead Sales and Support Data Sheets Products supported by a preliminary Data Sheet may have an errata sheet describing minor operational differences and recommended workarounds. To determine if an errata sheet exists for a particular device, please contact one of the following: 1. 2. 3. Your local Microchip sales office The Microchip Corporate Literature Center U.S. FAX: (480) 792-7277 The Microchip Worldwide Site (www.microchip.com) Please specify which device, revision of silicon and Data Sheet (include Literature #) you are using. Customer Notification System Register on our web site (www.microchip.com/cn) to receive the most current information on our products. 2004 Microchip Technology Inc. DS21908A-page 37 MCP6S91/2/3 NOTES: DS21908A-page 38 2004 Microchip Technology Inc. Note the following details of the code protection feature on Microchip devices: • Microchip products meet the specification contained in their particular Microchip Data Sheet. • Microchip believes that its family of products is one of the most secure families of its kind on the market today, when used in the intended manner and under normal conditions. • There are dishonest and possibly illegal methods used to breach the code protection feature. All of these methods, to our knowledge, require using the Microchip products in a manner outside the operating specifications contained in Microchip’s Data Sheets. Most likely, the person doing so is engaged in theft of intellectual property. • Microchip is willing to work with the customer who is concerned about the integrity of their code. • Neither Microchip nor any other semiconductor manufacturer can guarantee the security of their code. Code protection does not mean that we are guaranteeing the product as “unbreakable.” Code protection is constantly evolving. We at Microchip are committed to continuously improving the code protection features of our products. Attempts to break Microchip’s code protection feature may be a violation of the Digital Millennium Copyright Act. If such acts allow unauthorized access to your software or other copyrighted work, you may have a right to sue for relief under that Act. Information contained in this publication regarding device applications and the like is provided only for your convenience and may be superseded by updates. It is your responsibility to ensure that your application meets with your specifications. MICROCHIP MAKES NO REPRESENTATIONS OR WARRANTIES OF ANY KIND WHETHER EXPRESS OR IMPLIED, WRITTEN OR ORAL, STATUTORY OR OTHERWISE, RELATED TO THE INFORMATION, INCLUDING BUT NOT LIMITED TO ITS CONDITION, QUALITY, PERFORMANCE, MERCHANTABILITY OR FITNESS FOR PURPOSE. Microchip disclaims all liability arising from this information and its use. Use of Microchip’s products as critical components in life support systems is not authorized except with express written approval by Microchip. No licenses are conveyed, implicitly or otherwise, under any Microchip intellectual property rights. Trademarks The Microchip name and logo, the Microchip logo, Accuron, dsPIC, KEELOQ, microID, MPLAB, PIC, PICmicro, PICSTART, PRO MATE, PowerSmart, rfPIC, and SmartShunt are registered trademarks of Microchip Technology Incorporated in the U.S.A. and other countries. AmpLab, FilterLab, MXDEV, MXLAB, PICMASTER, SEEVAL, SmartSensor and The Embedded Control Solutions Company are registered trademarks of Microchip Technology Incorporated in the U.S.A. Analog-for-the-Digital Age, Application Maestro, dsPICDEM, dsPICDEM.net, dsPICworks, ECAN, ECONOMONITOR, FanSense, FlexROM, fuzzyLAB, In-Circuit Serial Programming, ICSP, ICEPIC, Migratable Memory, MPASM, MPLIB, MPLINK, MPSIM, PICkit, PICDEM, PICDEM.net, PICLAB, PICtail, PowerCal, PowerInfo, PowerMate, PowerTool, rfLAB, rfPICDEM, Select Mode, Smart Serial, SmartTel and Total Endurance are trademarks of Microchip Technology Incorporated in the U.S.A. and other countries. SQTP is a service mark of Microchip Technology Incorporated in the U.S.A. All other trademarks mentioned herein are property of their respective companies. © 2004, Microchip Technology Incorporated, Printed in the U.S.A., All Rights Reserved. Printed on recycled paper. Microchip received ISO/TS-16949:2002 quality system certification for its worldwide headquarters, design and wafer fabrication facilities in Chandler and Tempe, Arizona and Mountain View, California in October 2003. The Company’s quality system processes and procedures are for its PICmicro® 8-bit MCUs, KEELOQ® code hopping devices, Serial EEPROMs, microperipherals, nonvolatile memory and analog products. In addition, Microchip’s quality system for the design and manufacture of development systems is ISO 9001:2000 certified. DS21908A-page 39 2004 Microchip Technology Inc. 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