INA330 INA3 30 SBOS260 – NOVEMBER 2002 THERMISTOR SIGNAL AMPLIFIER FOR TEMPERATURE CONTROL FEATURES DESCRIPTION ● OPTIMIZED FOR PRECISION 10kΩ THERMISTOR APPLICATIONS ● LOW OFFSET OVER TEMPERATURE: 0.009°C Temperature Error, –40°C to +85°C The INA330 is a precision amplifier designed for thermoelectric cooler (TEC) control in optical networking applications. It is optimized for use in 10kΩ thermistor-based temperature controllers. The INA330 provides thermistor excitation and generates an output voltage proportional to the difference in resistances applied to the inputs. It uses only one precision resistor plus the thermistor, thus providing an alternative to the traditional bridge circuit. This new topology eliminates the need for two precision resistors while maintaining excellent accuracy for temperature control applications. ● EXCELLENT LONG-TERM STABILITY ● VERY LOW 1/f NOISE: (0.01Hz to 10Hz) (Peak-to-Peak Equivalent to 0.0001°C) ● WIDE OUTPUT SWING: Within 10mV of Rails An excitation voltage is applied to the thermistor (RTHERM) and precision resistor (RSET), creating currents I1 and I2. The current conveyor circuit produces an output current, IO, equal to I1 – I2, which flows through the external gain-setting resistor. A buffered voltage output proportional to IO is also provided. ● SUPPLY RANGE: Single +2.7V to +5.5V ● microPACKAGE: MSOP-10 ● REQUIRES ONLY ONE PRECISION RESISTOR APPLICATIONS The INA330 offers excellent long-term stability, and very low 1/f noise throughout the life of the product. The low offset results in a 0.009°C temperature error from –40°C to +85°C. It comes in MSOP-10 packaging and operates with supply voltages from +2.7V to +5.5V. It is specified over the industrial temperature range, –40°C to +85°C, with operation from –40°C to +125°C. ● THERMISTOR-BASED TEMPERATURE CONTROLLERS FOR OPTICAL NETWORKING ● HIGH ACCURACY FOR TEC APPLICATIONS ● LASER TEMPERATURE CONTROL V+ Enable High = On Low = Off PID CONTROLLER 9 VEXCITE 1V V2 2 V1 3 5 6 VO 8 VREF 2.5V 10 7 I O = I1 – I2 I1 1 4 I2 Thermistor RTHERM = 10kΩ RSET 10kΩ CFILTER 500pF RG 200kΩ D/A Converter VADJUST = +2.5V INA330 In A Temperature Control Loop Please be aware that an important notice concerning availability, standard warranty, and use in critical applications of Texas Instruments semiconductor products and disclaimers thereto appears at the end of this data sheet. Copyright © 2002, Texas Instruments Incorporated PRODUCTION DATA information is current as of publication date. Products conform to specifications per the terms of Texas Instruments standard warranty. Production processing does not necessarily include testing of all parameters. www.ti.com ABSOLUTE MAXIMUM RATINGS(1) ELECTROSTATIC DISCHARGE SENSITIVITY Supply Voltage .................................................................................. +5.5V Signal Input Terminals: (Pins 1, 2, 3, 6, and 10) Voltage(2) ......................... –0.5V to (V+) + 0.5V Current(2) ............................................... ±10mA Output Short-Circuit(3) .............................................................. Continuous Operating Temperature Range ....................................... –40°C to +125°C Storage Temperature Range .......................................... –65°C to +150°C Junction Temperature .................................................................... +150°C Lead Temperature (soldering, 10s) ............................................... +300°C This integrated circuit can be damaged by ESD. Texas Instruments recommends that all integrated circuits be handled with appropriate precautions. Failure to observe proper handling and installation procedures can cause damage. ESD damage can range from subtle performance degradation to complete device failure. Precision integrated circuits may be more susceptible to damage because very small parametric changes could cause the device not to meet its published specifications. NOTES: (1) Stresses above these ratings may cause permanent damage. Exposure to absolute maximum conditions for extended periods may degrade device reliability. These are stress ratings only, and functional operation of the device at these or any other conditions beyond those specified is not implied. (2) Input terminals are diode clamped to the power-supply rails. Input signals that can swing more than 0.5V beyond the supply rails should be current limited to 10mA or less. (3) Short-circuit to ground. PACKAGE/ORDERING INFORMATION PRODUCT INA330 PACKAGE-LEAD PACKAGE DESIGNATOR(1) SPECIFIED TEMPERATURE RANGE PACKAGE MARKING ORDERING NUMBER TRANSPORT MEDIA, QUANTITY MSOP-10 DGS –40°C to +85°C TLB " " " " INA330AIDGST INA330AIDGSR Tape and Reel, 250 Tape and Reel, 2500 " NOTE: (1) For the most current specifications and package information, refer to our web site at www.ti.com. PIN CONFIGURATION Top View 2 MSOP I2 (RSET) 1 10 I1 (RTHERM) V2 2 9 V+ V1 3 8 VO GND 4 7 IO (RG) (Connect to V+) 5 6 Enable INA330 INA330 www.ti.com SBOS260 ELECTRICAL CHARACTERISTICS: VS = +5V BOLDFACE limits apply over the specified temperature range, TA = –40°C to +85°C At TA = +25°C, V1 = V2 = +1V, VADJUST = +2.5V, RSET = 10kΩ, RTHERM = 10kΩ, RG = 200kΩ, CFILTER = 500pF, external 1kHz filtering, unless otherwise noted. INA330 PARAMETER VOLTAGE EXCITATION BUFFERS Voltage Range Offset Voltage vs Temperature vs Power Supply Offset Voltage Match(1) vs Temperature Input Bias Current Output Current VOS ∆VOS PSR CONDITION MIN RSET = 10kΩ, RTHERM = 10kΩ RSET = 100kΩ, RTHERM = 100kΩ VS = +5V, V1 – V2 = 0 0.1 MAX UNITS 1.25 V V µV µV/°C µV/V µV µV/°C nA µA 0.1 to 4.9 ±60 ±0.2 3 ±30 0.2 ±0.2 VS = +2.7V to +5.5V, V1 – V2 = 0 IB +125 CURRENT CONVEYOR(2) Gain Equation Current Output Range Voltage Compliance Range Gain Gain Error Current Offset Error Change Over Temperature vs V1, V2 vs Power Supply Noise Current f = 0.01Hz to 10Hz ±12.5 0.075 IO = I1 – I2 4.925 1 ±0.1 ±100 VO = +0.075V to +4.925V I1 = I2 +25°C to +85°C, or +25°C to –40°C V1 = V2 = +0.1V to +1.25V IERROR OUTPUT BUFFER Voltage Output Swing-to-Rail Offset Voltage vs Temperature Input Bias Current Short-Circuit Current TYP ±0.2 ±200 ±40 ±200 ±100 25 12 500 RL = 100kΩ RL = 10kΩ 75 dVOS /dT ISC 5 10 30 0.1 Included in IERROR ±25 µA V A/A % nA nA nA/V nA/V pA/√Hz pAp-p mV mV µV µV/°C mA NOTES: (1) Total errors in voltage seen between pin 1 and pin 10. (2) See Figure 2. 9 VEXCITE 1V Enable High = On Low = Off V+ TEST CONFIGURATION V2 2 V1 3 5 6 8 10 7 VO IO = I1 – I2 I1 1 I2 4 Thermistor RTHERM = 10kΩ RSET 10kΩ CFILTER 500pF RG 200kΩ VADJUST = +2.5V INA330 SBOS260 www.ti.com 3 ELECTRICAL CHARACTERISTICS: VS = +5V (Cont.) BOLDFACE limits apply over the specified temperature range, TA = –40°C to +85°C. At TA = +25°C, V1 = V2 = +1V, VADJUST = +2.5V, RSET = 10kΩ, RTHERM = 10kΩ, RG = 200kΩ, CFILTER = 500pF, external 1kHz filtering, unless otherwise noted. INA330 PARAMETER FREQUENCY RESPONSE Bandwidth, –3dB(3) Slew Rate POWER SUPPLY Specified Voltage Range Quiescent Current Over Temperature CONDITION MIN BW SR TYP 1 Not Slew Rate Limited +2.7 IQ MAX IO = 0, V1 – V2 = 0V, VS = +5V SHUTDOWN Disable (Logic LOW Threshold) Enable (Logic HIGH Threshold) Enable Time Disable Time Shutdown Current and Enable Pin Current TEMPERATURE RANGE Specified Range Operating Range Storage Range Thermal Resistance 2.6 kHz +5.5 3.6 3.9 V mA mA 0.25 V V µs µs µA 1.6 75 100 2 VS = +5V, Disabled –40 –40 –65 MSOP-10 Surface-Mount 5 +85 +125 +150 150 UNITS °C °C °C °C/W NOTES: (3) Dynamic response is limited by filtering. 4 INA330 www.ti.com SBOS260 TYPICAL CHARACTERISTICS At TA = +25°C, V1 = V2 = +1V, VADJUST = +2.5V, RSET = 10kΩ, RTHERM = 10kΩ (5%), RG = 200kΩ, CFILTER = 500pF, and external 1kHz filtering, unless otherwise noted. CURRENT CONVEYOR OFFSET ERROR CHANGE OVER TEMPERATURE PRODUCTION DISTRIBUTION CURRENT CONVEYOR OFFSET ERROR PRODUCTION DISTRIBUTION Change in offset error from +25°C to +85°C, or from +25°C to –40°C. –40 –36 –32 –28 –24 –20 –16 –12 –8 –4 0 4 8 12 16 20 24 28 32 36 40 A 40nA current offset error variation with ambient temperature results in a 0.009°C variation in setpoint temperature over –40°C to +85°C ambient. 209 –190 –171 –152 –133 –114 –95 –76 –57 –38 –19 0 19 38 57 76 95 114 133 152 171 190 209 Population Population This error is generally calibrated out. Current Conveyor Offset Error (nA) Current Conveyor Offset Error Change Over Temperature (nA) +5V Test Configuration for this page. 0.01Hz TO 10Hz VOLTAGE NOISE VEXCITE V2 2 1V V1 3 0.001°C 200µV/div 0.0002°C/div 9 10 5 6 8 VO INA330 7 I1 1 4 I2 5s/div 10kΩ 10kΩ CFILTER 500pF RG 200kΩ 2.5V INA330 SBOS260 www.ti.com 5 APPLICATIONS INFORMATION OVERVIEW 2 1V 8 3 Precision temperature controllers are generally adjusted to their set-point temperature to achieve the desired system performance and to compensate for tolerance of the thermistor and reference circuitry. After this adjustment, the crucial issue is the stability of this set-point temperature. When used in a temperature control loop (Figure 1), the INA330 provides excellent control-point stability over time and ambient temperature changes. Low 1/f noise assures excellent short-term stability. Internal auto-zero circuitry assures excellent stability throughout product life. Current Conveyor: measures the current difference between pins 10 and 1. 10 7 IO = I1 – I2 + IERROR + ∆IERROR /∆T I1 I2 1 RTHERM 10kΩ at 25°C 9.55kΩ at 26°C ∆I = 4500nA RSET SOURCES OF ERRORS The largest source of error in a control system will occur due to RSET, see “Selecting Components” section. FIGURE 2. Current Conveyor Portion of the INA330. The INA330 errors are extremely low. The primary errors in the INA330 occur in the current conveyer circuitry, as shown in Figure 2. Equal currents in RSET and RTHERM produce a small output current error of 200nA (maximum), and some variation with temperature of 40nA (maximum). The offset is calibrated out. Only the variation affects set-point stability. ambient). This is the variation in set-point temperature due to variation in ambient temperature of the INA330. Insignificant Errors Input offset voltage of the voltage excitation buffers are autozeroed to approximately 60µV and match to 30µV. Drift with temperature is very low. They contribute negligible error. The variation can be referred to the input as a set-point temp variation: 10kΩ thermistor with a 4.5% temperature coefficient, (α = –0.045) changes resistance by 450Ω/°C. This results in 4500nA change in I1 for a 1°C temperature change at the thermistor. Therefore, the 40nA maximum current offset error variation with ambient temperature results in a 0.009°C variation in set-point temperature over –40°C to +85°C ambient (40nA/4500nA/°C = 0.009°C set-point/°C Place 0.1µF capacitor close to and across the power- 0.1µF supply pins. V+ V2 2 V1 3 Output buffer errors are auto-zeroed. When referred to the input, their errors are negligible. Gain error does not produce any significant temperature setpoint error when used in a temperature set-point control loop. Enable High = On Low = Off PID CONTROLLER 9 VEXCITE 1V Voltage excitation buffers have an input bias current of 0.2nA. With a source impedance of less than 10kΩ, errors produced by the input bias current will be negligible. 5 6 VO 8 +0.9V/°C for increasing temperature. Power Amp VREF 2.5V TEC 10 7 IO = I 1 – I 2 I1 1 4 I2 Thermistor RTHERM = 10kΩ RSET 10kΩ (Selection of RSET significantly affects control system—see “Selecting Components” section.) CFILTER 500pF RG 200kΩ D/A Converter VADJUST = +2.5V FIGURE 1. The INA330 In Simplified Temperature Control Loop. 6 INA330 www.ti.com SBOS260 SELECTING COMPONENTS RSET is the primary “reference” for the temperature control loop. Its absolute resistance controls the set-point temperature. Again, its initial accuracy can be calibrated, but its stability is crucial. Therefore, a high-quality, low-temperature coefficient type must be used. A 25ppm/°C precision resistor changes 0.15% from –40°C to +85°C. This will produce a 0.03°C change in set-point temperature. This error is approximately three-times larger than that produced by the INA330. loop can be accomplished by simply reversing the connections to the TEC, or by creating the desired polarity in the intervening control circuitry. If differing values of V1 and V2 are used, resistor values should be chosen to maintain balanced currents, I1 and I2. Likewise, if a lower value of RSET is used, the excitation voltage must be lowered to keep I1 and I2 at or below 125µA. CFILTER is calculated by: CFILTER = The transfer function for the configuration shown in Figure 3 is: VO = VADJ + R G (I1 – I2 ) NOISE PERFORMANCE or Temperature control loops require low noise over a small bandwidth, typically 10Hz, or less. The INA330’s internal auto-correction circuitry eliminates virtually all 1/f noise (noise that increases at low frequency). The peak-to-peak voltage noise due to IERROR, RTHERM, RSET, and the buffers at 0.01Hz to 10Hz results in a 0.0001°C contribution. V1 V2 VO = VADJ + R G – R THERM R SET With V1 = V2 = VEXCITE, 1 1 VO = VADJ + VEXCITE R G – R THERM R SET V+ 9 VEXCITE 1V V2 2 V1 3 Enable 5 1 2πR G (1.6kHz) OUTPUT The INA330 output (pin 8) is capable of swinging to within 10mV of the power-supply rails. It is able to achieve rail-torail output performance while sinking or sourcing 12.5µA. High = On Low = Off VADJUST can be used to create an offset voltage around which the output can be centered. 6 8 VO ENABLE FUNCTION 10 7 I O = I 1 – I2 I1 1 4 I2 Thermistor RTHERM = 10kΩ RSET 10kΩ CFILTER 500pF The INA330 is enabled by applying a logic HIGH voltage level to the Enable pin. Conversely, a logic LOW voltage level will disable the amplifier, reducing its supply current from 2.6mA to typically 2µA. This pin should be connected to a valid HIGH or LOW voltage or driven, not left open circuit. Applications not requiring disable can connect pin 6 directly to V+. The Enable pin can be modeled as a CMOS input gate, as shown in Figure 4. RG 200kΩ VADJUST = +2.5V V+ FIGURE 3. Basic Configuration for the INA330. 2µA Nominal values should use RSET = RTHERM = 10kΩ at the designed control temperature. Values less than 2kΩ can cause the voltage excitation buffers to become unstable. The buffer connected to pin 10 is characterized and tested to supply the changing current in the thermistor. The thermistor should not be connected to pin 1. An inversion of the control Enable 6 FIGURE 4. Enable Pin Model. INA330 SBOS260 www.ti.com 7 INSIDE THE INA330 The INA330 is designed and tested for amplifying 10kΩ thermistor signals used in the control of thermoelectric coolers for optical networking applications. The simplified schematic in Figure 5 shows the basic function of the INA330. An excitation voltage is applied as V1 and V2. Typically, these voltages are equal. They generate currents I1 and I2 in the thermistor and RSET resistor. Auto-corrected current mirror circuitry around A1 and A2 produce an output current, IO, equal to the difference current I1 – I2. The gain is set by the value of RG. The output voltage, VO, is the voltage resulting from IO flowing through RG. The INA330 uses internal charge pumps to create voltages beyond the power-supply rails. As a result, the voltage on RG can actually swing 20mV below the negative power-supply rail, and 100mV beyond the positive supply rail. An internal oscillator has a frequency of 90kHz and accuracy of ±20%. V+ Enable 9 5 6 Current Mirror INA330 I2 2 V2 I2 A1 1 Current Mirror I2 Current Mirror I2 10 I1 RSET I1 – I2 IO = I1 – I2 RTHERM 3 A2 A3 IO 8 VO IO Current Mirror V1 4 7 RG CFILTER VADJUST FIGURE 5. INA330 Simplified Schematic. INA330 PIN 5 Pin 5 of the INA330 should be connected to V+ to ensure proper operation. COMPLETE TEMPERATURE CONTROLLER See Figure 6 for a complete temperature control loop with a TEC (thermoelectric cooler) for cooling and heating. PID (proportional, integral, differential) control circuitry is shown for loop compensation and stability. The loop controls temperature to an adjustable set-point of 22.5°C to 27.5°C. The nominal 10kΩ at 25°C thermistor ranges from approximately 11.4kΩ to 8.7kΩ over this range. A 1V excitation voltage is applied to V1 and V2, producing a nominal 100µA current in the 10kΩ RSET resistor. The ther- 8 mistor current is approximately 100µA at 25°C, but will vary above or below this value over the ±2.5°C set-point temperature range. The difference of these two currents flows in the gain-set resistor, RG. This produces a voltage output of approximately 0.9V/°C. The set-point temperature is adjusted with VADJ. Thus, the voltage at VO is the sum of (IO)(RG) + VADJ. VADJ can be manually adjusted or set with a Digital-to-Analog (D/A) converter. Optionally, set-point temperature can be adjusted by choosing a different fixed value resistor more closely approximating the value of RTHERM at the desired temperature. The noninverting input of the integrator in the PID compensation is connected to VBIAS. Thus, the feedback loop will drive the heating or cooling of the TEC to force VO to equal VBIAS. VADJ = 2.5V will produce a set-point temperature of INA330 www.ti.com SBOS260 25°C. VADJ = 2.5V + 0.9V will change the set-point by 1°C. A 0V to 5V D/A converter will provide approximately ±2.5°C adjustment range. A 12-bit D/A converter will allow for approximately 0.001°C resolution on the set-point temperature. source for V1 and V2 should be derived from the same reference. The PID loop compensation can be optimized for loop stability and best response to thermal transients by adjusting C1, C2, C3, R2, R3, and R4. This is highly dependant on the thermal characteristics of the temperature-controlled block and thermistor/TEC mounting. Figure 7 shows a circuit that can be used as an intermediate circuit to easily adjust components and determine system requirements. For best temperature stability, the set-point temperature voltage should be derived ratiometrically from VBIAS. A D/A converter used to derive the set-point voltage should share the same reference voltage source as VBIAS. Likewise, the 1V TEC DRIVER AMPLIFIER OPTIONS Enable +5V +5V(2) VREF(1) +5V PID C1 9 5 OPA569 DRV591 DRV593 DRV594 R2 R4 C2 2 V1 3 R1 ➜ V2 3.3V 3.3V 6 4kΩ ✻ VO C3 R3 10kΩ 8 INA330 10 10kΩ VREF(1) +5V IO = I1 – I2 10kΩ +5V 7 I1 10kΩ 10kΩ OPA348 VBIAS(1) Thermistor RSET = 10kΩ RSET 10kΩ – ✻ + TEC ✻ OPA569 ✻ 2.5V 10kΩ Cooling 4 I2 OPA569 ➜ 1 ➜ 1kΩ ➜ 1V(1) 2A Linear Amplifier 3A PWM Power Driver 3A PWM Power Driver 3A PWM Power Driver 10kΩ CFILTER 500pF VREF(1) = +5V RG 200kΩ Temperature Adjust ➜ ➜ D/A Converter NOTES: (1) Ratiometrically derived voltages. (2) The INA330 can also use a 3.3V, supply; however, components must be chosen appropriate to the smaller output voltage range. ✻ indicates direction of voltage change for rising temperature at the thermistor. VADJUST = 0V to 5V = 2.5V at 25°C Set-Point FIGURE 6. PID Temperature Control Loop. This versatile PID compensation circuit allows independent adjustment of the Proportional, Integral, and Derivative control signals to facilitate optimization of loop dynamics. The results can then be duplicated using the circuit shown in Figure 6. R7 10MΩ R6 5kΩ 1/4 OPA4340 Enable +5V R2 200Ω +1V V2 2 V1 3 5 R9 100kΩ R1 2kΩ 6 R4 10kΩ 8 1/4 OPA4340 1/4 OPA340 10 R5 5kΩ C3 1µF R12 100kΩ 4 RSET 10kΩ 1/2 OPA2340 Power Amplifier OPA569 DRV591 DRV593 DRV594 To TEC VBIAS R13 1MΩ 7 1 Thermistor RTHERM = 10kΩ R11 10kΩ Proportional I1 I2 R15 10kΩ VBIAS C1 22nF INA330 C4 0.1µF R10 100kΩ R3 10kΩ VBIAS 7 R8 10kΩ Integrator TC: 1s to 10s VBIAS +5V C2 1µF CFILTER 500pF RG 200kΩ VADJ Ref VBIAS 1/4 OPA4340 R14 10kΩ Differentiator TC: 100ms to 1s D/A Converter FIGURE 7. Diagnostic and Optimization PID Temperature Control Loop. INA330 SBOS260 www.ti.com 9 100pF(1) +5V 10MΩ(1) 9 REF3012 VEXCITE 1.25V 5 2µF(1) 6 +5V 2 8 3 VO 10MΩ(1) 0.1µF Output to Power Amp OPA340 VREF 2.5V INA330 Proportional-Integrator compensation is simpler to adjust and often provides adequate thermal transient response. 10 NOTE: (1) Time constants were selected for THORLABS model TCLM9 Laser Diode Mount. 7 1 4 RTHERM 10kΩ RSET 10kΩ RG 200kΩ CFILTER 500pF VADJ FIGURE 8. Simple PI Temperature Control Amplifier. FILTERING Subsequent stages will frequently provide adequate filtering for the INA330. However, filtering can be adjusted through selection of RGCFILTER, and by adding a filter at VO for the desired trade-off of noise and bandwidth. Adjustment of these components will result in more or less ripple due to auto-correction circuitry noise and will also affect broadband noise. 2 It is generally desirable to keep any resistor added at VO (see RO in Figure 9) relatively low to avoid DC gain error created by the subsequent stage loading. This may result in relatively high values for the filter capacitor at VO to produce the desired filter response. The impedance of this filter can be scaled higher to produce smaller capacitor values if the load impedance is very high. Electrolytic capacitors are not recommended for the filters due to dielectric absorption effects. 10 8 3 RO 100Ω CO 1µF 7 1 CFILTER 500pF RG 200kΩ VADJ FIGURE 9. Required 1.6kHz (or lower) Filtering. 10 INA330 www.ti.com SBOS260 DIGITALLY COMPENSATED LOOP The PID compensation can be replaced with a microcontroller or DSP, as shown in Figure 10. An Analog-to-Digital (A/D) converter would be used to digitize the output of the INA330. The analog PID provides sufficient filtering inherently, and, therefore requires no additional filtering. The digital control loop shown in Figure 10 does not provide this inherent filtering, requiring additional output filtering (RO and CO) as shown to avoid sampling the internal chopping noise of the INA330 and the A/D converter input and affecting accuracy. High-frequency noise is created by internal auto-correction circuitry and is highly dependent on the filter characteristics +1V V1 2 V2 3 5 Loop Compensation is performed in DSP. 8 RSET 10kΩ The traditional bridge circuit (Figure 11) uses three matched resistors and a thermistor to detect temperature changes. The INA326 and INA327 instrumentation amplifiers are well suited to a bridge implementation for thermistor measurement. 6 RO 100Ω A/D Converter DSP D/A Converter CO 1µF INA330 RTHERM TRADITIONAL BRIDGE CIRCUIT Enable +5V +5V 9 chosen. “Spurs” occur at approximately 90kHz and its harmonics which is reduced by additional filtering at or below 1kHz. This may be the dominant source of noise visible when viewing the output on an oscilloscope. Low cutoff frequency filters will provide lowest noise. TEC 7 CFILTER 500pF RG 200kΩ VADJ 0V to 5V Ref D/A Converter Temp Adjust FIGURE 10. Digitally Compensated Loop. VEXCITE 10kΩ(1) ✻ PID CONTROLLER 10kΩ(1) 10kΩ(2) 5kΩ +5V INA326 VREF 2.5V ✻ 10kΩ at set-point temperature. 1nF 100kΩ VADJ D/A Converter NOTES: (1) Requires ratio matching tracking. (2) Requires absolute accuracy and stability. FIGURE 11. Traditional Bridge Circuit. INA330 SBOS260 www.ti.com 11 PACKAGE DRAWING DGS (S-PDSO-G10) PLASTIC SMALL-OUTLINE PACKAGE 0,27 0,17 0,50 10 0,08 M 6 0,15 NOM 3,05 2,95 4,98 4,78 Gage Plane 0,25 1 0°– 6° 5 3,05 2,95 0,69 0,41 Seating Plane 1,07 MAX 0,15 0,05 0,10 4073272/B 08/01 NOTES: A. B. C. A. 12 All linear dimensions are in millimeters. This drawing is subject to change without notice. Body dimensions do not include mold flash or protrusion. Falls within JEDEC MO-187 INA330 www.ti.com SBOS260 PACKAGE OPTION ADDENDUM www.ti.com 9-Dec-2004 PACKAGING INFORMATION Orderable Device Status (1) Package Type Package Drawing Pins Package Eco Plan (2) Qty INA330AIDGSR ACTIVE MSOP DGS 10 2500 None CU NIPDAU Level-3-235C-168 HR INA330AIDGST ACTIVE MSOP DGS 10 250 None CU NIPDAU Level-3-235C-168 HR Lead/Ball Finish MSL Peak Temp (3) (1) The marketing status values are defined as follows: ACTIVE: Product device recommended for new designs. LIFEBUY: TI has announced that the device will be discontinued, and a lifetime-buy period is in effect. NRND: Not recommended for new designs. Device is in production to support existing customers, but TI does not recommend using this part in a new design. PREVIEW: Device has been announced but is not in production. Samples may or may not be available. OBSOLETE: TI has discontinued the production of the device. (2) Eco Plan - May not be currently available - please check http://www.ti.com/productcontent for the latest availability information and additional product content details. None: Not yet available Lead (Pb-Free). Pb-Free (RoHS): TI's terms "Lead-Free" or "Pb-Free" mean semiconductor products that are compatible with the current RoHS requirements for all 6 substances, including the requirement that lead not exceed 0.1% by weight in homogeneous materials. Where designed to be soldered at high temperatures, TI Pb-Free products are suitable for use in specified lead-free processes. Green (RoHS & no Sb/Br): TI defines "Green" to mean "Pb-Free" and in addition, uses package materials that do not contain halogens, including bromine (Br) or antimony (Sb) above 0.1% of total product weight. (3) MSL, Peak Temp. -- The Moisture Sensitivity Level rating according to the JEDECindustry standard classifications, and peak solder temperature. Important Information and Disclaimer:The information provided on this page represents TI's knowledge and belief as of the date that it is provided. TI bases its knowledge and belief on information provided by third parties, and makes no representation or warranty as to the accuracy of such information. Efforts are underway to better integrate information from third parties. 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