® SP6651A High Efficiency 800mA Synchronous Buck Regulator Ideal for portable designs powered with Li Ion battery FEATURES ■ DFN Package (3mm x 3mm) ■ Ultra-low 20µA Quiescent Current ■ 98% Efficiency Possible ■ 800mA Output Current ■ 2.7V to 5.5V Input Voltage Range ■ Output Adjustable Down to 1.0V ■ No External FET’s Required ■ 1.25A Inductor Peak Current Limit ■ 100% Duty Ratio Low Dropout Operation ■ 80µA Light Load Quiescent Current in Dropout ■ Over Temperature Protection ■ Logic Shutdown Control ■ Programmable UVLO and Adaptive Battery Low Output PV IN 1 V IN 2 BLON 3 D1 4 7 VOUT D0 5 6 FB 10 LX 9 PGND SP6651A 8 GND 10 Pin DFN Now Available in Lead Free Packaging APPLICATIONS ■ PDA's ■ DSC's ■ MP3 Players ■ USB Devices ■ Point of Use Power DESCRIPTION The SP6651A is a 800mA synchronous buck regulator which is ideal for portable applications that use a Li-Ion or 3 cell alkaline/NiCD/NiMH input. The SP6651A’s proprietary control loop, 20µA light load quiescent current, and 0.3Ω power switches provide excellent efficiency across a wide range of output currents. As the input battery supply decreases towards the output voltage the SP6651A seamlessly transitions into 100% duty ratio operation further extending useful battery life. The SP6651A is protected against overload and short circuit conditions with a precise inductor peak current limit. Other features include programmable under voltage lockout and low battery detection, externally programmed output voltage down to 1.0V, logic level shutdown control, and 140°C over temperature shutdown. TYPICAL APPLICATION SCHEMATIC 2.7V to 5.5V Input L1 10µH VI CIN 22µF 10Ω RVIN CVIN LX 1µF VO COUT 22µF PGND VIN 1M BLON SP6651A PVIN VOUT 800mA BLON GND D1 D1 VOUT D0 D0 FB CF RF 22pF RI 200K Date: 5/25/04 SP6651A High Efficiency 800mA Synchronous Buck Regulator 1 © Copyright 2004 Sipex Corporation ABSOLUTE MAXIMUM RATINGS These are stress ratings only and functional operation of the device at these ratings or any other above those indicated in the operation sections of the specifications below is not implied. Exposure to absolute maximum rating conditions for extended periods of time may affect reliability. PVIN,VIN .............................................................................................. 6V All other pins .............................................................. -0.3V to VIN+0.3V PVIN, PGND, LX current ........................................................................ 2A Storage Temperature .................................................. -65 °C to 150 °C Operating Temperature ................................................. -40°C to +85°C Lead Temperature (Soldering, 10 sec) ....................................... 300 °C Thermal Resistance øJA: 10-Pin MSOP....................................................................128°C/W 10-Pin DFN ........................................................................68°C/W ELECTRICAL CHARACTERISTICS VIN=UVIN=VSDN=3.6V, VOUT=VFB, IO = 0mA, TAMB = -40°C to +85°C, typical values at 27°C unless otherwise noted. PARAMETER Input Voltage Operating Range Minimum Output Voltage FB Set Voltage, Vr Overall Accuracy (-40°C to 85°C) (0°C to 70°C) On-Time Constant - KON Min, TON=KON/(VIN-VOUT) Off-Time Constant - KOFF Min, TOFF=KOFF/VOUT Off-Time Blanking PMOS Switch Resistance NMOS Switch Resistance Inductor Current Limit LX Leakage Current Power Efficiency Minimum Guaranteed Load Current VIN Quiescent Current VIN Shutdown Current VOUT Quiescent Current VOUT Shutdown Current UVLO Undervoltage Lockout Threshold, VIN falling UVLO hysteresis Battlo Trip Voltage, VIN falling Battlo Trip Voltage Hysteresis BLON Low Output Voltage BLON Leakage Current Over-Temperature Rising Trip Point Over-Temperature Hysteresis D1,D0 Leakage Current D1,D0 Input Threshold Voltage FB Leakage Current Date: 5/25/04 MIN UVLO TYP MAX 5.5 UNITS V 0.800 0.816 V V 1.5 2.25 ±5 ±4 3.0 V*µs Close Loop, LI = 10µH,COUT = 22µF 1.6 2.4 3.2 V*µs Inductor current limit tripped, VFB=0.5V Measured at VOUT = 2V 0.6 0.6 1.50 3 ns Ω Ω A µA % 1.0 0.784 1.0 800 2.55 2.70 2.85 265 100 0.3 0.3 1.25 0.01 96 92 900 20 1 2 1 2.70 2.85 3.00 40 300 9 % 30 500 5 500 2.85 3.00 3.15 335 140 0.60 25°C, IO=200mA Close Loop. LI = 10µH, COUT = 22µF Measured at VIN=5.5V, no load and VIN=3.6V, 200mA load, Close Loop IPMOS = 200mA INMOS = 200mA VFB=0.5V D0=D1=0 VOUT=2.5V, IO=200mA VOUT=3.3V, IO=800mA mA 0.4 1 14 1 0.90 1.25 1 CONDITIONS Result of IQ measurement at VIN=PVIN=5.5V 500 1.8 100 µA nA µA nA V mV mV mV V µA °C °C nA V V nA VOUT=3.3V, VIN=3.6V and VIN= 5.5V D1=D0=0V VOUT = 3.3V D1=D0=0V D1=0V, D0=VIN D1=VIN, D0=0V D1=VIN, D0=VIN Measured as VIN-VOUT VIN=3.3V, ISINK=1mA VBLON=3.6V High to Low Transition Low to High Transition FB=1V SP6651A High Efficiency 800mA Synchronous Buck Regulator 2 © Copyright 2004 Sipex Corporation PIN DESCRIPTION PIN NUMBER PIN NAME 1 PVIN DESCRIPTION 2 VIN 3 BLON 4 D1 Digital mode control input. See table I for definition. 5 D0 Digital mode control input. See table I for definition. 6 FB External feedback network input connection. Connect a resistor from FB to ground and FB to VOUT to set the output voltage. This pin regulates to the internal bandgap reference voltage of 0.8V. 7 VOUT Output voltage sense pin. Used by the timing circuit to set minimum on and off times. 8 GND Internal ground pin. Control circuitry returns current to this pin. 9 PGND Power ground pin. Synchronous rectifier current returns through this pin. 10 LX Inductor switching node. Inductor tied between this pin and the output capacitor to create regulated output voltage. Input voltage power pin. Inductor charging current passes through this pin. Internal supply voltage. Control circuitry powered from this pin. Open drain battery low output. (VIN-VO) less than 300mV pulls this node to ground. (VIN-VO) above threshold, this node is open. D1 D0 0 0 Shutdown. All internal circuitry is disabled and the power switches are opened. 0 1 Device enabled, falling UVLO threshold =2.70V 1 0 Device enabled, falling UVLO threshold =2.85V 1 1 Device enabled, falling UVLO threshold =3.00V Table 1. Operating Mode Definition FUNCTIONAL DIAGRAM PVIN VOUT Vin DRVON VOLOW TONOVER MIN Ton Internal Supply TONOVER Min Ton Vos VOLOW REF + -REF' + - VRAMP FB Min Ton = KON/(VIN -VOUT) M C R Q + S ILIM/M DRIVER _ OVR_I 1 DRVON - C Q - FB' + OVR_I RST LX DRVON + REF D0 Ref Block One-Shot =100ns UVLO TSD ILIM/M C Zero_X PGND BLANK D1 GND - TOFF = KOFF/VOUT 300mV OVR_I VOUT DRVON - + VIN + - BLON C BLANK UVLO BLANK = Tblank(=100ns) or Toff = Koff/Vout Date: 5/25/04 SP6651A High Efficiency 800mA Synchronous Buck Regulator 3 © Copyright 2004 Sipex Corporation TYPICAL PERFORMANCE CHARACTERISTICS 100 100 95 95 90 90 Efficiency (%) Efficiency (%) Refer to the typical application schematic, TAMB= +27°C 85 80 75 Vi=3.6V Vi=3.9V Vi=4.2V Vi=5.0V 70 65 60 0. 1.0 10.0 100.0 85 80 75 70 Vi=3.6V Vi=3.9V Vi=4.2V Vi=5.0V 65 60 0.1 1000.0 1.0 10.0 ILoad (mA) 1000.0 Figure 2. Efficiency vs Load, VOUT = 1.5V Figure 1. Efficiency vs Load, VOUT = 3.3V 3.40 1.55 Vi=3.6V Vi=3.9V Vi=4.2V Vi=5.0V 3.35 Vi=3.6V Vi=3.9V Vi=4.2V Vi=5.0V 1.53 1.51 Vout (V) Vout (V) 100.0 ILoad (mA) 3.30 3.25 1.49 1.47 1.45 3.20 0 200 400 600 ILoad (mA) 800 0 1000 200 400 600 50 500 Tamb = 85°C Tamb = 25°C Tamb = -40°C Tamb = 85°C Tamb = 25°C Tamb = -40°C 40 300 Iin (µA) Iin (uA) 400 30 20 200 10 100 3.3 3.6 Vin (V) 3.9 0 3.0 4.2 Figure 5. No Load Battery Current, VOUT=3.3V Date: 5/25/04 1000 Figure 4. Line/Load Rejection, VOUT = 1.5V Figure 3. Line/Load Rejection, VOUT = 3.3V 0 3.0 800 ILoad (mA) 3.3 3.6 Vin (V) 3.9 4.2 Figure 6. No Load Battery Current, VOUT=1.5V SP6651A High Efficiency 800mA Synchronous Buck Regulator 4 © Copyright 2004 Sipex Corporation TYPICAL PERFORMANCE CHARACTERISTICS: Continued 3.5 3.5 3.0 3.0 2.5 2.5 Kon (V*usec) Kon (V*usec) Refer to the typical application schematic, TAMB= +27°C 2.0 1.5 2.0 1.5 1.0 1.0 0.5 0.0 3.6 0.5 3.9 4.2 4.5 4.8 5.1 0.0 3.0 5.4 Vin (V) 3.5 3.5 3.0 3.0 2.5 2.5 2.0 1.5 0.5 0.5 4.2 4.5 4.8 5.1 3.0 5.4 3.3 3.6 3.9 4.2 4.5 4.8 5.1 5.4 Figure 10. KOFF vs VIN, VOUT=1.5V 700.0 600.0 600.0 500.0 500.0 Frequency (KHz) 700.0 400.0 300.0 200.0 400.0 300.0 200.0 Vout = 3.3V Measured Vout = 3.3V Calculated 100.0 Vout = 1.5V Measured Vout = 1.5V Calculated 100.0 0.0 4.0 4.5 0.0 5.0 3.4 Vin (V) 3.8 4.2 4.6 5.0 Vin (V) Figure 11. Ripple Frequency vs. VIN, IOUT=600mA, VOUT=3.3V Date: 5/25/04 5.1 Vin (V) Figure 9. KOFF vs VIN, VOUT=3.3V 3.5 4.8 0.0 5.4 Vin (V) Frequency (KHz) 4.2 4.5 Vin (V) 1.5 1.0 3.9 3.9 2.0 1.0 0.0 3.6 3.6 Figure 8. KON vs VIN, VOUT=1.5V Koff (V*usec) Koff (V*usec) Figure 7. KON vs VIN, VOUT=3.3V 3.3 Figure 12. Ripple Frequency vs. VIN, IOUT=600mA, VOUT=1.5V SP6651A High Efficiency 800mA Synchronous Buck Regulator 5 © Copyright 2004 Sipex Corporation TYPICAL PERFORMANCE CHARACTERISTICS: Continued Refer to the typical application schematic, TAMB= +27°C CH.1=VIN 2.5V/div CH.1=VIN 2.5V/div CH.2=VOUT 2.0V/div CH.2=VOUT 5.0V/div CH.4=IIN 0.5A/div CH.4=IIN 0.5A/div Figure 14. VIN Start up, IOUT=0.6A, VOUT=1.5V Figure 13. VIN Start up, IOUT=0.6A, VOUT=3.3V CH.2=VOUT 50mV/div. AC CH.2=VOUT 50mV/div. AC CH.4=IIN 0.5A/div CH.4=IOUT 0.5A/div Figure 15. Load Step, IOUT=0.4A to 0.8A, VOUT=3.3V Figure 16. Load Step, IOUT=0.4A to 0.8A, VOUT=1.5V CH.1=VSHDN 10V/div. CH.1=VSHDN 10V/div. CH.2=VOUT 1V/div. AC CH.2=VOUT 2V/div. AC CH.4=ILx 0.5A/div CH.4=ILx 0.5A/div Figure 17. Start up from SHDN, IOUT=0.6A, VOUT=3.3V Date: 5/25/04 Figure 18. Start up from SHDN, IOUT=0.6A, VOUT=1.5V SP6651A High Efficiency 800mA Synchronous Buck Regulator 6 © Copyright 2004 Sipex Corporation THEORY OF OPERATION The SP6651A is a high efficiency synchronous buck regulator with an input voltage range of +2.7V to +5.5Vand an output that is adjustable between +1.0V and VIN. The SP6651A features a unique on-time control loop that runs in discontinuous conduction mode (DCM) or continuous conduction mode (CCM) using synchronous rectification. Other features include over-temperature shutdown, over-current protection, digitally controlled enable and undervoltage lockout, a battery low indicator, and an external feedback pin. RAMP: CCM OPERATION DRVON I(L1) REF, FB VOS FB’ The SP6651A operates with a light load quiescent current of 20µA using a 0.3Ω PMOS main switch and a 0.3Ω NMOS synchronous switch. It operates with excellent efficiency across the entire load range, making it an ideal solution for battery powered applications and low current step-down conversions. The part smoothly transitions into a 100% duty cycle under heavy load/ low input voltage conditions. REF’ RAMP: DCM OPERATION DRVON I(L1) On-Time Control - Charge Phase FB’ The SP6651A uses a precision comparator and a minimum on-time to regulate the output voltage and control the inductor current under normal load conditions. As the feedback pin drops below the regulation point, the loop comparator output goes high and closes the main switch. The minimum on-timer is triggered, setting a logic high for the duration defined by: TON = REF’ ramp voltage (VRAMP in the functional diagram) is added to FB and this creates the FB's signal. This FB signal is applied to the negative terminal of the loop comparator. To the positive terminal of the loop comparator is applied the REF voltage of 0.8V plus an offset voltage Vos to compensate for the DC level of VRAMP applied to the negative terminal. The result is an internal ramp with enough negative going offset (approximately 50mV) to trip the loop comparator whenever FB falls below regulation. KON VIN - VOUT where: KON = 2.25V*µsec constant VIN = VIN pin voltage VOUT = VOUT pin voltage To accommodate the use of ceramic and other low ESR capacitors, an open loop ramp is added to the feedback signal to mimic the inductor current ripple. The following waveforms describe the ideal ramp operation in both CCM and DCM operation. The output of the loop comparator, a rising VOLOW, causes a SET if BLANK = 0 and OVR_I = 0. This starts inductor charging (DRVON = 1) and starts the minimum on-timer. The minimum on-timer times out and indicates DRVON can be reset if the voltage loop is satisfied. If VOUT is still below the regulation In either CCM or DCM, the negative going Date: 5/25/04 REF, FB VOS SP6651A High Efficiency 800mA Synchronous Buck Regulator 7 © Copyright 2004 Sipex Corporation THEORY OF OPERATION : Continued point RESET is held low until VOUT is above regulation. Once RESET occurs TON minimum is reset, and the TOFF one-shot is triggered to blank the loop comparator from starting a new charge cycle for a minimum period. This blanking period occurs during the noisy LX transition to discharge, where spurious comparator states may occur. For TOFF > TBLANK the loop is in a discharge or wait state until the loop comparator starts the next charge cycle by DRVON going high. where: If an over current occurs during charge the loop is interrupted and DRVON is RESET. The offtime one-shot pulse width is widened to TOFF = KOFF / VOUT, which holds the loop in discharge for that time. At the end of the off-time the loop is released and controlled by VOLOW. In this manner maximum inductor current is controlled on a cycle-by-cycle basis. An assertion of UVLO (undervoltage lockout) or TSD (thermal shutdown) holds the loop in no-charge until the fault has ended. For most applications, the inductor current ripple controlled by the SP6651A is constant regardless of input and output voltage. Because the output voltage ripple is equal to: L = Inductor value IOUT = Load current RCH = PMOS on resistance, 0.3Ω typ. If the IOUT * RCH term is negligible compared with (VIN - VOUT), the above equation simplifies to: ILR ≈ where: RESR = ESR of the output capacitor the output ripple of the SP6651A regulator is independent of the input and output voltages. For battery powered applications, where the battery voltage changes significantly, the SP6651A provides constant output voltage ripple through-out the battery lifetime. This greatly simplifies the LC filter design. The discharge phase follows with the high side PMOS switch opening and the low side NMOS switch closing to provide a discharge path for the inductor current. The decreasing inductor current and the load current cause the output voltage to drop. Under normal load conditions when the inductor current is below the programmed limit, the off-time will continue until the output voltage falls below the regulation threshold, which initiates a new charge cycle via the loop comparator. The maximum loop frequency in CCM is defined by the equation: FLP ≈ L Date: 5/25/04 * (VIN - VOUT) * (VOUT + IOUT * RDC) KON * [VIN + IOUT * (RDC - RCH)] where: FLP = CCM loop frequency RDC = NMOS on resistance, 0.3Ω typ. The inductor current “floats” in continuous conduction mode. During this mode the inductor peak current is below the programmed limit and the valley current is above zero. This is to satisfy load currents that are greater than half the minimum current ripple. The current ripple, ILR, is defined by the equation: KON L VOUT (ripple) = ILR * RESR On-Time Control - Discharge Phase ILR ≈ KON Ignoring conduction losses simplifies the loop frequency to: FLP ≈ 1 KON * VOUT VIN * (VIN - VOUT) AND’ing the loop comparator and the on-timer reduces the switching frequency for load currents below half the inductor ripple current. This increases light load efficiency. The minimum on-time insures that the inductor current ripple VIN - VOUT - IOUT * RCH VIN - VOUT SP6651A High Efficiency 800mA Synchronous Buck Regulator 8 © Copyright 2004 Sipex Corporation THEORY OF OPERATION: Continued drop of the PMOS passing the inductor current with a second voltage drop representing the maximum allowable inductor current. As the two voltages become equal, the over-current comparator triggers a minimum off-time one shot. The off-time one shot forces the loop into the discharge phase for a minimum TOFF time causing the inductor current to decrease. At the end of the off-time, loop control is handed back to the AND’d on-time signal. If the output voltage is still low, charging begins until the output is in regulation or the current limit has been reached again. During startup and overload conditions, the converter behaves like a current source at the programmed limit minus half the current ripple. The minimum TOFF is controlled by the equation: is a minimum of KON/L, more than the load current demands. The converter goes in to a standard pulse frequency modulation (PFM) mode where the switching frequency is proportional to the load current. Low Dropout and Load Transient Operation AND’ing the loop comparator also increases the duty ratio past the ideal D= VOUT /VIN up to and including 100%. Under a light to heavy load transient, the loop comparator will hold the main switch on longer than the minimum on timer until the output is brought back into regulation. Also, as the input voltage supply drops down close to the output voltage, the main MOSFET resistance loss will dictate a much higher duty ratio to regulate the output. Eventually as the input voltage drops low enough, the output voltage will follow, causing the loop comparator to hold the converter at 100% duty cycle. TOFF (MIN) = VOUT Under-Voltage Lockout This mode is critical in extending battery life when the output voltage is at or above the minimum usable input voltage. The dropout voltage is the minimum (VIN -VOUT) below which the output regulation cannot be maintained. The dropout voltage of SP6651A is equal to IL* (0.3Ω+ RL1) where 0.3Ω is the typical RDS(ON) of the P-Channel MOSFET and RL is the DC resistance of the inductor. The SP6651A is equipped with a programmable under-voltage lockout to protect the input battery source from excessive currents when substantially discharged. When the input supply is below the UVLO threshold both power switches are open to prevent inductor current from flowing. The three levels of falling input voltage UVLO threshold are shown in Table 1, with a typical hysteresis of 120mV to prevent chattering due to the impedance of the input source. During UVLO, BLON is forced low. The SP6651A has been designed to operate in dropout with a light load Iq of only 80µA. The on-time control circuit seamlessly operates the converter between CCM, DCM, and low dropout modes without the need for compensation. The converter’s transient response is quick since there is no compensated error amplifier in the loop. Under-Current Detection The synchronous rectifier is comprised of an inductor discharge switch, a voltage comparator, and a driver latch. During the off-time, positive inductor current flows into the PGND pin 9 through the low side NMOS switch to LX pin 10, through the inductor and the output capacitor, and back to pin 9. The comparator monitors the voltage drop across the discharge NMOS. As the inductor current approaches zero, the channel voltage sign goes from negative to positive, causing the comparator to trigger the Inductor Over-Current Protection To reduce the light load dropout Iq, the SP6651A over-current system is only enabled when IL1 > 400mA. The inductor over-current protection circuitry is programmed to limit the peak inductor current to 1.25A. This is done during the ontime by comparing the source to drain voltage Date: 5/25/04 KOFF SP6651A High Efficiency 800mA Synchronous Buck Regulator 9 © Copyright 2004 Sipex Corporation THEORY OF OPERATION: Continued driver latch and open the switch to prevent inductor current reversal. This circuit along with the on-timer puts the converter into PFM mode and improves light load efficiency when the load current is less than half the inductor ripple current defined by KON/L. circuitry to re-establish itself. Power conversion begins with the assertion of the internal reference ready signal which occurs approximately 150µs after the enable signal is received. Battery Low Indicator The BLON function is a differential measurement of (VIN -VOUT) which causes the open drain NMOS on pin 3 to sink current to ground when (VIN -VOUT) < 300mV. Tying a resistor from pin 3 to VIN or VOUT creates a logic level battery low indicator. A low bandwidth comparator and 3% hysteresis filter the input voltage ripple to prevent noisy transitions at the thresh old. BLON is forced Low when in UVLO. Thermal Shutdown The converter will open both power switches if the die junction temperature rises above 140°C. The die must cool down below 126°C before the regulator is re-enabled. This feature protects the SP6651A and surrounding circuitry from excessive power dissipation due to fault conditions. Shutdown/Enable Control External Feedback Pin The D0, D1 pins 4,5 of the device are logic level control pins that according to Table 1 shut down the converter when both are a logic low, or enables the converter when either are a logic high. When the converter is shut down, the power switches are opened and all circuit biasing is extinguished leaving only junction leakage currents on supply pins 1 and 2. After pins 4 or 5 are brought high to enable the converter, there is a turn on delay to allow the regulator The FB pin 6 is compared to an internal reference voltage of 0.8V to regulate the SP6651A output. The output voltage can be externally programmed within the range +1.0V to +5.0V by tying a resistor from FB to ground and FB to VOUT (pin7). See the applications section for resistor selection information. APPLICATION INFORMATION and would be fairly constant for different input and output voltages, simplifying the selection of components for the SP6651A power circuit. Other inductor values could be selected, as shown in Table 2 Components Selection. Using a larger value than 10µH in an attempt to reduce output voltage ripple would reduce inductor current ripple and may not produce as stable an output ripple. For larger inductors with the SP6651A, which has a peak inductor current of 1.25A, most 15µH or 22µH inductors would have to be larger physical sizes, limiting their use in small portable applications. Smaller values like 6.8µH would more easily meet the 1.25A limit and come in small case sizes, and the increased Inductor Selection The SP6651A uses a specially adapted minimum on-time control of regulation utilizing a precision comparator and bandgap reference. This adaptive minimum on-time control has the advantage of setting a constant current ripple for a given inductor size. From the operations section it has been shown: K Inductor Current Ripple, ILR ≈ ON L For the typical SP6651A application circuit with inductor size of 10µH, and KON of 2V*µsec, the SP6651A current ripple would be about 200mA, Date: 5/25/04 SP6651A High Efficiency 800mA Synchronous Buck Regulator 10 © Copyright 2004 Sipex Corporation APPLICATION INFORMATION: Continued inductor current ripple of almost 300mA would produce very stable regulation and fast load transient response at the expense of slightly reduced efficiency. For the 22µF POSCAP with 0.04Ω ESR, and a 10µH inductor yielding 200mA inductor current ripple ILR, the VOUT ripple would be 8mVpp. Since 8mV is a very small signal level, the actual value would probably be larger due to noise and layout issues, but this illustrates that the SP6651A output ripple can be very low indeed. To improve stability, a small ceramic capacitor, CF = 22pF should be paralleled with the feedback voltage divider RF, as shown on the typical application schematic on page 1. Another function of the output capacitance is to hold up the output voltage during the load transients and prevent excessive overshoot and undershoot. The typical performance characteristics curves show very good load step transient response for the SP6651A with the recommended output capacitance of 22µF ceramic. Other inductor parameters are important: the inductor current rating and the DC resistance. When the current through the inductor reaches the level of ISAT, the inductance drops to 70% of the nominal value. This non-linear change can cause stability problems or excessive fluctuation in inductor current ripple. To avoid this, the inductor should be selected with saturation current at least equal to the maximum output current of the converter plus half the inductor current ripple. To provide the best performance in dynamic conditions such as start-up and load transients, inductors should be chosen with saturation current close to the SP6651A inductor current limit of 1.25A. The input capacitor will reduce the peak current drawn from the battery, improve efficiency and significantly reduce high frequency noises induced by a switching power supply. The typical input capacitor for the SP6651A is 22µF ceramic, POSCAP or Aluminum Polymer. These capacitors will provide good high frequency bypassing and their low ESR will reduce resistive losses for higher efficiency. An RC filter is recommended for the VIN pin 2 to effectively reduce the noise for the ICs analog supply rail which powers sensitive circuits. This time constant needs to be at least 5 times greater than the switching period, which is calculated as 1/FLP during the CCM mode. The typical application schematic uses the values of RVIN = 10Ω and CVIN = 1µF to meet these requirements. DC resistance, another important inductor characteristic, directly affects the efficiency of the converter, so inductors with minimum DC resistance should be chosen for high efficiency designs. Recommended inductors with low DC resistance are listed in table 2. Preferred inductors for on board power supplies with the SP6651A are magnetically shielded types to minimize radiated magnetic field emissions. Capacitor Selection The SP6651A has been designed to work with very low ESR output capacitors (listed in Table 2 Component Selection) which for the typical application circuit are 22µF ceramic, POSCAP or Aluminum Polymer. These capacitors combine small size, low ESR and good value. To regulate the output with low ESR capacitors of 0.01Ω or less, an internal ramp voltage VRAMP has been added to the FB signal to reliably trip the loop comparator (as described in the Operations section). Output ripple for a buck regulator is determined mostly by output capacitor ESR, which for the SP6651A with a constant inductor current ripple can be expressed as: VOUT (ripple) = ILR * RESR Date: 5/25/04 SP6651A High Efficiency 800mA Synchronous Buck Regulator 11 © Copyright 2004 Sipex Corporation APPLICATION INFORMATION: Continued INDUCTORS SURFACE MOUNT Inductor Specification Inductance (µH) Manufacturer/Part No. Series R Ω ISAT (A) Size LxW(mm) Ht. (mm) Inductor Type Manufacturer Website 10 Sumida CDRH5D28-100 0.048 1.30 5.7 x 5.5 3.0 Shielded Ferrite Core sumida.com 10 TDK RLF5018T-100MR94 0.056 0.94 5.6 x 5.2 2.0 Shielded Ferrite Core tdk.com 10 Coilcraft DO1608C-103 0.160 1.10 6.6 x 4.5 2.9 Unshielded Ferrite Core coilcraft.com 10 Coilcraft LPO6013-103 0.300 0.70 6.0 x 5.4 1.3 Unshielded Ferrite Core coilcraft.com 6.8 Sumida CDRH5D28-6R8 0.081 1.12 4.7 x 4.5 3.0 Shielded Ferrite Core sumida.com 6.8 TDK RLF5018T-6R8M1R1 0.47 1.10 5.6 x 5.2 2.0 Shielded Ferrite Core tdk.com 6.8 Coilcraft DO1608C-682 0.130 1.20 6.6 x 4.5 2.9 Unshielded Ferrite Core coilcraft.com 6.8 Coilcraft LPO6013-103 0.200 0.60 6.0 x 5.4 1.3 Unshielded Ferrite Core coilcraft.com CAPACITORS - SURFACE MOUNT Capacitor Specification Capacitance (µF) Manufacturer/Part No. ESR RippleCurrent Size Ω (max) (A) @ 45°C LxW(mm) Ht. (mm) Voltage (V) Capacitor Type Manufacturer Website 22 TDK C3216X5R0J226M 0.002 3.00 3.2 x 1.6 1.6 6.3 X5R Ceramic tdk.com 22 SANYO 6APA22M 0.040 1.90 7.3 x 4.3 2.0 6.3 POSCAP sanyovideo.com 47 TDK C3225X5R0J46M 0.002 4.00 3.2 x 1.6 1.6 6.3 X5R Ceramic tdk.com 47 SANYO 6TPA47M 0.040 1.90 6.0 x 3.2 2.8 6.3 POSCAP sanyovideo.com Note: Components highlighted in bold are those used on the SP6651A Evaluation Board. Table 2 Component Selection current ripple, (for the typical 10µH inductor application on 100mA is half the 200mA inductor current ripple), the output ripple frequency will be fairly constant. From the operations section, this maximum loop frequency in continuous conduction mode is: Output Voltage Program The output voltage is programmed by the external divider, as shown in the typical application circuit on page 1. First pick a value for RI that is no larger than 300K. Too large a value of RI will reduce the AC voltage seen by the loop comparator since the internal FB pin capacitance can form a low pass filter with RF in parallel with RI. The formula for RF with a given RI and output voltage is: RF = ( FLP ≈ 1 * KON VOUT * (VIN - VOUT) VIN Data for loop frequency, as measured from output voltage ripple frequency, can be found in the typical performance curves. VOUT - 1 ) • RI 0.8V Output Voltage Ripple Frequency Layout Considerations An important consideration in a power supply application is the frequency value of the output ripple. Given the control technique of the SP6651A (as described in the operations section), the frequency of the output ripple will vary when in light to moderate load in the discontinuous or PFM mode. For moderate to heavy loads greater than about 100mA inductor Proper layout of the power and control circuits is necessary in a switching power supply to obtain good output regulation with stability and a minimum of output noise. The SP6651A application circuit can be made very small and reside close to the IC for best performance and solution size, as long as some layout techniques are taken into consideration. To avoid excessive interference Date: 5/25/04 SP6651A High Efficiency 800mA Synchronous Buck Regulator 12 © Copyright 2004 Sipex Corporation APPLICATION INFORMATION: Continued between the SP6651A high frequency converter and the other active components on the board, some rules should be followed. Refer to the typical application schematic on page 1 and the sample PCB layout shown in the following figures to illustrate how to layout a SP6651A power supply. SP6651A pin 9 GND is connected to pin 10 PGND. Power loops on the input and output of the converter should be laid out with the shortest and widest traces possible. The longer and narrower the trace, the higher the resistance and inductance it will have. The length of traces in series with the capacitors increases its ESR and ESL and reduces their effectiveness at high frequencies. Therefore, put the 1µF bypass capacitor as close to the VIN and GND pins of the converter as possible, the 22µF CIN close to the PVIN pin and the 22µF output capacitor as close to the inductor as possible. The external voltage feedback network RF, RI and feedforward capacitor CF should be placed very close to the FB pin. Any noise traces like the LX pin should be kept away from the voltage feedback network and separated from it by using power ground copper to minimize EMI. Avoid injecting noise into the sensitive part of circuit via the ground plane. Input and output capacitors conduct high frequency current through the ground plane. Separate the control and power grounds and connect them together at a single point. Power ground plane is shown in the figure titled PCB top sample layout and connects the ground of the COUT capacitor to the ground of the CIN capacitor and then to the PGND pin 10. The control ground plane connects from pin 9 GND to ground of the CVIN capacitor and the RI ground return of the feedback resistor. These two separate control and power ground planes come together in the figure titled PCB top sample layout where Figure 19. SP6651A PCB Component Sample Layout Figure 20. SP6651A PCB Top Sample Layout Figure 21. SP6651A PCB Bottom Sample Layout Date: 5/25/04 SP6651A High Efficiency 800mA Synchronous Buck Regulator 13 © Copyright 2004 Sipex Corporation PACKAGE: 10 PIN MSOP D e1 Ø1 E/2 R1 R E1 E L2 Ø1 Seating Plane L Gauge Plane Ø 00 L1 1 2 e Pin #1 indentifier must be indicated within this shaded area (D/2 * E1/2) 10-PIN MSOP JEDEC MO-187 (BA) Variation A Dimensions in (mm) MIN - 0.00 A1 1.10 - 0.75 b 0.17 - 0.27 c 0.08 - 0.23 0.85 B 0.15 A2 D B NOM MAX - 0.95 (b) WITH PLATING 3.00 BSC E 4.90 BSC E1 3.00 BSC e 0.50 BSC e1 c 2.00 BSC L 0.4 0.60 0.80 L1 0.95 REF L2 0.25 BSC N BASE METAL Section B-B 10 R 0.07 - - R1 0.07 - - Ø 0º Ø1 5º - A2 A 8º b 15º A1 10-PIN MSOP 1 Date: 5/25/04 SP6651A High Efficiency 800mA Synchronous Buck Regulator 14 © Copyright 2004 Sipex Corporation PACKAGE: 10 PIN DFN Bottom View Top View D e b D/2 1 2 E/2 E2 E K L D2 Pin 1 identifier to be located within this shaded area. Terminal #1 Index Area (D/2 * E/2) 10 Pin DFN DIMENSIONS in (mm) (JEDEC MO-229, VEED-5 VARIATION) SYMBOL A A1 A3 b D D2 e E E2 K L Date: 5/25/04 MIN NOM MAX 0.80 0 0.90 1.00 0.02 0.05 0.20 REF A 0.18 0.25 0.30 3.00 BSC 2.20 2.70 0.50 PITCH 3.00 BSC 1.40 1.75 0.20 0.30 0.40 0.50 A1 A3 Side View 10 PIN DFN SP6651A High Efficiency 800mA Synchronous Buck Regulator 15 © Copyright 2004 Sipex Corporation ORDERING INFORMATION Part Number Top Mark Operating Temperature Range Package Type SP6651AEU..............6651AEU....................... -40°C to +85°C ................................................... 10 Pin MSOP SP6651AEU/TR........6651AEU ............ ........... -40°C to +85°C .................................................. 10 Pin MSOP SP6651AER.............6651AER......................... -40°C to +85°C ..................................................... 10 Pin DFN SP6651AER/TR.......6651AER......................... -40°C to +85°C ..................................................... 10 Pin DFN Available in lead free packaging. To order add "-L" suffix to part number. Example: SP6651AEU/TR = standard; SP6651AEU-L/TR = lead free /TR = Tape and Reel Pack quantity is 2500 for MSOP and 3,000 for DFN. Corporation ANALOG EXCELLENCE Sipex Corporation Headquarters and Sales Office 233 South Hillview Drive Milpitas, CA 95035 TEL: (408) 934-7500 FAX: (408) 935-7600 Sipex Corporation reserves the right to make changes to any products described herein. Sipex does not assume any liability arising out of the application or use of any product or circuit described herein; neither does it convey any license under its patent rights nor the rights of others. Date: 5/25/04 SP6651A High Efficiency 800mA Synchronous Buck Regulator 16 © Copyright 2004 Sipex Corporation