TI CDCM9102RHBR

CDCM9102
SCAS922 – FEBRUARY 2012
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Low-Noise Two-Channel 100-MHz Clock Generator
Check for Samples: CDCM9102
FEATURES
1
•
2
•
•
•
Integrated Low-Noise Clock Generator
Including PLL, VCO, and Loop Filter
Two Low-Noise 100-MHz Clocks (LVPECL,
LVDS, or pair of LVCMOS)
– Support for HCSL Signaling Levels
(AC-Coupled)
– Typical Period Jitter: 21 ps pk-pk
– Typical Random Jitter: 510 fs
– Output Type Set by Pins
Bonus Single-ended 25-MHz Output
Integrated Crystal Oscillator Input Accepts
25-MHz Crystal
•
•
•
•
•
Output Enable Pin Shuts Off Device and
Outputs.
5-mm × 5-mm QFN-32 Package
ESD Protection Exceeds 2 kV HBM, 500 V CDM
Industrial Temperature Range (–40°C to 85°C)
3.3-V Power Supply
APPLICATIONS
•
•
Reference Clock Generation for PCI Express
Gen 1, Gen2, and Gen3
General-Purpose Clocking
DESCRIPTION
The CDCM9102 is a low-jitter clock generator designed to provide reference clocks for communications
standards such as PCI Express™. The device is easy to configure and use. The CDCM9102 provides two
100-MHz differential clock ports. The output types supported for these ports include LVPECL, LVDS, or a pair of
LVCMOS buffers. HCSL signaling is supported using an ac-coupled network. The user configures the output
buffer type desired by strapping device pins. Additionally, a single-ended 25-MHz clock output port is provided.
Uses for this port include general-purpose clocking, clocking Ethernet PHYs, or providing a reference clock for
additional clock generators. All clocks generated are derived from a single external 25-MHz crystal.
25 MHz
XO
25 MHz
Low
Noise
Clock
Generator
PCIe
100 MHz
PCIe
100 MHz
CDCM9102
Figure 1. CDCM9102 Typical Application Example
1
2
Please be aware that an important notice concerning availability, standard warranty, and use in critical applications of Texas
Instruments semiconductor products and disclaimers thereto appears at the end of this data sheet.
PCI Express is a trademark of PCI-SIG .
PRODUCTION DATA information is current as of publication date.
Products conform to specifications per the terms of the Texas
Instruments standard warranty. Production processing does not
necessarily include testing of all parameters.
Copyright © 2012, Texas Instruments Incorporated
CDCM9102
SCAS922 – FEBRUARY 2012
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These devices have limited built-in ESD protection. The leads should be shorted together or the device placed in conductive foam
during storage or handling to prevent electrostatic damage to the MOS gates.
REGCAP1
REGCAP2
Vreg
Vreg
OE
OSCOUT
XIN
OUT1P
Low
Noise
Clock
Generator
XO
OUT1N
OUT0P
OUT0N
CDCM9102
RESET
OS1 OS0
Figure 2. CDCM9102 Block Diagram
white space
white space
white space
NC
OSCOUT
GND
XIN
VDD6
REGCAP1
VDD5
REGCAP2
TOP VIEW
24
23
22
21
20
19
18
17
NC
25
16
VDD4
NC
26
15
NC
NC
27
14
GND
NC
28
13
NC
NC
29
12
RESET
NC
30
11
OS0
10
OS1
9
VDD3
1
2
3
4
5
6
7
8
VDD1
OUT0N
OUT0P
OE
NC
32
OUT1P
NC
OUT1N
31
GND
(thermal pad)
VDD2
NC
CDCM9102
Figure 3. Pin Diagram
2
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PIN FUNCTIONS
NAME
QFN32 PIN NO.
DESCRIPTION
POWER SUPPLIES
GND
Thermal pad, 14, 22
VDD2
1
Power supply ground and thermal relief
Power Supply, OUT1 clock port
VDD1
4
Power Supply, OUT0 clock port
VDD3
9
Power supply, low-noise clock generator
VDD4
16
Power supply, low-noise clock generator
VDD5
18
Power supply, low-noise clock generator
VDD6
20
Power supply, crystal oscillator input
REGCAP1
19
Capacitor for internal regulator, connect 10-μF Y5V capacitor to GND
REGCAP2
17
Capacitor for internal regulator, connect 10-μF Y5V capacitor to GND
DEVICE CONFIGURATION AND CONTROL
NC
8, 13, 15, 24–32
OE
7
No connection permitted
Output enable/shutdown control input (see Table 1)
OS1
10
Output format select control inputs (see Table 2)
OS0
11
RESET
12
Device reset input (active-low) (see Table 3) (1)
21
Parallel resonant crystal input (25 MHz)
OUT0P
6
Output 0 – positive terminal (100 MHz)
OUT0N
5
Output 0 – negative terminal (100 MHz)
OUT1P
3
Output 1 – positive terminal (100 MHz)
OUT1N
2
Output 1 – negative terminal (100 MHz)
OSCOUT
23
Oscillator output port (25 MHz)
CRYSTAL OSCILLATOR
XIN
DEVICE OUTPUTS
(1)
For proper device startup, it is recommended that a capacitor be installed from pin 12 to GND. See STARTUP TIME ESTIMATION
section for more details.
ORDERING INFORMATION
TA
PACKAGED DEVICES
–40°C to 85°C
FEATURES
CDCM9102RHBT
32-pin QFN (RHB) package, small tape and reel
CDCM9102RHBR
32-pin QFN (RHB) package, tape and reel
ABSOLUTE MAXIMUM RATINGS
over operating free-air temperature range (unless otherwise noted) (1)
MIN
VDDx
Supply voltage range (2)
(3)
TYP
MAX
UNIT
–0.5
4.6
V
–0.5
VDDx + 0.5
V
–0.5
VDDx + 0.5
VIN
Input voltage range
VOUT
Output voltage range (3)
IIN
Input current
20
mA
IOUT
Output current
50
mA
Tstg
Storage temperature range
150
°C
(1)
(2)
(3)
–65
V
Stresses beyond those listed under Absolute Maximum Ratings may cause permanent damage to the device. These are stress ratings
only, and functional operation of the device at these or any other conditions beyond those indicated under Recommended Operating
Conditions is not implied. Exposure to absolute-maximum-rated conditions for extended periods may affect device reliability.
Supply voltages must be applied simultaneously.
The input and output negative voltage ratings may be exceeded if the input and output clamp–current ratings are observed
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DISSIPATION RATINGS (1) (2)
PARAMETER
θJA
Junction-to-ambient thermal resistance
θJP (3)
Junction-to-thermal pad (top) thermal resistance
(1)
(2)
(3)
TEST CONDITIONS
VALUE, 4 × 4 Vias on Pad
UNIT
0 LFM
35
ºC/W
4
ºC/W
The package thermal resistance is calculated in accordance with JESD 51 and JEDEC 2S2P (high-K board).
Connected to GND with sixteen thermal vias (0.3 mm in diameter)
θJP (junction-to-pad) is used for the QFN package, because the primary heat flow is from the junction to the GND pad of the QFN
package.
ELECTRICAL CHARACTERISTICS
RECOMMENDED OPERATING CONDITIONS
MIN
TYP
MAX
UNIT
3
3.3
3.6
V
85
°C
POWER SUPPLIES
VDDX
DC power-supply voltage
TEMPERATURE
TA
–40
Ambient temperature
DEVICE CURRENT CONSUMPTION
TA = –40°C to 85°C, VDDx = 3.3 V, OE = 1, values represent cumulative current/power on all VDDx pins.
BLOCK
CURRENT
(mA)
DEVICE POWER
(mW)
85
280
LVPECL
28
42.4
LVDS
20
66
V × ƒout × (CL + 20 × 10–12) × 103
V2 × ƒout × (CL + 20 × 10–12) × 103
CONDITION
Entire device, core
current
Output Buffers
LVCMOS
EXTERNAL
RESISTOR POWER
(mW)
50
DIGITAL INPUT CHARACTERISTICS – RESET, OE, OS1, OS0
TA = –40°C to 85°C
PARAMETER
TEST CONDITIONS
MIN
TYP
MAX
UNIT
LVCMOS INPUTS
VIH
Input high voltage
VIL
Input low voltage
IIH
Input high current
VDD = 3.6 V, VIL = 0 V
IIL
Input low current
VDD = 3 V, VIH = 3.6 V
CIN
Input capacitance
RPU
Input pullup resistor
4
0.6 VDD
V
8
150
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0.4 VDD
V
200
µA
–200
µA
10
pF
kΩ
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CRYSTAL-OSCILLATOR INPUT-PORT CHARACTERISTICS (XIN)
VDD = 3.3 V, TA = –40°C to 85°C
PARAMETER
TEST CONDITIONS
MIN
TYP
MAX
UNIT
CRYSTAL CHARACTERISTICS (External 25 MHz Crystal)
fXTAL
Crystal input frequency
ESR
Effective series resistance of crystal
CIN
On-chip load capacitance
XTALDL
Maximum drive level - XTAL
CSHUNT
Maximum shunt capacitance
Fundamental mode
25
8
MHz
50
Ω
10
pF
1
mW
7
pF
0.1
CLOCK OUTPUT BUFFER CHARACTERISTICS (OUTPUT MODE = LVPECL)
VDD1, VDD2 = 3.3 V; TA = –40°C to 85°C
PARAMETER
VOH
Output high voltage
VOL
Output low voltage
|VOD|
Differential output voltage
tR/tF
Output rise/fall time
ODC
Output duty cycle
tSKEW
Skew between outputs
TEST CONDITIONS
MIN
TYP
MAX
UNIT
VDD – 1.18
VDD – 0.73
V
VDD – 2
VDD – 1.55
V
0.6
1.23
V
175
ps
20% to 80%
45%
55%
20
ps
CLOCK OUTPUT BUFFER CHARACTERISTICS (OUTPUT MODE = LVDS)
VDD1, VDD2 = 3.3V; TA = –40°C to 85°C
PARAMETER
|VOD|
Differential output voltage
ΔVOD
VOD magnitude change
VOS
Common-mode voltage
ΔVOS
VOS magnitude change
tR/tF
Output rise/fall time
ODC
Output duty cycle
tSKEW
Skew between outputs
TEST CONDITIONS
MAX
UNIT
0.247
MIN
TYP
0.454
V
1.125
1.375
50
20% to 80%
45%
mV
V
50
mV
255
ps
55%
30
ps
CLOCK OUTPUT BUFFER CHARACTERISTICS (OUTPUT MODE = LVCMOS)
VDD1, VDD2 = 3.3V; TA = –40°C to 85°C
PARAMETER
TEST CONDITIONS
VOH
Output high voltage
VCC = 3 V to 3.6 V, IOH = –100 µA
VOL
Output low voltage
VCC = 3 V to 3.6 V, IOH = 100 µA
tSLEW
Output rise/fall slew rate
20% to 80%
ODC
Output duty cycle
tSKEW
Skew between outputs
MIN
TYP
MAX
UNIT
VDD – 0.5
V
0.3
2.4
45%
V
V/ns
55%
50
ps
OUTPUT JITTER PERFORMANCE
fOUT = 100 MHz, VDD = 3.3 V, TA = 25°C, jitter integration bandwidth 10 kHz–20 MHz
LVCMOS OUTPUT MODE
LVPECL OUTPUT MODE
LVDS OUTPUT MODE
Random jitter
(fs)
Period jitter
(ps pk-pk)
Random jitter
(fs)
Period jitter
(ps pk-pk)
Random jitter
(fs)
Period jitter
(ps pk-pk)
507
24.5
510
20.7
533
26.5
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TEST CONFIGURATIONS
LVCMOS
5 pF
Figure 4. LVCMOS Output Test Load
Phase Noise Analyzer
RF
50 W
LVCMOS
50 W
Figure 5. LVCMOS AC Configuration for Device Test
Oscilloscope
CH1
CH2
50 W
LVPECL
50 W
50 W (2)
VDD - 2 V
Figure 6. LVPECL DC Configuration for Device Test
Phase Noise Analyzer
RF
50 W
LVPECL
150 W (2)
50 W
Figure 7. LVPECL AC Configuration for Device Test
6
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Oscilloscope
CH1
CH2
50 W
LVDS
100 W
50 W
Figure 8. LVDS DC Configuration for Device Test
Phase Noise Analyzer
RF
50 W
50 W
LVDS
50 W
50 W
Figure 9. LVDS AC Configuration for Device Test
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PERFORMANCE CHARACTERISTICS
Figure 10. CDCM9102 Typical Phase Noise Performance (LVPECL Mode)
FUNCTIONAL DESCRIPTION
DEVICE CONFIGURATION
Table 1. CDCM9102 Pin Control of Output Enable
OE (Pin 7)
MODE
DEVICE CORE
0
Power down
Power down
OUTPUT
Hi-Z
1
Normal
Active
Active
Table 2. CDCM9102 Pin Configuration of Output Type
CONTROL PINS
8
OUTPUT MODE
OS1 (Pin 10)
OS0 (Pin 11)
0
0
0
1
LVDS, OSCOUT = OFF
1
0
LVPECL, OSCOUT = OFF
1
1
LVPECL, OSCOUT = ON
LVCMOS, OSCOUT = OFF
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Table 3. CDCM9102 Device Reset
RESET (Pin 12)
OPERATING MODE
DEVICE OUTPUTS
0
Device reset
Hi-Z
0→1
Clock generator calibration
Hi-Z
1
Normal
Active
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APPLICATION INFORMATION
CRYSTAL INPUT (XIN) INTERFACE
The CDCM9102 implements a Colpitts oscillator; therefore, one side of the crystal connects to the XIN pin and
the other crystal terminal connects to ground. The device requires the use of a fundamental-mode crystal, and
the oscillator operates in parallel resonance mode. The correct load capacitance is necessary to ensure that the
circuit oscillates properly. The load capacitance comprises all capacitances in the oscillator feedback loop (the
capacitances seen between the terminals of the crystal in the circuit). It is important to account for all sources of
capacitance when calculating the correct value for the external discrete load capacitance shown in Figure 11.
XIN
(Pin 21)
XO
25 MHz
CL
CSTRAY
CPARASITIC
CIN
Figure 11. Configuration of Circuit for CDCM9102 XIN Oscillator
The CDCM9102 has been characterized with 10-pF parallel-resonant crystals. The input stage of the crystal
oscillator in the CDCM9102 is designed to oscillate at the correct frequency for all parallel-resonant crystals with
low-pull capability and rated with a load capacitance that is equal to the sum of the on-chip load capacitance at
the XIN pin (CIN = 10 pF maximum), crystal stray capacitance, and board parasitic capacitance between the
crystal and XIN pin. To minimize stray and parasitic capacitances, minimize the trace distance routed from the
crystal to the XIN pin and avoid other active traces and/or active circuitry in the area of the crystal oscillator
circuit. Table 4 lists crystal types that have been evaluated with the CDCM9102.
Table 4. CDCM9102 Crystal Recommendations
MANUFACTURER
PART NUMBER
Vectron
VXC1-1133
Fox
218-3
Saronix
FP2650002
A mismatch of the load capacitance results in a frequency error according to Equation 1:
C
C
Δf
S
S
=
f
2 C +C
2 C +C
Lr
La
O
O
(
) (
)
(1)
where:
Δƒ is the frequency error required by the application.
f is the fundamental frequency of the crystal.
CS is the motional capacitance of the crystal. This is a parameter in the data sheet of the crystal.
C0 is the shunt capacitance of the crystal. This is a parameter in the data sheet of the crystal.
CLr is the rated load capacitance of the crystal. This is a parameter in the data sheet of the crystal.
CLa is the actual load capacitance implemented on the PCB (CIN + stray capacitance + parasitic capacitance
+ CL).
The difference between the rated load capacitance (from the crystal datasheet) and the actual load capacitance
(CLa = CIN + CL + CSTRAY + CPARASITIC) should be minimized. A crystal with a low pull-ability rating (low CS) is
ideal.
Design Example:
Desired frequency tolerance Δf ≤ ±80 ppm
Crystal Vendor Parameters:
Intrinsic Frequency Tolerance = ±30 ppm
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C0 = 7 pF (shunt capacitance)
CS = 10 fF (motional capacitance)
CLr = 12 pF (load capacitance)
Substituting these parameters into Equation 1 yields a maximum value of CLa = 17 pF in order to achieve the
desired Δf (±50 ppm). Recall that CLa = CIN + CL + CSTRAY + CPARASITIC = 8 pF + (CL + CSTRAY + CPARASITIC) (1) .
Ideally, the load presented to this crystal should be 12 pF; therefore the sum of (CL + CSTRAY + CPARASITIC) must
be less than 9 pF. Stray and parasitic capacitance must be controlled. This is because the Colpitts oscillator is
particularly sensitive to capacitance in parallel with the crystal; therefore, good layout practice is essential. It is
recommended that the designer extract the stray and parasitic capacitance from the printed circuit board design
tool and adjust CL accordingly to achieve CLr = CLa. In common scenarios, the external load capacitor is often
unnecessary; however, it is recommended that pads be implemented to accommodate an external load capacitor
so that the ppm error can be minimized.
STARTUP TIME ESTIMATION
The CDCM9102 contains a low-noise clock generator that calibrates to an optimal operating point at device
power up. In order to ensure proper device operation, the oscillator must be stable prior to the low-noise clock
generator calibration procedure. Quartz-based oscillators can take up to 2 ms to stabilize; therefore it is
recommended that the application ensure that the RESET pin is de-asserted at least 5 ms after the power supply
has finished ramping. This can be accomplished by controlling the RESET pin directly, or by applying a 47-nF
capacitor to ground on the RESET pin (this provides a delay because the RESET pin includes a 150-kΩ pullup
resistor.
The CDCM9102 startup time can be estimated based on parameters defined in Table 5 and graphically shown in
Figure 12.
Table 5. CDCM9102 Startup Time Dependencies
Parameter
Definition
Description
Formula / Method of Determination
1
tREF
Reference clock period
The reciprocal of the applied reference
frequency in seconds
tpul
Power-up time (low limit)
Power-supply rise time to low limit of
power-on-reset trip point
Time required for power supply to ramp to 2.27 V
tpuh
Power-up time (high limit)
Power supply rise time to high limit of
power-on-reset trip point
Time required for power supply to ramp to 2.64 V
trsu
Reference start-up time
After POR releases, the Colpitts oscillator is
enabled. This start-up time is required for the
oscillator to generate the requisite signal
levels for the delay block to be clocked by the
reference input.
500 μs best case and 800 μs worst case (for a crystal
input)
tdelay
Delay time
Internal delay time generated from the
reference clock. This delay provides time for
the reference oscillator to stabilize.
tdelay = 16,384 × tREF = 655 µs
tVCO_CAL
VCO calibration time
VCO calibration time generated from the
reference clock. This process selects the
operating point for the VCO based on the PLL
settings.
tVCO_CAL = 550 × tREF = 22 µs
tPLL_LOCK
PLL lock time
Time requried for PLL to lock within ±10 ppm
of fREF
(1)
t REF =
fREF
= 0.04 μs
The PLL settles in 12.5 μs
CIN = 8 pF (typical), 10 pF (maximum). See the Crystal Oscillator Input Port Characteristics (XIN) table.
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Reference
Start-Up
Delay
VCO Calibration
PLL Lock
trsu
tdelay
tVCO_CAL
tPLL_LOCK
2.64
2.27
tpd
Time - (S)
tpuh
Figure 12. CDCM9102 Start-Up Time Dependencies
The CDCM9102 startup time limits, tMAX and tMIN, can now be calculated as follows
tMAX = tpuh + trsu + tdelay + tVCO_CAL + tPLL_LOCK
tMIN = tpul + trsu + tdelay + tVCO_CAL + tPLL_LOCK
THERMAL MANAGEMENT
To ensure optimal performance and reliability, good thermal design practices are important when using the
CDCM9102. Die temperature should be limited to a maximum of 125°C. That is, as an estimate, TA (ambient
temperature) plus device power consumption times θJA should not exceed 125°C.
The device package has an exposed pad that provides the primary heat removal path as well as an electrical
grounding to the printed circuit board (PCB). To maximize the removal of heat from the package, a thermal
landing pattern including multiple vias to a ground plane must be incorporated on the PCB within the footprint of
the package. The exposed pad must be soldered down to ensure adequate heat conduction out of the package.
A recommended land and via pattern is shown in Figure 13.
5.0 mm,min
0.33 mm, typ
2.1 mm, typ
Figure 13. Recommended PCB Layout for CDCM9102
POWER SUPPLY FILTERING
PLL-based frequency synthesizers are very sensitive to noise on the power supply, which can dramatically
increase the jitter of the PLL. This is especially true for analog-based PLLs. Thus, it is essential to reduce noise
from the system power supply, especially when jitter/phase noise is very critical to applications. A PLL has
attenuated jitter due to power supply noise at frequencies beyond the PLL bandwidth due to attenuation by the
loop response.
Filter capacitors are used to eliminate the low-frequency noise from the power supply, where the bypass
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capacitors provide the very low-impedance path for high-frequency noise and guard the power supply system
against induced fluctuations. The bypass capacitors also provide a source of instantaneous current as required
by the device output stages. Therefore, bypass capacitors must have low ESR. To properly use the bypass
capacitors, they must be placed very close to the power supply pins and must be laid out with short loops to
minimize inductance.
Figure 14 shows a general recommendation for decoupling the power supply. The CDCXM9102 power supplies
fall into one of two categories: analog supplies (VDD3, VDD4, and VDD5), and input/output supplies (VDD1,
VDD2, and VDD6). Short the analog supplies together to form the analog supply node; likewise, short the
input/output supplies together to form the I/O supply node. Isolate the analog node from the PCB power supply
and I/O node by inserting a ferrite bead. This helps isolate the high-frequency switching noises generated by the
clock drivers and I/O from the sensitive analog supply node. Choosing an appropriate ferrite bead with low dc
resistance is important, as it is imperative to maintain a voltage at the power-supply pin of the CDCM9102 that is
over the minimum voltage needed for its proper operation.
PCB
Supply
Analog Node
I/O Node
Ferrite Bead
0.1 µF
(´3)
10 µF
10 µF
0.1 µF
(´3)
Figure 14. CDCM9102 Power Supply Decoupling – Power Pin Bypass Concept
OUTPUT TERMINATION
The CDCM9102 is a 3.3-V clock driver which has the following options for the output type: LVPECL, LVDS, and
LVCMOS.
LVPECL TERMINATION
The CDCM9102 is an open emitter for LVPECL outputs. Therefore, proper biasing and termination is required to
ensure correct operation of the device and to optimize signal integrity. The proper termination for LVPECL is
50 Ω to (Vcc-2) V but this dc voltage is not readily available on a board. Thus a Thevenin’s equivalent circuit is
worked out for the LVPECL termination in both direct-coupled (dc) and ac-coupled cases, as shown in Figure 15
and Figure 16. It is recommended to place all resistive components close to either the driver end or the receiver
end. If the supply voltages of the driver and receiver are different, ac coupling is required.
VDDOUT
130 W (2)
LVPECL
LVPECL
82 W (2)
Figure 15. LVPECL Output Termination (DC-Coupled)
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Vb
50 W (2)
LVPECL
150 W (2)
Figure 16. LVPECL Output Termination (AC-Coupled)
LVDS TERMINATION
The proper LVDS termination for signal integrity over two 50-Ω lines is 100 Ω between the outputs on the
receiver end. Either a direct-coupled (dc) termination or ac-coupled termination can be used for LVDS outputs,
as shown in Figure 17 and Figure 18. It is recommended to place all resistive components close to either the
driver end or the receiver end. If the supply voltages of the driver and receiver are different, ac coupling is
required.
100 W
LVDS
LVDS
Figure 17. LVDS Output Termination (DC Coupled)
100 W
LVDS
Figure 18. LVDS Output Termination (AC Coupling)
LVCMOS TERMINATION
Series termination is a common method to maintain the signal integrity for LVCMOS drivers, if connected to a
receiver with a high-impedance input. For series termination, a series resistor, Rs, is placed close to the driver,
as shown in Figure 19. The sum of the driver impedance and Rs should be close to the transmission-line
impedance, which is usually 50 Ω. Because the LVCMOS driver in the CDCM9102 has an impedance of 30 Ω,
Rs is recommended to be 22 Ω to maintain proper signal integrity.
LVCMOS
LVCMOS
22 W
Figure 19. LVCMOS Output Termination
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INTERFACING BETWEEN LVPECL and HCSL (PCI Express)
Certain PCI Express applications require HCSL signaling. Because the common-mode voltage for LVPECL and
HCSL are different, applications requiring HCSL signaling must use ac coupling as shown in Figure 20. The
150-Ω resistors ensure proper biasing of the CDCM9102 LVPECL output stage. The 471-Ω and 56-Ω resistor
network biases the HCSL receiver input stage.
VDDHCSL
471 W (2)
HCSL
LVPECL
150 W (2)
56 W (2)
Figure 20. Interfacing Between LVPECL and HCSL
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Copyright © 2012, Texas Instruments Incorporated
Product Folder Link(s): CDCM9102
15
PACKAGE OPTION ADDENDUM
www.ti.com
17-Mar-2012
PACKAGING INFORMATION
Orderable Device
Status
(1)
Package Type Package
Drawing
Pins
Package Qty
Eco Plan
(2)
Lead/
Ball Finish
MSL Peak Temp
(3)
CDCM9102RHBR
ACTIVE
QFN
RHB
32
3000
Green (RoHS
& no Sb/Br)
CU NIPDAU Level-2-260C-1 YEAR
CDCM9102RHBT
ACTIVE
QFN
RHB
32
250
Green (RoHS
& no Sb/Br)
CU NIPDAU Level-2-260C-1 YEAR
Samples
(Requires Login)
(1)
The marketing status values are defined as follows:
ACTIVE: Product device recommended for new designs.
LIFEBUY: TI has announced that the device will be discontinued, and a lifetime-buy period is in effect.
NRND: Not recommended for new designs. Device is in production to support existing customers, but TI does not recommend using this part in a new design.
PREVIEW: Device has been announced but is not in production. Samples may or may not be available.
OBSOLETE: TI has discontinued the production of the device.
(2)
Eco Plan - The planned eco-friendly classification: Pb-Free (RoHS), Pb-Free (RoHS Exempt), or Green (RoHS & no Sb/Br) - please check http://www.ti.com/productcontent for the latest availability
information and additional product content details.
TBD: The Pb-Free/Green conversion plan has not been defined.
Pb-Free (RoHS): TI's terms "Lead-Free" or "Pb-Free" mean semiconductor products that are compatible with the current RoHS requirements for all 6 substances, including the requirement that
lead not exceed 0.1% by weight in homogeneous materials. Where designed to be soldered at high temperatures, TI Pb-Free products are suitable for use in specified lead-free processes.
Pb-Free (RoHS Exempt): This component has a RoHS exemption for either 1) lead-based flip-chip solder bumps used between the die and package, or 2) lead-based die adhesive used between
the die and leadframe. The component is otherwise considered Pb-Free (RoHS compatible) as defined above.
Green (RoHS & no Sb/Br): TI defines "Green" to mean Pb-Free (RoHS compatible), and free of Bromine (Br) and Antimony (Sb) based flame retardants (Br or Sb do not exceed 0.1% by weight
in homogeneous material)
(3)
MSL, Peak Temp. -- The Moisture Sensitivity Level rating according to the JEDEC industry standard classifications, and peak solder temperature.
Important Information and Disclaimer:The information provided on this page represents TI's knowledge and belief as of the date that it is provided. TI bases its knowledge and belief on information
provided by third parties, and makes no representation or warranty as to the accuracy of such information. Efforts are underway to better integrate information from third parties. TI has taken and
continues to take reasonable steps to provide representative and accurate information but may not have conducted destructive testing or chemical analysis on incoming materials and chemicals.
TI and TI suppliers consider certain information to be proprietary, and thus CAS numbers and other limited information may not be available for release.
In no event shall TI's liability arising out of such information exceed the total purchase price of the TI part(s) at issue in this document sold by TI to Customer on an annual basis.
Addendum-Page 1
PACKAGE MATERIALS INFORMATION
www.ti.com
16-Mar-2012
TAPE AND REEL INFORMATION
*All dimensions are nominal
Device
Package Package Pins
Type Drawing
SPQ
Reel
Reel
A0
Diameter Width (mm)
(mm) W1 (mm)
B0
(mm)
K0
(mm)
P1
(mm)
W
Pin1
(mm) Quadrant
CDCM9102RHBR
QFN
RHB
32
3000
330.0
12.4
5.3
5.3
1.5
8.0
12.0
Q2
CDCM9102RHBT
QFN
RHB
32
250
180.0
12.4
5.3
5.3
1.5
8.0
12.0
Q2
Pack Materials-Page 1
PACKAGE MATERIALS INFORMATION
www.ti.com
16-Mar-2012
*All dimensions are nominal
Device
Package Type
Package Drawing
Pins
SPQ
Length (mm)
Width (mm)
Height (mm)
CDCM9102RHBR
QFN
RHB
32
3000
346.0
346.0
29.0
CDCM9102RHBT
QFN
RHB
32
250
210.0
185.0
35.0
Pack Materials-Page 2
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