SP5669 2.7GHz I2C Bus Controlled Synthesiser Preliminary Information DS4852 - 1.4 November 1997 The SP5669 is a single chip frequency synthesiser designed for tuning systems up to 2.7GHz and offers step size compatible with DTT offset requirements. The RF preamplifier drives a divide by two prescaler which can be disabled for applications up to 2GHz, allowing direct interfacing with the programmable divider so enabling a step size equal to the comparison frequency. For applications up to 2.7GHz the divide by two is enabled, giving a step size of twice the comparison frequency. The comparison frequency is obtained either from an on– chip crystal controlled oscillator, or from an external source. The oscillator frequency Fref or the comparison frequency Fcomp may be switched to the REF/COMP output. This feature is ideally suited to providing the reference frequency for a second synthesiser such as in a double conversion tuner (see Fig. 8). The synthesiser is controlled via an I 2 C bus, and responds to one of four programmable addresses which are selected by applying a specific voltage to the ‘address’ input. This feature enables two or more synthesisers to be used in a system. The device contains four switching ports P0–P3 and a 5–level ADC. The output of the ADC can be read via the I 2 C bus. The device also contains a varactor line disable and charge pump disable facility. FEATURES ■ Complete 2.7GHz single chip system ■ Compatible with UK DTT offset requirements ■ Optimised for low phase noise ■ Selectable divide by two prescaler ■ Selectable reference division ratio ■ Selectable reference/comparison frequency output ■ Selectable charge pump current ■ Four selectable I2C bus address ■ 5–level ADC ■ Pin compatible with the SP5658 3–wire bus controlled synthesiser and SP5659 I2C bus synthesiser and SP5659 I2C bus synthesiser ■ ESD protection; (Normal ESD handling procedures should be observed) APPLICATIONS ■ SAT, TV, VCR and Cable tuning systems CHARGE PUMP 1 16 DRIVE CRYSTAL 2 15 Vee REF/COMP 3 14 RF INPUT ADDRESS 4 13 RF INPUT SDA 5 12 Vcc SCL 6 11 ADC PORT P3 7 10 PORT P0 PORT P2 8 9 PORT P1 MP16 Fig.1 Pin connections - top view APPLICATIONS ■ Complete 2.7GHz single chip system ■ Optimised for low phase noise ORDERING INFORMATION SP5669/KG/MP1S (Tubes) SP5669/KG/MP1T (Tape and reel) SP5669 3 REF/COMP 13 PRE AMP Fpd 13 BIT COUNT Fref REFERENCE DIVIDER (see Fig. 3) PHASE COMP 2 CRYSTAL OSC 16/17 2/1 LOCK DETECT 14 1 4 BIT COUNT CHARGE PUMP 2 BIT LATCH 17 BIT LATCH DIVIDE RATIO 4 BIT LATCH DRIVE DISABLE C1, C0 PE 1 BIT LATCH CHARGE PUMP 16 MODE CONTROL RF INPUTS Fcomp PROGRAMMABLE DIVIDER 5 BIT LATCH and MODE CONTROL LOGIC (see Fig. 5) ADDRESS SDA SCL 4 5 I 2C TRANSCEIVER 6 FPD /2 FL POWER ON DETECT ADC 11 15 V EE 4 BIT LATCH AND PORT INTERFACE POR P0 TEST CONTROL 12 V CC 3 BIT ADC 7 PORT P3 8 PORT P2 9 10 PORT P1 PORT P0 Fig. 2 Block diagram ELECTRICAL CHARACTERISTICS T amb = –20°C to +80°C, V CC = +4.5V to +5.5V. Reference frequency = 4MHz. These characteristics are guaranteed by either production test or design. They apply within the specified ambient temperature and supply voltage ranges unless otherwise stated. Characteristics Pin Supply current, I CC 12 Value Min RF input voltage 2 Units Conditions Typ 68 Max 85 mA V CC = 5V prescaler enabled, PE = 1 58 mA mV rms V CC = 5V prescaler disabled, PE = 0 300MHz to 2.7GHz Prescaled enabled, PE = 1, See Fig. 7b. 80MHz Prescaler enabled, PE=1, See Fig. 7b. 13, 14 40 73 300 13, 14 100 300 mV rms 13,14 50 300 mV rms RF input impedance 13, 14 50 Ω 80MHz to 2.0GHz Prescaler disabled, PE = 0, See Fig. 7a. Refer to Fig. 13 RF input capacitance 13, 14 2 pF Refer to Fig. 13 SP5669 ELECTRICAL CHARACTERISTICS (cont.) T amb = –20°C to 80 °C, V CC =+ 4.5V to + 5.5V. Reference frequency = 4MHz. These characteristics are guaranteed by either production test or design. They apply within the specified ambient temperature and supply voltage ranges unless otherwise stated. Characteristics Pin Min SDA, SCL Input High voltage Input Low voltage Input High current Input Low Current LeakageCurrent Input hysteresis SDA Output voltage Charge pump output current Charge pump output leakage Charge pump drive output current Drive output saturation voltage when disabled External reference input frequency External reference input ampltude Crystal frequency Crystal oscillator drive level Recommended crystal series resistance Crystal oscillator negative resistance REF/COMP output Voltage 3 0 5.5 1.5 10 –10 10 Conditions 0.4 V V µA µA µA V V ± 10 nA I sink = 3mA See Fig. 6, V pin = 2V V pin1 = 2V mA V pin16 = 0.7V 0.8 5 1 1 16 ±3 1 16 350 mV Input voltage = V CC Input voltage = VEE VCC = VEE 2 2 20 MHz AC coupled sinewave 2 2 2 200 4 500 16 mV p–p MHz mV p–p AC coupled sinewave 200 Ω Applies to 4MHz crystal only. ‘Parallel resonant’ crystal. Figure quoted is under all conditions including start up. Ω Includes temperature and process tolerances. mV p–p AC coupled output. Output enabled,RE=1. See Note 1. 35 10 2 400 3 350 2 –148 RF division ratio Sink current Leakage current ADC input voltage ADC input current Address input current High Address input current Low Units Max 5, 6 Comparison frequency Equivalent phase noise at phase detector Reference division ratio Output ports P0, P1, P2, P3 Value Typ 240 480 MHz dBC/Hz 131071 262142 6kHz loop BW, phase comparator freq 250kHz. Figure measured @ 1kHz offset, SSB (within loop band width). Prescaler disabled, PE = 0 Prescaler enabled, PE = 1 See Fig. 3 7,8,9, 10 10 11 11 4 4 10 mA µA ±10 1 –0.5 µA mA mA V port = 0.7V V port = 13.2V See Table 4, Fig 4 VCC ≥ V input ≥ VEE Input voltage =V CC Input voltage =VEE Note 1: If the REF/COMP output is not used, the output should be left open circuit or connected to V CC , and disabled by setting RE=0. 3 SP5669 ABSOLUTE MAXIMUM RATINGS All voltages are referred to VEE at 0V. Characteristics Pin Value Max Supply Voltage, V CC RF input voltage 12 13,14 0.3 7 2.5 V V p–p RF input DC offset Port voltage 13,14 7–10 –0.3 –0.3 V CC +0.3 14 V V –0.3 Total port current 7–10 7–10 6 50 V mA ADC input DC offset REF/COMP output DC offset 11 3 –0.3 –0.3 V CC +0.3 V CC +0.3 V V Charge pump DC offset Drive DC offset 1 16 –0.3 –0.3 V CC +0.3 V CC +0.3 V V Crystal oscillator DC offset Address DC offset 2 4 –0.3 –0.3 V CC +0.3 V CC +0.3 V V 5, 6 –0.3 –55 6V +150 V °C +150 °C chip to ambient chip to case 111 41 °C/W °C/W Power consumption at V CC =5.5V ESD protection 468 mW kV SDA and SCL DC offset Storage temperature Junction temperature MP16 thermal resistance All 4 FUNCTIONAL DESCRIPTION The SP5669 contains all the elements necessary, with the exception of a frequency reference, loop filter and external high voltage transistor, to control a varicap tuned local oscillator, so forming a complete PLL frequency synthesised source. The device allows for operation with a high comparison frequency and is fabricated in high speed logic, which enables the generation of a loop with good phase noise performance. The block diagram is shown in Fig. 2. The RF input signal is fed to an internal preamplifier, which provides gain and reverse isolation from the divider signals. The output of the preamplifier interfaces with the 17–bit fully programmable divider via a divide–by–two prescaler. For applications up to 2GHz RF input, the prescaler may be disabled so eliminating the degradation in phase noise due to prescaler action. The divider is of MN+A architecture, where the dual modulus prescaler is 16/17, the A counter is 4–bits, and the M counter is 13–bits. The output of the programmable divider is fed to the phase comparator where it is compared in both phase and frequency domain with the comparison frequency. This frequency is derived either from the on–board crystal controlled oscillator or from an external reference source. In both cases the reference frequency is divided down to the comparison frequency by the reference divider which is programmable into 1 of 15 ratios as detailed in Fig. 3. The output of the phase detector feeds a charge pump and loop amplifier section, which when used with an external high 4 Units Min Conditions AC coupled as per application Port in off state Port in on state All ports off, prescaler enabled Mil Std 883 TM 3015 voltage transistor and loop filter, integrates the current pulses into the varactor line voltage. By invoking the device test modes as described in Fig. 5, the varactor drive output can be disabled so switching the external transistor ’off’ and allowing an external voltage to be written to the varactor line for tuner alignment purposes. Similarly, the charge pump may be also disabled to a high impedance state. The programmable divider output Fpd/2 can be switched to port P0 by programming the device into test mode. The test modes are described in Fig. 5 PROGRAMMING The SP5669 is controlled by an I 2 C data bus. Data and Clock are fed in on the SDA and SCL lines respectively as defined by I2C bus format. The synthesiser can either accept data (write mode) or send data (read mode). The LSB of the address byte (R/W) sets the device into write mode if it is low, and read mode if it is high. Tables 1 and 2 in Fig. 4 illustrate the format of the data. The device can be programmed to respond to several addresses, which enables the use of more than one synthesiser in an I2C bus system. Table 3 in Fig.4 shows how the address is selected by applying a voltage to the ’address’ input. When the device receives a valid address byte, it pulls the SDA line low during the acknowledge period, and during following acknowledge periods after further data bytes are received. When the device is programmed into read mode, the controller accepting the data must pull the SDA line low during all status byte acknowledge periods to read another status SP5669 byte. If the controller fails to pull the SDA line low during this period, the device generates an internal STOP condition, which inhibits further reading. WRITE MODE With reference to Table 1, bytes 2 and 3 contain frequency information bits 2 14 –2 0 inclusive. Auxillary frequency bits 2 16 –2 15 are in byte 4. For most frequencies only bytes 2 and 3 will be required. The remainder of byte 4 and byte 5 control the prescaler enable, reference divider ratio (see Fig. 3), charge pump, REF/COMP output (see Fig. 5), output ports and test modes (see Fig. 5). After reception and acknowledgement of a correct address (byte 1), the first bit of the following byte determines whether the byte is interpreted as a byte 2 or 4, a logic ’0’ indicating byte 2 and a logic ’1’ indicating byte 4. Having interpreted this byte as either byte 2 or 4 the following data byte will be interpreted as byte 3 or 5 respectively. Having received two complete data bytes, additional data bytes can be entered, where byte interpretation follows the same procedure, without readdressing the device. This procedure continues until a STOP condition is received. The STOP condition can be generated after any data byte, if however it occurs during a byte transmission, the previous data is retained. To facilitate smooth fine tuning, the frequency data bytes are only accepted by the device after all 17 bits of frequency data have been received, or after the generation of a STOP condition. Repeatedly sending bytes 2 and 3 only will not change the frequency. A frequency change occurs when one of the following data sequences is sent to an addressed device; Bytes 2, 3, 4, 5 Bytes 4, 5, 2, 3 or when a STOP condition follows valid data bytes as follows; Bytes 2, 3, 4, STOP Bytes 4, 5, 2 STOP Bytes 2, 3, STOP Bytes 2, STOP Bytes 4, STOP It should be noted that the device must be initially addressed with both frequency AND control byte data, since the control byte contains reference divider information which must be provided before a chosen frequency can be synthesised. This implies that after initial turn on, bytes 2, 3, 4 must be sent followed by a STOP condition as a minimum requirement. Alternatively bytes 2, 3, 4, 5 must be sent if port information is also required. READ MODE When the device is in read mode, the status byte read from the device takes the form shown in Table 2, Fig. 4. Bit 1 (POR) is the power–on reset indicator, and this is set to a logic ’1’ if the VCC supply to the device has dropped below 3V (at 25°C), e.g. when the device is initially turned ON. The POR is reset to ’0’ when the read sequence is terminated by a STOP command. When POR is set high (at low VCC), the programmed information is lost and the output ports are all set to high impedance. Bit 2 (FL) indicates whether the device is phase locked, a logic ’1’ is present if the device is locked, and a logic ’0’ if the device is unlocked. Bits 6,7 and 8 (A2, A1, A0) combine to give the output of the ADC. The ADC can be used to feed AFC information to the microprocessor via the I 2 C bus. ADDITIONAL PROGRAMMABLE FEATURES Prescaler enable The divide by two prescaler is enabled by setting bit PE within byte 4 to a logic ’1’. A logic ’0’ disables the prescaler, directly passing the RF input frequency to the 17–bit programmable counter. Bit PE is a static select only. Charge pump current The charge pump current can be programmed by bits C1 and C0 within data byte 5, as defined in Fig. 6. Test mode The test modes are invoked by setting bits RE=0 and RTS=1 within the programming data, and are selected by bits TS2, TS1 and TS0 as shown in Fig. 5. When TS2, TS1 and TS0 are received, the device retains previously received P2, P1 and P0 data. Reference/Comparison frequency output The reference frequency F ref can be switched to the REF/ COMP output, pin 3, by setting bit RE=1 and RTS=0 within byte 5. The comparison frequency F comp can be switched to the REF/COMP output, pin 3, by setting bit RE=1 and RTS=1 within byte 5. For RE set to logic ’0’, the output is disabled and set to a high state. RE and RTS default to logic ’1’ during device power up, thus enabling the comparison frequency F comp at the REF/COMP output. Comparison frequency with a 4MHz external reference R3 R2 R1 R0 Ratio 0 0 0 0 0 0 0 1 2 4 2MHz 1MHz 0 0 0 0 1 1 0 1 8 16 500kHz 250kHz 0 0 1 1 0 0 0 1 32 64 125kHz 62.5kHz 0 0 1 1 0 1 0 1 128 256 31.25kHz 15.625kHz 1 0 0 0 Not Allowed - 1 1 0 0 0 1 1 0 6 12 666.67kHz 333.33kHz 1 1 0 1 1 0 1 0 24 48 166.67kHz 83.33kHz 1 1 1 1 0 1 1 0 96 192 41.67kHz 20.83kHz 1 1 1 1 384 10.42kHz Fig. 3 Reference division ratios 5 SP5669 ADDRESS PROGRAMMABLE DIVIDER PROGRAMMABLE DIVIDER CONTROL DATA CONTROL DATA MSB 1 1 0 0 0 MA1 MA0 LSB 0 A Byte 1 0 2 14 2 13 2 12 2 11 210 29 28 A Byte 2 27 26 25 24 23 22 21 20 A Byte 3 1 C1 16 15 PE RTS R3 P3 A A Byte 4 Byte 5 A A Byte 1 Byte 2 2 RE 2 C0 R2 R1 R0 P2/TS2 P1/TS1 P0/TS0 Table 1 Write data format (MSB is transmitted first) MSB ADDRESS STATUS BYTE 1 POR LSB 1 FL 0 X 0 X 0 X MA1 A2 MA0 A1 1 A0 Table 2 Read data format (MSB is transmitted first) A MA1, MA0 2 16 –2 0 PE R3,R2,R1,R0 C1, C0 RE RTS RTS TS2, TS1, TS0 P0 P3, P2, P1 POR FL A2, A1, A0 X : : : : : : : : : : : : : : : : Acknowledge bit Variable address bits (see Table 3) Programmable division ratio control bits Prescaler enable Reference division ratio select (see Fig. 3) Charge pump current select (see Fig.6) Reference oscillator output enable REF/COMP output select when RE=1 (see Fig.5) Test mode enable when RE=0 (see Fig.5) Test mode control bits (valid when RE=0, RTS=1, see Fig. 5) P0 port output state (always valid except when RE=0, RTS=1) P3, P2 and P1 port output states Power On Reset indicator Phase Lock Flag ADC data (see Table 4) Don’t care MA1 MA0 Address input voltage level A2 A1 A0 Voltage on ADC input 0 0 0 1 0 – 0.1VCC Open circuit 1 0 0 1 0 1 0.6V CC toV CC 0.45V CC to 0.6VCC 1 1 0 1 0.4V CC – 0.6VCC # 0.9V CC – VCC 0 0 1 0 0 1 0.3V CC to 0.45VCC 0.15V CC to 0.3VCC 0 0 0 0 to 0.15VCC # Programmed by connecting a 15kΩ resistor between pin 4 and VCC Table 3 Address selection Fig. 4 Data formats 6 Table 4 ADC levels SP5669 RE RTS TS2 TS1 TS0 REF/COMP OUTPUT MODE Test mode description 0 0 0 1 X X X 0 X 0 Disabled to high state Disabled to high state Normal operation Charge pump sink. Status byte FL = logic ‘1’ 0 1 X 0 1 Disabled to high state Charge pump source. Status byte FL = logic ‘0’ 0 1 X 1 0 Disabled to high state Charge pump disabled. Status byte FL=logic ‘0’ 0 0 1 1 X 1 1 X 1 X Disabled to high state Disabled to high state Port P0 = F pd /2 Varactor Drive Output 1 0 X X X F ref switched disabled Normal operation 1 1 X X X F comp switched Normal operation X=don’t care Fig. 5 REF/COMP output mode and Test modes C1 byte 5, bit 1 Current in µA C0 byte 5, bit 2 min typ max 0 0 0 1 ±90 ±195 ±120 ±260 ±150 ±325 1 1 0 1 ±416 ±900 ±555 ±1200 ±694 ±1500 Fig 6. Charge pump current 300 VIN (mV RMS INTO 50 ) 300 VIN (mV RMS INTO 50 ) OPERATING WINDOW 100 50 50 10 10 80 100 1000 OPERATING WINDOW 100 2000 3000 3500 FREQUENCY (MHz) Fig. 7a Typical input sensitivity (prescaler disabled, PE=0) 80 300 1000 2000 3000 3500 2700 FREQUENCY (MHz) Fig. 7b Typical input sensitivity (prescaler disabled, PE=1) 7 SP5669 DOUBLE CONVERSION TUNER SYSTEMS the SP5669 to be used both for the up converter LO with a high phase comparator frequency (hence low phase noise) and the down converter which utilises the device in a lower comparison frequency mode (which offers a fine step size). The high 2.7GHz maximum operating frequency and excellent noise characteristics of the SP5669 enables the construction of double conversion high IF tuners. A typical system shown in Fig.8 will use the SP5669 as the first LO control for full band upconversion to an IF of greater than 1GHz. The wide range of reference division ratios allows 1.6GHz 50–900MHz 38.9MHz 1650–2700MHz Reference Clock First LO Second LO SP5659 SP5669 SP5659 SP5669 Fig. 8 Example of double conversion from VHF/UHF frequencies to TV IF +30V 68pF 4MHz 18pF 15nF +5V 22k 16k 13k3 BCW31 REF 10n CONTROL MICRO ADDRESS SDA 1 16 2 15 3 14 4 5 SCL 6 SP5669 SP5659 Optional application utilising on–board crystal controlled oscillator +12V 47k 2n2 TUNER 1n 1n OSCILLATOR OUTPUT 13 12 11 P3 7 10 ADC P0 P2 8 9 P1 10n Fig. 9 Typical appliction APPLICATION NOTES A generic set of application notes AN168 for designing with synthesisers such as the SP5659 has been written. This covers aspects such as loop filter design and decoupling. This application note is also featured in the Media Data Book, or refer to the Mitel Semicondor Internet Site http:// www.gpsemi.com. A generic test/demo board has been produced which can be used for the SP5669. A circuit diagram and list of components for the board is shown in Figs. 10 and 11. 8 The board can be used for the following purposes: (A) Measuring RF sensitivity performance. (B) Indicating port function. (C) Synthesising a voltage controlled oscillator. (D) Testing of external reference SP5669 P2 +30V +5V +12V C8 C9 C7/C8/C9 = 100nF EXTERNAL REFERENCE SKT2 C6 10nF* *(NOT FITTED) C3 68pF C2 15nF R6 13K3 1 16 2 15 3 14 ENABLE 4 13 DATA / SDA 5 12 CLOCK / SCL 6 11 7 10 8 9 X1 4MHz C1 R8 R9 16K 47K C12 2n2F T1 2N3904 VAR GND RF INPUT C4 C5 1nF 1nF SKT1 C10 1nF R5 4K7 R4 4K7 R3 4K7 C14 100pF R2 4K7 C13 100pF C7 18pF R1 4K7 P1 DISABLE / REF R7 22K D1 D2 D3 D4 D5 LOCK C11 1nF NOTE : The circuit diagram shown is designed for use with a number of synthesisers. . is redundant when The LED connected to pin 11 a SP5669 SP5659 is used in this board. Fig. 10 Test board Fig. 11 Test board (layout) 9 SP5669 LOOP BANDWIDTH performance will be achieved when the overall LO to phase comparator division ratio is a minimum. There are two ways of achieving a higher phase comparator sampling frequency:– The majority of applications for which the SP5669 is intended require a loop filter bandwidth of between 2kHz and10kHz. Typically the VCO phase noise will be specified at both 1kHz and10kHz offset. It is common practice to arrange the loop filter bandwidth such that the 1kHz figure lies within the loop bandwidth. Thus the phase noise depends on the synthesiser comparator noise floor, rather than the VCO. The 10kHz offset figure should depend on the VCO providing the loop is designed correctly, and is not underdamped. A) Reduce the division ratio between the reference source and the phase comparator B) use a higher reference source frequency. Approach B) may be preferred for best performance since it is possible that the noise floor of the reference oscillator may degrade the phase comparator performance if the reference division ratio is very small. REFERENCE SOURCE The SP5669 offers optimal LO phase noise performance when operated with a large step size. This is due to the fact that the LO phase noise within the loop bandwidth is: ( DRIVING TWO DEVICES FROM A COMMON REFERENCE ) phase comparator LO frequency noise floor + 20 log 10 phase comparator frequency As mentioned earlier in the Datasheet, the SP5669 has a REF/COMP output which allows two synthesisers to be driven from a common reference. To do this, the ‘‘Master” should be programmed by setting RE = 1 and RTS = 0. The driven device should be programmed for normal operation i.e. RE = 0, and RTS = 0. The two devices should be connected as shown below. Assuming the phase comparator noise floor is flat irrespective of sampling frequency, this means that the best 16 1 16 2 15 2 15 3 14 3 14 13 4 12 5 4 5 6 1nF SP5669 SP5659 1 SP5669 SP5659 4MHz 18pF 13 12 11 6 11 7 10 7 10 8 9 8 9 Fig. 12 Driving two devices from a common reference +j1 +j0.5 +j2 +j0.2 0 +j5 0.2 0.5 1 2 5 X X –j0.2 –j5 X S11:Z0 = 50 –j0.5 X NORMALISED TO 50 –j2 –j1 Fig. 13 typical RF input impedance 10 FREQUENCY MARKERS AT 100MHz, 500MHz, 1GHz AND 2.7GHz SP5669 VREF VCC 500 500 CHARGE PUMP RF INPUTS 200 DRIVE OUTPUT 100 OS (Output disable) RF inputs Loop amplifier V CC PORT SCL/SDA/ADC 3k ACK SDA ONLY Output Ports SDA and SCL and ADC VCC VCC VCC 30k REF/COMP ADDRESS 3k CRYSTAL enable/ disable 10K Reference oscillator Address input REF/COMP output Fig. 14 Input/Output interface circuits 11 SP5669 PACKAGE DETAILS Dimensions are shown thus: mm (in). For further package information, please contact your local Customer Service Centre. 9·80/10·01 (0·386/0·394) 16 SPOT REF. 0·18/0·25 (0·007/0·010) 0·25/0·51 (0·010/0·020) 5·80/6·20 3·80/4·00 ×45° (0·150/0·157) (0·228/0·244) CHAMFER REF. PIN 1 0-8° 0·35/0·49 (0·014/0·019) 0·41/1·27 (0·016/0·050) 0·69 (0·027) MAX 16 LEADS AT 1·27 (0·050) NOM SPACING 0·10/0·25 1·35/1·91 (0·004/0·010) (0·053/0·075) NOTES 1. Controlling dimensions are inches. 2. This package outline diagram is for guidance only. Please contact your Mitel Semiconductor Customer Service Centre for further 16-LEAD MINIATURE PLASTIC DIL - MP16 Purchase of Mitel Semiconductor I2C components conveys a licence under the Philips I2C Patent rights to use these components in an I2C System, provided that the system conforms to the I2C Standard Specification as defined by Philips. HEADQUARTERS OPERATIONS MITEL SEMICONDUCTOR Cheney Manor, Swindon, Wiltshire SN2 2QW, United Kingdom. Tel: (01793) 518000 Fax: (01793) 518411 MITEL SEMICONDUCTOR 1500 Green Hills Road, Scotts Valley, California 95066-4922 United States of America. Tel (408) 438 2900 Fax: (408) 438 5576/6231 Internet: http://www.gpsemi.com CUSTOMER SERVICE CENTRES ● FRANCE & BENELUX Les Ulis Cedex Tel: (1) 69 18 90 00 Fax : (1) 64 46 06 07 ● GERMANY Munich Tel: (089) 419508-20 Fax : (089) 419508-55 ● ITALY Milan Tel: (02) 6607151 Fax: (02) 66040993 ● JAPAN Tokyo Tel: (03) 5276-5501 Fax: (03) 5276-5510 ● KOREA Seoul Tel: (2) 5668141 Fax: (2) 5697933 ● NORTH AMERICA Scotts Valley, USA Tel: (408) 438 2900 Fax: (408) 438 5576/6231 ● SOUTH EAST ASIA Singapore Tel:(65) 3827708 Fax: (65) 3828872 ● SWEDEN Stockholm Tel: 46 8 702 97 70 Fax: 46 8 640 47 36 ● TAIWAN, ROC Taipei Tel: 886 2 25461260 Fax: 886 2 27190260 ● UK, EIRE, DENMARK, FINLAND & NORWAY Swindon Tel: (01793) 726666 Fax : (01793) 518582 These are supported by Agents and Distributors in major countries world-wide. © Mitel Corporation 1998 Publication No. DS4852 Issue No. 1.3 November 1997 TECHNICAL DOCUMENTATION – NOT FOR RESALE. PRINTED IN UNITED KINGDOM This publication is issued to provide information only which (unless agreed by the Company in writing) may not be used, applied or reproduced for any purpose nor form part of any order or contract nor to be regarded as a representation relating to the products or services concerned. No warranty or guarantee express or implied is made regarding the capability, performance or suitability of any product or service. The Company reserves the right to alter without prior notice the specification, design or price of any product or service. Information concerning possible methods of use is provided as a guide only and does not constitute any guarantee that such methods of use will be satisfactory in a specific piece of equipment. It is the user's responsibility to fully determine the performance and suitability of any equipment using such information and to ensure that any publication or data used is up to date and has not been superseded. These products are not suitable for use in any medical products whose failure to perform may result in significant injury or death to the user. All products and materials are sold and services provided subject to the Company's conditions of sale, which are available on request. All brand names and product names used in this publication are trademarks, registered trademarks or trade names of their respective owners. 12