ISSI IS31AP2010B

IS31AP2010B
[email protected] MONO FILTER-LESS, CLASS-D AUDIO POWER AMPLIFIER
GENERAL DESCRIPTION
The IS31AP2010B is a high efficiency, [email protected]
mono filter-less class-D audio power amplifier. A low
noise, filter-less PWM architecture eliminates the
output filter, reduces external component count,
system cost, and simplifying design.
Operating in a single 5.0V supply, IS31AP2010B is
capable of driving 4Ω speaker load at a continuous
average output of 3W@10% THD+N. The
IS31AP2010B has high efficiency with speaker load
compared to a typical class- AB amplifier.
In cellular handsets, the earpiece, speaker phone, and
melody ringer speaker can each be driven by the
IS31AP2010B. The gain of IS31AP2010B is externally
configurable which allows independent gain control
from multiple sources by summing signals from each
function.
IS31AP2010B is available in UTQFN-9 packages. It
operates from 2.7V to 5.5V over the temperature range
of -40°C to +85°C.
AUGUST 2011
FEATURES
 5.0V supply at THD+N = 10%
 ―3W into 4Ω (Typ.)
 ―1.68W into 8Ω (Typ.)
 Efficiency at 5.0V
 ―85% at 400mW with a 4Ω speaker
 ―88% at 400mW with a 8Ω speaker
 Less than 1μA shutdown current
 Optimized PWM output stage eliminates LC
output filter
 Fully differential design reduces RF
rectification and eliminates bypass capacitor
 Improved CMRR eliminates two input coupling
capacitors
 Integrated click-and-pop suppression circuitry
 UTQFN-9 package
 RoHS compliant and 100% lead(Pb)-free
APPLICATIONS
 Wireless or cellular handsets and PDAs
 Portable DVD player
 Notebook PC
 Portable radio
 Educational toys
 Portable gaming
TYPICAL APPLICATION CIRCUIT
Figure 1 Typical Application Circuit
Copyright © 2011 Integrated Silicon Solution, Inc. All rights reserved. ISSI reserves the right to make changes to this specification and its products at any time without notice. ISSI assumes no liability arising out of the application or use of any information, products or services described herein. Customers are advised to obtain the latest version of this device specification before relying on any published information and before placing orders for products. Integrated Silicon Solution, Inc. does not recommend the use of any of its products in life support applications where the failure or malfunction of the product can reasonably be expected to cause failure of the life support system or to significantly affect its safety or effectiveness. Products are not authorized for use in such applications unless Integrated Silicon Solution, Inc. receives written assurance to its satisfaction, that: a.) the risk of injury or damage has been minimized; b.) the user assume all such risks; and c.) potential liability of Integrated Silicon Solution, Inc is adequately protected under the circumstances
Integrated Silicon Solution, Inc. – www.issi.com
Rev. A, 06/24/2011
1
IS31AP2010B
PIN CONFIGURATION
Package
Pin Configuration (Top View)
IN+
GND
OUT-
A1
A2
A3
VDD
VDD
GND
B1
B2
B3
IN-
SDB
OUT+
C1
C2
C3
UTQFN-9
PIN DESCRIPTION
No.
Pin
I/O
Description
A1
IN+
I
Positive audio input.
A2, B3
GND
-
Connect to ground.
A3
OUT-
O
Negative audio output.
B1, B2
VDD
-
Power supply.
C1
IN-
I
Negative audio input.
C2
SDB
I
Enter in shutdown mode when active low.
C3
OUT+
O
Positive audio output.
ORDERING INFORMATION
Industrial Range: -40°C to +85°C
Order Part No.
Package
QTY/Reel
IS31AP2010B-UTLS2-TR
UTQFN-9, Lead-free
3000
Integrated Silicon Solution, Inc. – www.issi.com
Rev. A, 06/24/2011
2
IS31AP2010B
ABSOLUTE MAXIMUM RATINGS (NOTE 1)
Supply voltage, VDD
Voltage at any input pin
Junction temperature, TJMAX
Storage temperature rang, Tstg
Lead temperature 1.6mm(1/16 inch) from case for 10s
Thermal resistance θJA(UTQFN)
ESD (HBM)
-0.3V ~ +5.5V
-0.3V ~ VDD +0.3V
-40°C ~ +150°C
-65°C ~ +150°C
- 260°C
70°C/W
6kV
ELECTRICAL CHARACTERISTICS
VDD = 2.7V ~ 5.5V, TA = 25°C, unless otherwise noted. (Note 2)
Symbol Parameter
VDD
| VOS |
Supply voltage
Output offset voltage
(measured differentially)
IDD
Quiescent current
ISD
Shutdown current
fsw
Switching frequency
RIN
Condition
Input resistor
Gain
Min.
Typ.
2.7
VSDB = 0V, AV = 2V/V
10
VDD = 5.5V, no load
2.6
VDD = 2.7V, no load
1.2
VSDB = 0.4V
Max.
Unit
5.5
V
mV
mA
1
250
Gain  20V/V
kHz
15
RIN = 150kΩ
μA
kΩ
2
V/V
VIH
High-level input voltage
1.4
VDD
V
VIL
Low-level input voltage
0
0.4
V
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Rev. A, 06/24/2011
3
IS31AP2010B
ELECTRICAL CHARACTERISTICS
TA = 25°C, Gain = 2V/V, CIN = 2μF, unless otherwise noted. (Note 3)
Symbol Parameter
Condition
THD+N = 10%
f = 1kHz, RL = 8Ω
THD+N = 10%
f = 1kHz, RL = 4Ω
PO
Output power
THD+N = 1%
f = 1kHz, RL = 8Ω
THD+N = 1%
f = 1kHz, RL = 4Ω
Min.
Typ.
VDD = 5.0V
1.68
VDD = 4.2V
1.2
VDD = 3.6V
0.88
VDD = 5.0V
3.0
VDD = 4.2V
2.0
VDD = 3.6V
1.5
VDD = 5.0V
1.4
VDD = 4.2V
1.0
VDD = 3.6V
0.7
VDD = 5.0V
2.4
VDD = 4.2V
1.68
VDD = 3.6V
1.2
VDD = 4.2V, PO = 0.6W, RL = 8Ω, f = 1kHz
0.18
VDD = 4.2V, PO = 1.1W, RL = 4Ω, f = 1kHz
0.22
Max.
Unit
W
W
W
W
THD+N
Total harmonic
distortion plus noise
VNO
Output voltage noise
VDD = 4.2V, f = 20Hz to 20kHz
Inputs AC-grounded
80
μVrms
TWU
Wake-up time from
shutdown
VDD = 3.6V
32
ms
SNR
Signal-to-noise ratio
PO = 1.0W, RL = 8Ω, VDD = 4.2V
91
dB
Power supply rejection f = 217Hz,RL = 8Ω
PSRR
ratio
Input grounded
VDD = 5.0V
-75
VDD = 4.2V
-70
VDD = 3.6V
-66
%
dB
Note:
1. Stresses beyond those listed under absolute maximum ratings may cause permanent damage to the device. These are stress ratings only,
and functional operation of the device at these or any other conditions beyond those indicated under recommended operating conditions is
not implied. Exposure to absolute-maximum-rated conditions for extended periods may affect device reliability.
2. All parts are production tested at TA = 25°C. Other temperature limits are guaranteed by design.
3. Guaranteed by design.
Integrated Silicon Solution, Inc. – www.issi.com
Rev. A, 06/24/2011
4
IS31AP2010B
TYPICAL PERFORMANCE CHARACTERISTIC
20
20
RL = 8Ω
f = 1kHz
10
10
VDD = 5.0V
5
5
VDD = 5.0V
THD+N(%)
THD+N(%)
RL = 4Ω
f = 1kHz
2
VDD = 4.2V
1
2
VDD = 4.2V
1
VDD = 3.6V
0.5
0.5
VDD = 3.6V
0.2
0.2
0.1
10m
50m
20m
100m
500m
1
2
0.1
10m
3
Figure 3
THD+N vs. Output Power
5
RL = 8Ω
THD+N(%)
THD+N(%)
1
0.5
0.2
VDD = 3.6V
Po = 0.45W
VDD = 5.0V
Po = 0.9W
2
3
4
THD+N vs. Output Power
RL = 4Ω
1
0.5
0.2
0.01
20
200
500
1k
2k
5k
50
100
20k
200
500
1k
2k
20k
5k
Frequency(Hz)
Frequency(Hz)
Figure 4
VDD = 3.6V
Po = 0.8W
0.02
0.02
100
VDD = 5.0V
Po = 1.5W
0.1
VDD = 4.2V
Po = 0.6W
50
VDD = 4.2V
Po = 1.1W
0.05
0.05
0.01
20
1
2
2
0.1
500m
10
10
5
100m
50m
Output Power(W)
Output Power(W)
Figure 2
20m
Figure 5
THD+N vs. Frequency
THD+N vs. Frequency
+0
+0
RL = 8Ω
Input Grouded
-20
RL = 4Ω
Input Grouded
-20
VDD = 5.0V
-40
PSRR(dB)
PSRR(dB)
-40
VDD = 5.0V
VDD = 3.6V
-60
VDD = 3.6V
-60
-80
VDD = 4.2V
-100
-80
-100
20
VDD = 4.2V
-120
20
50
100
200
500
1k
2k
5k
Frequency(Hz)
Figure 6
50
100
20k
200
500
1k
2k
20k
5k
Frequency(Hz)
Figure 7
PSRR vs. Frequency
PSRR vs. Frequency
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Rev. A, 06/24/2011
5
IS31AP2010B
200
100
80
100
RL=8Ω
Efficiency(%)
Output Voltage(uV)
VDD = 3.6V~5.0V
RL = 4Ω, 8Ω
70
50
30
20
RL=4Ω
60
40
20
VDD = 5.0V
10
20
50
100
200
500
1k
2k
5k
Frequency(Hz)
Figure 8
Noise
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Rev. A, 06/24/2011
20k
0
0
0.3
0.6
0.9
1.2
1.5
Output Power(W)
Figure 9
Efficiency
6
IS31AP2010B
APPLICATION INFORMATION
VBattery
Cs
1 F
Fully Differential Amplifier
The IS31AP2010B is a fully differential amplifier with
differential inputs and outputs. The fully differential
amplifier consists of a differential amplifier and a
common mode amplifier. The differential amplifier
ensures that the amplifier outputs a differential voltage
on the output that is equal to the differential input times
the gain. The common-mode feedback ensures that
the common-mode voltage at the output is biased
around VDD/2 regardless of the common-mode voltage
at the input. The fully differential IS31AP2010B can still
be used with a single-ended input; however, the
IS31AP2010B should be used with differential inputs
when in a noisy environment, like a wireless handset,
to ensure maximum noise rejection.
CIN
0.1 F
RIN
150k
Single-ended
Input
CIN
0.1 F
B1
B2
GSM handsets save power by turning on and shutting
off the RF transmitter at a rate of 217Hz. The
transmitted signal is picked-up on input and output
traces. The fully differential amplifier cancels the signal
much better than the typical audio amplifier.
Component Selection
Figure 10 shows the IS31AP2010B with differential
inputs and input capacitors, and Figure 11 shows the
IS31AP2010B with single-ended inputs. Differential
inputs should be used whenever possible because the
single-ended inputs are much more susceptible to
noise.
Internal
Oscillator
C1
IN-
A1
IN+
C2
SDB
OUT+ C3
PWM
H-Bridge
OUT- A3
RIN
150k
Shutdown
Control
Bias Circuitry
GND
100k
Figure 11
A2, B3
300k
Single-Ended Input
Input Resistors (RIN)
The input resistors (RIN) set the gain of the amplifier
according to Equation (1).
Advantages of Fully Differential Amplifiers
The fully differential amplifier does not require a
bypass capacitor. This is because any shift in the
mid-supply affects both positive and negative channels
equally and cancels at the differential output.
VDD
Gain 
2  RF  V 
R IN
 
V 
(1)
Resistor matching is very important in fully differential
amplifiers. The balance of the output on the reference
voltage depends on matched ratios of the resistors.
CMRR, PSRR, and cancellation of the second
harmonic distortion diminish if resistor mismatch
occurs. Therefore, it is recommended to use 1%
tolerance resistors or better to keep the performance
optimized. Matching is more important than overall
tolerance. Resistor arrays with 1% matching can be
used with a tolerance greater than 1%.
Place the input resistors very close to the
IS31AP2010B to limit noise injection on the
high-impedance nodes.
For optimal performance the gain should be set to
2V/V or lower. Lower gain allows the IS31AP2010B to
operate at its best, and keeps a high voltage at the
input making the inputs less susceptible to noise.
Decoupling Capacitor (CS)
Figure 10
Differential Input
Integrated Silicon Solution, Inc. – www.issi.com
Rev. A, 06/24/2011
The IS31AP2010B is a high performance class-D
audio amplifier that requires adequate power supply
decoupling to ensure the efficiency is high and total
harmonic distortion (THD) is low. For higher frequency
transients, spikes, or digital hash on the line, a good
low equivalent-series-resistance (ESR) ceramic
capacitor, typically 1μF, placed as close as possible to
the device VDD lead works best. Placing this
decoupling capacitor close to the IS31AP2010B is very
important for the efficiency of the class-D amplifier,
because any resistance or inductance in the trace
between the device and the capacitor can cause a loss
in efficiency. For filtering lower frequency noise
signals, a 10μF or greater capacitor placed near the
audio power amplifier would also help, but it is not
required in most applications because of the high
PSRR of this device
7
IS31AP2010B
Input Capacitors (CIN)
The input capacitors and input resistors form a high
pass filter with the corner frequency, fC, determined in
Equation (2).
1
f 
c 2R C 
IN IN
(2)
1
2RIN f c 
CIN2
0.1 F
RIN2
150k
CIN2
0.1 F
RIN2
150k
CIN1
0.1 F
RIN1
150k
Differential
Input 2
The value of the input capacitor is important to
consider as it directly affects the bass (low frequency)
performance of the circuit. Speakers in wireless
phones cannot usually respond well to low
frequencies, so the corner frequency can be set to
block low frequencies in this application.
Equation (3) is reconfigured to solve for the input
coupling capacitance.
C IN 
If summing a ring tone and a phone signal, set the
ring-tone gain to Gain2 = 2V/V, and the phone gain to
Gain1 = 0.1V/V. The resistor values would be
RIN1 = 3MΩ, RIN2 = 150kΩ
(3)
Differential
Input 1
CIN1
0.1 F
For a flat low frequency response, use large input
coupling capacitors (1μF). However, in a GSM phone
the ground signal is fluctuating at 217Hz, but the signal
from the codec does not have the same 217Hz
fluctuation. The difference between the two signals is
amplified, sent to the speaker, and heard as a 217Hz
hum.
Summing Input Signals
Most wireless phones or PDAs need to sum signals at
the audio power amplifier or just have two signal
sources that need separate gain. The IS31AP2010B
makes it easy to sum signals or use separate signal
sources with different gains. Many phones now use the
same speaker for the earpiece and ringer, where the
wireless phone would require a much lower gain for
the phone earpiece than for the ringer. PDAs and
phones that have stereo headphones require summing
of the right and left channels to output the stereo signal
to the mono speaker.
Summing Two Differential Input Signals
Two extra resistors are needed for summing
differential signals (a total of 5 components). The gain
for each input source can be set independently (see
Equations (4) and (5) and Figure 12).
Gain1 
VO 2  R F  V 

 
R IN 1  V 
VI 1
(4)
Gain 2 
VO 2  R F  V 

 
R IN 2  V 
VI 2
(5)
C1
IN-
A1
IN+
PWM
B1
OUT+
C3
OUT-
A3
H-Bridge
VBattery
Cs
1 F
B2
RIN1
150k
C2
Shutdown
Control
SDB
Bias Circuitry
GND
A2, B3
300k
Figure 12
If the corner frequency is within the audio band, the
capacitors should have a tolerance of ±10% or better,
because any mismatch in capacitance causes an
impedance mismatch at the corner frequency and
below.
VDD
Internal
Oscillator
Summing Two Differential Inputs
Summing a Differential Input Signal and a
Single-Ended Input Signal
Figure 13 shows how to sum a differential input signal
and a single-ended input signal. Ground noise may
couple in through IN- with this method. It is better to
use differential inputs. The corner frequency of the
single-ended input is set by CIN2, shown in Equation
(8). To assure that each input is balanced, the
single-ended input must be driven by a low-impedance
source even if the input is not in use.
VO 2  R F  V 

 
R IN 1  V 
VI 1
V
2  RF  V 
Gain 2  O 
 
R IN 2  V 
VI 2
Gain1 
C IN 2 
1
2RIN 2 f c 2 
(6)
(7)
(8)
If summing a ring tone and a phone signal, the phone
signal should use a differential input signal while the
ring tone might be limited to a single-ended signal.
Phone gain is set at Gain1 = 0.1V/V, and the ring-tone
gain is set to Gain2 = 2V/V, the resistor values would
be
RIN1 = 3MΩ, RIN2 = 150kΩ
The high pass corner frequency of the single-ended
input is set by CIN2. If the desired corner frequency is
less than 20Hz.
C IN 2 
1
2 150 k  20 Hz 
C IN 2  53 pF
(9)
(10)
If summing left and right inputs with a gain of 1V/V, use
RIN1 = RIN2 = 300kΩ.
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Rev. A, 06/24/2011
8
IS31AP2010B
Figure 13
Signals
Summing Differential Input and Single-Ended Input
Figure 14
Summing Two Single-Ended Input Signals
The gain and corner frequencies (fC1 and fC2) for each
input source can be set independently (see Equations (11)
through (14) and Figure 14). Resistor, RP, and capacitor,
CP, are needed on the IN- terminal to match the
impedance on the IN+ terminal. The single-ended inputs
must be driven by low impedance sources even if one of
the inputs is not outputting an ac signal.
Gain1 
VO 2  R F  V 

 
R IN 1  V 
VI 1
VO 2  R F  V 

 
R IN 2  V 
VI 2
1
C IN 1 
2RIN 1 f c1 
(11)
1
2RIN 2 f c 2 
C p  C IN 1  C IN 2
RP 
R IN 1  R IN 2
R IN 1  R IN 2 
EMI Evaluation Result
80
dBuV/m
70
60
50
RE_B
40
30
Gain 2 
C IN 2 
Summing Two Single-Ended Inputs
(12)
20
10
(13)
0
(14)
30
Figure 15
100
1000 MHz
EMI Evaluation Result
(15)
(16)
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Rev. A, 06/24/2011
9
IS31AP2010B
CLASSIFICATION REFLOW PROFILES
Profile Feature
Pb-Free Assembly
Preheat & Soak
Temperature min (Tsmin)
Temperature max (Tsmax)
Time (Tsmin to Tsmax) (ts)
150°C
200°C
60-120 seconds
Average ramp-up rate (Tsmax to Tp)
3°C/second max.
Liquidous temperature (TL)
Time at liquidous (tL)
217°C
60-150 seconds
Peak package body temperature (Tp)*
Max 260°C
Time (tp)** within 5°C of the specified
classification temperature (Tc)
Max 30 seconds
Average ramp-down rate (Tp to Tsmax)
6°C/second max.
Time 25°C to peak temperature
8 minutes max.
Figure 16
Classification Profile
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Rev. A, 06/24/2011
10
IS31AP2010B
TAPE AND REEL INFORMATION
Note: All dimensions in millimeters unless otherwise stated.
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Rev. A, 06/24/2011
11
IS31AP2010B
PACKAGING INFORMATION
UTQFN-9
Note: All dimensions in millimeters unless otherwise stated.
Integrated Silicon Solution, Inc. – www.issi.com
Rev. A, 06/24/2011
12