CS52510-1 10 A LDO 5-Pin Adjustable Linear Regulator This new very low dropout regulator is designed to power the next generation of advanced microprocessor. To achieve very low dropout, the internal pass transistor is powered separately from the control circuitry. Furthermore, with the control and power inputs tied together, this device can be used in single supply configuration and still offer a better dropout voltage than conventional PNP–NPN based LDO regulators. In this mode the dropout is determined by the minimum control voltage. It is supplied in a five–terminal TO–220 package, which allows for the implementation of a remote–sense pin permitting very accurate regulation of output voltage directly at the load, where it counts, rather than at the regulator. This remote sensing feature virtually eliminates output voltage variations due to load changes and resistive voltage drops. Typical load regulation measured at the sense pin is 1.0 mV for an output voltage of 2.5 V with a load step of 10 mA to 10 A. The very fast transient loop response easily meets the needs of the latest microprocessors. In addition, a small capacitor on the Adjust pin will further improve the transient capabilities. Internal protection circuitry provides for “bust–proof” operation, similar to three–terminal regulators. This circuitry, which includes overcurrent, short circuit, supply sequencing and overtemperature protection, will self protect the regulator under all fault conditions. The CS52510–1 is ideal for generating a secondary 2.0–2.5 V low voltage supply on a motherboard where both 5.0 V and 3.3 V are already available. Features 1.25 V to 5.0 V VOUT at 10 A VPOWER Dropout < 0.65 V @ 10 A VCONTROL Dropout < 1.25 V @ 10 A 1.5% Trimmed Reference Fast Transient Response Remote Voltage Sensing Thermal Shutdown Current Limit Short Circuit Protection Backwards Compatible with 3–Pin Regulators • • • • • • • • • • Semiconductor Components Industries, LLC, 2001 March, 2001 – Rev. 4 http://onsemi.com Tab = VOUT Pin 1. VSENSE 2. Adjust 3. VOUT 4. VCONTROL 5. VPOWER 1 5 TO–220 FIVE LEAD T SUFFIX CASE 314D MARKING DIAGRAM CS52510–1 AWLYWW 1 A WL, L YY, Y WW, W = Assembly Location = Wafer Lot = Year = Work Week ORDERING INFORMATION Device CS52510–1GT5 1 Package Shipping TO–220 FIVE LEAD 50 Units/Rail Publication Order Number: CS52510–1/D CS52510–1 5.0 V VCONTROL VOUT CS52510–1 2.5 V @ 10 A 3.3 V VPOWER VSENSE 124 1.0% Adjust 10 µF 10 V 100 µF 5.0 V 0.1 µF 5.0 V 124 1.0% 300 µF 5.0 V Load Figure 1. Application Diagram ABSOLUTE MAXIMUM RATINGS* Rating Value Unit VPOWER Input Voltage 6.0 V VCONTROL Input Voltage 13 V 0 to 150 °C –65 to +150 °C 2.0 kV 260 peak °C Operating Junction Temperature Range, TJ Storage Temperature Range ESD Damage Threshold Lead Temperature Soldering: Wave Solder: (through hole styles only) (Note 1.) 1. 10 second maximum. *The maximum package power dissipation must be observed. ELECTRICAL CHARACTERISTICS (0°C ≤ TA ≤ 70°C; 0°C ≤ TJ ≤ 150°C; VSENSE = VOUT and VADJ = 0 V; unless otherwise specified.) Characteristic Test Conditions Min Typ Max Unit Reference Voltage VCONTROL = 2.75 V to 12 V, VPOWER = 2.5 V to 5.5 V, 10 mA ≤ IOUT ≤ 10 A 1.234 (–1.5%) 1.253 1.272 (+1.5%) V Line Regulation VCONTROL = 2.5 V to 12 V, VPOWER = 1.75 V to 5.5 V, IOUT = 10 mA – 0.02 0.2 % Load Regulation (Note 2.) VCONTROL = 2.75 V, VPOWER = 2.5 V, IOUT = 10 mA to 10 A, with Remote Sense – 0.04 0.2 % Minimum Load Current (Note 3.) VCONTROL = 5.0 V, VPOWER = 3.3 V, ∆VOUT = +1.0% – 5.0 10 mA Control Pin Current (Note 4.) VCONTROL = 2.75 V, VPOWER = 2.5 V, IOUT = 100 mA VCONTROL = 2.75 V, VPOWER = 2.5 V, IOUT = 4.0 A VCONTROL = 2.75 V, VPOWER = 1.75 V, IOUT = 4.0 A VCONTROL = 2.75 V, VPOWER = 2.5 V, IOUT = 10 A – – – – 6.0 30 33 80 10 60 70 180 mA mA mA mA Adjust Pin Current VCONTROL = 2.75 V, VPOWER = 2.5 V, IOUT = 10 mA – 60 120 µA Current Limit VCONTROL = 2.75 V, VPOWER = 2.5 V, ∆VOUT = –1.5% 10.1 11 – A Short Circuit Current VCONTROL = 2.75 V, VPOWER = 2.5 V, VOUT = 0 V 8.0 9.5 – A CS52510–1 2. This parameter is guaranteed by design and is not 100% production tested. 3. The minimum load current is the minimum current required to maintain regulation. Normally the current in the resistor divider used to set the output voltage is selected to meet the minimum load current requirement. 4. The control pin current is the drive current required for the output transistor. This current will track output current with roughly a 1:100 ratio. The minimum value is equal to the quiescent current of the device. http://onsemi.com 2 CS52510–1 ELECTRICAL CHARACTERISTICS (continued) (0°C ≤ TA ≤ 70°C; 0°C ≤ TJ ≤ 150°C; VSENSE = VOUT and VADJ = 0 V; unless otherwise specified.) Characteristic Test Conditions Min Typ Max Unit CS52510–1 Ripple Rejection (Note 5.) VCONTROL = VPOWER = 3.25 V Avg, VRIPPLE = 1.0 VP–P @ 120 Hz, IOUT = 4.0 A, CADJ = 0.1 µF 60 80 – dB Thermal Regulation 30 ms Pulse, TA = 25°C – 0.002 – %/W VCONTROL Dropout Voltage (Minimum VCONTROL – VOUT) (Note 6.) VPOWER = 2.5 V, IOUT = 100 mA VPOWER = 2.5 V, IOUT = 1.0 A VPOWER = 2.5 V, IOUT = 2.75 A VPOWER = 2.5 V, IOUT = 4.0 mA VPOWER = 2.5 V, IOUT = 10 A – – – – – 1.00 1.00 1.00 1.00 1.25 1.15 1.15 1.15 1.15 1.40 V V V V V VPOWER Dropout Voltage (Minimum VPOWER – VOUT) (Note 6.) VCONTROL = 2.75 V, IOUT = 100 mA VCONTROL = 2.75 V, IOUT = 1.0 A VCONTROL = 2.75 V, IOUT = 2.75 A VCONTROL = 2.75 V, IOUT = 4.0 mA VCONTROL = 2.75 V, IOUT = 10 A – – – – – 0.10 0.15 0.20 0.26 0.65 0.15 0.20 0.30 0.40 0.80 V V V V V RMS Output Noise Freq = 10 Hz to 10 kHz, TA = 25°C – 0.003 – %VOUT Temperature Stability – – 0.5 – % Thermal Shutdown (Note 7.) – 150 180 210 °C Thermal Shutdown Hysteresis – – 25 – °C VCONTROL Supply Only Output Current VCONTROL = 13 V, VPOWER Not Connected, VADJ = VOUT = VSENSE = 0 V – – 50 mA VPOWER Supply Only Output Current VPOWER = 6.0 V, VCONTROL Not Connected, VADJ = VOUT = VSENSE = 0 V – 0.1 1.0 mA 5. This parameter is guaranteed by design and is not 100% production tested. 6. Dropout is defined as either minimum control voltage (VCONTROL) or minimum power voltage (VPOWER) to output voltage differential required to maintain 1.5% regulation at a particular load. 7. This parameter is guaranteed by design, but not parametrically tested in production. However, a 100% thermal shutdown functional test is performed on each part. PACKAGE PIN DESCRIPTION PACKAGE PIN # TO–220 PIN SYMBOL 1 VSENSE This Kelvin sense pin allows for remote sensing of the output voltage at the load for improved regulation. It is internally connected to the positive input of the voltage sensing error amplifier. 2 Adjust This pin is connected to the low side of the internally trimmed 1.5% bandgap reference voltage and carries a bias current of about 50 µA. A resistor divider from Adjust to VOUT and from Adjust to ground sets the output voltage. Also, transient response can be improved by adding a small bypass capacitor from this pin to ground. 3 VOUT This pin is connected to the emitter of the power pass transistor and provides a regulated voltage capable of sourcing 10 A of current. 4 VCONTROL 5 VPOWER FUNCTION This is the supply voltage for the regulator control circuitry. For the device to regulate, this voltage should be between 1.0 V and 1.4 V (depending on the output current) greater than the output voltage. The control pin current will be about 1.0% of the power pin output current. This is the power input voltage. This pin is physically connected to the collector of the power pass transistor. For the device to regulate, this voltage should be between 1.0 V and 0.8 V greater than the output voltage depending on the output current. The output load current of 10 A is supplied through this pin. http://onsemi.com 3 CS52510–1 VPOWER VCONTROL BIAS and TSD EA – + VREF IA + – VOUT VSENSE Adjust Figure 2. Block Diagram TYPICAL PERFORMANCE CHARACTERISTICS 90 75 VPOWER = 2.5 V IL = 10 mA Adjust Pin Current (µA) Ripple Rejection (dB) 80 70 60 50 VIN – VOUT = 2.0 V IOUT = 4.0 A VRIPPLE = 1.0 VP–P COUT = 22 µF CADJ = 0.1 µF 40 30 20 10 1 10 102 103 104 105 74 73 72 71 70 1.0 106 2.0 3.0 4.0 Frequency (Hz) Figure 3. Ripple Rejection vs Frequency 7.0 8.0 9.0 10 11 75 VCONTROL = 5.0 V ∆VOUT = +1.0% Adjust Pin Current (µA) Minimum Load Current (µA) 916.2 6.0 Figure 4. Adjust Pin Current vs VCONTROL – VOUT 916.4 916.3 5.0 VCONTROL – VOUT (V) 916.1 916.0 915.9 915.8 915.7 915.6 74 VCONTROL = 2.75 V IL = 10 mA 73 72 71 915.5 915.4 0.5 1.5 2.5 3.5 4.5 70 0.5 VPOWER – VOUT (V) 1.5 2.5 3.5 VPOWER – VOUT (V) Figure 5. Minimum Load Current vs VPOWER – VOUT Figure 6. Adjust Pin Current vs VPOWER – VOUT http://onsemi.com 4 4.5 CS52510–1 1200 14.0 Minimum Load Current (µA) VCONTROL = 2.75 V Output Current (A) 12.0 10.0 8.0 6.0 4.0 1100 1050 1000 950 900 2.0 0 VPOWER = 3.3 V ∆VOUT = +1.0% 1150 850 0.5 1.0 1.5 2.0 2.5 3.0 3.5 0 4.0 4.5 800 1.0 5.0 5.5 2.0 3.0 VPOWER – VOUT (V) 5.0 6.0 7.0 8.0 9.0 10 11 VCONTROL – VOUT (V) Figure 7. Short Circuit Current vs VPOWER – VOUT Figure 8. Minimum Load Current vs VCONTROL – VOUT 77 0.10 VPOWER = 2.5 V VCONTROL = 2.75 V 76 VPOWER = 2.5 V VCONTROL = 2.75 V 0.09 Output Voltage Deviation (%) Adjust Pin Current (µA) 4.0 75 74 73 0.08 0.07 0.06 0.05 0.04 0.03 0.02 0.01 72 1.0 0 2.0 3.0 4.0 5.0 6.0 7.0 8.0 9.0 0 10 0 1.0 2.0 3.0 Output Current (A) 5.0 6.0 7.0 8.0 9.0 10 Output Current (A) Figure 9. Adjust Pin Current vs Output Current Figure 10. Load Regulation vs Output Current 1.0 1.25 0.8 VCONTROL Dropout Voltage (V) VPOWER = 2.5 V VCONTROL = 2.75 V 0.9 VPOWER Dropout Voltage (V) 4.0 0.7 0.6 0.5 0.4 0.3 0.2 VPOWER = 2.5 V 1.00 0.75 0.50 0.25 0.1 0 0 1.0 2.0 3.0 4.0 5.0 6.0 7.0 8.0 9.0 0 10 0 Output Current (A) 1.0 2.0 3.0 4.0 5.0 6.0 7.0 8.0 9.0 Output Current (A) Figure 11. VPOWER Dropout Voltage vs IOUT Figure 12. VCONTROL Dropout Voltage vs IOUT http://onsemi.com 5 10 CS52510–1 0.100 0.35 Output Voltage Deviation (%) Output Voltage Deviation (%) 0.075 0.050 0.025 0 –0.025 –0.050 –0.075 IO = 10 mA VCONTROL = 2.75 V VPOWER = 2.5 V –0.100 –0.125 –0.150 0 0.30 0.25 TCase = 25°C 0.20 0.15 TCase = 125°C 0.10 TCase = 0°C 0.05 0 10 20 30 40 50 60 70 80 90 100 110 120 130 0 2.0 TJ (°C) Figure 13. Reference Voltage vs Temperature 6.0 10 Output Voltage Deviation (mV) 100 81 79 77 75 50 0 COUT = 330 µF CPOWER = 110 µF CCONTROL = 10 µF CADJ = 25 µF VCONTROL = 5.0 V VPOWER = 3.3 V VOUT = 2.5 V –50 –100 73 Current (A) 71 69 67 65 8.0 Figure 14. Load Regulation vs Output Current 83 Adjust Pin Current (µA) 4.0 Output Current (A) 0 20 40 60 80 100 120 140 160 7.0 0 0 0 1 Temperature (°C) 2 3 4 5 Time (µs) Figure 15. Adjust Pin Current vs Temperature Figure 16. Current Step Transient Response APPLICATIONS NOTES THEORY OF OPERATION The CS52510–1 linear regulator provides adjustable voltages from 1.25 V to 5.0 V at currents up to 10 A. The regulator is protected against short circuits, and includes a thermal shutdown circuit with hysteresis. The output, which is current limited, consists of a PNP–NPN transistor pair and requires an output capacitor for stability. A detailed procedure for selecting this capacitor is included in the Stability Considerations section. output voltage will not turn on until both supplies are operating. If the control voltage comes up first, the output current will be typically limited to about 3.0 mA until the power input voltage comes up. If the power input voltage comes up first the output will not turn on at all until the control voltage comes up. The output can never come up unregulated. The CS52510–1 can also be used as a single supply device with the control and power inputs tied together. In this mode, the dropout will be determined by the minimum control voltage. VPOWER Function The CS52510–1 utilizes a two supply approach to maximize efficiency. The collector of the power device is brought out to the VPOWER pin to minimize internal power dissipation under high current loads.VCONTROL provides power for the control circuitry and the drive for the output NPN transistor. VCONTROL should be at least 1.0 V greater than the output voltage. Special care has been taken to ensure that there are no supply sequencing problems. The Output Voltage Sensing The CS52510–1 five terminal linear regulator includes a dedicated VSENSE function. This allows for true Kelvin sensing of the output voltage. This feature can virtually eliminate errors in the output voltage due to load regulation. Regulation will be optimized at the point where the sense pin is tied to the output. http://onsemi.com 6 CS52510–1 DESIGN GUIDELINES Power supply sequencing should be such that the VCONTROL supply is brought up coincidentally with or before the VPOWER supply. This allows the IC to begin charging output capacitor as soon as the VPOWER to VOUT differential is large enough that the pass transistor conducts. As VPOWER increases, the pass transistor will remain in dropout, and current is passed to the load until VOUT is in regulation. Further increase in the supply voltage brings the pass transistor out of dropout. In this manner, any output voltage less than 13 V may be regulated, provided the VPOWER to VOUT differential is less than 6.0 V. In the case where VCONTROL and VPOWER are shorted, there is no theoretical limit to the regulated voltage as long as the VPOWER to VOUT differential of 6.0 V is not exceeded. There is a possibility of damaging the IC when VPOWER – VIN is greater than 6.0 V if a short circuit occurs. Short circuit conditions will result in the immediate operation of the pass transistor outside of its safe operating area. Overvoltage stresses will then cause destruction of the pass transistor before overcurrent or thermal shutdown circuitry can become active. Additional circuitry may be required to clamp the VPOWER to VOUT differential to less than 6.0 V if fail safe operation is required. One possible clamp circuit is illustrated in Figure 18; however, the design of clamp circuitry must be done on an application by application basis. Care must be taken to ensure the clamp actually protects the design. Components used in the clamp design must be able to withstand the short circuit condition indefinitely while protecting the IC. Adjustable Operation This LDO adjustable regulator has an output voltage range of 1.25 V to 5.0 V. An external resistor divider sets the output voltage as shown in Figure 17. The regulator’s voltage sensing error amplifier maintains a fixed 1.253 V reference between the output pin and the adjust pin. VCONTROL VOUT CS52510–1 VPOWER VSENSE Adjust R1 R2 Figure 17. An External Resistor Divider Sets the Value of VOUT. The 1.253 V Reference Voltage Drops Across R1. A resistor divider network R1 and R2 causes a fixed current to flow to ground. This current creates a voltage across R2 that adds to the 1.253 V across R1 and sets the overall output voltage. The adjust pin current (typically 50 µA) also flows through R2 and adds a small error that should be taken into account if precise adjustment of VOUT is necessary. The output voltage is set according to the formula: External Supply VOUT 1.253 V R1 R2 R2 IADJ R1 VCONTROL The term IADJ × R2 represents the error added by the adjust pin current. R1 is chosen so that the minimum load current is a least 10 mA. R1 and R2 should be of the same composition for best tracking over temperature. The divider resistors should be placed as close to the load as possible. While not required, a bypass capacitor connected between the adjust pin and ground will improve transient response and ripple rejection. A 0.1 µF tantalum capacitor is recommended for “first cut” design. Value and type may be varied to optimize performance vs. price. VSENSE VPOWER VOUT VADJ Figure 18. Example Clamp Circuitry for VPOWER – VOUT > 6.0 V Other Adjustable Operation Considerations The CS52510–1 linear regulator has an absolute maximum specification of 6.0 V for the voltage difference between VIN and VOUT. However, the IC may be used to regulate voltages in excess of 6.0 V. The two main considerations in such a design are the sequencing of power supplies and short circuit capability. Stability Considerations The output compensation capacitor helps determine three main characteristics of a linear regulator: start–up delay, load transient response, and loop stability. The capacitor value and type is based on cost, availability, size and temperature constraints. A tantalum or aluminum http://onsemi.com 7 CS52510–1 electrolytic capacitor is best, since a film or ceramic capacitor with almost zero ESR can cause instability. The aluminum electrolytic capacitor is the least expensive solution. However, when the circuit operates at low temperatures, both the value and ESR of the capacitor will vary considerably. The capacitor manufacturers data sheet provides this information. A 300 µF tantalum capacitor will work for most applications, but with high current regulators such as the CS52510–1 the transient response and stability improve with higher values of capacitor. The majority of applications for this regulator involve large changes in load current so the output capacitor must supply the instantaneous load current. The ESR of the output capacitor causes an immediate drop in output voltage given by: A rule of thumb useful in determining if a protection diode is required is to solve for current ICV T where: I is the current flow out of the load capacitance when VCONTROL is shorted, C is the value of load capacitance V is the output voltage, and T is the time duration required for VCONTROL to transition from high to being shorted. If the calculated current is greater than or equal to the typical short circuit current value provided in the specifications, serious thought should be given to the use of a protection diode. V I ESR Current Limit For microprocessor applications it is customary to use an output capacitor network consisting of several tantalum and ceramic capacitors in parallel. This reduces the overall ESR and reduces the instantaneous output voltage drop under transient load conditions. The output capacitor network should be as close to the load as possible for the best results. The internal current limit circuit limits the output current under excessive load conditions. Short Circuit Protection The device includes short circuit protection circuitry that clamps the output current at approximately two amperes less than its current limit value. This provides for a current foldback function, which reduces power dissipation under a direct shorted load. Protection Diodes When large external capacitors are used with a linear regulator it is sometimes necessary to add protection diodes. If the input voltage of the regulator gets shorted, the output capacitor will discharge into the output of the regulator. The discharge current depends on the value of the capacitor, the output voltage, and the rate at which VCONTROL drops. In the CS52510–1 regulator, the discharge path is through a large junction and protection diodes are not usually needed. If the regulator is used with large values of output capacitance and the input voltage is instantaneously shorted to ground, damage can occur. In this case, a diode connected as shown in Figure 19 is recommended. Use of this diode has the added benefit of bleeding VOUT to ground if VCONTROL is shorted. This prevents an unregulated output from causing system damage. VCONTROL Thermal Shutdown The thermal shutdown circuitry is guaranteed by design to become activate above a die junction temperature of approximately 150°C and to shut down the regulator output. This circuitry has 25°C of typical hysteresis, thereby allowing the regulator to recover from a thermal fault automatically. Calculating Power Dissipation and Heat Sink Requirements High power regulators such as the CS52510–1 family usually operate at high junction temperatures. Therefore, it is important to calculate the power dissipation and junction temperatures accurately to ensure that an adequate heat sink is used. Since the package tab is connected to VOUT on the CS52510–1, electrical isolation may be required for some applications. Also, as with all high power packages, thermal compound is necessary to ensure proper heat flow. For added safety, this high current LDO includes an internal thermal shutdown circuit. The thermal characteristics of an IC depend on the following four factors: junction temperature, ambient temperature, die power dissipation, and the thermal resistance from the die junction to ambient air. The maximum junction temperature can be determined by: VOUT CS52510–1 VPOWER VSENSE Adjust TJ(max) TA(max) PD(max) RJA The maximum ambient temperature and the power dissipation are determined by the design while the maximum junction temperature and the thermal resistance Figure 19. Diode Protection Against VCONTROL Short Circuit Conditions http://onsemi.com 8 CS52510–1 RJA RJC RCS RSA depend on the manufacturer and the package type. The maximum power dissipation for a regulator is: The value for RΘJC is 1.4°C/watt for the CS52510–1 in a TO–220 package. For a high current regulator such as the CS52510–1 the majority of heat is generated in the power transistor section. The value for RΘSA depends on the heat sink type, while the RΘCS depends on factors such as package type, heat sink interface (is an insulator and thermal grease used?), and the contact area between the heat sink and the package. Once these calculations are complete, the maximum permissible value of RΘJA can be calculated and the proper heat sink selected. For further discussion on heat sink selection, see our application note “Thermal Management for Linear Regulators,” document number SR006AN/D, available through the Literature Distribution Center or via our website at http://www.onsemi.com. PD(max) (VIN(max) VOUT(min))IOUT(max) VIN(max) IIN(max) A heat sink effectively increases the surface area of the package to improve the flow of heat away from the IC and into the surrounding air. Each material in the heat flow path between the IC and the outside environment has a thermal resistance which is measured in degrees per watt. Like series electrical resistances, these thermal resistances are summed to determine the total thermal resistance between the die junction and the surrounding air, RΘJA. This total thermal resistance is comprised of three components. These resistive terms are measured from junction to case (RΘJC), case to heat sink RΘCS), and heat sink to ambient air (RΘSA). The equation is: http://onsemi.com 9 CS52510–1 PACKAGE DIMENSIONS TO–220 FIVE LEAD T SUFFIX CASE 314D–04 ISSUE E –T– –Q– SEATING PLANE NOTES: 1. DIMENSIONING AND TOLERANCING PER ANSI Y14.5M, 1982. 2. CONTROLLING DIMENSION: INCH. 3. DIMENSION D DOES NOT INCLUDE INTERCONNECT BAR (DAMBAR) PROTRUSION. DIMENSION D INCLUDING PROTRUSION SHALL NOT EXCEED 10.92 (0.043) MAXIMUM. C B E A U L K J H G D DIM A B C D E G H J K L Q U 1234 5 5 PL 0.356 (0.014) M T Q M INCHES MIN MAX 0.572 0.613 0.390 0.415 0.170 0.180 0.025 0.038 0.048 0.055 0.067 BSC 0.087 0.112 0.015 0.025 0.990 1.045 0.320 0.365 0.140 0.153 0.105 0.117 MILLIMETERS MIN MAX 14.529 15.570 9.906 10.541 4.318 4.572 0.635 0.965 1.219 1.397 1.702 BSC 2.210 2.845 0.381 0.635 25.146 26.543 8.128 9.271 3.556 3.886 2.667 2.972 PACKAGE THERMAL DATA Parameter TO–220 Five Lead Unit RΘJC Typical 1.4 °C/W RΘJA Typical 50 °C/W http://onsemi.com 10 CS52510–1 Notes http://onsemi.com 11 CS52510–1 ON Semiconductor and are trademarks of Semiconductor Components Industries, LLC (SCILLC). SCILLC reserves the right to make changes without further notice to any products herein. SCILLC makes no warranty, representation or guarantee regarding the suitability of its products for any particular purpose, nor does SCILLC assume any liability arising out of the application or use of any product or circuit, and specifically disclaims any and all liability, including without limitation special, consequential or incidental damages. “Typical” parameters which may be provided in SCILLC data sheets and/or specifications can and do vary in different applications and actual performance may vary over time. All operating parameters, including “Typicals” must be validated for each customer application by customer’s technical experts. SCILLC does not convey any license under its patent rights nor the rights of others. SCILLC products are not designed, intended, or authorized for use as components in systems intended for surgical implant into the body, or other applications intended to support or sustain life, or for any other application in which the failure of the SCILLC product could create a situation where personal injury or death may occur. Should Buyer purchase or use SCILLC products for any such unintended or unauthorized application, Buyer shall indemnify and hold SCILLC and its officers, employees, subsidiaries, affiliates, and distributors harmless against all claims, costs, damages, and expenses, and reasonable attorney fees arising out of, directly or indirectly, any claim of personal injury or death associated with such unintended or unauthorized use, even if such claim alleges that SCILLC was negligent regarding the design or manufacture of the part. SCILLC is an Equal Opportunity/Affirmative Action Employer. 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