CS5203−1
3.0 A Adjustable Linear
Regulator
The CS5203−1 linear regulator provides 3.0 A at adjustable output
voltages with an accuracy of ±1.5 %. The device uses two external
resistors to set the output voltage within a 1.25 V to 5.5 V range.
The regulator is intended for use as a post regulator and
microprocessor supply. The fast loop response and low dropout
voltage make this regulator ideal for applications where low voltage
operation and good transient response are important.
The circuit is designed to operate with dropout voltages less than 1.4 V
at 3.0 A output current. Device protection includes overcurrent and
thermal shutdown.
The CS5203−1 is pin compatible with the LT1085 family of linear
regulators but has lower dropout voltage.
The regulator is available in TO−220−3 and surface mount D2PAK−3
packages.
12
2
3
Tab = VOUT
Pin 1. Adj
2. VOUT
3. VIN
3
ORDERING INFORMATION
See detailed ordering and shipping information in the package
dimensions section on page 8 of this data sheet.
See general marking information in the device marking
section on page 8 of this data sheet.
3.3 V @ 3.0 A
CS5203−1
124 W
1.0%
Adj
10 mF
5.0 V
1
DEVICE MARKING INFORMATION
VOUT
VIN
TO−220−3
T SUFFIX
CASE 221A
D2PAK−3
DP SUFFIX
CASE 418AB
Features
• Output Current to 3.0 A
• Output Accuracy to ±1.5% Over Temperature
• Dropout Voltage (typical) 1.2 V @ 3.0 A
• Fast Transient Response
• Fault Protection
− Current Limit
− Thermal Shutdown
5.0 V
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0.1 mF
5.0 V
200 W
1.0%
22 mF
5.0 V
Figure 1. Applications Diagram
© Semiconductor Components Industries, LLC, 2006
September, 2006 − Rev. 8
1
Publication Order Number:
CS5203−1/D
CS5203−1
MAXIMUM RATINGS*
Parameter
Supply Voltage, VIN
Operating Temperature Range
Junction Temperature
Storage Temperature Range
ESD Damage Threshold
Lead Temperature Soldering:
Wave Solder (through hole styles only) Note 1
Reflow (SMD styles only) Note 2
Value
Unit
7.0
V
−40 to +70
°C
150
°C
−60 to +150
°C
2.0
kV
260 Peak
230 Peak
°C
°C
1. 10 second maximum.
2. 60 second maximum above 183°C
*The maximum package power dissipation must be observed.
ELECTRICAL CHARACTERISTICS (CIN = 10 mF, COUT = 22 mF Tantalum, VOUT + VDROPOUT < VIN < 7.0 V, 0°C ≤ TA ≤ 70°C,
TJ ≤ +150°C, unless otherwise specified, Ifull load = 3.0 A)
Characteristic
Test Conditions
Min
Typ
Max
Unit
1.235
(−1.5%)
1.254
1.273
(+1.5%)
V
Adjustable Output Voltage
Reference Voltage (Notes 3 and 4)
VIN − VOUT = 1.5 V; VAdj = 0 V
10 mA ≤ IOUT ≤ 3.0 A
Line Regulation
2.0 V ≤ VIN − VOUT ≤ 5.75 V; IOUT = 10 mA
−
0.02
0.20
%
Load Regulation (Notes 3 and 4)
VIN − VOUT = 2.0 V; 10 mA ≤ IOUT ≤ 3.0 A
−
0.04
0.4
%
Dropout Voltage (Note 5)
IOUT = 3.0 A
−
1.15
1.40
V
Current Limit
VIN − VOUT = 3.0 V; TJ ≥ 25°C
3.1
4.6
−
A
Minimum Load Current (Note 6)
VIN = 7.0 V, VAdj = 0 V
−
0.6
2.0
mA
Adjust Pin Current
VIN − VOUT = 3.0 V; IOUT = 10 mA
−
50
100
mA
Thermal Regulation (Note 7)
30 ms Pulse, TA = 25°C
−
0.002
0.020
%/W
Ripple Rejection (Note 7)
f = 120 Hz; IOUT = 3.0 A; VIN − VOUT = 3.0 V;
VRIPPLE = 1.0 VPP
−
80
−
dB
Thermal Shutdown (Note 8)
−
150
180
210
°C
Thermal Shutdown Hysteresis (Note 8)
−
−
−
25
°C
3. Load regulation and output voltage are measured at a constant junction temperature by low duty cycle pulse testing. Changes in output
voltage due to temperature changes must be taken into account separately.
4. Specifications apply for an external Kelvin sense connection at a point on the output pin 1/4” from the bottom of the package.
5. Dropout voltage is a measurement of the minimum input/output differential at full load.
6. Minimum load current is defined as the minimum output current required to maintain regulation. The reference resistor in the output divider
is usually sized to fulfill the minimum load current requirement.
7. Guaranteed by design, not 100% functionally tested in production.
8. Guaranteed by design, not 100% parametrically tested in production. However, every part is subject to functional testing for thermal
shutdown.
PACKAGE PIN DESCRIPTION
Package Pin Number
TO−220−3
D2PAK−3
Pin Symbol
1
1
Adj
2
2
VOUT
3
3
VIN
Function
Adjust pin (low side of the internal reference).
Regulated output voltage (case).
Input voltage.
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2
CS5203−1
VOUT
VIN
Output
Current
Limit
Thermal
Shutdown
− +
Error
Amplifier
Bandgap
Reference
Adj
Figure 2. Block Diagram
TYPICAL PERFORMANCE CHARACTERISTICS
+0.3
1.20
1.10
Reference Voltage Deviation (%)
Dropout Voltage (V)
1.15
TCASE = 0°C
1.05
1.00
0.95
0.90
TCASE = 125°C
TCASE = 25°C
0.85
0.80
0.75
0
−0.1
−0.2
0
30
60
90
120
TJ (°C)
Figure 3. Dropout Voltage vs. Output
Current
Figure 4. Bandgap Reference Voltage
Deviation vs. Temperature
0.65
Minimum Load Current (mA)
Ripple Rejection (dB)
0
Output Current (A)
80
70
60
50
40
30
20
101
+0.1
−0.3
0.30 0.60 0.90 1.20 1.50 1.80 2.10 2.40 2.70 3.00
90
10
+0.2
102
103
104
105
0.60
0.55
TCASE = 125°C
0.50
TCASE = 0°C
0.45
0.40
106
TCASE = 25°C
1
2
3
4
5
6
7
Frequency (Hz)
VIN − VOUT (V)
Figure 5. Ripple Rejection vs. Frequency
Figure 6. Minimum Load Current vs.
VIN − VOUT
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3
8
CS5203−1
68
TCASE = 125°C
66
Adjust Pin Current (mA)
Adjust Pin Current, IAdj (mA)
75
65
55
64
62
60
TCASE = 25°C
58
56
45
0
30
60
90
54
120
TCASE = 0°C
1
2
3
4
5
6
7
TA (°C)
VIN − VOUT (V)
Figure 7. Adjust Pin Current vs.
Temperature
Figure 8. Adjust Pin Current vs. VIN − VOUT
8
70.00
DVOUT (mV)
67.00
65.50
64.00
+200
0
−200
VIN = 5.0 V
62.50
61.00
I (A)
58.00
2
1
56.50
55.00
VOUT = 3.3 V
CIN = 100 mF
COUT = 10 mF Tantalum
3
59.50
0
0.3
0.6
0.9
1.2
1.5
1.8
2.1
2.4
2.7
0
3.0
0
5
IOUT (A)
Time (ms)
Figure 9. Adjust Pin Current vs. Output
Current
Figure 10. Transient Response
6
5
4
ISC (A)
Adjust Pin Current (mA)
68.50
3
2
1
0
1
2
3
4
5
6
VIN − VOUT (V)
Figure 11. Short Circuit Current vs.
VIN − VOUT
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4
7
10
CS5203−1
APPLICATIONS INFORMATION
The CS5203−1 linear regulator provides adjustable voltages
at currents up to 3.0 A. The regulator is protected against
overcurrent conditions and includes thermal shutdown.
The CS5203−1 has a composite PNP−NPN output
transistor and requires an output capacitor for stability. A
detailed procedure for selecting this capacitor is included in
the Stability Considerations section.
In most applications, ramp−up of the power supply to VIN
is fairly slow, typically on the order of several tens of
milliseconds, while the regulator responds in less than one
microsecond. In this case, the linear regulator begins
charging the load as soon as the VIN to VOUT differential is
large enough that the pass transistor conducts current. The
load at this point is essentially at ground, and the supply
voltage is on the order of several hundred millivolts, with the
result that the pass transistor is in dropout. As the supply to
VIN increases, the pass transistor will remain in dropout, and
current is passed to the load until VOUT reaches the point at
which the IC is in regulation. Further increase in the supply
voltage brings the pass transistor out of dropout. The result
is that the output voltage follows the power supply ramp−up,
staying in dropout until the regulation point is reached. In
this manner, any output voltage may be regulated. There is
no theoretical limit to the regulated voltage as long as the
VIN to VOUT differential of 7.0 V is not exceeded.
However, the possibility of destroying the IC in a short
circuit condition is very real for this type of design. Short
circuit conditions will result in the immediate operation of
the pass transistor outside of its safe operating area.
Over−voltage stresses will then cause destruction of the pass
transistor before overcurrent or thermal shutdown circuitry
can become active. Additional circuitry may be required to
clamp the VIN to VOUT differential to less than 7.0 V if
fail−safe operation is required. One possible clamp circuit is
illustrated in Figure 13; however, the design of clamp
circuitry must be done on an application by application
basis. Care must be taken to ensure the clamp actually
protects the design. Components used in the clamp design
must be able to withstand the short circuit condition
indefinitely while protecting the IC.
Adjustable Operation
The CS5203−1 has an output voltage range of 1.25 V to
5.5 V. An external resistor divider sets the output voltage as
shown in Figure 12. The regulator maintains a fixed 1.25V
(typical) reference between the output pin and the adjust pin.
A resistor divider network R1 and R2 causes a fixed current
to flow to ground. This current creates a voltage across R2
that adds to the 1.25 V across R1 and sets the overall output
voltage. The adjust pin current (typically 50 mA) also flows
through R2 and adds a small error that should be taken into
account if precise adjustment of VOUT is necessary.
The output voltage is set according to the formula:
) R2Ǔ
ǒR1 R1
) IAdj
VOUT + VREF
R2
The term IAdj × R2 represents the error added by the adjust
pin current.
R1 is chosen so that the minimum load current is at least
2.0 mA. R1 and R2 should be the same type, e.g. metal film
for best tracking over temperature. While not required, a
bypass capacitor from the adjust pin to ground will improve
ripple rejection and transient response. A 0.1 mF tantalum
capacitor is recommended for “first cut” design. Type and
value may be varied to obtain optimum performance vs.
price.
VIN
VIN
C1
VOUT
VOUT
CS5203−1
Adj
VREF
IAdj
CAdj
R1
EXTERNAL SUPPLY
C2
VIN
R2
VOUT
VAdj
Figure 12. Resistor Divider Scheme
VOUT
The CS5201−1 linear regulator has an absolute maximum
specification of 7.0 V for the voltage difference between VIN
and VOUT. However, the IC may be used to regulate voltages
in excess of 7.0 V. The main considerations in such a design
are power−up and short circuit capability.
Figure 13. Short Circuit Protection Circuit for
High Voltage Application.
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5
CS5203−1
Stability Considerations
The output or compensation capacitor helps determine
three main characteristics of a linear regulator: start−up
delay, load transient response, and loop stability.
The capacitor value and type is based on cost, availability,
size and temperature constraints. A tantalum or aluminum
electrolytic capacitor is best, since a film or ceramic
capacitor with almost zero ESR can cause instability. The
aluminum electrolytic capacitor is the least expensive
solution. However, when the circuit operates at low
temperatures, both the value and ESR of the capacitor will
vary considerably. The capacitor manufacturer’s data sheet
provides this information.
A 22 mF tantalum capacitor will work for most
applications, but with high current regulators such as the
CS5203−1 the transient response and stability improve with
higher values of capacitor. The majority of applications for
this regulator involve large changes in load current so the
output capacitor must supply the instantaneous load current.
The ESR of the output capacitor causes an immediate drop
in output voltage given by:
DV + DI
IN4002 (Optional)
VIN
VIN
VOUT
VOUT
CS5203−1
C1
Adj
R1
C2
R2
CAdj
Figure 14. Protection Diode Scheme for Large
Output Capacitors
Output Voltage Sensing
Since the CS5203−1 is a three terminal regulator, it is not
possible to provide true remote load sensing. Load
regulation is limited by the resistance of the conductors
connecting the regulator to the load.
For the adjustable regulator, the best load regulation
occurs when R1 is connected directly to the output pin of the
regulator as shown in Figure 15. If R1 is connected to the
load, RC is multiplied by the divider ratio and the effective
resistance between the regulator and the load becomes.
ESR
For microprocessor applications it is customary to use an
output capacitor network consisting of several tantalum and
ceramic capacitors in parallel. This reduces the overall ESR
and reduces the instantaneous output voltage drop under
transient load conditions. The output capacitor network
should be as close to the load as possible for the best results.
RC
) R2Ǔ
ǒR1 R1
where RC = conductor parasitic resistance.
Protection Diodes
When large external capacitors are used with a linear
regulator it is sometimes necessary to add protection diodes.
If the input voltage of the regulator gets shorted, the output
capacitor will discharge into the output of the regulator. The
discharge current depends on the value of the capacitor, the
output voltage and the rate at which VIN drops. In the
CS5203−1 linear regulator, the discharge path is through a
large junction and protection diodes are not usually needed.
If the regulator is used with large values of output
capacitance and the input voltage is instantaneously shorted
to ground, damage can occur. In this case, a diode connected
as shown in Figure 14 is recommended.
VIN
VIN
RC
VOUT
CS5203−1
R1
Adj
Conductor Parasitic
Resistance
RLOAD
R2
Figure 15. Grounding Scheme for Adjustable Output
Regulator to Minimize Parasitic Resistance Effects
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CS5203−1
Calculating Power Dissipation and Heat Sink
Requirements
A heat sink effectively increases the surface area of the
package to improve the flow of heat away from the IC and
into the surrounding air.
Each material in the heat flow path between the IC and the
outside environment has a thermal resistance. Like series
electrical resistances, these resistances are summed to
determine RqJA, the total thermal resistance between the
junction and the surrounding air.
1. Thermal Resistance of the junction to case, RqJC
(°C/W)
2. Thermal Resistance of the case to Heat Sink, RqCS
(°C/W)
3. Thermal Resistance of the Heat Sink to the ambient
air, RqSA (°C/W)
These are connected by the equation:
The CS5203−1 linear regulator includes thermal
shutdown and current limit circuitry to protect the device.
High power regulators such as these usually operate at high
junction temperatures so it is important to calculate the
power dissipation and junction temperatures accurately to
ensure that an adequate heat sink is used.
The case is connected to VOUT on the CS5203−1,
electrical isolation may be required for some applications.
Thermal compound should always be used with high current
regulators such as these.
The thermal characteristics of an IC depend on the
following four factors:
1.
2.
3.
4.
Maximum Ambient Temperature TA (°C)
Power dissipation PD (Watts)
Maximum junction temperature TJ (°C)
Thermal resistance junction to ambient RqJA (°C/W)
RQJA + RQJC ) RQCS ) RQSA
The value for RqJA is calculated using equation (3) and the
result can be substituted in equation (1).
The value for RqJC is 3.5°C/W for a given package type
based on an average die size. For a high current regulator
such as the CS5203−1 the majority of the heat is generated
in the power transistor section. The value for RqSA depends
on the heat sink type, while RqCS depends on factors such as
package type, heat sink interface (is an insulator and thermal
grease used?), and the contact area between the heat sink and
the package. Once these calculations are complete, the
maximum permissible value of RqJA can be calculated and
the proper heat sink selected. For further discussion on heat
sink selection, see application note “Thermal
Management,” document number AND8036/D, available
through the Literature Distribution Center or via our website
at http://onsemi.com.
These four are related by the equation
TJ + TA ) PD
RQJA
(3)
(1)
The maximum ambient temperature and the power
dissipation are determined by the design while the
maximum junction temperature and the thermal resistance
depend on the manufacturer and the package type.
The maximum power dissipation for a regulator is:
PD(max) + {VIN(max) * VOUT(min)}IOUT(max) ) VIN(max)IQ
(2)
where:
VIN(max) is the maximum input voltage,
VOUT(min) is the minimum output voltage,
IOUT(max) is the maximum output current, for the
application
IQ is the maximum quiescent current at IOUT(max).
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7
CS5203−1
ORDERING INFORMATION
Type*
Package
Shipping†
3.0 A, Adj. Output
TO−220−3, STRAIGHT
50 Units / Rail
CS5203−1GDP3
3.0 A, Adj. Output
D2PAK−3
50 Units / Rail
CS5203−1GDPR3
3.0 A, Adj. Output
D2PAK−3
750 / Tape & Reel
Orderable Part Number
CS5203−1GT3
*Consult your local sales representative for fixed output voltage versions.
†For information on tape and reel specifications, including part orientation and tape sizes, please refer to our Tape and Reel Packaging
Specifications Brochure, BRD8011/D.
MARKING DIAGRAMS
D2PAK−3
DP SUFFIX
CASE 418AB
TO−220−3
T SUFFIX
CASE 221A
CS5203−1
AWLYWW
CS5203−1
AWLYWW
1
1
A
WL, L
YY, Y
WW, W
= Assembly Location
= Wafer Lot
= Year
= Work Week
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8
CS5203−1
PACKAGE DIMENSIONS
TO−220−3
T SUFFIX
CASE 221A−08
ISSUE AA
−T−
F
−B−
4
Q
C
T
S
DIM
A
B
C
D
F
G
H
J
K
L
N
Q
R
S
T
U
V
A
U
1 2 3
−Y−
NOTES:
1. DIMENSIONING AND TOLERANCING PER ANSI
Y14.5M, 1982.
2. CONTROLLING DIMENSION: INCH.
SEATING
PLANE
H
K
L
R
V
G
J
D 3 PL
0.25 (0.010)
N
M
B
M
INCHES
MIN
MAX
0.560
0.625
0.380
0.420
0.140
0.190
0.025
0.035
0.139
0.155
0.100 BSC
−−−
0.280
0.012
0.045
0.500
0.580
0.045
0.060
0.200 BSC
0.100
0.135
0.080
0.115
0.020
0.055
0.235
0.255
0.000
0.050
0.045
−−−
MILLIMETERS
MIN
MAX
14.23
15.87
9.66
10.66
3.56
4.82
0.64
0.89
3.53
3.93
2.54 BSC
−−−
7.11
0.31
1.14
12.70
14.73
1.15
1.52
5.08 BSC
2.54
3.42
2.04
2.92
0.51
1.39
5.97
6.47
0.00
1.27
1.15
−−−
Y
D2PAK−3
DP SUFFIX
CASE 418AB−01
ISSUE O
For D2PAK Outline and
Dimensions − Contact Factory
PACKAGE THERMAL DATA
Parameter
TO−220−3
D2PAK−3
Unit
RqJC
Typical
3.5
3.5
°C/W
RqJA
Typical
50
10−50*
°C/W
* Depending on thermal properties of substrate. RqJA = RqJC + RqCA
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CS5203−1
ON Semiconductor and
are registered trademarks of Semiconductor Components Industries, LLC (SCILLC). SCILLC reserves the right to make changes without further notice
to any products herein. SCILLC makes no warranty, representation or guarantee regarding the suitability of its products for any particular purpose, nor does SCILLC assume any liability
arising out of the application or use of any product or circuit, and specifically disclaims any and all liability, including without limitation special, consequential or incidental damages.
“Typical” parameters which may be provided in SCILLC data sheets and/or specifications can and do vary in different applications and actual performance may vary over time. All
operating parameters, including “Typicals” must be validated for each customer application by customer’s technical experts. SCILLC does not convey any license under its patent rights
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For additional information, please contact your local
Sales Representative
CS5203−1/D