LM4936 Stereo 2W Audio Power Amplifiers with Volume Control and Selectable Control Interface (SPI or I2C) General Description Key Specifications The LM4936 is a monolithic integrated circuit that provides volume control, and stereo bridged audio power amplifiers capable of producing 2W into 4Ω (Note 1) with less than 1% THD or 2.2W into 3Ω (Note 2) with less than 1% THD. Boomer ® audio integrated circuits were designed specifically to provide high quality audio while requiring a minimum amount of external components. The LM4936 incorporates a SPI or I2C Control Interface that runs the volume control, stereo bridged audio power amplifiers and a selectable gain or bass boost. All of the LM4936’s features (i.e. SD, Mode, Mute, Gain Sel) make it optimally suited for multimedia monitors, portable radios, desktop, and portable computer applications. The LM4936 features an externally controlled, low-power consumption shutdown mode, and both a power amplifier and headphone mute for maximum system flexibility and performance. n PO at 1% THD+N n into 3Ω 2.2W (typ) n into 4Ω 2.0W (typ) n into 8Ω 1.25W (typ) n Single-ended mode - THD+N at 90mW into 32Ω 1%(typ) n Shutdown current 0.7µA (typ) Note 1: When properly mounted to the circuit board, LM4936MH will deliver 2W into 4Ω. See Application Information section Exposed-DAP package PCB Mounting Considerations for more information. Applications Note 2: An LM4936MH that has been properly mounted to the circuit board and forced-air cooled will deliver 2.2W into 3Ω. Features n n n n n n n Selectable SPI or I2C Control Interface System Beep Detect Stereo switchable bridged/single-ended power amplifiers Selectable internal/external gain and bass boost “Click and pop” suppression circuitry Thermal shutdown protection circuitry Headphone Sense n Portable and Desktop Computers n Multimedia Monitors n Portable Radios, PDAs, and Portable TVs Connection Diagram TSSOP Package 20117802 Top View Order Number LM4936MH See NS Package Number MXA28A for Exposed-DAP TSSOP Boomer ® is a registered trademark of NationalSemiconductor Corporation. © 2005 National Semiconductor Corporation DS201178 www.national.com LM4936 Stereo 2W Audio Power Amplifiers with Volume Control and Selectable Control Interface (SPI or I2C) April 2005 LM4936 Block Diagram 20117801 FIGURE 1. LM4936 Block Diagram www.national.com 2 θJC (typ) - MXA28A If Military/Aerospace specified devices are required, please contact the National Semiconductor Sales Office/ Distributors for availability and specifications. θJA (typ) - MXA28A (exposed DAP) (Note 4) 41˚C/W θJA (typ) - MXA28A (exposed DAP) (Note 3) 54˚C/W θJA (typ) - MXA28A (exposed DAP) (Note 5) 59˚C/W θJA (typ) - MXA28A (exposed DAP) (Note 6) 93˚C/W Supply Voltage 6.0V Storage Temperature 2˚C/W -65˚C to +150˚C −0.3V to VDD +0.3V Input Voltage Power Dissipation (Note 11) Internally limited ESD Susceptibility (Note 12) 2000V ESD Susceptibility (Note 13) 200V Junction Temperature Operating Ratings 150˚C Soldering Information Small Outline Package Vapor Phase (60 sec.) 215˚C Infrared (15 sec.) 220˚C Temperature Range TMIN ≤ TA ≤TMAX −40˚C ≤ TA ≤ 85˚C Supply Voltage (Note 17) 2.7V ≤ VDD ≤ 5.5V I2C/SPI VDD ≤ VDD 2.4V ≤ I2C/SPI VDD ≤ 5.5V See AN-450 “Surface Mounting and their Effects on Product Reliability” for other methods of soldering surface mount devices. Electrical Characteristics for Entire IC (Notes 7, 10) The following specifications apply for VDD = 5V unless otherwise noted. Limits apply for TA = 25˚C. LM4936 Symbol Parameter Conditions Typical (Note 14) Units (Limits) Limit (Note 15) VDD Supply Voltage 5.5 V (max) IDD Quiescent Power Supply Current VIN = 0V, IO = 0A 10 25 mA (max) ISD Shutdown Current Vshutdown = VDD 0.7 2.0 µA (max) VIH Headphone Sense High Input Voltage 4 V (min) VIL Headphone Sense Low Input Voltage 0.8 V (max) 2.7 V (min) Electrical Characteristics for Volume Control (Notes 7, 10) The following specifications apply for VDD = 5V. Limits apply for TA = 25˚C. LM4936 Symbol Parameter Conditions Units (Limits) Typical (Note 14) Limit (Note 15) 0 ± 0.75 dB (max) -75 dB (min) -78 dB (min) CRANGE Volume Control Range Maximum gain setting Minimum gain setting -91 ACh-Ch Channel to Channel Gain Mismatch fIN = 1kHz 0.35 AM Mute Attenuation Mute Mode dB Electrical Characteristics for Control Interface (Notes 7, 10) The following specifications apply for VDD = 5V, VDD = 3V and 2.4V ≤ I2C/SPI VDD ≤ 5.5V. Limits apply for TA = 25˚C. LM4936 Symbol Parameter Conditions Typical (Note 14) Limit (Note 15) Units (Limits) t1 SCL period 2.5 µs (min) t2 SDA Set-up Time 100 ns (min) t3 SDA Stable Time 0 ns (min) t4 Start Condition Time 100 ns (min) t5 Stop Condition Time 100 ns (min) 3 www.national.com LM4936 Absolute Maximum Ratings (Note 10) LM4936 Electrical Characteristics for Control Interface (Notes 7, 10) (Continued) The following specifications apply for VDD = 5V, VDD = 3V and 2.4V ≤ I2C/SPI VDD ≤ 5.5V. Limits apply for TA = 25˚C. LM4936 Symbol Parameter Conditions Typical (Note 14) Limit (Note 15) Units (Limits) VIH Digital Input High Voltage 0.7 X I2C/SPIVDD V (min) VIL Digital Input Low Voltage 0.3 X I2C/SPIVDD V (max) tES SPI ENABLE Setup Time 50 ns (min) tEH SPI ENABLE Hold Time 50 ns (min) tEL SPI ENABLE High Time 50 ns (min) tDS SPI DATA Setup Time 50 ns (min) tDH SPI DATA HOLD Time 50 ns (min) tCS SPI CLOCK Setup Time 50 ns (min) tCH SPI CLOCK High Pulse Width 100 ns (min) tCL SPI CLOCK Low Pulse Width 100 ns (min) fCLK SPI CLOCK Frequency 5 MHz (max) Electrical Characteristics for Single-Ended Mode Operation (Notes 7, 10) The following specifications apply for VDD = 5V. Limits apply for TA = 25˚C. LM4936 Symbol PO Parameter Output Power Conditions Typical (Note 14) Limit (Note 15) Units (Limits) THD = 1%; f = 1kHz; RL = 32Ω 90 mW THD = 10%; f = 1 kHz; RL = 32Ω 110 mW 0.02 % THD+N Total Harmonic Distortion+Noise POUT = 20mW, f = 1kHz, RL = 32Ω, AVD = 1, 80kHz BW PSRR Power Supply Rejection Ratio CB = 1µF, f = 120Hz, Input Terminated VRIPPLE = 200mVp-p 57 dB NOUT Output Noise A-Wtd Filter 18 µV Xtalk Channel Separation (Note 17) f = 1kHz, CB = 1µF 63 dB Electrical Characteristics for Bridged Mode Operation (Notes 7, 10) The following specifications apply for VDD = 5V, unless otherwise noted. Limits apply for TA = 25˚C. LM4936 Symbol Parameter Conditions Typical (Note 14) Limit (Note 15) 50 Units (Limits) VOS Output Offset Voltage VIN = 0V, No Load 10 PO Output Power THD + N = 1%; f = 1kHz; RL = 3Ω (Note 8) 2.2 W THD + N = 1%; f = 1kHz; RL = 4Ω (Note 9) 2 W THD+N = 1% (max); f = 1kHz; RL = 8Ω 1.25 1.0 mV (max) W (min) THD+N = 10%; f = 1kHz; RL = 8Ω 1.6 W THD+N Total Harmonic Distortion+Noise PO = 0.4W, f = 1kHz RL = 8Ω, AVD = 2, 80kHz BW 0.06 % PSRR Power Supply Rejection Ratio CB = 1µF, f = 120Hz, Input Terminated VRIPPLE = 200mVp-p; RL = 8Ω 55 dB www.national.com 4 LM4936 Electrical Characteristics for Bridged Mode Operation (Notes 7, 10) (Continued) The following specifications apply for VDD = 5V, unless otherwise noted. Limits apply for TA = 25˚C. LM4936 Symbol Parameter Conditions Typical (Note 14) Units (Limits) Limit (Note 15) NOUT Output Noise A-Wtd Filter 36 µV Xtalk Channel Separation (Note 17) f = 1kHz, CB = 1µF 63 dB Note 3: The θJA given is for an MXA28A package whose exposed-DAP is soldered to an exposed 2in 2 piece of 1 ounce printed circuit board copper. Note 4: The θJA given is for an MXA28A package whose exposed-DAP is soldered to a 2in2 piece of 1 ounce printed circuit board copper on a bottom side layer through 21 8mil vias. Note 5: The θJA given is for an MXA28A package whose exposed-DAP is soldered to an exposed 1in 2 piece of 1 ounce printed circuit board copper. Note 6: The θJA given is for an MXA28A package whose exposed-DAP is not soldered to any copper. Note 7: All voltages are measured with respect to the ground pins, unless otherwise specified. All specifications are tested using the typical application as shown in Figure 1. Note 8: When driving 3Ω loads from a 5V supply the LM4936MH must be mounted to the circuit board and forced-air cooled. The demo board shown in the datasheet has planes for heat sinking. The top layer plane is 1.05 in2 (675mm2), the inner two layers each have a 1.03 in2 (667mm2) plane and the bottom layer has a 3.32 in2 (2143mm2) plane. The planes are electrically GND and interconnected through six 15 mil vias directly under the package and eight 28 mil vias in various locations. Note 9: When driving 4Ω loads from a 5V supply the LM4936MH must be mounted to the circuit board. The demo board shown in the datasheet has planes for heat sinking. The top layer plane is 1.05 in2 (675mm2), the inner two layers each have a 1.03 in2 (667mm2) plane and the bottom layer has a 3.32 in2 (2143mm2) plane. The planes are electrically GND and interconnected through six 15 mil vias directly under the package and eight 28 mil vias in various locations. Note 10: Absolute Maximum Ratings indicate limits beyond which damage to the device may occur. Operating Ratings indicate conditions for which the device is functional, but do not guarantee specific performance limits. Electrical Characteristics state DC and AC electrical specifications under particular test conditions which guarantee specific performance limits. This assumes that the device is within the Operating Ratings. Specifications are not guaranteed for parameters where no limit is given, however, the typical value is a good indication of device performance. Note 11: The maximum power dissipation must be derated at elevated temperatures and is dictated by TJMAX, θ JA, and the ambient temperature TA. The maximum allowable power dissipation is PDMAX = (TJMAX − TA )/θJA. For the LM4936, TJMAX = 150˚C, and the typical junction-to-ambient thermal resistance for each package can be found in the Absolute Maximum Ratings section above. Note 12: Human body model, 100pF discharged through a 1.5kΩ resistor. Note 13: Machine Model, 220pF – 240pF discharged through all pins. Note 14: Typicals are measured at 25˚C and represent the parametric norm. Note 15: Limits are guaranteed to National’s AOQL ( Average Outgoing Quality Level). Datasheet min/max specification limits are guaranteed by design, test, or statistical analysis. Note 16: I2C/SPI VDD must not be larger than VDD at any time or damage to the IC may occur. During power up and power down, I2C/SPI VDD must remain equal to VDD or lower. Note 17: PCB design will affect Crosstalk performance. 5 www.national.com LM4936 Typical Application 20117812 FIGURE 2. Typical Application Circuit www.national.com 6 B7 B6 B5 B4 B3 B2 B1 B0 I2C Address 1 1 0 1 1 0 ID 0 Mode Control Register 0 0 0 HP Control Gain Sel Mode Mute Shutdown Volume Control Register (See Table 4 ) 1 0 0 V4 V3 V2 V1 V0 TABLE 2. Headphone Control HP Sense Pin I2C/SPI HP Control (B4) Output Stage Configuration 0 0 BTL 0 1 SE 1 (VDD) 0 SE 1 (VDD) 1 SE TABLE 3. Logic Controls Logic Level B3 (Gain Sel) B2 (Mode) B1 (Mute) B0 (Shutdown) I2C/SPI Select 0 Internal Gain Fixed Volume, 0dB Mute Off (Play) Device Shutdown I2C mode 1 External Gain Adjustable Volume Mute On Device Active SPI mode Note 18: If system beep is detected on the Beep In pin, the system beep will be passed through the bridged amplifier regardless of the logic of the Mute and HP Control bits (B1, B4) and HP Sense pin. 7 www.national.com LM4936 TABLE 1. I2C/SPI Interface Controls (Note 18) LM4936 Typical Performance Characteristics THD+N vs Frequency VDD = 5V, RL = 3Ω, AV-BTL = 2V/V POUT = 1.5W/Channel, 80kHz BW THD+N vs Output Power/Channel VDD = 5V, RL = 3Ω, AV-BTL = 2V/V f = 1kHz, 80kHz BW 201178B5 201178A4 THD+N vs Frequency VDD = 5V, RL = 4Ω, AV-BTL = 2V/V POUT = 1.5W/Channel, 80kHz BW THD+N vs Output Power/Channel VDD = 5V, RL = 4Ω, AV-BTL = 2V/V f = 1kHz, 80kHz BW 201178B6 201178A5 THD+N vs Frequency VDD = 5V, RL = 8Ω, AV-BTL = 2V/V POUT = 1W/Channel, 80kHz BW THD+N vs Output Power/Channel VDD = 5V, RL = 8Ω, AV-BTL = 2V/V f = 1kHz, 80kHz BW 201178B7 www.national.com 201178A6 8 LM4936 Typical Performance Characteristics (Continued) THD+N vs Frequency VDD = 5V, RL = 8Ω, AV-SE = 1V/V POUT = 100mW/Channel, 80kHz BW THD+N vs Output Power/Channel VDD = 5V, RL = 8Ω, AV-SE = 1V/V f = 1kHz, COUT = 220µF, 80kHz BW 201178B8 201178A7 THD+N vs Frequency VDD = 5V, RL = 32Ω, AV-SE = 1V/V POUT = 40mW/Channel, 80kHz BW THD+N vs Output Power/Channel VDD = 5V, RL = 32Ω, AV-SE = 1V/V f = 1kHz, COUT = 220µF, 80kHz BW 201178B9 201178A9 THD+N vs Frequency VDD = 3V, RL = 3Ω, AV-SE = 2V/V POUT = 500mW/Channel, 80kHz BW THD+N vs Output Power/Channel VDD = 3V, RL = 3Ω, AV-BTL = 2V/V f = 1kHz, 80kHz BW 201178B0 20117898 9 www.national.com LM4936 Typical Performance Characteristics (Continued) THD+N vs Output Power/Channel VDD = 3V, RL = 4Ω, AV-BTL = 2V/V f = 1kHz, 80kHz BW THD+N vs Frequency VDD = 3V, RL = 4Ω, AV-BTL = 2V/V POUT = 450mW/Channel, 80kHz BW 201178B1 20117899 THD+N vs Frequency VDD = 3V, RL = 8Ω, AV-BTL = 2V/V POUT = 250mW/Channel, 80kHz BW THD+N vs Output Power/Channel VDD = 3V, RL = 8Ω, AV-BTL = 2V/V f = 1kHz, 80kHz BW 201178B2 201178A0 THD+N vs Frequency VDD = 3V, RL = 8Ω, AV-SE = 1V/V POUT = 50mW/Channel, 80kHz BW THD+N vs Output Power/Channel VDD = 3V, RL = 8Ω, AV-SE = 1V/V f = 1kHz, COUT = 220µF, 80kHz BW 201178B3 www.national.com 201178A1 10 LM4936 Typical Performance Characteristics (Continued) THD+N vs Frequency VDD = 3V, RL = 32Ω, AV-SE = 1V/V POUT = 20mW/Channel, 80kHz BW THD+N vs Output Power/Channel VDD = 3V, RL = 32Ω, AV-SE = 1V/V f = 1kHz, COUT = 220µF, 80kHz BW 201178B4 201178A3 THD+N vs Frequency VDD = 5V, RLDOCK = 10kΩ, Dock Pins VIN = 1Vp-p, CO = 1µF, 80kHz BW THD+N vs Output Voltage VDD = 5V, RLDOCK = 10kΩ, Dock Pins f = 1kHz, CO = 1µF, 80kHz BW 201178C1 201178A8 THD+N vs Frequency VDD = 3V, RLDOCK= 10kΩ, Dock Pins VIN = 1Vp-p, CO = 1µF, 80kHz BW THD+N vs Output Voltage VDD = 3V, RLDOCK = 10kΩ, Dock Pins f = 1kHz, CO = 1µF, 80kHz BW 201178C0 201178A2 11 www.national.com LM4936 Typical Performance Characteristics (Continued) PSRR vs Frequency VDD = 5V, VRIPPLE = 200mVp-p Inputs Terminated, 80kHz BW PSRR vs Frequency VDD = 3V, VRIPPLE = 200mVp-p Inputs Terminated, 80kHz BW 20117887 20117869 Crosstalk vs Frequency VDD = 3V, RL = 8Ω, AV-BTL = 2V/V POUT = 250mW, 80kHz BW Crosstalk vs Frequency VDD = 5V, RL = 8Ω, AV-BTL = 2V/V POUT = 1W, 80kHz BW 201178C5 201178C3 Crosstalk vs Frequency VDD = 3V, RL = 32Ω, AV-SE = 1V/V POUT = 20mW, 80kHz BW Crosstalk vs Frequency VDD = 5V, RL = 32Ω, AV-SE = 1V/V POUT = 40mW, 80kHz BW 201178C6 www.national.com 201178C4 12 LM4936 Typical Performance Characteristics (Continued) Output Level vs Frequency External Gain with Bass Boost Headphone Sense Threshold vs Supply Voltage RL = 8Ω, AV-SE = 1V/V COUT = 220µF, 80kHz BW 20117861 201178C2 Output Power/Channel vs Supply Voltage RL = 4Ω, AV-BTL = 2V/V, 80kHz BW Output Power/Channel vs Supply Voltage RL = 3Ω, AV-BTL = 2V/V, 80kHz BW 20117850 20117855 Output Power/Channel vs Supply Voltage RL = 8Ω, AV-SE = 1V/V, 80kHz BW Output Power/Channel vs Supply Voltage RL = 8Ω, AV-BTL = 2V/V, 80kHz BW 20117866 20117867 13 www.national.com LM4936 Typical Performance Characteristics (Continued) Output Power/Channel vs Supply Voltage RL = 32Ω, AV-SE = 1V/V, 80kHz BW Power Derating Curve (Note 19) 20117864 20117868 Power Dissipation vs Output Power/Channel VDD = 3V, AV-BTL = 2V/V, THD+N ≤ 1%, 80kHz BW Power Dissipation vs Output Power/Channel VDD = 5V, AV-BTL = 2V/V, THD+N ≤ 1%, 80kHz BW 20117837 20117835 Power Dissipation vs Output Power/Channel VDD = 3V, AV-SE = 1V/V, THD+N ≤ 1%, 80kHz BW Power Dissipation vs Output Power/Channel VDD = 5V, AV-SE = 1V/V, THD+N ≤ 1%, 80kHz BW 20117838 www.national.com 20117836 14 LM4936 Typical Performance Characteristics (Continued) Supply Current vs Supply Voltage RL = 8Ω Dropout Voltage 20117888 20117853 Output Power/Channel vs Load Resistance Output Power/Channel vs Load Resistance 20117862 20117807 Output Power/Channel vs Load Resistance Output Power/Channel vs Load Resistance 20117806 20117808 Note 19: These curves show the thermal dissipation ability of the LM4936MH at different ambient temperatures given these conditions: 15 www.national.com LM4936 Typical Performance Characteristics 2 (Continued) 2 500LFPM + 2in : The part is soldered to a 2in , 1 oz. copper plane with 500 linear feet per minute of forced-air flow across it. 2in2on bottom: The part is soldered to a 2in2, 1oz. copper plane that is on the bottom side of the PC board through 21 8 mil vias. 2in2: The part is soldered to a 2in2, 1oz. copper plane. 1in2: The part is soldered to a 1in2, 1oz. copper plane. Not Attached: The part is not soldered down and is not forced-air cooled. www.national.com 16 I2C COMPATIBLE INTERFACE The LM4936 uses a serial bus, which conforms to the I2C protocol, to control the chip’s functions with two wires: clock (SCL) and data (SDA). The clock line is uni-directional. The data line is bi-directional (open-collector). The maximum clock frequency specified by the I2C standard is 400kHz. In this discussion, the master is the controlling microcontroller and the slave is the LM4936. The I2C address for the LM4936 is determined using the ID/CE pin. The LM4936’s two possible I2C chip addresses are of the form 110110X10 (binary), where X1 = 0, if ID/CE is logic low; and X1 = 1, if ID/CE is logic high. If the I2C interface is used to address a number of chips in a system, the LM4936’s chip address can be changed to avoid any possible address conflicts. The bus format for the I2C interface is shown in Figure 5. The bus format diagram is broken up into six major sections: The packages must have their exposed DAPs soldered to a grounded copper pad on the PCB. The DAP’s PCB copper pad is connected to a large grounded plane of continuous unbroken copper. This plane forms a thermal mass heat sink and radiation area. Place the heat sink area on either outside plane in the case of a two-sided PCB, or on an inner layer of a board with more than two layers. Connect the DAP copper pad to the inner layer or backside copper heat sink area with vias. The via diameter should be 0.012in–0.013in with a 1.27mm pitch. Ensure efficient thermal conductivity by plating-through and solder-filling the vias. Best thermal performance is achieved with the largest practical copper heat sink area. If the heatsink and amplifier share the same PCB layer, a nominal 2.5in2 (min) area is necessary for 5V operation with a 4Ω load. Heatsink areas not placed on the same PCB layer as the LM4936 should be 5in2 (min) for the same supply voltage and load resistance. The last two area recommendations apply for 25˚C ambient temperature. Increase the area to compensate for ambient temperatures above 25˚C. In systems using cooling fans, the LM4936MH can take advantage of forced air cooling. With an air flow rate of 450 linear-feet per minute and a 2.5in2 exposed copper or 5.0in2 inner layer copper plane heatsink, the LM4936MH can continuously drive a 3Ω load to full power. In all circumstances and conditions, the junction temperature must be held below 150˚C to prevent activating the LM4936’s thermal shutdown protection. The LM4936’s power de-rating curve in the Typical Performance Characteristics shows the maximum power dissipation versus temperature. Example PCB layouts are shown in the Demonstration Board Layout section. Further detailed and specific information concerning PCB layout, fabrication, and mounting is available in National Semiconductor’s AN1187. The "start" signal is generated by lowering the data signal while the clock signal is high. The start signal will alert all devices attached to the I2C bus to check the incoming address against their own address. The 8-bit chip address is sent next, most significant bit first. The data is latched in on the rising edge of the clock. Each address bit must be stable while the clock level is high. After the last bit of the address bit is sent, the master releases the data line high (through a pull-up resistor). Then the master sends an acknowledge clock pulse. If the LM4936 has received the address correctly, then it holds the data line low during the clock pulse. If the data line is not held low during the acknowledge clock pulse, then the master should abort the rest of the data transfer to the LM4936. The 8 bits of data are sent next, most significant bit first. Each data bit should be valid while the clock level is stable high. After the data byte is sent, the master must check for another acknowledge to see if the LM4936 received the data. If the master has more data bytes to send to the LM4936, then the master can repeat the previous two steps until all data bytes have been sent. PCB LAYOUT AND SUPPLY REGULATION CONSIDERATIONS FOR DRIVING 3Ω AND 4Ω LOADS Power dissipated by a load is a function of the voltage swing across the load and the load’s impedance. As load impedance decreases, load dissipation becomes increasingly dependent on the interconnect (PCB trace and wire) resistance between the amplifier output pins and the load’s connections. Residual trace resistance causes a voltage drop, which results in power dissipated in the trace and not in the load as desired. For example, 0.1Ω trace resistance reduces the output power dissipated by a 4Ω load from 2.1W to 2.0W. This problem of decreased load dissipation is exacerbated as load impedance decreases. Therefore, to maintain the highest load dissipation and widest output voltage swing, PCB traces that connect the output pins to a load must be as wide as possible. Poor power supply regulation adversely affects maximum output power. A poorly regulated supply’s output voltage decreases with increasing load current. Reduced supply voltage causes decreased headroom, output signal clipping, and reduced output power. Even with tightly regulated supplies, trace resistance creates the same effects as poor supply regulation. Therefore, making the power supply traces as wide as possible helps maintain full output voltage swing. The "stop" signal ends the transfer. To signal "stop", the data signal goes high while the clock signal is high. The data line should be held high when not in use. I2C/SPI INTERFACE POWER SUPPLY PIN (I2C/SPI VDD) The LM4936’s I2C/SPI interface is powered up through the I2C/SPI VDD pin. The LM4936’s I2C/SPI interface operates at a voltage level set by the I2C/SPI VDD pin which can be set independent to that of the main power supply pin VDD. This is ideal whenever logic levels for the I2C/SPI interface are dictated by a microcontroller or microprocessor that is operating at a lower supply voltage than the main battery of a portable system. EXPOSED-DAP PACKAGE PCB MOUNTING CONSIDERATIONS Exposed-DAP (die attach paddle) packages provide a low thermal resistance between the die and the PCB to which the part is mounted and soldered. This allows rapid heat transfer from the die to the surrounding PCB copper traces, ground plane and, finally, surrounding air. The result is a low voltage audio power amplifier that produces 2.1W at ≤ 1% THD with a 4Ω load. This high power is achieved through 17 www.national.com LM4936 careful consideration of necessary thermal design. Failing to optimize thermal design may compromise the LM4936’s high power performance and activate unwanted, though necessary, thermal shutdown protection. Application Information LM4936 Application Information mode or bridge mode, respectively due to stereo operation. Twice the maximum power dissipation point given by Equation (3) must not exceed the power dissipation given by Equation (4): (Continued) BRIDGE CONFIGURATION EXPLANATION As shown in Figure 2, the LM4936 output stage consists of two pairs of operational amplifiers, forming a two-channel (channel A and channel B) stereo amplifier. (Though the following discusses channel A, it applies equally to channel B.) Figure 2 shows that the first amplifier’s negative (-) output serves as the second amplifier’s input. This results in both amplifiers producing signals identical in magnitude, but 180˚ out of phase. Taking advantage of this phase difference, a load is placed between −OUTA and +OUTA and driven differentially (commonly referred to as “bridge mode”). This results in a differential gain of AVD = 2 * (Rf/R i) PDMAX' = (TJMAX − TA)/θJA The LM4936’s TJMAX = 150˚C. In the MH package soldered to a DAP pad that expands to a copper area of 2in2 on a PCB, the LM4936MH’s θJA is 41˚C/W. At any given ambient temperature TA, use Equation (4) to find the maximum internal power dissipation supported by the IC packaging. Rearranging Equation (4) and substituting PDMAX for PDMAX' results in Equation (5). This equation gives the maximum ambient temperature that still allows maximum stereo power dissipation without violating the LM4936’s maximum junction temperature. (1) TA = TJMAX – 2*PDMAX θJA Bridge mode amplifiers are different from single-ended amplifiers that drive loads connected between a single amplifier’s output and ground. For a given supply voltage, bridge mode has a distinct advantage over the single-ended configuration: its differential output doubles the voltage swing across the load. This produces four times the output power when compared to a single-ended amplifier under the same conditions. This increase in attainable output power assumes that the amplifier is not current limited or that the output signal is not clipped. To ensure minimum output signal clipping when choosing an amplifier’s closed-loop gain, refer to the Audio Power Amplifier Design section. Another advantage of the differential bridge output is no net DC voltage across the load. This is accomplished by biasing channel A’s and channel B’s outputs at half-supply. This eliminates the coupling capacitor that single supply, singleended amplifiers require. Eliminating an output coupling capacitor in a single-ended configuration forces a single-supply amplifier’s half-supply bias voltage across the load. This increases internal IC power dissipation and may permanently damage loads such as speakers. POWER DISSIPATION Power dissipation is a major concern when successful single-ended or bridged amplifier. states the maximum power dissipation point ended amplifier operating at a given supply driving a specified output load. PDMAX = (VDD)2/(2π2RL) TJMAX = PDMAX θJA + TA Bridge Mode (2) POWER SUPPLY BYPASSING As with any power amplifier, proper supply bypassing is critical for low noise performance and high power supply rejection. Applications that employ a 5V regulator typically use a 10µF in parallel with a 0.1µF filter capacitor to stabilize the regulator’s output, reduce noise on the supply line, and improve the supply’s transient response. However, their presence does not eliminate the need for a local 1µF tantalum bypass capacitance connected between the LM4936’s supply pins and ground. Do not substitute a ceramic capacitor for the tantalum. Doing so may cause oscillation. Keep (3) The LM4936’s power dissipation is twice that given by Equation (2) or Equation (3) when operating in the single-ended www.national.com (6) Equation (6) gives the maximum junction temperature TJMAX. If the result violates the LM4936’s 150˚C TJMAX, reduce the maximum junction temperature by reducing the power supply voltage or increasing the load resistance. Further allowance should be made for increased ambient temperatures. The above examples assume that a device is a surface mount part operating around the maximum power dissipation point. If the result of Equation (3) multiplied by 2 for stereo operation is greater than that of Equation (4), then decrease the supply voltage, increase the load impedance, or reduce the ambient temperature. If these measures are insufficient, a heat sink can be added to reduce θJA. The heat sink can be created using additional copper area around the package, with connections to the ground pin(s), supply pin and amplifier output pins. External, solder attached SMT heatsinks such as the Thermalloy 7106D can also improve power dissipation. When adding a heat sink, the θJA is the sum of θJC, θCS, and θSA. (θJC is the junction-to-case thermal impedance, θCS is the case-to-sink thermal impedance, and θSA is the sink-to-ambient thermal impedance.) Refer to the Typical Performance Characteristics curves for power dissipation information at lower output power levels. However, a direct consequence of the increased power delivered to the load by a bridge amplifier is higher internal power dissipation for the same conditions. The LM4936 has two operational amplifiers per channel. The maximum internal power dissipation per channel operating in the bridge mode is four times that of a single-ended amplifier. From Equation (3), assuming a 5V power supply and a 4Ω load, the maximum single channel power dissipation is 1.27W or 2.54W for stereo operation. PDMAX = 4 * (VDD)2/(2π2RL) (5) For a typical application with a 5V power supply and an 4Ω load, the maximum ambient temperature that allows maximum stereo power dissipation without exceeding the maximum junction temperature is approximately 45˚C for the MH package. designing a Equation (2) for a singlevoltage and Single-Ended (4) 18 As an example when using a speaker with a low frequency limit of 150Hz, the input coupling capacitor, using Equation (7), is 0.053µF. The 0.33µF input coupling capacitor shown in Figure 2 allows the LM4936 to drive a high efficiency, full range speaker whose response extends below 30Hz. (Continued) the length of leads and traces that connect capacitors between the LM4936’s power supply pin and ground as short as possible. Connecting a 1µF capacitor, CB, between the BYPASS pin and ground improves the internal bias voltage’s stability and the amplifier’s PSRR. The PSRR improvements increase as the BYPASS pin capacitor value increases. Too large a capacitor, however, increases turn-on time and can compromise the amplifier’s click and pop performance. The selection of bypass capacitor values, especially CB, depends on desired PSRR requirements, click and pop performance (as explained in the following section, Selecting Proper External Components), system cost, and size constraints. OPTIMIZING CLICK AND POP REDUCTION PERFORMANCE The LM4936 contains circuitry that minimizes turn-on and shutdown transients or “clicks and pops”. For this discussion, turn-on refers to either applying the power supply voltage or when the shutdown mode is deactivated. While the power supply is ramping to its final value, the LM4936’s internal amplifiers are configured as unity gain buffers. An internal current source changes the voltage of the BYPASS pin in a controlled, linear manner. Ideally, the input and outputs track the voltage applied to the BYPASS pin. The gain of the internal amplifiers remains unity until the voltage on the BYPASS pin reaches 1/2 VDD . As soon as the voltage on the BYPASS pin is stable, the device becomes fully operational. Although the BYPASS pin current cannot be modified, changing the size of CB alters the device’s turn-on time and the magnitude of “clicks and pops”. Increasing the value of CB reduces the magnitude of turn-on pops. However, this presents a tradeoff: as the size of CB increases, the turn-on time increases. There is a linear relationship between the size of CB and the turn-on time. Below are some typical turn-on times for various values of CB: SELECTING PROPER EXTERNAL COMPONENTS Optimizing the LM4936’s performance requires properly selecting external components. Though the LM4936 operates well when using external components with wide tolerances, best performance is achieved by optimizing component values. The LM4936 is unity-gain stable, giving a designer maximum design flexibility. The gain should be set to no more than a given application requires. This allows the amplifier to achieve minimum THD+N and maximum signal-to-noise ratio. These parameters are compromised as the closed-loop gain increases. However, low gain circuits demand input signals with greater voltage swings to achieve maximum output power. Fortunately, many signal sources such as audio CODECs have outputs of 1VRMS (2.83VP-P). Please refer to the Audio Power Amplifier Design section for more information on selecting the proper gain. INPUT CAPACITOR VALUE SELECTION Amplifying the lowest audio frequencies requires a high value input coupling capacitor (0.33µF in Figure 2), but high value capacitors can be expensive and may compromise space efficiency in portable designs. In many cases, however, the speakers used in portable systems, whether internal or external, have little ability to reproduce signals below 150 Hz. Applications using speakers with this limited frequency response reap little improvement by using a large input capacitor. Besides affecting system cost and size, the input coupling capacitor has an effect on the LM4936’s click and pop performance. When the supply voltage is first applied, a transient (pop) is created as the charge on the input capacitor changes from zero to a quiescent state. The magnitude of the pop is directly proportional to the input capacitor’s size. Higher value capacitors need more time to reach a quiescent DC voltage (VDD/2) when charged with a fixed current. The amplifier’s output charges the input capacitor through the feedback resistor, Rf. Thus, pops can be minimized by selecting an input capacitor value that is no higher than necessary to meet the desired −6dB frequency. As shown in Figure 2, the input resistor (RIR, RIL = 20kΩ) and the input capacitor (CIR, CIL = 0.33µF) produce a −6dB high pass filter cutoff frequency that is found using Equation (7). (7) 19 www.national.com LM4936 Application Information LM4936 Application Information CB MICRO-POWER SHUTDOWN Shutdown mode is activated when a digital 0 is loaded into the Shutdown bit, B0. When active, the LM4936’s micropower shutdown feature turns off the amplifier’s bias circuitry reducing supply current to a typical 0.7µA. Loading a digital 1 into B0 disables shutdown mode. When the LM4936 has power applied, all register bits will have a default value of 0. Because of this, the LM4936 will be in shutdown mode when power is applied. (Continued) TON 0.01µF 2ms 0.1µF 20ms 0.22µF 44ms 0.47µF 94ms 1.0µF 200ms MODE FUNCTION The LM4936’s Mode function has two states controlled by bit B2. A digital 0 in bit B2 disables the volume control and forces the LM4936 to function as a fixed gain amplifier. The gain selection is determined by the GAIN SEL bit (B3) While in the fixed gain mode the volume setting has no effect on the output. When a digital 1 is loaded into B2 the output level is determined by the volume control bits. See Table 4 for volume settings. DOCKING STATION INTERFACE Applications such as notebook computers can take advantage of a docking station to connect to external devices such as monitors or audio/visual equipment that sends or receives line level signals. The LM4936 has two outputs, Right Dock and Left Dock, which connect to outputs of the internal input amplifiers that drive the volume control inputs. These input amplifiers can drive loads of > 1kΩ (such as powered speakers) with a rail-to-rail signal. Since the output signal present on the RIGHT DOCK and LEFT DOCK pins is biased to VDD/2, coupling capacitors should be connected in series with the load when using these outputs. Typical values for the output coupling capacitors are 0.33µF to 1.0µF. If polarized coupling capacitors are used, connect their "+" terminals to the respective output pin, see Figure 2. Since the DOCK outputs precede the internal volume control, the signal amplitude will be equal to the input signal’s magnitude and cannot be adjusted. However, the input amplifier’s closed-loop gain can be adjusted using external resistors. These 20kΩ (RDOCK1, RDOCK2) are shown in Figure 2 and they set each input amplifier’s gain to -1. Use Equation 8 to determine the input and feedback resistor values for a desired gain. (8) - AVR = RDOCK1/RIN1 and - AVL = RDOCK2/RIN2 Adjusting the input amplifier’s gain sets the minimum gain for that channel. Although the single ended output of the Bridge Output Amplifiers can be used to drive line level outputs, it is recommended that the R & L Dock Outputs simpler signal path be used for better performance. MUTE FUNCTION The LM4936 mutes the amplifier and DOCK outputs when a digital 1 is loaded in bit B1. Even while muted, the LM4936 will amplify a system alert (beep) signal whose magnitude satisfies the BEEP DETECT circuitry. Loading a digital 0 into B1 returns the LM4936 to normal operation. BEEP DETECT FUNCTION Computers and notebooks produce a system “beep“ signal that drives a small speaker. The speaker’s auditory output signifies that the system requires user attention or input. To accommodate this system alert signal, the LM4936’s beep input pin is a mono input that accepts the beep signal. Internal level detection circuitry at this input monitors the beep signal’s magnitude. When a signal level greater than VDD/2 is detected on the BEEP IN pin, the bridge output amplifiers are enabled. The beep signal is amplified and applied to the load connected to the output amplifiers. A valid beep signal will be applied to the load even when MUTE is active. Use the input resistors connected between the BEEP IN pin and the stereo input pins to accommodate different beep signal amplitudes. These resistors (RBEEP) are shown as 200kΩ values in Figure 2. Use higher value resistors to reduce the gain applied to the beep signal. The resistors must be used to pass the beep signal to the stereo inputs. The BEEP IN pin is used only to detect the beep signal’s magnitude: it does not pass the signal to the output amplifiers. The LM4936’s shutdown mode must be deactivated before a system alert signal is applied to BEEP IN pin. www.national.com 20117805 FIGURE 3. Headphone Sensing Circuit HP SENSE FUNCTION ( Headphone In ) Applying a voltage between the VIH threshold shown in the graph found in the Typical Performance Characteristics and VDD to the LM4936’s HP SENSE control pin or loading a digital 1 into the HP Control bit (B4) will change the output mode. The ’+’ outputs will change to be in phase with the ’-’ outputs instead of 180 degrees out of phase. This action mutes a bridged-connected load since the differential voltage across the load is now close to 0V. The HP SENSE pin over rides the HP Control bit. See Table 2 for more info. Quiescent current consumption is reduced when the IC is in this single-ended mode. Figure 3 shows the implementation of the LM4936’s headphone control function. With no headphones connected to the headphone jack, the R1-R2 voltage divider sets the 20 RBS, and a capacitor, CBS, in parallel, can be placed in series with the feedback resistor of the bridged amplifier as seen in Figure 2. (Continued) voltage applied to the HP SENSE pin at approximately 50mV. This 50mV puts the LM4936 into bridged mode operation. The output coupling capacitor blocks the amplifier’s half supply DC voltage, protecting the headphones. The HP SENSE threshold is set so the output signal cannot cause an output mode change. While the LM4936 operates in bridge mode, the DC potential across the load is essentially 0V. Connecting headphones to the headphone jack disconnects the headphone jack contact pin from R2 and allows R1 to pull the HP SENSE pin up to VDD through R4. This enables the headphone function and mutes the bridged speaker. The single-ended ’-’ outputs then drive the headphones, whose impedance is in parallel with resistors R2 and R3. These resistors have negligible effect on the LM4936’s output drive capability since the typical impedance of headphones is 32Ω. At low, frequencies CBS is a virtual open circuit and at high frequencies, its nearly zero ohm impedance shorts RBS. The result is increased bridge-amplifier gain at low frequencies. The combination of RBS and CBS form a -6dB corner frequency at fC = 1/(2πRBSCBS) (9) The bridged-amplifier low frequency differential gain is: AVD = 2(RF + RBS) / Ri Figure 3 also shows the suggested headphone jack electrical connections. The jack is designed to mate with a threewire plug. The plug’s tip and ring should each carry one of the two stereo output signals, whereas the sleeve should carry the ground return. A headphone jack with one control pin contact is sufficient to drive the HP-IN pin when connecting headphones. (10) Using the component values shown in Figure 2 (RF = 20kΩ, RBS = 20kΩ, and CBS = 0.068µF), a first-order, -6dB pole is created at 120Hz. Assuming R i = 20kΩ, the low frequency differential gain is 4V/V or 12dB. The input (Ci) and output (COUT) capacitor values must be selected for a low frequency response that covers the range of frequencies affected by the desired bass-boost operation. GAIN SELECT FUNCTION (Bass Boost) The LM4936 features selectable gain, using either internal or external feedback resistors. The GAIN SEL bit (B3) controls which gain is selected. Loading a digital 0 into the GAIN SEL bit sets the gain to internal resulting in a gain of 6dB for BTL mode or unity for singled-ended mode. Loading a digital 1 into the GAIN SEL bit sets the gain to be determined by the external resistors, RI and RF. In some cases a designer may want to improve the low frequency response of the bridged amplifier or incorporate a bass boost feature. This bass boost can be useful in systems where speakers are housed in small enclosures. A resistor, VOLUME CONTROL The LM4936 has an internal stereo volume control whose setting is a function of the digital values in the V4 – V0 bits. See Table 4. The LM4936 volume control consists of 31 steps that are individually selected. The range of the steps, are from 0dB 78dB. The gain levels are 1dB/step from 0dB to -6dB, 2dB/ step from -6dB to -36dB, 3dB/step from -36dB to -47dB, 4dB/step from -47dB to -51dB, 5dB/step from -51dB to -66dB, and 12dB to the last step at -78dB. 21 www.national.com LM4936 Application Information LM4936 Application Information (Continued) TABLE 4. Volume Control Table Serial Number V4 V3 V2 V1 V0 Gain (dB) 0 0 0 0 0 0 –90 1 0 0 0 0 1 –90 2 0 0 0 1 0 –68 3 0 0 0 1 1 –63 4 0 0 1 0 0 –57 5 0 0 1 0 1 –51 6 0 0 1 1 0 –47 7 0 0 1 1 1 –45 8 0 1 0 0 0 –42 –39 9 0 1 0 0 1 10 0 1 0 1 0 –36 11 0 1 0 1 1 –34 12 0 1 1 0 0 –32 13 0 1 1 0 1 –30 14 0 1 1 1 0 –28 15 0 1 1 1 1 –26 16 1 0 0 0 0 –24 17 1 0 0 0 1 –22 18 1 0 0 1 0 –20 19 1 0 0 1 1 –18 20 1 0 1 0 0 –16 21 1 0 1 0 1 –14 22 1 0 1 1 0 –12 23 1 0 1 1 1 –10 24 1 1 0 0 0 –8 25 1 1 0 0 1 –6 26 1 1 0 1 0 –5 27 1 1 0 1 1 –4 28 1 1 1 0 0 –3 29 1 1 1 0 1 –2 30 1 1 1 1 0 –1 31 1 1 1 1 1 0 www.national.com 22 Thus, a minimum overall gain of 2.83 allows the LM4936’s to reach full output swing and maintain low noise and THD+N performance. (Continued) AUDIO POWER AMPLIFIER DESIGN Audio Amplifier Design: Driving 1W into an 8Ω Load The last step in this design example is setting the amplifier’s −6dB frequency bandwidth. To achieve the desired ± 0.25dB pass band magnitude variation limit, the low frequency response must extend to at least one-fifth the lower bandwidth limit and the high frequency response must extend to at least five times the upper bandwidth limit. The gain variation for both response limits is 0.17dB, well within the ± 0.25dB desired limit. The results are an The following are the desired operational parameters: Power Output: 1 WRMS Load Impedance: 8Ω Input Level: 1 VRMS Input Impedance: Bandwidth: 20 kΩ 100 Hz−20 kHz ± 0.25 dB The design begins by specifying the minimum supply voltage necessary to obtain the specified output power. One way to find the minimum supply voltage is to use the Output Power vs Supply Voltage curve in the Typical Performance Characteristics section. Another way, using Equation (10), is to calculate the peak output voltage necessary to achieve the desired output power for a given load impedance. To account for the amplifier’s dropout voltage, two additional voltages, based on the Dropout Voltage vs Supply Voltage in the Typical Performance Characteristics curves, must be added to the result obtained by Equation (10). The result is Equation (11). (14) fH = 20kHz x 5 = 100kHz (15) and an As mentioned in the Selecting Proper External Components section, Ri (Right & Left) and Ci (Right & Left) create a highpass filter that sets the amplifier’s lower bandpass frequency limit. Find the input coupling capacitor’s value using Equation (14). (11) VDD ≥ (VOUTPEAK+ (VODTOP + VODBOT)) fL = 100Hz/5 = 20Hz Ci≥ 1/(2πRifL) (16) 1/(2π*20kΩ*20Hz) = 0.397µF (17) The result is (12) The Output Power vs Supply Voltage graph for an 8Ω load indicates a minimum supply voltage of 4.6V. This is easily met by the commonly used 5V supply voltage. The additional voltage creates the benefit of headroom, allowing the LM4936 to produce peak output power in excess of 1W without clipping or other audible distortion. The choice of supply voltage must also not create a situation that violates of maximum power dissipation as explained above in the Power Dissipation section. After satisfying the LM4936’s power dissipation requirements, the minimum differential gain needed to achieve 1W dissipation in an 8Ω load is found using Equation (12). Use a 0.39µF capacitor, the closest standard value. The product of the desired high frequency cutoff (100kHz in this example) and the differential gain AVD, determines the upper passband response limit. With AVD = 3 and fH = 100kHz, the closed-loop gain bandwidth product (GBWP) is 300kHz. This is less than the LM4936’s 3.5MHz GBWP. With this margin, the amplifier can be used in designs that require more differential gain while avoiding performance,restricting bandwidth limitations. (13) 23 www.national.com LM4936 Application Information LM4936 Application Information SPI TIMING DIAGRAM (Continued) 20117823 FIGURE 4. 6. ENABLE must be logic-low at least 50ns (tES ) before the first rising edge of CLK, and ENABLE has to remain logiclow at least 50ns (tEH ) after the eighth rising edge of CLK. 7. If ENABLE remains logic-high for more than 50ns before all 8 bits are transmitted then the data latch will be aborted. SPI OPERATIONAL REQUIREMENTS 1. The maximum clock rate is 5MHz for the CLK pin. 2. CLK must remain logic-high for at least 100ns (tCH ) after the rising edge of CLK, and CLK must remain logic-low for at least 100ns (tCL ) after the falling edge of CLK. 3. Data bits are written to the DATA pin with the most significant bit (MSB) first. 4. The serial data bits are sampled at the rising edge of CLK. Any transition on DATA must occur at least 50ns (tDS) before the rising edge of CLK. Also, any transition on DATA must occur at least 50ns (tDH) after the rising edge of CLK and stabilize before the next rising edge of CLK. 8. If ENABLE is logic-low for more than 8 CLK pulses then only the first 8 data bits will be latched and activated at rising edge of eighth CLK. 9. ENABLE must remain logic-high for at least 50ns (tEL ). 10. Coincidental rising or falling edges of CLK and ENABLE are not allowed. If CLK is to be held logic-high after the data transmission, the falling edge of CLK must occur at least 50ns (tCS ) before ENABLE transitions to logic-low for the next set of data. 5. ENABLE should be logic-low only during serial data transmission. www.national.com 24 LM4936 Application Information I2C TIMING DIAGRAMS (Continued) 20117895 FIGURE 5. I2C Bus Format 20117896 FIGURE 6. I2C Timing Diagram 25 www.national.com LM4936 LM4936 MH Exposed-DAP Board Artwork (Notes 8, 9) Composite View Silk Screen 20117844 20117847 Top Layer Internal Layer 1 20117848 20117845 Internal Layer 2 Bottom Layer 20117846 www.national.com 20117843 26 LM4936 LM4936 Board Bill of Materials Designator Value Tolerance Part Description RIN1, RIN2 20kΩ 1% 1/10W, 0805 Resistor RI1, RI2 20kΩ 1% 1/10W, 0805 Resistor RF1, RF2 20kΩ 1% 1/10W, 0805 Resistor RDOCK1, RDOCK2 20kΩ 1% 1/10W, 0805 Resistor RBS1, RBS2 20kΩ 1% 1/10W, 0805 Resistor RBEEP1, RBEEP2 200kΩ 1% 1/10W, 0805 Resistor RL1, RL2 1.5kΩ 1% 1/10W, 0805 Resistor RS, RPU 100kΩ 1% 1/10W, 0805 Resistor CIN1, CIN2, CIN3 0.33µF 10% 10V, Ceramic 1206 Capacitor CBS1, CBS2 0.068µF 10% 10V, Ceramic 1206 Capacitor CS1 10µF 10% 10V, Tantalum 1210 Capacitor CS2, CS3, CS4 0.1µF 10% 10V, Tantalum 1206 Capacitor CO1, CO2 1µF 10% 10V, Electrolytic 1210 Capacitor CB 1µF 10% 10V, Tantalum 1210 Capacitor COUT1, COUT2 220µF 10% 16V, Electrolytic 2220 Capacitor Comment J1 0.100 1x2 header, vertical mount Docking Outputs J2, J3, J4 RCA Input Jack, PCB Mount Mouser: 16PJ097 J5A Banana-Jack Red, Analog VDD Mouser: 164–6219 J5B Banana-Jack Blck, GND Mouser: 164–6218 J6A Banana-Jack Red, Right Out + Mouser: 164–6219 J6B Banana-Jack Black, Right Out - Mouser: 164–6218 J7A Banana-Jack Red, Left Out + Mouser: 164–6219 J7B Banana-Jack Black, Left Out - Mouser: 164–6218 J8 0.100” 2x3 header, vertical mount I2C/SPI Inputs J9 3.5mm Stereo Headphone Jack Shogyo: SJS–0354–5P J10 0.100” 1x3 header, vertical mount Digital Select J11 Banana Jack — Red, Digital VDD Mouser: 164–6219 27 www.national.com LM4936 Stereo 2W Audio Power Amplifiers with Volume Control and Selectable Control Interface (SPI or I2C) Physical Dimensions inches (millimeters) unless otherwise noted Exposed-DAP TSSOP Package Order Number LM4936MH NS Package Number MXA28A for Exposed-DAP TSSOP National does not assume any responsibility for use of any circuitry described, no circuit patent licenses are implied and National reserves the right at any time without notice to change said circuitry and specifications. For the most current product information visit us at www.national.com. LIFE SUPPORT POLICY NATIONAL’S PRODUCTS ARE NOT AUTHORIZED FOR USE AS CRITICAL COMPONENTS IN LIFE SUPPORT DEVICES OR SYSTEMS WITHOUT THE EXPRESS WRITTEN APPROVAL OF THE PRESIDENT AND GENERAL COUNSEL OF NATIONAL SEMICONDUCTOR CORPORATION. As used herein: 1. Life support devices or systems are devices or systems which, (a) are intended for surgical implant into the body, or (b) support or sustain life, and whose failure to perform when properly used in accordance with instructions for use provided in the labeling, can be reasonably expected to result in a significant injury to the user. 2. A critical component is any component of a life support device or system whose failure to perform can be reasonably expected to cause the failure of the life support device or system, or to affect its safety or effectiveness. BANNED SUBSTANCE COMPLIANCE National Semiconductor manufactures products and uses packing materials that meet the provisions of the Customer Products Stewardship Specification (CSP-9-111C2) and the Banned Substances and Materials of Interest Specification (CSP-9-111S2) and contain no ‘‘Banned Substances’’ as defined in CSP-9-111S2. National Semiconductor Americas Customer Support Center Email: [email protected] Tel: 1-800-272-9959 www.national.com National Semiconductor Europe Customer Support Center Fax: +49 (0) 180-530 85 86 Email: [email protected] Deutsch Tel: +49 (0) 69 9508 6208 English Tel: +44 (0) 870 24 0 2171 Français Tel: +33 (0) 1 41 91 8790 National Semiconductor Asia Pacific Customer Support Center Email: [email protected] National Semiconductor Japan Customer Support Center Fax: 81-3-5639-7507 Email: [email protected] Tel: 81-3-5639-7560