a FEATURES 16-Bit Monotonicity over Temperature ⴞ2 LSBs Integral Linearity Error Microprocessor Compatible with Readback Capability Unipolar or Bipolar Output Multiplying Capability Low Power (100 mW Typical) LC2MOS 16-Bit Voltage Output DAC AD7846 FUNCTIONAL BLOCK DIAGRAM VCC VREF + AD7846 R VDD R A2 RIN R R 16 SEGMENT SWITCH MATRIX R A3 A1 VREF – VOUT 12-BIT DAC 12 CS DAC LATCH 4 12 CONTROL LOGIC R/ W LDAC I/O LATCH CLR VSS DB15 DB0 DGND GENERAL DESCRIPTION PRODUCT HIGHLIGHTS The AD7846 is a 16-bit DAC constructed with Analog Devices’ LC2MOS process. It has VREF+ and VREF– reference inputs and an on-chip output amplifier. These can be configured to give a unipolar output range (0 V to +5 V, 0 V to +10 V) or bipolar output ranges (± 5 V, ± 10 V). 1. 16-Bit Monotonicity The guaranteed 16-bit monotonicity over temperature makes the AD7846 ideal for closed-loop applications. The DAC uses a segmented architecture. The 4 MSBs in the DAC latch select one of the segments in a 16-resistor string. Both taps of the segment are buffered by amplifiers and fed to a 12-bit DAC, which provides a further 12 bits of resolution. This architecture ensures 16-bit monotonicity. Excellent integral linearity results from tight matching between the input offset voltages of the two buffer amplifiers. 2. Readback The ability to read back the DAC register contents minimizes software routines when the AD7846 is used in ATE systems. 3. Power Dissipation Power dissipation of 100 mW makes the AD7846 the lowest power, high accuracy DAC on the market. In addition to the excellent accuracy specifications, the AD7846 also offers a comprehensive microprocessor interface. There are 16 data I/O pins, plus control lines (CS, R/W, LDAC and CLR). R/W and CS allow writing to and reading from the I/O latch. This is the readback function which is useful in ATE applications. LDAC allows simultaneous updating of DACs in a multiDAC system and the CLR line will reset the contents of the DAC latch to 00 . . . 000 or 10 . . . 000 depending on the state of R/W. This means that the DAC output can be reset to 0 V in both the unipolar and bipolar configurations. The AD7846 is available in 28-lead plastic, ceramic, and PLCC packages. REV. E Information furnished by Analog Devices is believed to be accurate and reliable. However, no responsibility is assumed by Analog Devices for its use, nor for any infringements of patents or other rights of third parties which may result from its use. No license is granted by implication or otherwise under any patent or patent rights of Analog Devices. One Technology Way, P.O. Box 9106, Norwood, MA 02062-9106, U.S.A. Tel: 781/329-4700 World Wide Web Site: http://www.analog.com Fax: 781/326-8703 © Analog Devices, Inc., 2000 (VDD = +14.25 V to +15.75 V; VSS = –14.25 V to –15.75 V; VCC = +4.75 V to +5.25 V. 1 VOUT loaded with 2 k⍀, 1000 pF to 0 V; VREF+ = +5 V; RIN connected to 0 V. All AD7846–SPECIFICATIONS specifications TMIN to TMAX, unless otherwise noted.) Parameter J, A Versions K, B Versions Unit RESOLUTION 16 16 Bits UNIPOLAR OUTPUT Relative Accuracy @ +25°C TMIN to TMAX Differential Nonlinearity Error Gain Error @ +25°C TMIN to TMAX Offset Error @ +25°C TMIN to TMAX Gain TC2 Offset TC2 ± 12 ± 16 ±1 ± 12 ± 16 ± 12 ± 16 ±1 ±1 ±4 ±8 ± 0.5 ±6 ± 16 ±6 ± 16 ±1 ±1 LSB typ LSB max LSB max LSB typ LSB max LSB typ LSB max ppm FSR/°C typ ppm FSR/°C typ BIPOLAR OUTPUT Relative Accuracy @ +25°C TMIN to TMAX Differential Nonlinearity Error Gain Error @ +25°C TMIN to TMAX Offset Error @ +25°C TMIN to TMAX Bipolar Zero Error @ +25°C TMIN to TMAX Gain TC2 Offset TC2 Bipolar Zero TC2 ±6 ±8 ±1 ±6 ± 16 ±6 ± 16 ±6 ± 12 ±1 ±1 ±1 ±2 ±4 ± 0.5 ±4 ± 16 ±4 ± 12 ±4 ±8 ±1 ±1 ±1 LSB typ LSB max LSB max LSB typ LSB max LSB typ LSB max LSB typ LSB max ppm FSR/°C typ ppm FSR/°C typ ppm FSR/°C typ 20 40 VSS + 6 to VDD – 6 VSS + 6 to VDD – 6 20 40 VSS + 6 to VDD – 6 VSS + 6 to VDD – 6 kΩ min kΩ max Volts VSS + 4 to VDD – 3 2 1000 0.3 ± 25 VSS + 4 to VDD – 3 2 1000 0.3 ± 25 V max kΩ min pF max Ω typ mA typ DIGITAL INPUTS VIH (Input High Voltage) VIL (Input Low Voltage) IIN (Input Current) CIN (Input Capacitance)2 2.4 0.8 ± 10 10 2.4 0.8 ± 10 10 V min V max µA max pF max DIGITAL OUTPUTS VOL (Output Low Voltage) VOH (Output High Voltage) Floating State Leakage Current Floating State Output Capacitance2 0.4 4.0 ± 10 10 0.4 4.0 ± 10 10 Volts max Volts min µA max pF max POWER REQUIREMENTS3 VDD VSS VCC IDD ISS ICC Power Supply Sensitivity4 Power Dissipation +11.4/+15.75 –11.4/–15.75 +4.75/+5.25 5 5 1 1.5 100 +11.4/+15.75 –11.4/–15.75 +4.75/+5.25 5 5 1 1.5 100 V min/V max V min/V max V min/V max mA max mA max mA max LSB/V max mW typ REFERENCE INPUT Input Resistance VREF+ Range VREF– Range OUTPUT CHARACTERISTICS Output Voltage Swing Resistive Load Capacitive Load Output Resistance Short Circuit Current Test Conditions/Comments VREF – = 0 V, VOUT = 0 V to +10 V 1 LSB = 153 µV All Grades Guaranteed Monotonic VOUT Load = 10 MΩ VREF– = –5 V, VOUT = –10 V to +10 V 1 LSB = 305 µV All Grades Guaranteed Monotonic VOUT Load = 10 MΩ VOUT Load = 10 MΩ Resistance from VREF+ to VREF – Typically 30 kΩ Volts To 0 V To 0 V To 0 V or Any Power Supply ISINK = 1.6 mA ISOURCE = 400 µA DB0–DB15 = 0 to VCC VOUT Unloaded VOUT Unloaded VOUT Unloaded NOTES 1 Temperature ranges as follows: J, K Versions: 0°C to +70°C; A, B Versions: –40°C to +85°C 2 Guaranteed by design and characterization, not production tested. 3 The AD7846 is functional with power supplies of ± 12 V. See Typical Performance Curves. 4 Sensitivity of Gain Error, Offset Error and Bipolar Zero Error to V DD, VSS variations. Specifications subject to change without notice. –2– REV. E AD7846 AC PERFORMANCE CHARACTERISTICS These characteristics are included for design guidance and are not subject to test. (VREF+ = +5 V; VDD = +14.25 V to +15.75 V; VSS = –14.25 V to –15.75 V; VCC = +4.75 V to +5.25 V; RIN connected to 0 V.) Limit at TMIN to TMAX (All Versions) Unit Test Conditions/Comments µs max µs max V/µs typ To 0.006% FSR. VOUT loaded. VREF– = 0 V. Typically 3.5 µs. To 0.003% FSR. VOUT loaded. VREF– = –5 V. Typically 6.5 µs. Slew Rate Digital-to-Analog Glitch Impulse 6 9 7 70 nV-secs typ AC Feedthrough 0.5 mV pk-pk typ Digital Feedthrough Output Noise Voltage Density 1 kHz–100 kHz 10 nV-secs typ DAC alternately loaded with 10 . . . 0000 and 01 . . . 1111. VOUT unloaded. VREF– = 0 V, VREF+ = 1 V rms, 10 kHz sine wave. DAC loaded with all 0s. DAC alternately loaded with all 1s and all 0s. CS High. 50 nV/√Hz typ Parameter 1 Output Settling Time Measured at VOUT. DAC loaded with 0111011 . . . 11. VREF+ = VREF– = 0 V. NOTES 1 LDAC = 0. Settling time does not include deglitching time of 2.5 µs (typ). Specifications subject to change without notice. TIMING CHARACTERISTICS (VDD = +14.25 V to +15.75 V; VSS = –14.25 V to –15.75 V; VCC = +4.75 V to +5.25 V) Parameter Limit at TMIN to TMAX (All Versions) Unit Test Conditions/Comments t1 t2 t3 t4 t5 t6 t7 0 60 0 60 0 120 10 60 0 70 0 70 130 ns min ns min ns min ns min ns min ns max ns min ns max ns min ns min ns min ns min ns min R/W to CS Setup Time CS Pulsewidth (Write Cycle) R/W to CS Hold Time Data Setup Time Data Hold Time Data Access Time Bus Relinquish Time t8 t9 t10 t11 t12 CLR Setup Time CLR Pulsewidth CLR Hold Time LDAC Pulsewidth CS Pulsewidth (Read Cycle) NOTES 1 Timing specifications are sample tested at +25°C to ensure compliance. All input control signals are specified with t R = tF = 5 ns (10% to 90% of +5 V) and timed from a voltage level of 1.6 V. 2 t6 is measured with the load circuits of Figure 1 and defined as the time required for an output to cross 0.8 V or 2.4 V. 3 t7 is defined as the time required for an output to change 0.5 V when loaded with the circuits of Figure 2. Specifications subject to change without notice. 5V 3k⍀ DBN DBN 3k⍀ 100pF 100pF t1 DGND DGND t3 t1 t3 5V R/ W a. High Z to VOH 0V b. High Z to VOL t4 5V DGND a. VOH to High Z 10pF 10pF 0V t7 t9 DATA VALID t 10 t8 tt99 0V t 10 5V CLR DGND t 11 LDAC b. VOL to High Z Figure 2. Load Circuits for Bus Relinquish Time (t7) REV. E t6 DATA VALID t8 DBN t5 5V DATA 3k⍀ 3k⍀ 5V CS Figure 1. Load Circuits for Access Time (t6) DBN t 12 t2 5V 0V Figure 3. Timing Diagram –3– 0V AD7846 ABSOLUTE MAXIMUM RATINGS 1 NOTES 1 Stresses above those listed under Absolute Maximum Ratings may cause permanent damage to the device. This is a stress rating only; functional operation of the device at these or any other conditions above those indicated in the operational sections of this specification is not implied. Exposure to absolute maximum rating conditions for extended periods may affect device reliability. Only one Absolute Maximum Rating may be applied at any one time. 2 V OUT may be shorted to DGND, V DD, VSS, VCC provided that the power dissipation of the package is not exceeded. VDD to DGND . . . . . . . . . . . . . . . . . . . . . . . . . –0.4 V to +17 V VCC to DGND . . . . . . . . . . . . . . . –0.4 V, VDD + 0.4 V or +7 V (Whichever Is Lower) VSS to DGND . . . . . . . . . . . . . . . . . . . . . . . . . +0.4 V to –17 V VREF+ to DGND . . . . . . . . . . . . . . . . VDD + 0.4 V, VSS – 0.4 V VREF– to DGND . . . . . . . . . . . . . . . . VDD + 0.4 V, VSS – 0.4 V VOUT to DGND2 . . . . . . . . VDD + 0.4 V, VSS – 0.4 V or ± 10 V (Whichever Is Lower) RIN to DGND . . . . . . . . . . . . . . . . . . VDD + 0.4 V, VSS – 0.4 V Digital Input Voltage to DGND . . . . . . –0.4 V to VCC + 0.4 V Digital Output Voltage to DGND . . . . . –0.4 V to VCC + 0.4 V Power Dissipation (Any Package) To +75°C . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 1000 mW Derates above +75°C . . . . . . . . . . . . . . . . . . . . . 10 mW/°C Operating Temperature Range J, K Versions . . . . . . . . . . . . . . . . . . . . . . . . . 0°C to +70°C A, B Versions . . . . . . . . . . . . . . . . . . . . . . . –25°C to +85°C Storage Temperature Range . . . . . . . . . . . . –65°C to +150°C Lead Temperature (Soldering) . . . . . . . . . . . . . . . . . . +300°C ORDERING GUIDE Model Temperature Range Relative Accuracy Package Description Package Options AD7846JN AD7846KN AD7846JP AD7846KP AD7846AP AD7846AQ AD7846BP 0°C to +70°C 0°C to +70°C 0°C to +70°C 0°C to +70°C –40°C to +85°C –40°C to +85°C –40°C to +85°C ± 16 LSB ± 8 LSB ± 16 LSB ± 8 LSB ± 16 LSB ± 16 LSB ± 8 LSB Plastic DIP Plastic DIP Plastic Leaded Chip Carrier (PLCC) Plastic Leaded Chip Carrier (PLCC) Plastic Leaded Chip Carrier (PLCC) Ceramic DIP Plastic Leaded Chip Carrier (PLCC) N-28A N-28A P-28A P-28A P-28A Q-28 P-28A CAUTION ESD (electrostatic discharge) sensitive device. The digital control inputs are diode protected; however, permanent damage may occur on unconnected devices subject to high energy electrostatic fields. Unused devices must be stored in conductive foam or shunts. The protective foam should be discharged to the destination socket before devices are removed. WARNING! ESD SENSITIVE DEVICE Offset Error TERMINOLOGY LEAST SIGNIFICANT BIT This is the analog weighting of 1 bit of the digital word in a DAC. For the AD7846, 1 LSB = (VREF+ – VREF–)/216. This is the error present at the device output with all 0s loaded in the DAC. It is due to op amp input offset voltage and bias current and the DAC leakage current. Relative Accuracy Bipolar Zero Error Relative accuracy or endpoint nonlinearity is a measure of the maximum deviation from a straight line passing through the endpoints of the DAC transfer function. It is measured after adjusting for both endpoints (i.e., offset and gain errors are adjusted out) and is normally expressed in least significant bits or as a percentage of full-scale range. When the AD7846 is connected for bipolar output and 10 . . . 000 is loaded to the DAC, the deviation of the analog output from the ideal midscale of 0 V is called the bipolar zero error. Digital-to-Analog Glitch Impulse This is the amount of charge injected from the digital inputs to the analog output when the inputs change state. This is normally specified as the area of the glitch in either pA-secs or nV-secs depending upon whether the glitch is measured as a current or a voltage. Differential Nonlinearity Differential nonlinearity is the difference between the measured change and the ideal change between any two adjacent codes. A specified differential nonlinearity of ± 1 LSB over the operating temperature range ensures monotonicity. Multiplying Feedthrough Error This is an ac error due to capacitive feedthrough from either of the VREF terminals to VOUT when the DAC is loaded with all 0s. Gain Error Digital Feedthrough Gain error is a measure of the output error between an ideal DAC and the actual device output with all 1s loaded after offset error has been adjusted out. Gain error is adjustable to zero with an external potentiometer. When the DAC is not selected (i.e., CS is held high), high frequency logic activity on the digital inputs is capacitively coupled through the device to show up as noise on the VOUT pin. This noise is digital feedthrough. –4– REV. E AD7846 PIN FUNCTION DESCRIPTION PIN CONFIGURATIONS DIP DB2 1 28 DB3 DB1 2 27 DB4 DB0 3 26 DB5 VDD 4 25 LDAC VOUT 5 24 CLR 23 CS RIN 6 AD7846 VREF+ 7 22 R/W TOP VIEW VREF– 8 (Not to Scale) 21 VCC VSS 9 20 DGND DB15 10 19 DB6 DB14 11 18 DB7 DB13 12 17 DB8 DB12 13 16 DB9 DB11 14 15 DB10 Pin Mnemonic Description 1–3 4 DB2–DB0 VDD 5 6 VOUT RIN 7 VREF+ 8 VREF– 9 VSS Data I/O pins. DB0 is LSB. Positive supply for analog circuitry. This is +15 V nominal. DAC output voltage pin. Input to summing resistor of DAC output amplifier. This is used to select output voltage ranges. See Table I. VREF+ Input. The DAC is specified for VREF+ = +5 V. VREF– Input. For unipolar operation connect VREF– to 0 V and for bipolar operation connect it to –5 V. The device is specified for both conditions. Negative supply for the analog circuitry. This is –15 V nominal. Data I/O pins. DB15 is MSB. Ground pin for digital circuitry. Positive supply for digital circuitry. This is +5 V nominal. R/W input. This can be used to load data to the DAC or to read back the DAC latch contents. Chip select input. This selects the device. Clear input. The DAC can be cleared to 000 . . . 000 or 100 . . . 000. See Table II. 10–19 DB15–DB6 20 DGND 21 VCC 2 1 VOUT 5 28 27 26 PIN 1 IDENTIFIER RIN 6 REV. E 25 LDAC 24 CLR VREF+ 7 AD7846 23 CS VREF– 8 TOP VIEW 22 R/W VSS 9 (Not to Scale) 12 13 14 15 16 17 18 DB7 DB6 DB9 19 DB8 DB14 11 DB11 DGND DB10 VCC 20 DB13 21 DB15 10 DB12 22 R/W 23 24 CS CLR 25 LDAC DB5 3 DB3 DB1 DB2 4 DB4 VDD DB0 PLCC Asynchronous load input to DAC. 26–28 DB5–DB3 Data I/O pins. Table I. Output Voltage Ranges –5– Output Range VREF+ VREF– RIN 0 V to +5 V 0 V to +10 V +5 V to –5 V +5 V to –5 V +10 V to –10 V +5 V +5 V +5 V +5 V +5 V 0V 0V –5 V 0V –5 V VOUT 0V VOUT +5 V 0V AD7846–Typical Performance Curves 8 30 VDD = +15V VSS = –15V VREF+ = +1Vrms VREF– = 0V VOUT – V p-p VOUT – mV p-p 6 4 VDD = +15V VSS = –15V VREF+ = ⴞ5V SINE WAVE VREF– = 0V GAIN = +2 20 10 2 0 102 Figure 4. AC Feedthrough. VREF+ = 1 V rms, 10 kHz Sine Wave 103 104 105 FREQUENCY – Hz 106 Figure 5. AC Feedthrough vs. Frequency 0 101 102 103 104 105 FREQUENCY – Hz 106 107 Figure 6. Large Signal Frequency Response NOISE SPECTRAL DENSITY – nV/冪Hz 500 VREF+ = VREF– = 0V GAIN = +1 DAC LOADED WITH ALL 1s 400 50mV/DIV VOUT VOUT 50mV/DIV 300 LDAC 200 100 DATA 0 102 103 104 105 FREQUENCY – Hz Figure 7. Noise Spectral Density Figure 10. Pulse Response (Large Signal) 106 5V/DIV 5V/DIV DATA 5V/DIV 0.5s/DIV 1s/DIV Figure 8. Digital-to-Analog Glitch Impulse Without Internal Deglitcher (10 . . . 000 to 011 . . . 111 Transition) Figure 9. Digital-to-Analog Glitch Impulse With Internal Deglitcher (10 . . . 000 to 011 . . . 111 Transition) Figure 11. Pulse Response (Small Signal) –6– Figure 12. Spectral Response of Digitally Constructed Sine Wave REV. E AD7846 1.0 4.0 TA = +25ⴗC VREF+ = +5V VREF– = 0V GAIN = +1 3.5 0.8 DNL – LSBs INL – LSBs 3.0 TA = +25ⴗC VREF+ = +5V VREF– = 0V GAIN = +1 2.5 2.0 0.6 0.4 1.5 0.2 1.0 0 0.5 11 12 13 14 VDD/VSS – Volts 15 11 16 12 13 14 VDD/VSS – Volts 15 16 Figure 14. Typical Monotonicity vs. VDD/VSS Figure 13. Typical Linearity vs. VDD/VSS Table II. Control Logic Truth Table CIRCUIT DESCRIPTION Digital Section Figure 15 shows the digital control logic and on-chip data latches in the AD7846. Table II is the associated truth table. The D/A converter has two latches that are controlled by four signals: CS, R/W, LDAC and CLR. The input latch is connected to the data bus (DB15–DB0). A word is written to the input latch by bringing CS low and R/W low. The contents of the input latch may be read back by bringing CS low and R/W high. This feature is called “readback” and is used in system diagnostic and calibration routines. CS R/W LDAC CLR Function 1 X X X 0 0 X X 0 1 X X X X 0 1 Data is transferred from the input latch to the DAC latch with the LDAC strobe. The equivalent analog value of the DAC latch contents appears at the DAC output. The CLR pin resets the DAC latch contents to 000 . . . 000 or 100 . . . 000, depending on the state of R/W. Writing a CLR loads 000 . . . 000 and reading a CLR loads 100 . . . 000. To reset a DAC to 0 V in a unipolar system the user should exercise CLR while R/W is low; to reset to 0 V in a bipolar system exercise the CLR while R/W is high. X 0 X 0 X 1 X 0 3-State DAC I/O Latch in HighZ State DAC I/O Latch Loaded with DB15–DB0 Contents of DAC I/O Latch Available on DB15–DB0 Contents of DAC I/O Latch Transferred to DAC Latch DAC Latch Loaded with 000 . . . 000 DAC Latch Loaded with 100 . . . 000 D/A Conversion Figure 16 shows the D/A section of the AD7846. There are three DACs, each of which have their own buffer amplifiers. DAC1 and DAC2 are 4-bit DACs. They share a 16-resistor string but have their own analog multiplexers. The voltage reference is applied to the resistor string. DAC3 is a 12-bit voltage mode DAC with its own output stage. R/W CLR The 4 MSBs of the 16-bit digital code drive DAC1 and DAC2 while the 12 LSBs control DAC3. Using DAC1 and DAC2, the MSBs select a pair of adjacent nodes on the resistor string and present that voltage to the positive and negative inputs of DAC3. This DAC interpolates between these two voltages to produce the analog output voltage. DAC 16 DB15 RST DB15 SET DB14–DB0 RST DB15–DB0 LATCHES LDAC To prevent nonmonotonicity in the DAC due to amplifier offset voltages, DAC1 and DAC2 “leap-frog” along the resistor string. For example, when switching from Segment 1 to Segment 2, DAC1 switches from the bottom of Segment 1 to the top of Segment 2 while DAC2 stays connected to the top of Segment 1. The code driving DAC3 is automatically complemented to compensate for the inversion of its inputs. This means that any linearity effects due to amplifier offset voltages remain unchanged when switching from one segment to the next and 16-bit monotonicity is ensured if DAC3 is monotonic. So, 12-bit resistor matching in DAC3 guarantees overall 16-bit monotonicity. This is much more achievable than the 16-bit matching which a conventional R-2R structure would have needed. 16 CS 3-STATE I/O LATCH 16 DB15 DB0 Figure 15. Input Control Logic REV. E –7– AD7846 VREF+ SEGMENT 16 DAC1 R DAC2 S1 S2 S3 RIN R DAC3 S4 A1 VOUT A3 12 BIT DAC S15 S14 S17 S16 A2 DB15–DB12 DB11–DB0 DB15–DB12 SEGMENT 1 VREF– Figure 16. D/A Conversion Output Stage The output stage of the AD7846 is shown in Figure 17. It is capable of driving a 2 kΩ/1000 pF load. It also has a resistor feedback network which allows the user to configure it for gains of one or two. Table I shows the different output ranges that are possible. 4 VDD VCC R1 10k⍀ C1 1F VOUT AD7846* VREF– VOUT (0V TO +10V) RIN DGND VSS SIGNAL GROUND *ADDITIONAL PINS OMITTED FOR CLARITY –15V Figure 18. Unipolar Binary Operation Table III. Code Table for Figure 18 RIN 10k⍀ +5V VREF+ AD586 An additional feature is that the output buffer is configured as a track-and-hold amplifier. Although normally tracking its input, this amplifier is placed in a hold mode for approximately 2.5 µs after the leading edge of LDAC. This short state keeps the DAC output at its previous voltage while the AD7846 is internally changing to its new value. So, any glitches that occur in the transition are not seen at the output. In systems where the LDAC is tied permanently low, the deglitching will not be in operation. Figures 8 and 9 show the outputs of the AD7846 without and with the deglitcher. +15V 10k⍀ C1 VOUT DAC3 ONE SHOT Binary Number in DAC Latch Analog Output (VOUT) MSB LSB 1111 1111 1111 1111 1000 0000 0000 0000 0000 0000 0000 0001 0000 0000 0000 0000 +10 (65535/65536) V +10 (32768/65536) V +10 (1/65536) V 0 NOTE 1 LSB = 10 V/216 = 10 V/65536 = 152 µV. LDAC Offset and gain may be adjusted in Figure 18 as follows: To adjust offset, disconnect the VREF– input from 0 V, load the DAC with all 0s and adjust the VREF– voltage until VOUT = 0 V. For gain adjustment, the AD7846 should be loaded with all 1s and R1 adjusted until VOUT = 10 (65535)/(65536) = 9.999847 V. If a simple resistor divider is used to vary the VREF– voltage, it is important that the temperature coefficients of these resistors match that of the DAC input resistance (–300 ppm/°C). Otherwise, extra offset errors will be introduced over temperature. Many circuits will not require these offset and gain adjustments. In these circuits, R1 can be omitted. Pin 5 of the AD586 may be left open circuit and Pin 8 (VREF– ) of the AD7846 tied to 0 V. Figure 17. Output Stage UNIPOLAR BINARY OPERATION Figure 18 shows the AD7846 in the unipolar binary circuit configuration. The DAC is driven by the AD586, +5 V reference. Since RIN is tied to 0 V, the output amplifier has a gain of 2 and the output range is 0 V to +10 V. If a 0 V to +5 V range is required, RIN should be tied to VOUT, configuring the output stage for a gain of 1. Table III gives the code table for the circuit of Figure 18. –8– REV. E AD7846 BIPOLAR OPERATION Other Output Voltage Ranges Figure 19 shows the AD7846 set up for ± 10 V bipolar operation. The AD588 provides precision ± 5 V tracking outputs which are fed to the VREF+ and VREF– inputs of the AD7846. The code table for Figure 19 is shown in Table IV. In some cases, users may require output voltage ranges other than those already mentioned. One example is systems which need the output voltage to be a whole number of millivolts (i.e., 1 mV, 2 mV, etc.). If the AD689 (8.192 V reference) is used with the AD7846 as in Figure 20, then the LSB size is 125 µV. This makes it possible to program whole millivolt values at the Output. Table V shows the code table for Figure 20. +15V +15V +5V 4 VDD VCC VREF+ VOUT R1 39k⍀ +15V C1 1F AD588 R2 10k⍀ VOUT (–10V TO +10V) AD7846* RIN VREF– +5V VDD VCC VOUT VREF+ AD689 AD7846* DGND SIGNAL GROUND –15V VSS VREF– SIGNAL GROUND R3 100k⍀ –15V *ADDITIONAL PINS OMITTED FOR CLARITY *ADDITIONAL PINS OMITTED FOR CLARITY Figure 19. Bipolar ± 10 V Operation Binary Number in DAC Latch Analog Output (VOUT) MSB LSB 1111 1111 1111 1111 1000 0000 0000 0001 1000 0000 0000 0000 0111 1111 1111 1111 0000 0000 0000 0000 +10 (32767/32768) V +10 (1/32768) V 0V –10 (1/32768) V –10 (32768/32768) V VSS VOUT (0V TO 8.192V) RIN DGND –15V Figure 20. Unipolar Output with AD689 Table IV. Offset Binary Code Table for Figure 19 Table V. Code Table for Figure 20 NOTE 1 LSB = 10 V/215 = 10 V/32768 = 305 µV. Binary Number in DAC Latch Analog Output (VOUT) MSB LSB 1111 1111 1111 1111 1000 0000 0000 0000 0000 0000 0000 1000 0000 0000 0000 0100 0000 0000 0000 0010 0000 0000 0000 0001 8.192 V (65535/65536) = 8.1919 V 8.192 V (32768/65536) = 4.096 V 8.192 V (8/65536) = 0.001 V 8.192 V (4/65536) = 0.0005 V 8.192 V (2/65536) = 0.00025 V 8.192 V (1/65536) = 0.000125 V NOTE 1 LSB = 8.192 V/2l6 = 125 µV. Full scale and bipolar zero adjustment are provided by varying the gain and balance on the AD588. R2 varies the gain on the AD588 while R3 adjusts the +5 V and –5 V outputs together with respect to ground. Multiplying Operation The AD7846 is a full multiplying DAC. To get four-quadrant multiplication, tie VREF– to 0 V, apply the ac input to VREF+ and tie RIN to VREF+. Figure 6 shows the Large Signal Frequency Response when the DAC is used in this fashion. For bipolar zero adjustment on the AD7846, load the DAC with 100 . . . 000 and adjust R3 until VOUT = 0 V. Full scale is adjusted by loading the DAC with all 1s and adjusting R2 until VOUT = 9.999694 V. When bipolar zero and full scale adjustment are not needed, R2 and R3 can be omitted, Pin 12 on the AD588 should be connected to Pin 11 and Pin 5 should be left floating. If a user wants a +5 V output range, there are two choices. By tying Pin 6 (RIN) of the AD7846 to VOUT (Pin 5), the output stage gain is reduced to unity and the output range is ± 5 V. If only a positive +5 V reference is available, bipolar ± 5 V operation is still possible. Tie VREF– to 0 V and connect RIN to VREF+. This will also give a ± 5 V output range. However, the linearity, gain, and offset error specifications will be the same as the unipolar 0 V to +5 V range. REV. E +15V –9– AD7846 TEST APPLICATION input or output. The AD345 is the pin driver for the digital inputs, and the AD9687 is the receiver for the digital outputs. The digital control circuitry determines the signal timing and format. Figure 21 shows the AD7846 in an Automatic Test Equipment application. The readback feature of the AD7846 is very useful in these systems. It allows the designer to eliminate phantom memory used for storing DAC contents and increases system reliability since the phantom memory is now effectively on chip with the DAC. The readback feature is used in the following manner to control a data transfer. First, write the desired 16-bit word to the DAC input latch using the CS and R/W inputs. Verify that correct data has been received by reading back the latch contents. Now, the data transfer can be completed by bringing the asynchronous LDAC control line low. The analog equivalent of the digital word now appears at the DAC output. In Figure 21, each pin on the Device Under Test can be an DACs 1 and 2 set the pin driver voltage levels (VH and VL), and DACs 3 and 4 set the receiver voltage levels. The pin drivers used in ATE systems normally have a nonlinearity between input and output. The 16-bit resolution of the AD7846 allows compensation for these input/output nonlinearities. The dc parametrics shown in Figure 21 measure the voltage at the device pin and feed this back to the system processor. The pin voltage can thus be fine-tuned by incrementing or decrementing DACs 1 and 2 under system processor control. DC PARAMETRICS VH STORED DATA AND INHIBIT PATTERN FORMATTER PERIOD GENERATION AND DELAY COMPARE DATA AND DON'T CARE DATA D D INH INH VL DUT AD345 COMPARE REGISTER AD9687 +15V R1 39k⍀ DAC1 DAC2 DAC3 DAC4 AD7846 AD7846 AD7846 AD7846 VOUT VREF+ AD588 VOUT VREF+ VOUT VREF+ VOUT VREF+ RIN RIN RIN RIN VREF– DGND VREF– DGND VREF– DGND VREF– DGND DB15 DB0 DB15 DB0 DB15 DB0 DB15 DB0 –15V Figure 21. Digital Test System with 16-Bit Performance –10– REV. E AD7846 POSITION MEASUREMENT APPLICATION Figure 22 shows the AD7846 in a position measurement application using an LVDT (Linear Variable Displacement Transducer), an AD630 synchronous demodulator and a comparator to make a 16-bit LVDT-to-Digital Converter. The LVDT is excited with a fixed frequency and fixed amplitude sine wave (usually 2.5 kHz, 2 V pk-pk). The outputs of the secondary coil are in antiphase and their relative amplitudes depend on the position of the core in the LVDT. The AD7846 output interpolates between these two inputs in response to the DAC input code. The AD630 is set up so that it rectifies the DAC output signal. Thus, if the output of the DAC is in phase with the VREF+ input, the inverting input to the comparator will be positive, and if it is in phase with VREF–, the output will be negative. By turning on each bit of the DAC in succession starting with the MSB, and deciding to leave it on or turn it off based on the comparator output, a 16-bit measurement of the core position is obtained. ASIN t x ASIN t LVDT In a multiple DAC system, the double buffering of the AD7846 allows the user to simultaneously update all DACs. In Figure 24, a 16-bit word is loaded to the input latches of each of the DACs in sequence. Then, with one instruction to the appropriate address, CS4 (i.e., LDAC) is brought low, updating all the DACs simultaneously. ADDRESS BUS ADDRESS DECODE ALE 16-BIT LATCH AD7846* 8086 LDAC DEN RD R/W WR CLR DATA BUS AD0–AD15 DB0–DB15 AD7846* RIN LDAC AD7846* –(1–x)ASIN t +5V CS VREF+ VOUT VREF– DGND DB15 DB0 CS R/W CLR +5V DB0–DB15 SIGNAL GROUND CS *ADDITIONAL PINS OMITTED FOR CLARITY PROCESSOR DATA BUS AD7846* LDAC R1 100k⍀ R/W AD630* *LINEAR CIRCUITRY OMITTED FOR CLARITY C1 1F TO PROCESSOR PORT Figure 22. AD7846 in Position Measurement Application MICROPROCESSOR INTERFACING AD7846-to-8086 Interface Figure 23 shows the 8086 16-bit processor interfacing to the AD7846. The double buffering feature of the DAC is not used in this circuit since LDAC is permanently tied to 0 V. AD0– AD15 (the 16-bit data bus) are connected to the DAC data bus (DB0–DB15). The 16-bit word is written to the DAC in one MOV instruction and the analog output responds immediately. In this example, the DAC address is D000H. ADDRESS DECODE AD7846-to-MC68000 Interface Interfacing between the AD7846 and MC68000 is accomplished using the circuit of Figure 25. The following routine writes data to the DAC latches and then outputs the data via the DAC latch. 1000 ALE CS LDAC 8086 +5V DEN CLR AD7846* RD R/W WR AD0–AD15 DATA BUS DB0–DB15 *LINEAR CIRCUITRY OMITTED FOR CLARITY Figure 23. AD7846-to-8086 Interface Circuit REV. E +5V Figure 24. AD7846-to-8086 Interface: Multiple DAC System MOVE.W #W, D0 The desired DAC data, W, is loaded into Data Register 0. W may be any value between 0 and 65535 (decimal) or 0 and FFFF (hexadecimal). MOVE.W D0, $E000 The data, W, is transferred between D0 and the DAC register. MOVE.W #228, D7 TRAP #14 Control is returned to the System Monitor using these two instructions. ADDRESS BUS 16-BIT LATCH CLR DB0–DB15 –11– AD7846 A1–A23 ADDRESS BUS ANALOG SUPPLY MC68000 DS +15V ADDRESS DECODE 0V DIGITAL SUPPLY –15V +5V DGND CS +5V DTACK CLR LDAC AD7846* R/W R1 R/W DATA BUS D0–D15 SIGNAL GROUND DB0–DB15 *LINEAR CIRCUITRY OMITTED FOR CLARITY R2 Figure 25. AD7846-to-MC68000 Interface AD588* AD7846* R3 DIGITAL FEEDTHROUGH In the preceding interface configurations, most digital inputs to the AD7846 are directly connected to the microprocessor bus. Even when the device is not selected, these inputs will be constantly changing. The high frequency logic activity on the bus can feed through the DAC package capacitance to show up as noise on the analog output. To minimize this Digital Feedthrough isolate the DAC from the noise source. Figure 26 shows an interface circuit which isolates the DAC from the bus. A1–A15 ADDRESS BUS ADDRESS DECODE CS MICROPROCESSOR +5V CLR R/W DIR D0–D15 DATA BUS B BUS G A BUS AD7846* DB0–DB15 2ⴛ 74LS245 RL R5 *ADDITIONAL PINS OMITTED FOR CLARITY Figure 27. AD7846 Grounding R1 to R5 represent lead and track resistances on the printed circuit board. R1 is the resistance between the Analog Power Supply ground and the Signal Ground. Since current flowing in R1 is very low (bias current of AD588 sense amplifier), the effect of R1 is negligible. R2 and R3 represent track resistance between the AD588 outputs and the AD7846 reference inputs. Because of the Force and Sense outputs on the AD588, these resistances will also have a negligible effect on accuracy. Printed Circuit Board Layout *LINEAR CIRCUITRY OMITTED FOR CLARITY Figure 26. AD7846 Interface Circuit Using Latches to Minimize Digital Feedthrough Note that to make use of the AD7846 readback feature using the isolation technique of Figure 26, the latch needs to be bidirectional. APPLICATION HINTS Noise In high resolution systems, noise is often the limiting factor. With a 10 volt span, a 16-bit LSB is 152 µV (–96 dB). Thus, the noise floor must stay below –96 dB in the frequency range of interest. Figure 7 shows the noise spectral density for the AD7846. Grounding VOUT (+5V TO –5V) R4 is the resistance between the DAC output and the load. If RL is constant, then R4 will introduce a gain error only which can be trimmed out in the calibration cycle. R5 is the resistance between the load and the analog common. If the output voltage is sensed across the load, R5 will introduce a further gain error which can be trimmed out. If, on the other hand, the output voltage is sensed at the analog supply common, R5 appears as part of the load and therefore introduces no errors. LDAC R/W R4 Figure 28 shows the AD7846 in a typical application with the AD588 reference, producing an output analog voltage in the ± 10 volts range. Full scale and bipolar zero adjustment are provided by potentiometers R2 and R3. Latches (2 × 74LS245) isolate the DAC digital inputs from the active microprocessor bus and minimize digital feedthrough. The printed circuit board layout for Figure 28 is shown in Figures 29 and 30. Figure 29 is the component side layout while Figure 30 is the solder side layout. The component overlay is shown in Figure 31. In the layout, the general grounding guidelines given in Figure 27 are followed. The AD588 and AD7846 are as close as possible, and the decoupling capacitors for these are also kept as close to the device pins as possible. As well as noise, the other prime consideration in high resolution DAC systems is grounding. With an LSB size of 152 µV and a load current of 5 mA, 1 LSB of error can be introduced by series resistance of only 0.03 Ω. Figure 27 below shows recommended grounding for the AD7846 in a typical application. –12– REV. E AD7846 +15V J1 C5 10F C1 10F R1 39k⍀ C6 0.1F C7 0.1F DB15 C2 0.1F DB14 DB13 C12 1F DB12 DB11 VREF+ DB10 AD7846 AD588 C31/A31 20 2 3 4 18 17 16 5 6 74LS245 15 14 7 8 13 12 9 11 DB9 10 1 C4/A4 C5/A5 C6/A6 C7/A7 C8/A8 C9/A9 C10/A10 C11/A11 19 DB8 R2 100k⍀ +5V VREF– –15V C4 0.1F DB7 18 DB6 19 C3 10F VSS DB5 26 DB4 27 DB3 28 DB2 1 DGND R3 100k⍀ DB1 2 20 2 18 3 4 17 16 5 6 74LS245 7 8 9 11 10 R/W CS VOUT (+10V TO –10V) VOUT CLR LDAC Figure 28. Schematic for AD7846 Board –13– 15 14 13 12 DB0 3 RIN REV. E +5V 1 19 C12/A12 C13/A13 C14/A14 C15/A15 C16/A16 C17/A17 C18/A18 C19/A19 C20/A20 C21/A21 C22/A22 C23/A23 C32/A32 AD7846 Figure 29. PCB Component Side Layout for Figure 28 Figure 30. PCB Solder Side Layout for Figure 30 –14– REV. E AD7846 Figure 31. Component Overlay for Circuit of Figure 28 REV. E –15– AD7846 OUTLINE DIMENSIONS Dimensions shown in inches and (mm). 28-Lead Ceramic DIP (Q-28) 0.005 (0.13) MIN 28 C1245c–1–6/00 (rev. E) 01201 0.100 (2.54) MAX 15 0.610 (15.49) 0.500 (12.70) 1 14 PIN 1 0.620 (15.75) 0.590 (14.99) 0.015 (0.38) MIN 0.150 (3.81) MIN 1.490 (37.85) MAX 0.225 (5.72) MAX 0.200 (5.08) 0.026 (0.66) 0.110 (2.79) 0.070 (1.78) SEATING 0.125 (3.18) 0.014 (0.36) 0.090 (2.29) 0.030 (0.76) PLANE 0.018 (0.46) 0.008 (0.20) 15° 0° 28-Lead Plastic DIP (N-28A) 1.450 (36.83) 1.440 (35.576) 28 15 0.550 (13.97) 0.530 (13.462) 1 14 PIN 1 0.160 (4.06) 0.140 (3.56) 0.606 (15.39) 0.594 (15.09) 0.200 (5.080) MAX SEATING PLANE 0.020 (0.508) 0.015 (0.381) 0.100 (2.54) BSC 0.065 (1.65) 0.045 (1.14) 15° 0° 0.012 (0.306) 0.008 (0.203) 28-Lead Plastic Leaded Chip Carrier (PLCC) (P-28A) 0.048 (1.21) 0.042 (1.07) 4 5 PIN 1 IDENTIFIER 0.180 (4.57) 0.165 (4.19) 0.056 (1.42) 0.042 (1.07) 26 25 0.020 (0.50) R 0.021 (0.53) 0.013 (0.33) 0.050 (1.27) BSC TOP VIEW (PINS DOWN) 11 12 0.025 (0.63) 0.015 (0.38) PRINTED IN U.S.A. 0.048 (1.21) 0.042 (1.07) 0.032 (0.81) 0.026 (0.66) 19 18 0.430 (10.92) 0.390 (9.91) 0.040 (1.01) 0.025 (0.64) 0.456 (11.58) SQ 0.450 (11.43) 0.495 (12.57) SQ 0.485 (12.32) 0.110 (2.79) 0.085 (2.16) –16– REV. E