AD AD8344ACPZ-WP

Active Receive Mixer
400 MHz to 1.2 GHz
AD8344
APPLICATIONS
12
11
COMM
EXRB
10
9
8
COMM
RFCM 14
7
IFOP
RFIN 15
6
IFOM
5
COMM
BIAS
2
3
4
LOIN
COMM
1
LOCM
VPMX 16
04826-0-001
COMM 13
PWDN
VPDC
Broadband RF port: 400 MHz to 1.2 GHz
Conversion gain: 4.5 dB
Noise figure: 10.5 dB
Input IP3: 24 dBm
Input P1dB: 8.5 dBm
LO drive: 0 dBm
External control of mixer bias for low power operation
Single-ended, 50 Ω RF and LO input ports
Single-supply operation: 5 V @ 84 mA
Power-down mode
Exposed paddle LFCSP: 3 mm × 3 mm
FUNCTIONAL BLOCK DIAGRAM
VPLO
FEATURES
Figure 1.
Cellular base station receivers
ISM receivers
Radio links
RF Instrumentation
GENERAL DESCRIPTION
The AD8344 is a high performance, broadband active mixer. It
is well suited for demanding receive-channel applications that
require wide bandwidth on all ports and very low intermodulation distortion and noise figure.
The AD8344 provides a typical conversion gain of 4.5 dB at
890 MHz. The integrated LO driver supports a 50 Ω input
impedance with a low LO drive level, helping to minimize
external component count.
The single-ended 50 Ω broadband RF port allows for easy
interfacing to both active devices and passive filters. The RF
input accepts input signals as large as 1.7 V p-p or 8.5 dBm
(re: 50 Ω) at P1dB.
The open-collector differential outputs provide excellent
balance and can be used with a differential filter or IF amplifier,
such as the AD8369 or AD8351. These outputs may also be converted to a single-ended signal through the use of a matching
network or a transformer (balun). When centered on the VPOS
supply voltage, each of the differential outputs may swing
2.5 V p-p.
The AD8344 is fabricated on an Analog Devices proprietary,
high performance SiGe IC process. The AD8344 is available
in a 16-lead LFCSP package. It operates over a −40°C to +85°C
temperature range. An evaluation board is also available.
Rev. 0
Information furnished by Analog Devices is believed to be accurate and reliable.
However, no responsibility is assumed by Analog Devices for its use, nor for any
infringements of patents or other rights of third parties that may result from its use.
Specifications subject to change without notice. No license is granted by implication
or otherwise under any patent or patent rights of Analog Devices. Trademarks and
registered trademarks are the property of their respective owners.
One Technology Way, P.O. Box 9106, Norwood, MA 02062-9106, U.S.A.
Tel: 781.329.4700
www.analog.com
Fax: 781.326.8703
© 2004 Analog Devices, Inc. All rights reserved.
AD8344
TABLE OF CONTENTS
Specifications..................................................................................... 3
IF Port .......................................................................................... 14
AC Performance ............................................................................... 4
LO Considerations ..................................................................... 15
Absolute Maximum Ratings............................................................ 5
Bias Resistor Selection ............................................................... 16
ESD Caution.................................................................................. 5
Conversion Gain and IF Loading............................................. 16
Pin Configuration and Function Descriptions............................. 6
Low IF Frequency Operation.................................................... 17
Typical Performance Characteristics ............................................. 7
Evaluation Board ............................................................................ 18
Circuit Description......................................................................... 13
Outline Dimensions ....................................................................... 20
AC Interfaces................................................................................... 14
Ordering Guide .......................................................................... 20
REVISION HISTORY
6/04—Revision 0: Initial Version
Rev. 0 | Page 2 of 20
AD8344
SPECIFICATIONS
VS = 5 V, TA = 25°C, fRF = 890 MHz, fLO = 1090 MHz, LO power = 0 dBm, ZO = 50 Ω, RBIAS = 2.43 kΩ, unless otherwise noted.
Table 1.
Parameter
RF INPUT INTERFACE
Return Loss
DC Bias Level
OUTPUT INTERFACE
Output Impedance
DC Bias Voltage
Power Range
LO INTERFACE
LO Power
Return Loss
DC Bias Voltage
POWER-DOWN INTERFACE
PWDN Threshold
PWDN Response Time
PWDN Input Bias Current
POWER SUPPLY
Positive Supply Voltage
Quiescent Current
VPDC
VPMX, IFOP, IFOM
VPLO
Total Quiescent Current
Power-Down Current
Conditions
(Pin 15, RFIN and Pin 14, RFCM)
Min
4.75
−10
9||1
VS
Internally generated; port must be ac-coupled
0
10
VS − 1.6
Device enabled, IF output to 90% of its final level
Device disabled, supply current < 5 mA
Device enabled
Device disabled
VS − 1.4
0.4
0.01
−80
100
4.75
Supply current for bias cells
Supply current for mixer, RBIAS = 2.43 kΩ
Supply current for LO limiting amplifier
73
Device disabled
Rev. 0 | Page 3 of 20
Max
10
2.6
Internally generated; port must be ac-coupled
Differential impedance, f = 200 MHz
Externally generated
Via a 4:1 balun
Typ
VS
5
44
35
84
500
Unit
dB
V
5.25
13
+4
kΩ||pF
V
dBm
dBm
dB
V
V
µs
µs
µA
µA
5.25
95
V
mA
mA
mA
mA
µA
AD8344
AC PERFORMANCE
VS = 5 V, TA = 25°C, LO power = 0 dBm, ZO = 50 Ω, RBIAS = 2.43 kΩ, unless otherwise noted.
Table 2.
Parameter
RF Frequency Range
LO Frequency Range
IF Frequency Range
Conversion Gain
SSB Noise Figure
Input Third-Order Intercept
Input Second-Order Intercept
Input 1 dB Compression Point
LO to IF Output Feedthrough
LO to RF Input Leakage
RF to IF Output Feedthrough
IF/2 Spurious
Conditions
Min
400
470
70
High Side LO
fRF = 450 MHz, fLO = 550 MHz, fIF = 100 MHz
fRF = 890 MHz, fLO = 1090 MHz, fIF = 200 MHz
fRF = 450 MHz, fLO = 550 MHz, fIF = 100 MHz
fRF = 890 MHz, fLO = 1090 MHz, fIF = 200 MHz
fRF1 = 450 MHz, fRF2 = 451 MHz, fLO = 550 MHz,
fIF = 100 MHz, each RF tone = −10 dBm
fRF1 = 890 MHz, fRF2 = 891 MHz, fLO = 1090 MHz,
fIF = 200 MHz, each RF tone = −10 dBm
fRF1 = 450 MHz, fRF2 = 500 MHz, fLO = 550 MHz, fIF = 100 MHz
fRF1 = 890 MHz, fRF2 = 940 MHz, fLO = 1090 MHz, fIF = 200 MHz
fRF = 450 MHz, fLO = 550 MHz, fIF = 100 MHz
fRF = 890 MHz, fLO = 1090 MHz, fIF = 200 MHz
LO Power = 0 dBm, fRF = 890 MHz, fLO = 1090 MHz
LO Power = 0 dBm, fRF = 890 MHz, fLO = 1090 MHz
RF Power = −10 dBm, fRF = 890 MHz, fLO = 1090 MHz
RF Power = −10 dBm, fRF = 890 MHz, fLO = 1090 MHz
Rev. 0 | Page 4 of 20
Typ
Max
1200
1600
400
9.25
4.5
7.75
10.5
14
Unit
MHz
MHz
MHz
dB
dB
dB
dB
dBm
24
dBm
36
51
2.5
8.5
−23
−48
−32
−66
dBm
dBm
dBm
dBm
dBc
dBc
dBc
dBm
AD8344
ABSOLUTE MAXIMUM RATINGS
Table 3.
Parameter
Supply Voltage, VS
RF Input Level
LO Input Level
PWDN Pin
IFOP, IFOM Bias Voltage
Minimum Resistor from EXRB to COMM
Internal Power Dissipation
θJA
Maximum Junction Temperature
Operating Temperature Range
Storage Temperature Range
Lead Temperature Range (Soldering 60 sec)
Rating
5.5 V
12 dBm
12 dBm
VS + 0.5 V
5.5 V
2.4 kΩ
580 mW
77°C/W
125°C
−40°C to +85°C
−65°C to +150°C
300°C
Stresses above those listed under Absolute Maximum Ratings
may cause permanent damage to the device. This is a stress rating only; functional operation of the device at these or any
other conditions above those indicated in the operational section of this specification is not implied. Exposure to absolute
maximum rating conditions for extended periods may affect
device reliability.
ESD CAUTION
ESD (electrostatic discharge) sensitive device. Electrostatic charges as high as 4000 V readily accumulate
on the human body and test equipment and can discharge without detection. Although this product features
proprietary ESD protection circuitry, permanent damage may occur on devices subjected to high energy
electrostatic discharges. Therefore, proper ESD precautions are recommended to avoid performance
degradation or loss of functionality.
Rev. 0 | Page 5 of 20
AD8344
12
11
10
COMM
EXRB
PWDN
VPDC
PIN CONFIGURATION AND FUNCTION DESCRIPTIONS
9
8
COMM
RFCM 14
7
IFOP
RFIN 15
6
IFOM
5
COMM
1
2
3
4
VPLO
LOCM
LOIN
COMM
VPMX 16
04826-0-002
COMM 13
Figure 2. 16-Lead LFCSP
Table 4. Pin Function Descriptions
Pin No.
1
2
3
4, 5, 8, 9, 13
6, 7
10
Mnemonic
VPLO
LOCM
LOIN
COMM
IFOM, IFOP
EXRB
11
12
14
15
16
PWDN
VPDC
RFCM
RFIN
VPMX
Function
Positive Supply Voltage for the LO Buffer: 4.75 V to 5.25 V.
AC Ground for Limiting LO Amplifier, AC-Coupled to Ground.
LO Input. Nominal input level 0 dBm, input level range −10 dBm to +4 dBm, re: 50 Ω, ac-coupled.
Device Common (DC Ground).
Differential IF Outputs; Open Collectors, Each Requires DC Bias of 5.00 V (Nominal).
Mixer Bias Voltage, Connect Resistor from EXRB to Ground, Typical Value of 2.43 kΩ
Sets Mixer Current to Nominal Value. Minimum resistor value from EXRB to ground = 2.4 kΩ.
Connect to Ground for Normal Operation. Connect pin to VS for disable mode.
Positive Supply Voltage for the DC Bias Cell: 4.75 V to 5.25 V.
AC Ground for RF Input, AC-Coupled to Ground.
RF Input. Must be ac-coupled.
Positive Supply Voltage for the Mixer: 4.75 V to 5.25 V.
Rev. 0 | Page 6 of 20
AD8344
TYPICAL PERFORMANCE CHARACTERISTICS
12
10
IF = 70MHz
IF = 100MHz
IF = 200MHz
IF = 400MHz
10
RF = 450MHz
9
8
7
GAIN (dB)
GAIN (dB)
8
6
4
6
5
RF = 890MHz
4
3
2
04826-0-010
–2
400
500
600
700
800
900
1000
RF FREQUENCY (MHz)
1100
04826-0-011
2
0
1
0
80
1200
Figure 3. Conversion Gain vs. RF Frequency
120
160
200
240
280
IF FREQUENCY (MHz)
360
400
Figure 6. Conversion Gain vs. IF Frequency
6.0
45
NORMAL (MEAN = 4.47,
STD DEV = 0.18)
GAIN PERCENTAGE
5.5
40
5.0
4.5
35
4.0
30
PERCENTAGE
GAIN (dB)
320
3.5
3.0
2.5
2.0
25
20
15
1.5
04826-0-022
0.5
0
–10 –9
–8
–7
–6
–5 –4 –3 –2 –1
LO LEVEL (dBm)
0
1
2
3
5
0
3.6
4
7.0
VS = 4.75V
VS = 5.0V
VS = 5.25V
6.0
GAIN (dB)
5.5
5.0
4.5
4.0
3.5
04826-0-018
3.0
2.5
2.0
–40 –30 –20 –10
0
10 20 30 40
TEMPERATURE (°C)
50
60
70
3.8
4.0
4.2
4.4
4.6
GAIN (dB)
4.8
5.0
5.2
5.4
Figure 7. Conversion Gain Distribution, FRF = 890 MHz, FIF = 200 MHz
Figure 4. Conversion Gain vs. LO Power, FRF = 890 MHz, FIF = 200 MHz
6.5
04826-0-031
10
1.0
80
Figure 5. Conversion Gain vs. Temperature, FRF = 890 MHz, FLO = 1090 MHz
Rev. 0 | Page 7 of 20
AD8344
28
30
IF = 70MHz
IF = 100MHz
IF = 200MHz
IF = 400MHz
26
28
26
20
18
16
22
20
18
16
14
RF = 450MHz
500
600
700
800
900
1000
RF FREQUENCY (MHz)
1100
04826-0-013
04826-0-012
14
12
10
400
RF = 890MHz
24
22
INPUT IP3 (dBm)
INPUT IP3 (dBm)
24
12
10
1200
80
Figure 8. Input IP3 vs. RF Frequency (RF Tone Spacing = 1 MHz)
120
160
200
240
280
IF FREQUENCY (MHz)
320
360
400
Figure 11. Input IP3 vs. IF Frequency (RF Tone Spacing = 1 MHz)
25.0
35
NORMAL (MEAN = 24.023,
STD DEV = 0.24)
IP3 PERCENTAGE
24.5
30
24.0
25
23.0
PERCENTAGE
INPUT IP3 (dBm)
23.5
22.5
22.0
21.5
20
15
10
04826-0-023
21.0
20.0
–10 –9
–8
–7
–6
–5 –4 –3 –2 –1
LO LEVEL (dBm)
0
1
2
3
5
0
23.0
4
Figure 9. Input IP3 vs. LO Power,
FRF1 = 890 MHz, FRF2 = 891 MHz, FLO = 1090 MHz
VS = 4.75V
VS = 5.0V
VS = 5.25V
28
26
25
24
23
22
04826-0-019
INPUT IP3 (dBm)
27
21
20
–40 –30 –20 –10
0
10 20 30 40
TEMPERATURE (°C)
50
60
70
23.2
23.4
23.6
23.8 24.0 24.2
INPUT IP3 (dBm)
24.4
24.6
24.8
Figure 12. Input IP3 Distribution,
FRF1 = 890 MHz, FRF2 = 891 MHz, FLO = 1090 MHz
30
29
04826-0-032
20.5
80
Figure 10. Input IP3 vs. Temperature,
FRF1 = 890 MHz, FRF2 = 891 MHz, FLO = 1090 MHz
Rev. 0 | Page 8 of 20
25.0
AD8344
50
60
58
48
56
46
52
INPUT IP2 (dBm)
44
42
40
38
36
50
48
46
44
RF = 450MHz
42
40
38
IF = 70
IF = 100
IF = 200
IF = 400
32
30
400
500
600
700
800
900
1000
RF FREQUENCY (MHz)
1100
36
04826-0-033
34
04826-0-015
INPUT IP2 (dBm)
RF = 890MHz
54
34
32
30
80
1200
Figure 13. Input IP2 vs. RF Frequency (RF Tone Spacing = 50 MHz)
120
160
200
240
280
IF FREQUENCY (MHz)
320
360
400
Figure 16. Input IP2 vs. IF Frequency (RF Tone Spacing = 50 MHz)
60
35
NORMAL (MEAN = 48.96,
STD DEV = 01.17)
IIP2 PERCENTAGE
58
56
30
54
25
50
PERCENTAGE
INPUT IP2 (dBm)
52
48
46
44
42
40
20
15
10
38
04826-0-034
36
32
30
–10 –9
–8
–7
–6
–5 –4 –3 –2 –1
LO LEVEL (dBm)
0
1
2
3
5
0
44
4
4.75V
5.0V
5.25V
50
48
46
44
04826-0-037
INPUT IP2 (dBm)
52
42
40
–40 –30 –20 –10
0
10 20 30 40
TEMPERATURE (°C)
50
60
70
45
46
47
48
49
50
51
INPUT IP2 (dBm)
52
53
Figure 17. Input IP2 Distribution, FRF = 890 MHz,
FLO = 1090 MHz (RF Tone Spacing = 50 MHz)
Figure 14. Input IP2 vs. LO Power,
FRF = 890 MHz, FLO = 1090 MHz (RF Tone Spacing = 50 MHz)
54
04826-0-035
34
80
Figure 15. Input IP2 vs. Temperature, FRF = 890 MHz,
FLO = 1090 MHz (RF Tone Spacing = 50 MHz)
Rev. 0 | Page 9 of 20
54
55
AD8344
10
12
IF = 70MHz
IF = 100MHz
IF = 200MHz
IF = 400MHz
9
RF = 890MHz
8
7
8
INPUT P1dB (dBm)
INPUT P1dB (dBm)
10
6
4
6
5
4
3
RF = 450MHz
04826-0-016
500
600
700
800
900
1000
RF FREQUENCY (MHz)
1100
1
0
80
1200
Figure 18. Input P1dB vs. RF Frequency
55
8.6
50
8.4
45
200
240
280
IF FREQUENCY (MHz)
320
360
400
NORMAL (MEAN = 8.50,
STD DEV = 0.38)
INPUT P1dB PERCENTAGE
40
8.2
PERCENTAGE
INPUT P1dB (dBm)
60
8.8
8.0
7.8
7.6
35
30
25
20
15
04826-0-024
7.4
7.2
–8
–7
–6
–5 –4 –3 –2 –1
LO LEVEL (dBm)
0
1
2
3
VS = 4.75V
VS = 5.0V
VS = 5.25V
9.0
8.5
8.0
7.5
7.0
6.5
04826-0-020
6.0
5.5
5.0
–40 –30 –20 –10
0
10 20 30 40
TEMPERATURE (°C)
50
60
70
5
7.5
8.0
8.5
9.0
INPUT P1dB (dBm)
9.5
10.0
Figure 22. Input P1dB Distribution, FRF = 890 MHz, FLO = 1090 MHz
10.0
9.5
10
0
7.0
4
Figure 19. Input P1dB vs. LO Power, FRF = 890 MHz, FLO = 1090 MHz
INPUT P1dB (dBm)
160
Figure 21. Input P1dB vs. IF Frequency
9.0
7.0
–10 –9
120
04826-0-036
0
400
04826-0-017
2
2
80
Figure 20. Input P1dB vs. Temperature, FRF = 890 MHz, FLO = 1090 MHz
Rev. 0 | Page 10 of 20
AD8344
25
INPUT IP3
95
12
85
CURRENT
80
15
75
70
10
65
NOISE FIGURE
10
INPUT P1dB (dBm)
SUPPLY CURRENT (mA)
90
20
8
6
4
2
04826-0-026
60
5
55
0
2.4
2.6
2.8
3.0
3.2
3.4
RBIAS (kΩ)
3.6
50
4.0
3.8
04826-0-025
NF AND IP3 (dBm)
14
100
0
–2
2.4
Figure 23. Noise Figure, Input IP3 and Supply Current vs. RBIAS, FRF1 = 890 MHz,
FRF2 = 891 MHz, FLO = 1090 MHz
2.6
2.8
3.0
3.2
3.4
RBIAS (kΩ)
3.6
3.8
4.0
Figure 26. Input P1dB vs. RBIAS, FRF = 890 MHz, FLO = 1090 MHz
14
11.0
10.5
13
890MHz
NOISE FIGURE SSB (dBm)
12
11
10
9
8
500
600
700
800
900
RF FREQUENCY (MHz)
1000
1100
8.5
8.0
7.5
6.5
6.0
70
1200
100
150
200
250
300
IF FREQUENCY (MHz)
350
400
Figure 27. Noise Figure vs. IF Frequency
100
13.0
95
VS = 4.75V
VS = 5.0V
VS = 5.25V
90
12.5
CURRENT (mA)
NOISE FIGURE SSB (dBm)
Figure 24. Noise Figure vs. RF Frequency
13.5
12.0
11.5
11.0
85
80
75
70
04826-0-029
10.5
10.0
–15
450MHz
–13
–11
–9
–7
–5
–3
LO POWER (dBm)
–1
1
3
5
Figure 25. Noise Figure vs. LO Power, FRF = 890 MHz, FLO = 1090 MHz
04826-0-021
6
400
9.0
04826-0-028
7
9.5
7.0
IF = 70
IF = 100
IF = 200
IF = 400
04826-0-027
NOISE FIGURE SSB (dBm)
10.0
65
60
–40 –30 –20 –10
0
10 20 30 40
TEMPERATURE (°C)
50
60
Figure 28. Total Supply Current vs. Temperature
Rev. 0 | Page 11 of 20
70
80
AD8344
90
90
60
120
60
120
150
150
30
30
1.6GHz
400MHz
180
0
180
0
400MHz
300
270
240
Figure 32. LOIN Return Loss vs. LO Frequency
0
0
–5
–5
–10
–10
FEEDTHROUGH (dBc)
–15
–20
–25
–30
–15
–20
–25
–30
04826-0-053
–35
–40
500
600
700
800
900
1000
RF FREQUENCY (MHz)
1100
04826-0-054
FEEDTHROUGH (dBc)
300
270
Figure 29. RFIN Return Loss vs. RF Frequency
–45
400
330
210
04826-0-051
240
330
04826-0-052
1.2GHz
210
–35
–40
400
1200
600
800
1000
1200
LO FREQUENCY (MHz)
1400
1600
Figure 33. LO to IF Feedthrough vs. LO Frequency, LO Power = 0 dBm
Figure 30. RF to IF Feedthrough vs. RF Frequency,
FLO = 1090 MHz, RF Power = −10 dBm
0
14000
3.0
12000
2.5
10000
2.0
8000
1.5
6000
1.0
4000
0.5
–10
–30
–40
–50
CAPACITANCE (pF)
RESISTANCE (Ω)
LEAKAGE (dBc)
–20
–70
–80
400
600
800
1000
1200
LO FREQUENCY (MHz)
1400
2000
70
1600
Figure 31. LO to RF Leakage vs. LO Frequency, LO Power = 0 dBm
0
120
170
220
270
FREQUENCY (MHz)
320
370
Figure 34. IF Port Output Resistance and Capacitance vs. IF Frequency
Rev. 0 | Page 12 of 20
04826-0-030
04826-0-055
–60
AD8344
CIRCUIT DESCRIPTION
The AD8344 also features a power-down function.
Application of a logic low at the PWDN pin allows normal
operation. A high logic level at the PWDN pin shuts down the
AD8344. Power consumption when the part is disabled is less
than 10 mW.
VPMX
RFIN
RFCM
EXTERNAL
BIAS
RESISTOR
PWDN
BIAS
IFOP
SE
TO
DIFF
IFOM
LO
INPUT
VPLO
Figure 35. AD8344 Simplified Schematic
As shown in Figure 36, the IF output pins, IFOP and IFOM, are
directly connected to the open collectors of the NPN transistors
in the mixer core so the differential and single-ended impedances looking into this port are relatively high, on the order of
several kΩ. A connection between the supply voltage and these
output pins is required for proper mixer core operation.
IFOP IFOM
LOIN
RFIN
RFCM
COMM
04826-0-003
The RF voltage to RF current conversion is done via an
inductively degenerated differential pair. When one side of the
differential pair is ac grounded, the other input can be driven
single-ended. The RF inputs can also be driven differentially.
The voltage-to-current converter then drives the emitters of a
four-transistor switching core. This switching core is driven by
an amplified version of the local oscillator signal connected to
the LO input. There are three limiting gain stages between the
external LO signal and the switching core. The first stage converts the single-ended LO drive to a well balanced differential
drive. The differential drive then passes through two more gain
stages, which ensures a limited signal drives the switching core.
This affords the user a lower LO drive requirement, while
maintaining excellent distortion and compression performance.
The output signal of these three LO gain stages drives the four
transistors within the mixer core to commutate at the rate of the
local oscillator frequency. The output of the mixer core is taken
directly from these open collectors. The open collector outputs
present a high impedance at the IF frequency. The conversion
gain of the mixer depends directly on the impedance presented
to these open collectors. In characterization, a 200 Ω load was
presented to the part via a 4:1 impedance transformer.
VPDC
04826-0-003
The AD8344 is a down converting mixer optimized for operation within the input frequency range of 400 MHz to 1.2 GHz. It
has a single-ended, 50 Ω RF input, as well as a single-ended,
50 Ω local oscillator (LO) input. The IF outputs are differential
open collectors. The mixer current can be adjusted by the value
of an external resistor to optimize performance for gain compression and intermodulation or for low power operation.
Figure 35 shows the basic blocks of the mixer, which includes
the LO buffer, RF voltage-to-current converter, bias cell, and
mixing core.
Figure 36. Mixer Core Simplified Schematic
The AD8344 has three pins for the supply voltage: VPDC,
VPMX, and VPLO. These pins are separated to minimize or
eliminate possible parasitic coupling paths within the AD8344
that could cause spurious signals or reduced interport isolation.
Consequently, each of these pins should be well bypassed and
decoupled as close to the AD8344 as possible.
The bias for the mixer is set with an external resistor from the
EXRB pin to ground. The value of this resistor directly affects
the dynamic range of the mixer. The external resistor should not
be lower than 2.4 kΩ. Permanent damage to the part will result
if values below 2.4 kΩ are used.
Rev. 0 | Page 13 of 20
AD8344
90
AC INTERFACES
The AD8344 is designed to operate using RF frequencies in the
400 MHz to 1200 MHz frequency range, with high-side LO
injection within the 470 MHz to 1600 MHz range. It is essential
to ac-couple RF and LO ports to prevent dc offsets from skewing the mixer core in an asymmetrical manner, potentially
degrading linear input swing and impacting distortion and
input compression characteristics.
The AD8344 RFIN port presents a 50 Ω impedance relative to
RFCM. In order to ensure a good impedance match, the RFIN
ac-coupling capacitor should be large enough in value so that
the presented reactance is negligible at the intended RF frequency. Additionally, the RFCM bypassing capacitor should be
sufficiently large to provide a low impedance return path to
board ground. Low inductance ceramic grade capacitors of no
more than 330 pF are sufficient for most applications.
Similarly the LOIN port provides a 50 Ω load impedance with
common-mode decoupling on LOCM. Again, common grade
ceramic capacitors will provide sufficient signal coupling and
bypassing of the LO interface.
60
120
150
30
10MHz
180
0
210
330
500MHz
240
300
270
04826-0-040
The AD8344 is a high-side downconverter. It is designed to
downconvert radio frequencies (RF) to lower intermediate
frequencies (IF) using a high-side local oscillator (LO). The LO
is injected into the mixer core at a frequency greater than the
desired input RF frequency. The difference between the LO and
RF frequencies, fLO − fRF, is the IF frequency, fIF. In addition to
the desired RF signal, an RF image will be downconverted to the
same IF frequency. The image frequency is at fLO + fIF. The conversion gain of the AD8344 decreases with increasing input
frequency. By choosing to use a high-side LO the image frequency at fLO + fIF is translated with less conversion gain than
the desired RF signal at fLO − fIF. Additionally, any wideband
noise present at the image frequency will be downconverted
with less conversion gain than would be the case if a low-side
LO was applied. In general, a high-side LO should be used with
the AD8344 to ensure optimal noise performance and image
rejection.
Figure 37. IF Port Reflection Coefficient from 10 MHz to 500 MHz
IF PORT
The IF port uses an open collector differential output interface.
The NPN open collectors can be modeled as high impedance
current sources. The stray capacitance associated with the IC
package presents a slightly capacitive source impedance as in
Figure 37. In general, the IFOP and IFOM output ports can be
modeled as current sources with an impedance of ~10 kΩ in
parallel with ~1 pF of shunt capacitance. Circuit board traces
connecting the IF outputs to the load should be narrow and
short to prevent excessive capacitive loading. In order to maintain the specified conversion gain of the mixer, the IF output
ports should be loaded into 200 Ω. It is not necessary to attempt
to provide a conjugate match to the IF port output source
impedance. If the IF signal needs to be delivered to a remote
load, more than a few centimeters away, it may be necessary to
use an appropriate buffer amplifier to present a real 200 Ω loading impedance at the IF output interface. The buffer amplifier
should have the appropriate source impedance to match the
characteristic impedance of the selected transmission line. An
example is provided in Figure 38, where the AD8351 differential
amplifier is used to drive a pair of 75 Ω transmission lines. The
gain of the buffer can be independently set by choosing an
appropriate gain resistor, RG.
+VS
AD8344
+VS
COMM 8
RFC
IFOP 7
200Ω
RG
IFOM 6
+
AD8351
–
Tx LINE ZO = 75Ω
ZL
Tx LINE ZO = 75Ω
+VS
ZL = 200Ω
04826-0-041
RFC
COMM 5
Figure 38. AD8351 Used as Transmission Line Driver and Impedance Buffer
Rev. 0 | Page 14 of 20
AD8344
90
The high input impedance of the AD8351 allows for a shunt
differential termination to provide the desired 200 Ω load to the
AD8344 IF output port.
• Chris Bowick, RF Circuit Design, Newnes, Reprint Edition,
1997.
• David M. Pozar, Microwave Engineering, Wiley Text Books,
Second Edition, 1997.
• Guillermo Gonzalez, Microwave Transistor Amplifiers: Analysis and Design, Prentice Hall, Second Edition, 1996.
+VS
AD8344
COMM 8
4:1
IFOP 7
IF OUT
ZO = 50Ω
COMM 5
ZL = 200Ω
04826-0-042
IFOM 6
Figure 39. Biasing the IF Port Open Collector Outputs
Using a Center-Tapped Impedance Transformer
150
30
50MHz
REAL
CHOKES
180
0
50MHz
500MHz
210
IDEAL
CHOKES
330
500MHz
240
300
04826-0-044
It is necessary to bias the open collector outputs using one of
the schemes presented in Figure 39 and Figure 40. Figure 39
illustrates the application of a center-tapped impedance transformer. The turns ratio of the transformer should be selected to
provide the desired impedance transformation. In the case of a
50 Ω load impedance, a 4-to-1 impedance ratio transformer
should be used to transform the 50 Ω load into a 200 Ω
differential load at the IF output pins. Figure 40 illustrates a
differential IF interface where pull-up choke inductors are used
to bias the open-collector outputs. The shunting impedance of
the choke inductors used to couple dc current into the mixer
core should be large enough at the IF frequency of operation as
to not load down the output current before reaching the
intended load. Additionally, the dc current handling capability
of the selected choke inductors needs to be at least 45 mA. The
self resonant frequency of the selected choke should be higher
than the intended IF frequency. A variety of suitable choke
inductors are commercially available from manufacturers such
as Murata and Coilcraft. An impedance transforming network
may be required to transform the final load impedance to 200 Ω
at the IF outputs. There are several good reference books that
explain general impedance matching procedures, including:
60
120
270
Figure 41. IF Port Loading Effects due to Finite-Q Pull-Up Inductors
(Murata BLM18HD601SN1D Chokes)
LO CONSIDERATIONS
The LO signal needs to have adequate phase noise characteristics and reasonable low second harmonic content to prevent
degradation of the noise figure performance of the AD8344. A
LO plagued with poor phase noise can result in reciprocal
mixing, a mechanism that causes spectral spreading of the
downconverted signal, limiting the sensitivity of the mixer at
frequencies close-in to any large input signals. The internal LO
buffer provides enough gain to hard limit the input LO and
provide fast switching of the mixer core. Odd harmonic content
present on the LO drive signal should not impact mixer
performance; however, even-order harmonics cause the mixer
core to commutate in an unbalanced manner, potentially
degrading noise performance. Simple lumped element low-pass
filtering can be applied to help reject the harmonic content of a
given local oscillator, as illustrated in Figure 42. The filter
depicted is a common 3-pole Chebyshev, designed to maintain a
1-to-1 source-to-load impedance ratio with no more than
0.5 dB of ripple in the pass band. Other filter structures can be
effective as long as the second harmonic of the LO is filtered to
negligible levels, e.g., ~30 dB below the fundamental. The measured frequency response of the Chebyshev filter for a 1200 MHz
−3 dB cutoff frequency is presented in Figure 43.
+VS
AD8344
AD8344
LOCM LOIN COMM
COMM 8
2
RS
RFC
3
4
IF OUT+
IFOP 7
ZL = 200Ω
IFOM 6
IMPEDANCE
TRANSFORMING
NETWORK
L2
LO
SOURCE
ZL
C1
C3
IF OUT–
RL
RFC
1.864
C1 =
2πfcRL
L2 =
1.28RL
2πfc
C3 =
fC - FILTER CUTOFF FREQUENCY
Figure 40. Biasing the IF Port Open Collector Outputs
Using Pull-Up Choke Inductors
1.834
2πfcRL
04826-0-045
+VS
FOR RS = RL
04826-0-043
COMM 5
Figure 42. Using a Low-Pass Filter to Reduce LO Second Harmonic
Rev. 0 | Page 15 of 20
AD8344
0
125
85
124
81
123
77
IDEAL LPF
–20
SFDR (dBc)
RESPONSE (dB)
–15
–25
–30
122
+VS
73
REAL LPF
RBIAS
–35
6.8nH
121
–45
4.7pF
–50
0.1
04826-0-046
–40
4.7pF
1
FREQUENCY (GHz)
120
2.4
10
10
69
9
AD8344
2.6
2.8
3.0
3.2
3.4
RBIAS (kΩ)
3.6
3.8
65
4.0
Figure 44. Impact of RBIAS Resistor Selection vs. Spurious-Free
Dynamic Range and Power Consumption,
FRF = 890 MHz and FLO = 1090 MHz
BIAS RESISTOR SELECTION
An external bias resistor is used to set the dc current in the
mixer core. This provides the ability to reduce power consumption at the expense of decreased dynamic range. Figure 44
shows the spurious-free dynamic range (SFDR) of the mixer for
a 1 Hz noise bandwidth versus the RBIAS resistor value. SFDR
was calculated using NF and IIP3 data collected at 900 MHz.
By definition,
2
3
11
VPDC PWDN EXRB COMM
Figure 43. Measured and Ideal LO Filter Frequency Response
SFDR =
12
04826-0-047
–10
SUPPLY CURRENT (mA)
–5
(IIP3 − NF − kT − 10log(B))
where IIP3 is the input third-order intercept in dBm. NF is the
noise figure in dB. kT is the thermal noise power density and is
−173.86 dBm/Hz at 298°K. B is the noise bandwidth in Hz.
In order to calculate the anticipated SFDR for a given application, it is necessary to factor in the actual noise bandwidth. For
instance, if the IF noise bandwidth was 5 MHz, the anticipated
SFDR using a 2.43 kΩ RBIAS would be 6.66 log10 (5 MHz) less
than the 1 Hz data in Figure 44 or ~80 dBc. Using a 2.43 kΩ bias
resistor will set the quiescent power dissipation to ~415 mW for
a 5 V supply. If the RBIAS resistor value was raised to 3.9 kΩ, the
SFDR for the same 5 MHz bandwidth would be reduced to
~77.5 dBc and the power dissipation would be reduced to
~335 mW. In low power portable applications it may be advantageous to reduce power consumption by using a larger value of RBIAS,
assuming reduced dynamic range performance is acceptable.
CONVERSION GAIN AND IF LOADING
The AD8344 is optimized for driving a 200 Ω differential load.
Although the device is capable of driving a wide variety of
loads, in order to maintain optimum distortion and noise
performance, it is advised that the presented load at the IF
outputs is reasonably close to 200 Ω. Figure 45 illustrates the
effect of IF loading on conversion gain. The mixer outputs
behave like Norton equivalent sources, where the conversion
gain is the effective transconductance of the mixer multiplied
by the loading impedance. The linear differential voltage
conversion gain of the mixer can be modeled as
Av = −0.46 × RLOAD ×
gm
1 + j × g m × 37.70 × f RF
where RLOAD is the differential loading impedance. gm is the
mixer transconductance and is equal to 4070/RBIAS. fRF is the
frequency of the signal applied to the RF port in GHz.
Large impedance loads cause the conversion gain to increase,
resulting in a decrease in input linearity and allowable signal
swing. In order to maintain positive conversion gain and preserve spurious-free dynamic range performance, the differential
load presented at the IF port should remain within a range of
~100 Ω to 250 Ω.
Rev. 0 | Page 16 of 20
15
10
MEASURED
5
–5
10
100
IF LOADING (Ω)
12
12
9
9
6
6
3
3
0
10
1000
Figure 45. Conversion Gain vs. IF Loading
15
20
25
30
35
IF FREQUENCY (MHz)
40
45
0
50
Figure 46. Conversion Gain, Input IP3, and P1dB vs.
IF Frequency, FRF = 450 MHz
The AD8344 may be used down to arbitrarily low IF frequencies. The conversion gain, noise, and linearity characteristics
remain quite flat as IF frequency is reduced, as indicated in
Figure 46 and Figure 47. Larger value pull-up inductors need to
be used at the lower IF frequencies. A 1 µH choke inductor
would present a common-mode loading impedance of 63 Ω at
an IF frequency of 10 MHz, severely loading down the mixer
outputs, reducing conversion gain, and sacrificing output power.
At low IF frequencies, choke inductors of several hundred µH
should be used for biasing the IF outputs.
CONVERSION GAIN (dB)
LOW IF FREQUENCY OPERATION
8
28.0
7
24.5
6
21.0
5
17.5
4
14.0
3
10.5
2
10
15
20
25
30
35
IF FREQUENCY (MHz)
40
45
Figure 47. Conversion Gain, Input IP3, and P1dB vs.
IF Frequency, FRF = 890 MHz
Rev. 0 | Page 17 of 20
7.0
50
INPUT IP3 AND P1dB (dBm)
0
15
04826-0-050
MODELED
15
04826-0-049
CONVERSION GAIN (dB)
20
04826-0-048
20LOG–CONVERSION GAIN (dB)
25
INPUT IP3 AND P1dB (dBm)
AD8344
AD8344
EVALUATION BOARD
An evaluation board is available for the AD8344. The evaluation
board is configured for single-ended signaling at the IF output
port via a balun transformer. The schematic for the evaluation
board is presented in Figure 48.
Table 5. Evaluation Boards Configuration Options
Component
R1, R2, R7,
C2, C4, C5, C6,
C12, C13, C14,
C15
Function
Supply Decoupling.
Jumpers or power supply decoupling resistors and filter capacitors.
R3, R4
R6, C11
Jumpers in Single-Ended IF Output Circuit.
RBIAS resistor that sets the bias current for the mixer core.
The capacitor provides ac bypass for R6.
Jumper for pull down of the PWDN pin.
Jumper.
RF Input AC Coupling. Provides dc block for RF input.
RF Common AC Coupling. Provides dc block for RF input common connection.
LO Input AC Coupling. Provides dc block for the LO input.
LO Common AC Coupling. Provides dc block for LO input common connection.
Power Down. The part is on when the PWDN is connected to ground via SW1.
The part is disabled when PWDN is connected to the positive supply (VS) via SW1.
IF Output Balun Transformer. Converts differential, high impedance IF output
to single-ended. When loaded with 50 Ω, this balun presents a 200 Ω load to the
mixers collectors. The center tap of the primary is used to supply the bias voltage
(VS) to the IF output pins.
IF Output Interface—IFOP, IFOM. These positions can be used to modify the
impedance presented to the IF outputs.
R8
R9
C3
C1
C8
C7
SW1
T1
R11, Z3, Z4
R12, Z1, Z2
Rev. 0 | Page 18 of 20
Default Conditions
R1, R2, R7 = 0 Ω (Size 0603)
C4, C6, C13, C14 = 100 pF
(Size 0603)
C2, C5, C12, C15 = 0.1 µF
(Size 0603)
0 Ω (Size 0603)
R6 = 2.43 kΩ (Size 0603)
C11 = 100 pF (Size 0603)
R8 = 10 kΩ (Size 0603)
R9 = 0 Ω (Size 0603)
C3 = 100 pF (Size 0402)
C1 = 100 pF (Size 0402)
C8 = 100 pF (Size 0402)
C7 = 100 pF (Size 0402)
T1 = TC4-1W, 4:1 (Mini-Circuits)
R11 = 0 Ω (Size 0603)
Z3, Z4 = Open
R12 = 0 Ω (Size 0603)
Z1, Z2 = Open
AD8344
POWER
DOWN
SW1
C11
100pF
COMMON
R8
10kΩ
COMM
COMM
RFCM
IFOP
C1
100pF
C3
100pF
AD8344
RF INPUT
IFOM
RFIN
R1
0Ω
R2
0Ω
C5
0.1µF
C6
100pF
C7
100pF
Z2
OPEN
R3
0Ω
R11
0Ω
Z3
OPEN
IF
OUTPUT
T1
TC4-1W
R4
0Ω
Z4
OPEN
COMM
LOIN
LOCM
C4
100pF
VPLO
C2
0.1µF
COMM
VPMX
VPOS
Z1
OPEN
R10
0Ω
C14
100pF
C15
0.1µF
C8
100pF
LO
INPUT
VPOS
04826-0-005
PWDN
VPDC
C13
100pF
EXRB
R9
0Ω
VPOS
C12
0.1µF
R6
2.43kΩ
COMM
R7
0Ω
04826-0-007
04826-0-008
Figure 48. Evaluation Board Schematic—Single-Ended IF Output
Figure 49. Single-Ended Evaluation Board, Component Side Layout
Figure 50. Single-Ended Evaluation Board, Component Side Silkscreen
Rev. 0 | Page 19 of 20
AD8344
OUTLINE DIMENSIONS
3.00
BSC SQ
0.60 MAX
2.75
BSC SQ
TOP VIEW
0.80 MAX
0.65 TYP
12° MAX
SEATING
PLANE
16
1
1.65
1.50 SQ*
1.35
BOTTOM
VIEW
0.50
BSC
1.00
0.85
0.80
PIN 1 INDICATOR
13
12
0.45
PIN 1
INDICATOR
0.50
0.40
0.30
9
8
5
4
0.25 MIN
1.50 REF
0.05 MAX
0.02 NOM
0.30
0.23
0.18
0.20 REF
* COMPLIANT TO JEDEC STANDARDS MO-220-VEED-2
EXCEPT FOR EXPOSED PAD DIMENSION
Figure 51. 16-Lead Lead Frame Chip Scale Package [LFCSP]
3 mm × 3 mm Body (CP-16-3)
Dimensions in millimeters
ORDERING GUIDE
Models
AD8344ACPZ-REEL71
AD8344ACPZ-WP1, 2
AD8344-EVAL
1
2
Temperature Range
−40°C to +85°C
−40°C to +85°C
Package Description
16-Lead Lead Frame Chip Scale Package (LFCSP)
16-Lead Lead Frame Chip Scale Package (LFCSP)
Evaluation Board
Z = Pb-free part.
WP = Waffle pack.
© 2004 Analog Devices, Inc. All rights reserved. Trademarks and registered trademarks are the property of their respective owners.
D04826–0–6/04(0)
Rev. 0 | Page 20 of 20
Package Option
CP-16-3
CP-16-3
Branding
JHA
JHA