Dual 8-/10-/12-Bit, High Bandwidth, Multiplying DACs with Serial Interface AD5429/AD5439/AD5449 FEATURES GENERAL DESCRIPTION 10 MHz multiplying bandwidth INL of ±0.25 LSB @ 8 bits 16-lead TSSOP package 2.5 V to 5.5 V supply operation ±10 V reference input 50 MHz serial interface 2.47 MSPS update rate Extended temperature range: −40°C to +125°C 4-quadrant multiplication Power-on reset 0.5 μA typical current consumption Guaranteed monotonic Daisy-chain mode Readback function The AD5429/AD5439/AD54491 are CMOS, 8-, 10-, and 12-bit, dual-channel, current output digital-to-analog converters (DAC), respectively. These devices operate from a 2.5 V to 5.5 V power supply, making them suited to battery-powered and other applications. As a result of being manufactured on a CMOS submicron process, these parts offer excellent 4-quadrant multiplication characteristics, with large signal multiplying bandwidths of 10 MHz. The applied external reference input voltage (VREF) determines the full-scale output current. An integrated feedback resistor (RFB) provides temperature tracking and full-scale voltage output when combined with an external current-to-voltage precision amplifier. APPLICATIONS These DACs use a double-buffered, 3-wire serial interface that is compatible with SPI, QSPI™, MICROWIRE™, and most DSP interface standards. In addition, a serial data out (SDO) pin allows daisy-chaining when multiple packages are used. Data readback allows the user to read the contents of the DAC register via the SDO pin. On power-up, the internal shift register and latches are filled with 0s, and the DAC outputs are at zero scale. Portable battery-powered applications Waveform generators Analog processing Instrumentation applications Programmable amplifiers and attenuators Digitally controlled calibration Programmable filters and oscillators Composite video Ultrasound Gain, offset, and voltage trimming The AD5429/AD5439/AD5449 DACs are available in 16-lead TSSOP packages. FUNCTIONAL BLOCK DIAGRAM VREFA AD5429/AD5439/AD5449 RFB R VDD SYNC SCLK SHIFT REGISTER INPUT REGISTER DAC REGISTER RFBA IOUT1A 8-/10-/12-BIT R-2R DAC A IOUT2A SDIN SDO LDAC POWER-ON RESET INPUT REGISTER DAC REGISTER IOUT1B 8-/10-/12-BIT R-2R DAC B IOUT2B RFB R LDAC VREFB RFBB 04464-001 CLR Figure 1. 1 U.S. Patent Number 5,689,257. Rev. C Information furnished by Analog Devices is believed to be accurate and reliable. However, no responsibility is assumed by Analog Devices for its use, nor for any infringements of patents or other rights of third parties that may result from its use. Specifications subject to change without notice. No license is granted by implication or otherwise under any patent or patent rights of Analog Devices. Trademarks and registered trademarks are the property of their respective owners. One Technology Way, P.O. Box 9106, Norwood, MA 02062-9106, U.S.A. Tel: 781.329.4700 www.analog.com Fax: 781.461.3113 ©2004–2010 Analog Devices, Inc. All rights reserved. AD5429/AD5439/AD5449 TABLE OF CONTENTS Features .............................................................................................. 1 Digital-to-Analog Converter .................................................... 15 Applications ....................................................................................... 1 Circuit Operation ....................................................................... 15 General Description ......................................................................... 1 Single-Supply Applications ....................................................... 17 Functional Block Diagram .............................................................. 1 Adding Gain ................................................................................ 18 Revision History ............................................................................... 2 Divider or Programmable Gain Element ................................ 18 Specifications..................................................................................... 3 Reference Selection .................................................................... 19 Timing Characteristics ................................................................ 5 Amplifier Selection .................................................................... 19 Timing Diagrams.......................................................................... 5 Serial Interface ............................................................................ 20 Absolute Maximum Ratings............................................................ 7 Microprocessor Interfacing ....................................................... 22 ESD Caution .................................................................................. 7 PCB Layout and Power Supply Decoupling ........................... 24 Pin Configuration and Function Descriptions ............................. 8 Evaluation Board for the DAC ................................................. 24 Typical Performance Characteristics ............................................. 9 Overview of AD54xx Devices ....................................................... 28 Terminology .................................................................................... 14 Outline Dimensions ....................................................................... 29 Theory of Operation ...................................................................... 15 Ordering Guide .......................................................................... 29 REVISION HISTORY 4/10—Rev. B to Rev. C Added to Figure 4 ............................................................................. 6 3/08—Rev. A to Rev. B Added t13 and t14 Parameters to Table 2 ......................................... 5 Changes to Figure 2 .......................................................................... 5 Changes to Figure 3 .......................................................................... 6 Changes to Figure 38 ...................................................................... 16 Changes to Ordering Guide .......................................................... 30 7/05—Rev. 0 to Rev. A Changes to Features List .................................................................. 1 Changes to Specifications ................................................................ 3 Changes to Timing Characteristics ................................................ 5 Changes to Absolute Maximum Ratings Section ......................... 7 Changes to General Description Section .................................... 15 Changes to Table 5.......................................................................... 15 Changes to Table 6.......................................................................... 16 Changes to Single-Supply Applications Section ......................... 17 Changes to Divider or Programmable Gain Element Section .... 18 Changes to Table 7 Through Table 10 ......................................... 20 Added ADSP-BF5xx-to-AD5429/AD5439/AD5449 Interface Section ........................................................................ 23 Change to PCB Layout and Power Supply Decoupling Section .......................................... 25 Changes to Power Supplies for the Evaluation Board Section .... 25 Changes to Table 13 ....................................................................... 29 Updated Outline Dimensions ....................................................... 30 Changes to Ordering Guide .......................................................... 30 7/04—Revision 0: Initial Version Rev. C | Page 2 of 32 AD5429/AD5439/AD5449 SPECIFICATIONS VDD = 2.5 V to 5.5 V, VREF = 10 V, IOUT2 = 0 V. Temperature range for Y version: −40°C to +125°C. All specifications TMIN to TMAX, unless otherwise noted. DC performance is measured with the OP177, and ac performance is measured with the AD8038, unless otherwise noted. Table 1. Parameter1 STATIC PERFORMANCE AD5429 Resolution Relative Accuracy Differential Nonlinearity AD5439 Resolution Relative Accuracy Differential Nonlinearity AD5449 Resolution Relative Accuracy Differential Nonlinearity Gain Error Gain Error Temperature Coefficient Output Leakage Current REFERENCE INPUT Reference Input Range VREFA, VREFB Input Resistance VREFA-to-VREFB Input Resistance Mismatch Input Capacitance Code 0 Code 4095 DIGITAL INPUTS/OUTPUT Input High Voltage, VIH Min Typ 9 ±10 11 1.6 Measured to ±1 mV of FS Measured to ±4 mV of FS Measured to ±16 mV of FS Digital Delay Digital-to-Analog Glitch Impulse Conditions 8 ±0.5 ±1 Bits LSB LSB Guaranteed monotonic 10 ±0.5 ±1 Bits LSB LSB Guaranteed monotonic 12 ±1 −1/+2 ±25 Bits LSB LSB mV ppm FSR/°C Guaranteed monotonic ±5 ±15 nA nA Data = 0x0000, TA = 25°C, IOUT1 Data = 0x0000, IOUT1 13 2.5 V kΩ % Input resistance temperature coefficient = −50 ppm/°C Typical = 25°C, maximum = 125°C 3.5 3.5 pF pF VDD = 3.6 V to 5.5 V VDD = 2.5 V to 3.6 V VDD = 2.7 V to 5.5 V VDD = 2.5 V to 2.7 V VDD = 4.5 V to 5.5 V, ISOURCE = 200 μA VDD = 2.5 V to 3.6 V, ISOURCE = 200 μA VDD = 4.5 V to 5.5 V, ISINK = 200 μA VDD = 2.5 V to 3.6 V, ISINK = 200 μA 4 V V V V V V V V μA pF MHz VREF = ±3.5 V p-p, DAC loaded all 1s RLOAD = 100 Ω, CLOAD = 15 pF, VREF = 10 V, DAC latch alternately loaded with 0s and 1s 1.7 1.7 0.8 0.7 VDD − 1 VDD − 0.5 Output Low Voltage, VOL Input Leakage Current, IIL Input Capacitance DYNAMIC PERFORMANCE Reference-Multiplying Bandwidth Output Voltage Settling Time Unit ±5 Input Low Voltage, VIL Output High Voltage, VOH Max 0.4 0.4 1 10 10 80 35 30 20 3 120 70 60 40 ns ns ns ns nV-sec Rev. C | Page 3 of 32 1 LSB change around major carry, VREF = 0 V AD5429/AD5439/AD5449 Parameter1 Multiplying Feedthrough Error Min Output Capacitance Digital Feedthrough Output Noise Spectral Density Analog THD Digital THD 100 kHz fOUT 50 kHz fOUT SFDR Performance (Wide Band) Clock = 10 MHz 500 kHz fOUT 100 kHz fOUT 50 kHz fOUT Clock = 25 MHz 500 kHz fOUT 100 kHz fOUT 50 kHz fOUT SFDR Performance (Narrow Band) Clock = 10 MHz 500 kHz fOUT 100 kHz fOUT 50 kHz fOUT Clock = 25 MHz 500 kHz fOUT 100 kHz fOUT 50 kHz fOUT Intermodulation Distortion f1 = 40 kHz, f2 = 50 kHz f1 = 40 kHz, f2 = 50 kHz POWER REQUIREMENTS Power Supply Range IDD Typ Max Unit 12 25 3 70 48 17 30 5 dB dB pF pF nV-sec 25 81 nV/√Hz dB 61 66 dB dB AD5449, 65k codes, VREF = 3.5 V 55 63 65 dB dB dB 50 60 62 dB dB dB AD5449, 65k codes, VREF = 3.5 V 73 80 87 dB dB dB 70 75 80 dB dB dB 72 65 dB dB AD5449, 65k codes, VREF = 3.5 V Clock = 10 MHz Clock = 25 MHz V μA μA %/% TA = 25°C, logic inputs = 0 V or VDD TA = −40°C to +125°C, logic inputs = 0 V or VDD ∆VDD = ±5% 2.5 0.5 Power Supply Sensitivity 1 Conditions DAC latches loaded with all 0s, VREF = ±3.5 V 1 MHz 10 MHz DAC latches loaded with all 0s DAC latches loaded with all 1s Feedthrough to DAC output with CS high and alternate loading of all 0s and all 1s @ 1 kHz VREF = 3. 5 V p-p, all 1s loaded, f = 1 kHz Clock = 10 MHz, VREF = 3.5 V 5.5 0.7 10 0.001 Guaranteed by design and characterization, not subject to production test. Rev. C | Page 4 of 32 AD5429/AD5439/AD5449 TIMING CHARACTERISTICS All input signals are specified with tR = tF = 1 ns (10% to 90% of VDD) and timed from a voltage level of (VIL + VIH)/2. VDD = 2.5 V to 5.5 V, VREF = 10 V, IOUT2 = 0 V, temperature range for Y version: −40°C to +125°C. All specifications TMIN to TMAX, unless otherwise noted. Table 2. Parameter 1 fSCLK t1 t2 t3 t4 t5 t6 t7 t8 t9 t10 t11 t12 3 t13 t14 Update Rate Limit at TMIN, TMAX 50 20 8 8 13 5 4 5 30 0 12 10 25 60 12 4.5 2.47 Unit MHz max ns min ns min ns min ns min ns min ns min ns min ns min ns min ns min ns min ns min ns min ns min ns min MSPS Conditions/Comments 2 Maximum clock frequency SCLK cycle time SCLK high time SCLK low time SYNC falling edge to SCLK falling edge setup time Data setup time Data hold time SYNC rising edge to SCLK falling edge Minimum SYNC high time SCLK falling edge to LDAC falling edge LDAC pulse width SCLK falling edge to LDAC rising edge SCLK active edge to SDO valid, strong SDO driver SCLK active edge to SDO valid, weak SDO driver CLR pulse width SYNC rising edge to LDAC falling edge Consists of cycle time, SYNC high time, data setup, and output voltage settling time 1 Guaranteed by design and characterization, not subject to production test. Falling or rising edge as determined by the control bits of the serial word. Strong or weak SDO driver selected via the control register. 3 Daisy-chain and readback modes cannot operate at maximum clock frequency. SDO timing specifications are measured with a load circuit, as shown in Figure 5. 2 TIMING DIAGRAMS t1 SCLK t8 t2 t4 t3 t7 SYNC t6 t5 SDIN DB15 DB0 t9 t10 LDAC1 t11 LDAC2 NOTES 1. ALTERNATIVELY, DATA CAN BE CLOCKED INTO THE INPUT SHIFT REGISTER ON THE RISING EDGE OF SCLK AS DETERMINED BY THE CONTROL BITS. TIMING IS AS ABOVE, WITH SCLK INVERTED. Figure 2. Standalone Mode Timing Diagram Rev. C | Page 5 of 32 04464-002 1ASYNCHRONOUS LDAC UPDATE MODE. 2SYNCHRONOUS LDAC UPDATE MODE. AD5429/AD5439/AD5449 t1 SCLK t2 t4 t3 t7 SYNC t5 SDIN t6 t8 DB0 (N) DB15 (N) DB15 (N + 1) DB0 (N + 1) DB15 (N) DB0 (N) t12 SDO 04464-003 NOTES 1. ALTERNATIVELY, DATA CAN BE CLOCKED INTO THE INPUT SHIFT REGISTER ON THE RISING EDGE OF SCLK AS DETERMINED BY THE CONTROL BITS. IN THIS CASE, DATA WOULD BE CLOCKED OUT OF SDO ON THE FALLING EDGE OF SCLK. TIMING IS AS ABOVE, WITH SCLK INVERTED. Figure 3. Daisy-Chain Timing Diagram SCLK 16 32 SYNC DB15 DB0 DB15 DB0 INPUT WORD SPECIFIES REGISTER TO BE READ NOP CONDITION DB0 SELECTED REGISTER DATA CLOCKED OUT UNDEFINED Figure 4. Readback Mode Timing Diagram 200μA TO OUTPUT PIN IOL VOH (MIN) + VOL (MAX) 2 CL 50pF 200μA IOH Figure 5. Load Circuit for SDO Timing Specifications Rev. C | Page 6 of 32 04464-059 DB15 SDO 04464-004 SDIN AD5429/AD5439/AD5449 ABSOLUTE MAXIMUM RATINGS Transient currents of up to 100 mA do not cause SCR latch-up. TA = 25°C, unless otherwise noted. Table 3. Parameter VDD to GND VREFx, RFBx to GND IOUT1, IOUT2 to GND Input Current to Any Pin Except Supplies Logic Inputs and Output 1 Operating Temperature Range Extended (Y Version) Storage Temperature Range Junction Temperature 16-Lead TSSOP, θJA Thermal Impedance Lead Temperature, Soldering (10 sec) IR Reflow, Peak Temperature (<20 sec) 1 Rating −0.3 V to +7 V −12 V to +12 V −0.3 V to +7 V ±10 mA −0.3 V to VDD + 0.3 V −40°C to +125°C −65°C to +150°C 150°C 150°C/W 300°C 235°C Stresses above those listed under Absolute Maximum Ratings may cause permanent damage to the device. This is a stress rating only; functional operation of the device at these or any other conditions above those indicated in the operational section of this specification is not implied. Exposure to absolute maximum rating conditions for extended periods may affect device reliability. Only one absolute maximum rating may be applied at any one time. ESD CAUTION Overvoltages at SCLK, SYNC, and SDIN are clamped by internal diodes. Rev. C | Page 7 of 32 AD5429/AD5439/AD5449 IOUT1A 1 16 IOUT1B IOUT2A 2 15 IOUT2B RFBA 3 14 RFBB VREFA 4 13 VREFB 12 VDD 11 CLR SYNC AD5429/ AD5439/ AD5449 GND 5 LDAC 6 SCLK 7 10 SDIN 8 9 TOP VIEW (Not to Scale) SDO NC = NO CONNECT 04464-005 PIN CONFIGURATION AND FUNCTION DESCRIPTIONS Figure 6. Pin Configuration Table 4. Pin Function Descriptions Pin No. 1 2 Mnemonic IOUT1A IOUT2A 3 RFBA 4 5 6 VREFA GND LDAC 7 SCLK 8 SDIN 9 SDO 10 SYNC 11 CLR 12 13 14 VDD VREFB RFBB 15 IOUT2B 16 IOUT1B Description DAC A Current Output. DAC A Analog Ground. This pin should typically be tied to the analog ground of the system, but it can be biased to achieve single-supply operation. DAC Feedback Resistor Pin. This pin establishes voltage output for the DAC by connecting to an external amplifier output. DAC A Reference Voltage Input Pin. Ground Pin. Load DAC Input. This pin allows asynchronous or synchronous updates to the DAC output. The DAC is asynchronously updated when this signal goes low. Alternatively, if this line is held permanently low, an automatic or synchronous update mode is selected, whereby the DAC is updated on the 16th clock falling edge when the device is in standalone mode, or on the rising edge of SYNC when in daisy-chain mode. Serial Clock Input. By default, data is clocked into the input shift register on the falling edge of the serial clock input. Alternatively, by means of the serial control bits, the device can be configured such that data is clocked into the shift register on the rising edge of SCLK. Serial Data Input. Data is clocked into the 16-bit input register on the active edge of the serial clock input. By default, data is clocked at power-on into the shift register on the falling edge of SCLK. The control bits allow the user to change the active edge to a rising edge. Serial Data Output. This pin allows a number of parts to be daisy-chained. By default, data is clocked into the shift register on the falling edge and clocked out via SDO on the rising edge of SCLK. Data is always clocked out on the alternate edge to loading data to the shift register. Writing the readback control word to the shift register makes the DAC register contents available for readback on the SDO pin, and they are clocked out on the next 16 opposite clock edges to the active clock edge. Active Low Control Input. This pin provides the frame synchronization signal for the input data. When SYNC goes low, it powers on the SCLK and DIN buffers, and the input shift register is enabled. Data is loaded into the shift register on the active edge of the subsequent clocks. In standalone mode, the serial interface counts the clocks, and data is latched into the shift register on the 16th active clock edge. Active Low Control Input. This pin clears the DAC output, input, and DAC registers. Configuration mode allows the user to enable the hardware CLR pin as a clear-to-zero scale or midscale, as required. Positive Power Supply Input. These parts can be operated from a supply of 2.5 V to 5.5 V. DAC B Reference Voltage Input Pin. DAC B Feedback Resistor Pin. This pin establishes voltage output for the DAC by connecting to an external amplifier output. DAC B Analog Ground. This pin typically should be tied to the analog ground of the system, but it can be biased to achieve single-supply operation. DAC B Current Output. Rev. C | Page 8 of 32 AD5429/AD5439/AD5449 TYPICAL PERFORMANCE CHARACTERISTICS 0.20 TA = 25°C VREF = 10V VDD = 5V 0.10 0.05 0.05 DNL (LSB) 0.10 0 0 –0.05 –0.05 –0.10 –0.10 –0.15 –0.15 –0.20 0 50 TA = 25°C VREF = 10V VDD = 5V 0.15 100 150 200 250 CODE –0.20 04464-017 0 50 250 0.5 TA = 25°C VREF = 10V VDD = 5V 0.3 0.3 0.2 0.1 0.1 DNL (LSB) 0.2 0 –0.1 0 –0.1 –0.2 –0.2 –0.3 –0.3 –0.4 –0.4 200 400 600 800 1000 CODE –0.5 04464-018 –0.5 0 TA = 25°C VREF = 10V VDD = 5V 0.4 0 200 400 600 800 1000 04464-021 0.4 INL (LSB) 200 Figure 10. DNL vs. Code (8-Bit DAC) 0.5 4000 CODE Figure 8. INL vs. Code (10-Bit DAC) Figure 11. DNL vs. Code (10-Bit DAC) 1.0 1.0 TA = 25°C VREF = 10V VDD = 5V 0.8 0.6 0.6 0.4 0.2 0.2 DNL (LSB) 0.4 0 –0.2 0 –0.2 –0.4 –0.4 –0.6 –0.6 –0.8 –0.8 0 500 1000 TA = 25°C VREF = 10V VDD = 5V 0.8 1500 2000 2500 3000 CODE 3500 4000 04464-019 INL (LSB) 150 CODE Figure 7. INL vs. Code (8-Bit DAC) –1.0 100 04464-022 INL (LSB) 0.15 04464-020 0.20 Figure 9. INL vs. Code (12-Bit DAC) –1.0 0 500 1000 1500 2000 2500 3000 CODE Figure 12. DNL vs. Code (12-Bit DAC) Rev. C | Page 9 of 32 3500 AD5429/AD5439/AD5449 0.6 8 0.5 7 SUPPLY CURRENT (mA) TA = 25°C 0.4 MAX INL INL (LSB) 0.3 0.2 TA = 25°C VDD = 5V 0.1 6 VDD = 5V 5 4 3 0 MIN INL 2 –0.1 2 3 4 5 6 7 8 9 10 REFERENCE VOLTAGE 0 0.5 1.5 1.0 2.0 2.5 3.0 3.5 4.0 4.5 5.0 INPUT VOLTAGE (V) Figure 13. INL vs. Reference Voltage 04464-038 VDD = 2.5V 0 04464-035 –0.3 VDD = 3V 1 –0.2 Figure 16. Supply Current vs. Logic Input Voltage 1.6 –0.40 TA = 25°C VDD = 5V 1.4 –0.45 1.2 IOUT1 VDD = 5V IOUT1 LEAKAGE (nA) –0.55 –0.60 MIN DNL –0.65 0.8 IOUT1 VDD = 3V 0.6 0.4 2 3 4 5 6 7 8 9 10 0 –40 REFERENCE VOLTAGE 40 60 80 100 120 140 0.50 0.45 4 VDD = 5V 2 1 0 VDD = 2.5V –1 VDD = 5V 0.40 SUPPLY CURRENT (µA) 3 –2 0.35 ALL 0s 0.30 ALL 1s 0.25 VDD = 2.5V 0.20 0.15 ALL 1s ALL 0s 0.10 –3 0.05 VREF = 10V –40 –20 0 20 40 60 80 100 TEMPERATURE (°C) 120 140 04464-037 GAIN ERROR (mV) 20 Figure 17. IOUT1 Leakage Current vs. Temperature 5 –5 –60 0 TEMPERATURE (°C) Figure 14. DNL vs. Reference Voltage –4 –20 04464-039 0.2 04464-036 –0.70 1.0 04464-040 DNL (LSB) –0.50 0 –60 –40 –20 0 20 40 60 80 100 TEMPERATURE (°C) Figure 18. Supply Current vs. Temperature Figure 15. Gain Error vs. Temperature Rev. C | Page 10 of 32 120 AD5429/AD5439/AD5449 3 14 VDD = 5V 0 8 6 VDD = 3V 4 –3 VREF VREF VREF VREF VREF –6 VDD = 2.5V 2 1 10 100 1k 10k 100k 1M 10M –9 10k 04464-041 100M FREQUENCY (Hz) 0.045 ALL ON DB11 DB10 DB9 DB8 DB7 DB6 DB5 DB4 DB3 DB2 DB1 DB0 10 100 OUTPUT VOLTAGE (V) TA = 25°C VDD = 5V VREF = ±3.5V CCOMP = 1.8pF AMP = AD8038 1k 10k 100k FREQUENCY (Hz) 1M 100M TA = 25°C VREF = 0V AMP = AD8038 CCOMP = 1.8pF 0x7FF TO 0x800 VDD = 5V 0.035 ALL OFF 1 10M 0.040 10M 0.030 0.025 VDD = 3V 0.020 0.015 0x800 TO 0x7FF 0.010 VDD = 3V 0.005 0 –0.005 100M 04464-042 GAIN (dB) TA = 25°C LOADING ZS TO FS 1M FREQUENCY (Hz) Figure 22. Reference Multiplying Bandwidth vs. Frequency and Compensation Capacitor Figure 19. Supply Current vs. Update Rate 6 0 –6 –12 –18 –24 –30 –36 –42 –48 –54 –60 –66 –72 –78 –84 –90 –96 –102 100k –0.010 VDD = 5V 0 20 40 60 80 100 120 140 160 180 200 TIME (ns) Figure 20. Reference Multiplying Bandwidth vs. Frequency and Code Figure 23. Midscale Transition, VREF = 0 V 0.2 –1.68 OUTPUT VOLTAGE (V) –0.2 –0.4 TA = 25°C VDD = 5V VREF = ±3.5V CCOMP = 1.8pF AMP = AD8038 –0.6 –0.8 VDD = 5V –1.70 1 10 100 –1.71 –1.72 VDD = 3V –1.73 VDD = 5V –1.74 VDD = 3V –1.75 –1.76 0x800 TO 0x7FF 1k 10k 100k 1M 10M 100M FREQUENCY (Hz) 04464-043 GAIN (dB) 0 TA = 25°C VREF = 3.5V AMP = AD8038 CCOMP = 1.8pF 0x7FF TO 0x800 –1.69 Figure 21. Reference Multiplying Bandwidth—All 1s Loaded –1.77 0 20 40 60 80 100 120 140 160 TIME (ns) Figure 24. Midscale Transition, VREF = 3.5 V Rev. C | Page 11 of 32 180 200 04464-046 0 = ±2V, AD8038 C C 1.47pF = ±2V, AD8038 C C 1pF = ±0.15V, AD8038 C C 1pF = ±0.15V, AD8038 C C 1.47pF = ±3.51V, AD8038 C C 1.8pF 04464-044 GAIN (dB) 10 04464-045 12 IDD (mA) TA = 25°C VDD = 5V TA = 25°C LOADING ZS TO FS AD5429/AD5439/AD5449 20 90 TA = 25°C VDD = 3V AMP = AD8038 0 80 MCLK = 5MHz 70 MCLK = 10MHz –20 SFDR (dB) PSRR (dB) 60 –40 FULL SCALE –60 ZERO SCALE 50 MCLK = 25MHz 40 30 –80 20 1 10 100 1k 10k 100k 1M 10M FREQUENCY (Hz) 04464-047 –120 TA = 25°C VREF = 3.5V AMP = AD8038 10 0 0 100 200 300 400 500 600 700 1000 Figure 28. Wideband SFDR vs. fOUT Frequency –60 0 TA = 25°C VDD = 3V VREF = 3.5V p-p TA = 25°C VDD = 5V AMP = AD8038 65k CODES –10 –20 –30 SFDR (dB) –70 THD + N (dB) 900 fOUT (kHz) Figure 25. Power Supply Rejection Ratio vs. Frequency –65 800 04464-050 –100 –75 –40 –50 –60 –80 –70 –85 1 10 100 1k 10k 100k 1M FREQUENCY (Hz) –90 04464-048 –90 2 0 4 6 8 FREQUENCY (MHz) 10 12 04464-051 –80 Figure 29. Wideband SFDR, fOUT = 100 kHz, Clock = 25 MHz Figure 26. THD + Noise vs. Frequency 100 0 MCLK = 1MHz TA= 25°C VDD = 5V AMP = AD8038 65k CODES –10 80 –20 SFDR (dB) MCLK = 200kHz 60 MCLK = 0.5MHz 40 –40 –50 –60 –70 –80 20 0 20 40 60 80 100 120 140 160 180 fOUT (kHz) 200 –90 Figure 27. Wideband SFDR vs. fOUT Frequency –100 0 0.5 1.0 1.5 2.0 2.5 3.0 3.5 FREQUENCY (MHz) 4.0 4.5 5.0 Figure 30. Wideband SFDR, fOUT = 500 kHz, Clock = 10 MHz Rev. C | Page 12 of 32 04464-052 0 TA = 25°C VREF = 3.5V AMP = AD8038 04464-049 SFDR (dB) –30 AD5429/AD5439/AD5449 0 0 TA = 25°C VDD = 5V AMP = AD8038 65k CODES –10 –20 –20 –30 –40 IMD (dB) –40 –50 –50 –60 –60 –70 –70 –80 –80 0.5 1.0 1.5 2.0 2.5 3.0 3.5 FREQUENCY (MHz) 4.0 4.5 5.0 Figure 31. Wideband SFDR, fOUT = 50 kHz, Clock = 10 MHz 0 –20 85 95 90 100 105 FREQUENCY (kHz) 110 115 120 TA= 25°C VDD = 5V AMP = AD8038 65k CODES –10 –20 –30 –30 IMD (dB) SFDR (dB) 80 0 –40 –50 –40 –50 –60 –60 –70 –80 –90 –90 300 350 400 450 500 550 600 FREQUENCY (kHz) 650 700 750 04464-054 –70 –80 –100 250 75 Figure 34. Narrow-Band IMD, fOUT = 90 kHz, 100 kHz, Clock = 10 MHz TA= 25°C VDD = 3V AMP = AD8038 65k CODES –10 70 04464-056 0 04464-053 –90 –100 –100 Figure 32. Narrow-Band Spectral Response, fOUT = 500 kHz, Clock = 25 MHz 20 50 100 150 200 250 FREQUENCY (kHz) 300 350 400 Figure 35. Wideband IMD, fOUT = 90 kHz, 100 kHz, Clock = 25 MHz 300 TA= 25°C VDD = 3V AMP = AD8038 65k CODES 0 0 04464-057 SFDR (dB) –30 –90 TA= 25°C VDD = 3V AMP = AD8038 65k CODES –10 TA = 25°C AMP = AD8038 ZERO SCALE LOADED TO DAC 250 MIDSCALE LOADED TO DAC OUTPUT NOISE (nV/ Hz) FULL SCALE LOADED TO DAC –40 –60 –80 150 100 50 60 70 80 90 100 110 120 FREQUENCY (kHz) 130 140 150 04464-055 –100 –120 50 200 0 100 1k 10k FREQUENCY (Hz) Figure 36. Output Noise Spectral Density Figure 33. Narrow-Band SFDR, fOUT = 100 kHz, Clock = 25 MHz Rev. C | Page 13 of 32 100k 04464-058 SFDR (dB) –20 AD5429/AD5439/AD5449 TERMINOLOGY Relative Accuracy (Endpoint Nonlinearity) A measure of the maximum deviation from a straight line passing through the endpoints of the DAC transfer function. It is measured after adjusting for zero and full scale and is typically expressed in LSBs or as a percentage of the full-scale reading. Differential Nonlinearity The difference in the measured change and the ideal 1 LSB change between two adjacent codes. A specified differential nonlinearity of −1 LSB maximum over the operating temperature range ensures monotonicity. Gain Error (Full-Scale Error) A measure of the output error between an ideal DAC and the actual device output. For these DACs, ideal maximum output is VREF − 1 LSB. The gain error of the DACs is adjustable to zero with an external resistance. Output Leakage Current The current that flows into the DAC ladder switches when they are turned off. For the IOUT1x terminal, it can be measured by loading all 0s to the DAC and measuring the IOUT1 current. Minimum current flows into the IOUT2x line when the DAC is loaded with all 1s. Digital Crosstalk The glitch impulse transferred to the outputs of one DAC in response to a full-scale code change (all 0s to all 1s, or vice versa) in the input register of the other DAC. It is expressed in nV-sec. Analog Crosstalk The glitch impulse transferred to the output of one DAC due to a change in the output of another DAC. It is measured by loading one of the input registers with a full-scale code change (all 0s to all 1s, or vice versa) while keeping LDAC high and then pulsing LDAC low and monitoring the output of the DAC whose digital code has not changed. The area of the glitch is expressed in nV-sec. Channel-to-Channel Isolation The portion of input signal from the reference input of a DAC that appears at the output of another DAC. It is expressed in dB. Total Harmonic Distortion (THD) The DAC is driven by an ac reference. The ratio of the rms sum of the harmonics of the DAC output to the fundamental value is the THD. Usually only the lower-order harmonics are included, such as the second to fifth harmonics. THD = 20 log Output Capacitance Capacitance from IOUT1 or IOUT2 to AGND. Output Current Settling Time The amount of time for the output to settle to a specified level for a full-scale input change. For these devices, it is specified with a 100 Ω resistor to ground. Digital-to-Analog Glitch Impulse The amount of charge injected from the digital inputs to the analog output when the inputs change state. This is normally specified as the area of the glitch in either pA-sec or nV-sec, depending on whether the glitch is measured as a current or voltage signal. Digital Feedthrough When the device is not selected, high frequency logic activity on the digital inputs of the device is capacitively coupled through the device and produces noise on the IOUT pins and, subsequently, on the circuitry that follows. This noise is digital feedthrough. V 2 2 + V3 2 + V4 2 + V5 2 V1 Intermodulation Distortion (IMD) The DAC is driven by two combined sine wave references of Frequency fa and Frequency fb. Distortion products are produced at sum and difference frequencies of mfa ± nfb, where m, n = 0, 1, 2, 3 … Intermodulation terms are those for which m or n is not equal to 0. The second-order terms include (fa + fb) and (fa − fb), and the third-order terms are (2fa + fb), (2fa − fb), (f + 2fa + 2fb), and (fa − 2fb). IMD is defined as IMD = 20 log RMS Sum of the Sum and Diff Distortion Products RMS Amplitude of the Fundamental Compliance Voltage Range The maximum range of (output) terminal voltage for which the device provides the specified characteristics. Multiplying Feedthrough Error The error due to capacitive feedthrough from the DAC reference input to the DAC IOUT1x terminal when all 0s are loaded to the DAC. Rev. C | Page 14 of 32 AD5429/AD5439/AD5449 THEORY OF OPERATION When an output amplifier is connected in unipolar mode, the output voltage is given by DIGITAL-TO-ANALOG CONVERTER The AD5429/AD5439/AD5449 are 8-, 10-, and 12-bit, dualchannel, current output DACs consisting of a standard inverting R-2R ladder configuration. Figure 37 shows a simplified diagram for a single channel of the AD5449. The feedback resistor, RFBA, has a value of R. The value of R is typically 10 kΩ (with a minimum of 8 kΩ and a maximum of 12 kΩ). If IOUT1A and IOUT2A are kept at the same potential, a constant current flows into each ladder leg, regardless of digital input code. Therefore, the input resistance presented at VREFA is always constant. VREFA R R VOUT = − VREF × D / 2n where: D is the fractional representation of the digital word loaded to the DAC. D = 0 to 255 (AD5429) = 0 to 1023 (AD5439) = 0 to 4095 (AD5449) n is the number of bits. R 2R 2R 2R 2R S1 S2 S3 S12 With a fixed 10 V reference, the circuit shown in Figure 38 gives a unipolar 0 V to −10 V output voltage swing. When VIN is an ac signal, the circuit performs 2-quadrant multiplication. 2R R RFBA IOUT1A Table 5 shows the relationship between digital code and the expected output voltage for unipolar operation using the 8-bit AD5429 DAC. 04464-006 IOUT2A DAC DATA LATCHES AND DRIVERS Table 5. Unipolar Code Table Figure 37. Simplified Ladder Digital Input 1111 1111 1000 0000 0000 0001 0000 0000 Access is provided to the VREFx, RFBx, IOUT1x, and IOUT2x terminals of the DACs, making the devices extremely versatile and allowing them to be configured in several operating modes, such as unipolar mode, bipolar output mode, or single-supply mode. CIRCUIT OPERATION Analog Output (V) −VREF (255/256) −VREF (128/256) = −VREF/2 −VREF (1/256) −VREF (0/256) = 0 Unipolar Mode Using a single op amp, these devices can easily be configured to provide 2-quadrant multiplying operation or a unipolar output voltage swing, as shown in Figure 38. VDD R2 VREF VREF x R1 AD5429/ AD5439/ AD5449 SYNC SCLK SDIN MICROCONTROLLER C1 RFBA IOUT1A A1 IOUT2A GND VOUT = 0V TO –VREF AGND NOTES 1. R1 AND R2 USED ONLY IF GAIN ADJUSTMENT IS REQUIRED. 2. C1 PHASE COMPENSATION (1pF TO 2pF) MAY BE REQUIRED IF A1 IS A HIGH SPEED AMPLIFIER. 3. DAC B OMITTED FOR CLARITY. Figure 38. Unipolar Operation Rev. C | Page 15 of 32 04464-007 VDD AD5429/AD5439/AD5449 Bipolar Operation Stability In some applications, it may be necessary to generate full 4-quadrant multiplying operation or a bipolar output swing. This can easily be accomplished by using another external amplifier and three external resistors, as shown in Figure 39. In the I-to-V configuration, the IOUT of the DAC and the inverting node of the op amp must be connected as closely as possible, and proper PCB layout techniques must be used. Because every code change corresponds to a step function, gain peaking may occur if the op amp has limited gain bandwidth product (GBP) and there is excessive parasitic capacitance at the inverting node. This parasitic capacitance introduces a pole into the open-loop response, which can cause ringing or instability in the closedloop applications circuit. When VIN is an ac signal, the circuit performs 4-quadrant multiplication. When connected in bipolar mode, the output voltage is VOUT = (VREF × D / 2n − 1 ) − VREF As shown in Figure 38 and Figure 39, an optional compensation capacitor, C1, can be added in parallel with RFBx for stability. Too small a value of C1 can produce ringing at the output, whereas too large a value can adversely affect the settling time. C1 should be found empirically, but 1 pF to 2 pF is generally adequate for the compensation. where: D is the fractional representation of the digital word loaded to the DAC. D = 0 to 255 (AD5429) = 0 to 1023 (AD5439) = 0 to 4095 (AD5449) n is the number of bits. Table 6 shows the relationship between digital code and the expected output voltage for bipolar operation with the AD5429. Table 6. Bipolar Code Analog Output (V) +VREF (255/256) 0 −VREF (255/256) −VREF (256/256) R3 20kΩ VDD VDD R1 VREF x VREF ±10V R1 R2 AD5429/ AD5439/ AD5449 SYNC SCLK SDIN R5 20kΩ C1 RFBA IOUT1A A1 R4 10kΩ A2 IOUT2A VOUT = –VREF TO +VREF GND MICROCONTROLLER AGND NOTES 1. R1 AND R2 USED ONLY IF GAIN ADJUSTMENT IS REQUIRED. ADJUST R1 FOR VOUT = 0V WITH CODE 10000000 LOADED TO DAC. 2. MATCHING AND TRACKING IS ESSENTIAL FOR RESISTOR PAIRS R3 AND R4. 3. C1 PHASE COMPENSATION (1pF TO 2pF) MAY BE REQUIRED IF A1/A2 IS A HIGH SPEED AMPLIFIER. 4. DAC B AND ADDITIONAL PINS OMITTED FOR CLARITY. Figure 39. Bipolar Operation Rev. C | Page 16 of 32 04464-008 Digital Input 1111 1111 1000 0000 0000 0001 0000 0000 AD5429/AD5439/AD5449 Note that VIN is limited to low voltages because the switches in the DAC ladder no longer have the same source-drain drive voltage. As a result, their on resistance differs and degrades the integral linearity of the DAC. Also, VIN must not go negative by more than 0.3 V, or an internal diode turns on, causing the device to exceed the maximum ratings. In this type of application, the full range of multiplying capability of the DAC is lost. SINGLE-SUPPLY APPLICATIONS Voltage-Switching Mode Figure 40 shows the DACs operating in voltage-switching mode. The reference voltage, VIN, is applied to the IOUT1A pin; IOUT2A is connected to AGND; and the output voltage is available at the VREFA terminal. In this configuration, a positive reference voltage results in a positive output voltage, making single-supply operation possible. The output from the DAC is voltage at a constant impedance (the DAC ladder resistance). Therefore, an op amp is necessary to buffer the output voltage. The reference input no longer sees a constant input impedance; instead, it sees one that varies with code. Therefore, the voltage input should be driven from a low impedance source. Positive Output Voltage The output voltage polarity is opposite to the VREF polarity for dc reference voltages. To achieve a positive voltage output, an applied negative reference to the input of the DAC is preferred over the output inversion through an inverting amplifier because of the resistor tolerance errors. To generate a negative reference, the reference can be level-shifted by an op amp such that the VOUT and GND pins of the reference become the virtual ground and −2.5 V, respectively, as shown in Figure 41. VDD R1 R2 RFBA VDD VIN IOUT1A IOUT2A VOUT 8-/10-/12-BIT V REF A DAC NOTES 1. ADDITIONAL PINS OMITTED FOR CLARITY. 2. C1 PHASE COMPENSATION (1pF TO 2pF) MAY BE REQUIRED IF A1 IS A HIGH SPEED AMPLIFIER. 04464-009 GND Figure 40. Single-Supply Voltage-Switching Mode VDD = +5V ADR03 VOUT VIN GND +5V C1 VDD –2.5V IOUT1A VREFA 8-/10-/12-BIT IOUT2A DAC VOUT = 0V TO +2.5V GND NOTES 1. ADDITIONAL PINS OMITTED FOR CLARITY. 2. C1 PHASE COMPENSATION (1pF TO 2pF) MAY BE REQUIRED IF A1 IS A HIGH SPEED AMPLIFIER. Figure 41. Positive Voltage Output with Minimum Components Rev. C | Page 17 of 32 04464-010 –5V RFBA AD5429/AD5439/AD5449 As D is reduced, the output voltage increases. For small values of the Digital Fraction D, it is important to ensure that the amplifier does not saturate and the required accuracy is met. For example, an 8-bit DAC driven with binary code of 0x10 (0001 0000)—that is, 16 decimal—in the circuit of Figure 43 should cause the output voltage to be 16 × VIN. However, if the DAC has a linearity specification of ±0.5 LSB, D can have a weight in the range of 15.5/256 to 16.5/256, so that the possible output voltage is in the range of 15.5 VIN to 16.5 VIN. This range represents an error of 3%, even though the DAC itself has a maximum error of 0.2%. ADDING GAIN In applications in which the output voltage must be greater than VIN, gain can be added with an additional external amplifier, or it can be achieved in a single stage. Consider the effect of temperature coefficients of the thin film resistors of the DAC. Simply placing a resistor in series with the RFB resistor causes mismatches in the temperature coefficients, resulting in larger gain temperature coefficient errors. Instead, the circuit in Figure 42 shows the recommended method of increasing the gain of the circuit. R1, R2, and R3 should have similar temperature coefficients, but they need not match the temperature coefficients of the DAC. This approach is recommended in circuits in which gains of greater than 1 are required. DAC leakage current is also a potential error source in divider circuits. The leakage current must be counterbalanced by an opposite current supplied from the op amp through the DAC. Because only a fraction, D, of the current into the VREFx terminal is routed to the IOUT1 terminal, the output voltage changes as follows: DIVIDER OR PROGRAMMABLE GAIN ELEMENT Current-steering DACs are very flexible and lend themselves to many applications. If this type of DAC is connected as the feedback element of an op amp and RFBA is used as the input resistor, as shown in Figure 43, the output voltage is inversely proportional to the digital input fraction, D. Output Error Voltage Due to DAC Leakage = (Leakage × R)/D where R is the DAC resistance at the VREFx terminal. For a DAC leakage current of 10 nA, R = 10 kΩ, and a gain (that is, 1/D) of 16, the error voltage is 1.6 mV. For D = 1 − 2−n, the output voltage is VOUT = − VIN / D = − VIN / (1 − 2 − n ) VDD VIN R1 C1 RFBA IOUT1A VREFA 8-/10-/12-BIT DAC IOUT2A VOUT R3 GND R2 GAIN = R2 + R3 R2 R2R3 R1 = R2 + R3 NOTES 1. ADDITIONAL PINS OMITTED FOR CLARITY. 2. C1 PHASE COMPENSATION (1pF TO 2pF) MAY BE REQUIRED IF A1 IS A HIGH SPEED AMPLIFIER. 04464-011 VDD Figure 42. Increasing Gain of Current Output DAC VDD VIN RFBA IOUT1A IOUT2A VDD 8-/10-/12-BIT V REF A DAC GND NOTES 1. ADDITIONAL PINS OMITTED FOR CLARITY. 04464-012 VOUT Figure 43. Current-Steering DAC Used as a Divider or Programmable Gain Element Rev. C | Page 18 of 32 AD5429/AD5439/AD5449 voltage change is superimposed on the desired change in output between the two codes and gives rise to a differential linearity error, which, if large enough, could cause the DAC to be nonmonotonic. The input bias current of an op amp also generates an offset at the voltage output as a result of the bias current flowing in the feedback resistor, RFB. Most op amps have input bias currents low enough to prevent significant errors in 12-bit applications. REFERENCE SELECTION When selecting a reference for use with the AD54xx series of current output DACs, pay attention to the reference output voltage temperature coefficient specification. This parameter affects not only the full-scale error, but it can also affect the linearity (INL and DNL) performance. The reference temperature coefficient should be consistent with the system accuracy specifications. For example, an 8-bit system required to hold its overall specification to within 1 LSB over the temperature range of 0°C to 50°C dictates that the maximum system drift with temperature should be less than 78 ppm/°C. A 12-bit system with the same temperature range to overall specification within 2 LSBs requires a maximum drift of 10 ppm/°C. By choosing a precision reference with a low output temperature coefficient, this error source can be minimized. Table 7 lists some references available from Analog Devices, Inc., that are suitable for use with this range of current output DACs. Common-mode rejection of the op amp is important in voltageswitching circuits because it produces a code-dependent error at the voltage output of the circuit. Most op amps have adequate common-mode rejection for use at 8-, 10-, and 12-bit resolution. If the DAC switches are driven from true wideband low impedance sources (VIN and AGND), they settle quickly. Consequently, the slew rate and settling time of a voltage-switching DAC circuit is determined largely by the output op amp. To obtain minimum settling time in this configuration, minimize capacitance at the VREF node (the voltage output node in this application) of the DAC by using low input capacitance buffer amplifiers and careful board design. AMPLIFIER SELECTION The primary requirement for the current-steering mode is an amplifier with low input bias currents and low input offset voltage. Because of the code-dependent output resistance of the DAC, the input offset voltage of an op amp is multiplied by the variable gain of the circuit. A change in this noise gain between two adjacent digital fractions produces a step change in the output voltage due to the amplifier input offset voltage. This output Most single-supply circuits include ground as part of the analog signal range, which, in turn, requires an amplifier that can handle rail-to-rail signals. Analog Devices offers a wide range of singlesupply amplifiers (see Table 8 and Table 9). Table 7. Suitable Analog Devices Precision References Part No. ADR01 ADR01 ADR02 ADR02 ADR03 ADR03 ADR06 ADR06 ADR431 ADR435 ADR391 ADR395 Output Voltage (V) 10 10 5 5 2.5 2.5 3 3 2.5 5 2.5 5 Initial Tolerance (%) 0.05 0.05 0.06 0.06 0.10 0.10 0.10 0.10 0.04 0.04 0.16 0.10 Temp Drift (ppm/°C) 3 9 3 9 3 9 3 9 3 3 9 9 ISS (mA) 1 1 1 1 1 1 1 1 0.8 0.8 0.12 0.12 Output Noise (μV p-p) 20 20 10 10 6 6 10 10 3.5 8 5 8 Package SOIC-8 TSOT-23, SC70 SOIC-8 TSOT-23, SC70 SOIC-8 TSOT-23, SC70 SOIC-8 TSOT-23, SC70 SOIC-8 SOIC-8 TSOT-23 TSOT-23 Table 8. Suitable Analog Devices Precision Op Amps Part No. OP97 OP1177 AD8551 AD8603 AD8628 Supply Voltage (V) ±2 to ±20 ±2.5 to ±15 2.7 to 5 1.8 to 6 2.7 to 6 VOS (Max) (μV) 25 60 5 50 5 IB (Max) (nA) 0.1 2 0.05 0.001 0.1 0.1 Hz to 10 Hz Noise (μV p-p) 0.5 0.4 1 2.3 0.5 Supply Current (μA) 600 500 975 50 850 Package SOIC-8 MSOP, SOIC-8 MSOP, SOIC-8 TSOT TSOT, SOIC-8 Table 9. Suitable Analog Devices High Speed Op Amps Part No. AD8065 AD8021 AD8038 AD9631 Supply Voltage (V) 5 to 24 ±2.5 to ±12 3 to 12 ±3 to ±6 BW @ ACL (MHz) 145 490 350 320 Slew Rate (V/μs) 180 120 425 1300 Rev. C | Page 19 of 32 VOS (Max) (μV) 1500 1000 3000 10,000 IB (Max) (nA) 6000 10,500 750 7000 Package SOIC-8, SOT-23, MSOP SOIC-8, MSOP SOIC-8, SC70-5 SOIC-8 AD5429/AD5439/AD5449 SERIAL INTERFACE SDO Control (SDO1 and SDO2) The AD5429/AD5439/AD5449 have an easy-to-use, 3-wire interface that is compatible with SPI, QSPI, MICROWIRE, and most DSP interface standards. Data is written to the device in 16-bit words. Each 16-bit word consists of four control bits and eight, 10, or 12 data bits, as shown in Figure 44 through Figure 46. The SDO bits enable the user to control the SDO output driver strength, disable the SDO output, or configure it as an open-drain driver. The strength of the SDO driver affects the timing of t12, and, when stronger, allows a faster clock cycle. Low Power Serial Interface To minimize the power consumption of the device, the interface powers up fully only when the device is being written to, that is, on the falling edge of SYNC. The SCLK and SDIN input buffers are powered down on the rising edge of SYNC. SDO2 0 SDO1 0 Function Implemented Full SDO driver 0 1 1 1 0 1 Weak SDO driver SDO configured as open drain Disable SDO output DAC Control Bit C3 to Control Bit C0 Daisy-Chain Control (DSY) Control Bit C3 to Control Bit C0 allow control of various functions of the DAC, as shown in Table 11. The default settings of the DAC at power-on are such that data is clocked into the shift register on falling clock edges and daisy-chain mode is enabled. The device powers on with a zero-scale load to the DAC register and IOUT lines. The DAC control bits allow the user to adjust certain features at power-on. For example, daisy-chaining can be disabled if not in use, an active clock edge can be changed to a rising edge, and DAC output can be cleared to either zero scale or midscale. The user can also initiate a readback of the DAC register contents for verification. DSY allows the enabling or disabling of daisy-chain mode. A 1 enables daisy-chain mode; a 0 disables daisy-chain mode. When disabled, a readback request is accepted; SDO is automatically enabled; the DAC register contents of the relevant DAC are clocked out on SDO; and, when complete, SDO is disabled again. Table 10. SDO Control Bits Hardware CLR Bit (HCLR) The default setting for the hardware CLR bit is to clear the registers and DAC output to zero code. A 1 in the HCLR bit allows the CLR pin to clear the DAC outputs to midscale, and a 0 clears to zero scale. Control Register (Control Bits = 1101) Active Clock Edge (SCLK) While maintaining software compatibility with single-channel current output DACs (AD5426/AD5432/AD5443), these DACs also feature additional interface functionality. Set the control bits to 1101 to enter control register mode. Figure 47 shows the contents of the control register, the functions of which are described in the following sections. The default active clock edge is a falling edge. Write a 1 to this bit to clock data in on the rising edge, or a 0 to clock it in on the falling edge. C3 DB0 (LSB) C2 C1 C0 DB7 DB6 DB5 DB4 DB3 CONTROL BITS DB2 DB1 DB0 0 0 0 0 DATA BITS 04464-013 DB15 (MSB) Figure 44. AD5429 8-Bit Input Shift Register Contents C3 DB0 (LSB) C2 C1 C0 DB9 DB8 DB7 DB6 DB5 CONTROL BITS DB4 DB3 DB2 DB1 DB0 0 0 DATA BITS 04464-014 DB15 (MSB) Figure 45. AD5439 10-Bit Input Shift Register Contents C3 DB0 (LSB) C2 C1 C0 DB11 DB10 DB9 DB8 DB7 CONTROL BITS DB6 DB5 DB4 DB3 DB2 DB1 DB0 DATA BITS 04464-015 DB15 (MSB) Figure 46. AD5449 12-Bit Input Shift Register Contents 1 DB0 (LSB) 1 0 1 SDO2 SDO1 DSY HCLR SCLK X X X CONTROL BITS Figure 47. Control Register Loading Sequence Rev. C | Page 20 of 32 X X X X 04464-016 DB15 (MSB) AD5429/AD5439/AD5449 SYNC Function SYNC is an edge-triggered input that acts as a frame synchronization signal and chip enable. Data can be transferred into the device only while SYNC is low. To start the serial data transfer, SYNC should be taken low, observing the minimum SYNC falling edge to SCLK falling edge setup time, t4. Daisy-Chain Mode Daisy-chain mode is the default power-on mode. To disable the daisy-chain function, write 1001 to the control word. In daisychain mode, the internal gating on SCLK is disabled. SCLK is continuously applied to the input shift register when SYNC is low. If more than 16 clock pulses are applied, the data ripples out of the shift register and appears on the SDO line. This data is clocked out on the rising edge of SCLK (this is the default; use the control word to change the active edge) and is valid for the next device on the falling edge of SCLK (default). By connecting this line to the SDIN input on the next device in the chain, a multidevice interface is constructed. For each device in the system, 16 clock pulses are required. Therefore, the total number of clock cycles must equal 16n, where n is the total number of devices in the chain. See Figure 4. When the serial transfer to all devices is complete, SYNC should be taken high. This prevents additional data from being clocked into the input shift register. A burst clock containing the exact number of clock cycles can be used, after which SYNC can be taken high. After the rising edge of SYNC, data is automatically transferred from the input shift register of each device to the addressed DAC. When control bits = 0000, the device is in no operation mode. This may be useful in daisy-chain applications in which the user does not want to change the settings of a particular DAC in the chain. Write 0000 to the control bits for that DAC; subsequent data bits are ignored. Standalone Mode After power-on, write 1001 to the control word to disable daisychain mode. The first falling edge of SYNC resets the serial clock counter to ensure that the correct number of bits are shifted in and out of the serial shift registers. A SYNC edge during the 16-bit write cycle causes the device to abort the current write cycle. After the falling edge of the 16th SCLK pulse, data is automatically transferred from the input shift register to the DAC. For another serial transfer to take place, the counter must be reset by the falling edge of SYNC. LDAC Function The LDAC function allows asynchronous and synchronous updates to the DAC output. The DAC is asynchronously updated when this signal goes low. Alternatively, if this line is held permanently low, an automatic or synchronous update mode is selected, whereby the DAC is updated on the 16th clock falling edge when the device is in standalone mode, or on the rising edge of SYNC when the device is in daisy-chain mode. Software LDAC Function Load-and-update mode can also serve as a software update function, irrespective of the voltage level on the LDAC pin. Table 11. DAC Control Bits C3 0 0 0 0 0 0 0 0 1 1 1 1 1 1 1 1 C2 0 0 0 0 1 1 1 1 0 0 0 0 1 1 1 1 C1 0 0 1 1 0 0 1 1 0 0 1 1 0 0 1 1 C0 0 1 0 1 0 1 0 1 0 1 0 1 0 1 0 1 DAC A and B A A A B B B A and B A and B N/A N/A N/A N/A N/A N/A N/A Function Implemented No operation (power-on default) Load and update Initiate readback Load input register Load and update Initiate readback Load input register Update DAC outputs Load input registers Disable daisy-chain Clock data to shift register on rising edge Clear DAC output to zero scale Clear DAC output to midscale Control word Reserved No operation Rev. C | Page 21 of 32 AD5429/AD5439/AD5449 MICROPROCESSOR INTERFACING Microprocessor interfacing to the AD54xx family of DACs is through a serial bus that uses standard protocol and is compatible with microcontrollers and DSP processors. The communication channel is a 3-wire interface consisting of a clock signal, a data signal, and a synchronization signal. The AD5429/AD5439/ AD5449 require a 16-bit word, with the default being data valid on the falling edge of SCLK; however, this is changeable using the control bits in the data-word. ADSP-21xx-to-AD5429/AD5439/AD5449 Interface The ADSP-21xx family of DSPs is easily interfaced to an AD5429/ AD5439/AD5449 DAC without the need for extra glue logic. Figure 48 is an example of a serial peripheral interface (SPI) between the DAC and the ADSP-2191. The MOSI (master output, slave input) pin of the DSP drives the serial data line, SDIN. SYNC is driven from a port line, in this case SPIxSEL. *ADDITIONAL PINS OMITTED FOR CLARITY. SPIxSEL The ADSP-2101/ADSP-2103/ADSP-2191 processor incorporates channel synchronous serial ports (SPORT). A serial interface between the DAC and DSP SPORT is shown in Figure 49. In this interface example, SPORT0 is used to transfer data to the DAC shift register. Transmission is initiated by writing a word to the Tx register after SPORT has been enabled. In a write sequence, data is clocked out on each rising edge of the DSP serial clock and clocked into the DAC input shift register on the falling edge of its SCLK. Updating of the DAC output takes place on the rising edge of the SYNC signal. AD5429/AD5439/ AD5449* TFS SYNC DT SDIN SDIN SCK SCLK Figure 50. ADSP-BF5xx-to-AD5429/AD5439/AD5449 Interface A serial interface between the DAC and the DSP SPORT is shown in Figure 51. When SPORT is enabled, initiate transmission by writing a word to the Tx register. The data is clocked out on each rising edge of the DSP serial clock and clocked into the DAC input shift register on the falling edge of its SCLK. The DAC output is updated by using the transmit frame synchronization (TFS) line to provide a SYNC signal. AD5429/AD5439/ AD5449* ADSP-BF5xx* SCLK *ADDITIONAL PINS OMITTED FOR CLARITY. Figure 49. ADSP-2101/ADSP-2103/ADSP-2191 SPORT-toAD5429/AD5439/AD5449 Interface SYNC MOSI *ADDITIONAL PINS OMITTED FOR CLARITY. 04464-028 SCLK AD5429/AD5439/ AD5449* ADSP-BF5xx* Figure 48. ADSP-2191 SPI-to-AD5429/AD5439/AD5449 Interface ADSP-2101/ ADSP-2103/ ADSP-2191* Description Alternate framing Active low frame signal Right-justify data Internal serial clock Frame every word Internal framing signal 16-bit data-word 04464-033 SCLK 04464-027 SDIN SCK Setting 1 1 00 1 1 1 1111 The ADSP-BF5xx family of processors has an SPI-compatible port that enables the processor to communicate with SPI-compatible devices. A serial interface between the BlackFin® processor and the AD5429/AD5439/AD5449 DAC is shown in Figure 50. In this configuration, data is transferred through the MOSI pin. SYNC is driven by the SPIxSEL pin, which is a reconfigured programmable flag pin. SYNC MOSI Name TFSW INVTFS DTYPE ISCLK TFSR ITFS SLEN TFS SYNC DT SDIN SCLK SCLK *ADDITIONAL PINS OMITTED FOR CLARITY. Communication between two devices at a given clock speed is possible when the following specifications are compatible: frame SYNC delay and frame SYNC setup-and-hold, data delay and data setup-and-hold, and SCLK width. The DAC interface expects a t4 (SYNC falling edge to SCLK falling edge setup time) of 13 ns minimum. Figure 51. ADSP-BF5xx SPORT-to-AD5429/AD5439/AD5449 Interface Rev. C | Page 22 of 32 04464-034 SPIxSEL Table 12. SPORT Control Register Setup ADSP-BF5xx-to-AD5429/AD5439/AD5449 Interface AD5429/AD5439/ AD5449* ADSP-2191* See the ADSP-21xx user manual at www.analog.com for details on clock and frame SYNC frequencies for the SPORT register. Table 12 shows the setup for the SPORT control register. AD5429/AD5439/AD5449 To load data correctly to the DAC, P1.1 is left low after the first eight bits are transmitted, and then a second write cycle is initiated to transmit the second byte of data. Data on RxD is clocked out of the microcontroller on the rising edge of TxD and is valid on the falling edge of TxD. As a result, no glue logic is required between the DAC and microcontroller interface. P1.1 is taken high following the completion of this cycle. The 80C51/80L51 provide the LSB of the SBUF register as the first bit in the data stream. The DAC input register requires its data with the MSB as the first bit received. The transmit routine should take this requirement into account. To load data to the DAC, leave PC7 low after the first eight bits are transferred and perform a second serial write operation to the DAC. PC7 is taken high at the end of this procedure. If the user wants to verify the data previously written to the input shift register, the SDO line can be connected to MISO of the MC68HC11, and, with SYNC low, the shift register clocks data out on the rising edges of SCLK. MICROWIRE-to-AD5429/AD5439/AD5449 Interface Figure 54 shows an interface between the DAC and any MICROWIRE-compatible device. Serial data is shifted out on the falling edge of the serial clock, SK, and is clocked into the DAC input shift register on the rising edge of SK, which corresponds to the falling edge of the DAC SCLK. MICROWIRE* AD5429/AD5439/ AD5449* 80C51* SCLK RxD SDIN P1.1 SYNC *ADDITIONAL PINS OMITTED FOR CLARITY. Figure 52. 80C51/80L51-to-AD5429/AD5439/AD5449 Interface MC68HC11-to-AD5429/AD5439/AD5449 Interface Figure 53 is an example of a serial interface between the DAC and the MC68HC11 microcontroller. The SPI on the MC68HC11 is configured for master mode (MSTR) = 1, clock polarity bit (CPOL) = 0, and clock phase bit (CPHA) = 1. The SPI is configured by writing to the SPI control register (SPCR); see the MC68HC11 user manual. The SCK of the MC68HC11 drives the SCLK of the DAC interface; the MOSI output drives the serial data line (SDIN) of the AD5429/AD5439/AD5449. MC68HC11* MOSI SDIN SYNC The PIC16C6x/7x synchronous serial port (SSP) is configured as an SPI master with the clock polarity bit (CKP) = 0. This is done by writing to the synchronous serial port control register (SSPCON). See the PIC16/17 microcontroller user manual for more information. In this example, the I/O port, RA1, is used to provide a SYNC signal and enable the serial port of the DAC. This microcontroller transfers only eight bits of data during each serial transfer operation; therefore, two consecutive write operations are required. Figure 55 shows the connection diagram. PIC16C6x/7x* AD5429/AD5439/ AD5449* SCK/RC3 SCLK SDI/RC4 SDIN RA1 04464-030 SCLK SDIN CS PIC16C6x/7x-to-AD5429/AD5439/AD5449 Interface SYNC SCK SCLK Figure 54. MICROWIRE-to-AD5429/AD5439/AD5449 Interface AD5429/AD5439/ AD5449* PC7 SK SO *ADDITIONAL PINS OMITTED FOR CLARITY. 04464-029 TxD AD5429/AD5439/ AD5449* 04464-031 A serial interface between the DAC and the 80C51/80L51 is shown in Figure 52. TxD of the 80C51/80L51 drives SCLK of the DAC serial interface, and RxD drives the serial data line, SDIN. P1.1 is a bit-programmable pin on the serial port and is used to drive SYNC. When data is to be transmitted to the switch, P1.1 is taken low. The 80C51/80L51 transmit data in 8-bit bytes only; therefore, only eight falling clock edges occur in the transmit cycle. valid on the falling edge of SCK. Serial data from the 68HC11 is transmitted in 8-bit bytes with only eight falling clock edges occurring in the transmit cycle. Data is transmitted MSB first. *ADDITIONAL PINS OMITTED FOR CLARITY. SYNC *ADDITIONAL PINS OMITTED FOR CLARITY. Figure 53. MCH68HC11/68L11-to-AD5429/AD5439/AD5449 Interface The SYNC signal is derived from a port line (PC7). When data is being transmitted to the AD5429/AD5439/AD5449, the SYNC line is taken low (PC7). Data appearing on the MOSI output is Rev. C | Page 23 of 32 Figure 55. PIC16C6x/7x-to-AD5429/AD5439/AD5449 Interface 04464-032 80C51/80L51-to-AD5429/AD5439/AD5449 Interface AD5429/AD5439/AD5449 PCB LAYOUT AND POWER SUPPLY DECOUPLING In any circuit where accuracy is important, careful consideration of the power supply and ground return layout helps to ensure the rated performance. The printed circuit board on which the AD5429/AD5439/AD5449 is mounted should be designed so that the analog and digital sections are separate and confined to certain areas of the board. If the DAC is in a system where multiple devices require an AGND-to-DGND connection, the connection should be made at one point only. The star ground point should be established as close as possible to the device. The DAC should have ample supply bypassing of 10 μF in parallel with 0.1 μF on the supply, located as close as possible to the package, ideally right up against the device. The 0.1 μF capacitor should have low effective series resistance (ESR) and low effective series inductance (ESI), such as the common ceramic types of capacitors that provide a low impedance path to ground at high frequencies, to handle transient currents due to internal logic switching. Low ESR, 1 μF to 10 μF tantalum or electrolytic capacitors should also be applied at the supplies to minimize transient disturbance and filter out low frequency ripple. layout reduces the effects of feedthrough on the board. A microstrip technique is by far the best method, but its use is not always possible with a double-sided board. In this technique, the component side of the board is dedicated to the ground plane, and signal traces are placed on the soldered side. It is good practice to use compact, minimum lead-length PCB layout design. Leads to the input should be as short as possible to minimize IR drops and stray inductance. The PCB metal traces between VREFx and RFBx should also be matched to minimize gain error. To maximize high frequency performance, the I-to-V amplifier should be located as close as possible to the device. EVALUATION BOARD FOR THE DAC The evaluation board consists of an AD5429/AD5439/AD5449 DAC and a current-to-voltage amplifier, the AD8065. Included on the evaluation board is a 10 V reference, the ADR01. An external reference can also be applied via an SMB input. The evaluation kit consists of a CD-ROM with self-installing PC software to control the DAC. The software allows the user to write a code to the device. Power Supplies for the Evaluation Board Components, such as clocks, that produce fast-switching signals, should be shielded with digital ground to avoid radiating noise to other parts of the board, and they should never be run near the reference inputs. The board requires ±12 V and +5 V supplies. The +12 V VDD and −12 V VSS are used to power the output amplifier; the +5 V supply is used to power the DAC (VDD) and transceivers (VCC). Avoid crossover of digital and analog signals. Traces on opposite sides of the board should run at right angles to each other. This Both supplies are decoupled to their respective ground plane with 10 μF tantalum and 0.1 μF ceramic capacitors. Rev. C | Page 24 of 32 Figure 56. Schematic of the Evaluation Board Rev. C | Page 25 of 32 04464-023 P1–19 P1–20 P1–21 P1–22 P1–23 P1–24 P1–25 P1–26 P1–27 P1–28 P1–29 P1–30 P1–6 P1–13 P1–5 P1–4 P1–2 P1–3 P2–4 P2–1 P2–2 P2–3 LDAC SDIN SCLK C15 0.1µF C13 0.1µF C11 0.1µF + + + A B C16 10µF C14 10µF C12 10µF LK2 R1 10kΩ VDD R2 10kΩ VDD R3 10kΩ VDD SDO VSS VDD1 AGND VDD J6 J5 J4 J3 CLR C3 10µF J7 LDAC SYNC SDIN SCLK 7 SCLK CLR SDO + VDD C4 0.1µF RFBB VREF A IOUT2A IOUT1A RFBB IOUT2B IOUT1B 5 TRIM 3 +V IN 4 GND U2 J8 1 LK1 B C5 0.1µF VREF B J9 VREF A VOUT 4 VREF B VREF A 5 13 4 2 1 3 15 16 14 C1 0.1µF + C2 10µF VREF B GND LDAC SYNC SDIN 12 VDD AD5429/AD5439/ AD5449 11 9 6 8 10 U1 VDD1 A C6 1.8pF C17 1.8pF VDD 7 V– V+ 3 U3 4 7 V– V+ 4 2 VSS VDD U4 3 2 VSS C10 0.1µF + C9 10µF AD8065AR 6 C8 0.1µF + C7 10µF C21 0.1µF + C20 10µF AD8065AR 6 C19 0.1µF + C18 10µF TP1 TP2 J1 J2 VOUT A VOUT B AD5429/AD5439/AD5449 Evaluation Board Schematic and Artwork 04464-024 AD5429/AD5439/AD5449 04464-025 Figure 57. Component-Side Artwork Figure 58. Silkscreen—Component-Side View (Top) Rev. C | Page 26 of 32 04464-026 AD5429/AD5439/AD5449 Figure 59. Solder-Side Artwork Rev. C | Page 27 of 32 AD5429/AD5439/AD5449 OVERVIEW OF AD54xx DEVICES Table 13. Part No. AD5424 AD5426 AD5428 AD5429 AD5450 AD5432 AD5433 AD5439 AD5440 AD5451 AD5443 AD5444 AD5415 AD5405 AD5445 AD5447 AD5449 AD5452 AD5446 AD5453 AD5553 AD5556 AD5555 AD5557 AD5543 AD5546 AD5545 AD5547 1 Resolution 8 8 8 8 8 10 10 10 10 10 12 12 12 12 12 12 12 12 14 14 14 14 14 14 16 16 16 16 No. DACs 1 1 2 2 1 1 1 2 2 1 1 1 2 2 2 2 2 1 1 1 1 1 2 2 1 1 2 2 INL (LSB) ±0.25 ±0.25 ±0.25 ±0.25 ±0.25 ±0.5 ±0.5 ±0.5 ±0.5 ±0.25 ±1 ±0.5 ±1 ±1 ±1 ±1 ±1 ±0.5 ±1 ±2 ±1 ±1 ±1 ±1 ±2 ±2 ±2 ±2 Interface Parallel Serial Parallel Serial Serial Serial Parallel Serial Parallel Serial Serial Serial Serial Parallel Parallel Parallel Serial Serial Serial Serial Serial Parallel Serial Parallel Serial Parallel Serial Parallel Package 1 RU-16, CP-20 RM-10 RU-20 RU-10 UJ-8 RM-10 RU-20, CP-20 RU-16 RU-24 UJ-8 RM-10 RM-8 RU-24 CP-40 RU-20, CP-20 RU-24 RU-16 UJ-8, RM-8 RM-8 UJ-8, RM-8 RM-8 RU-28 RM-8 RU-38 RM-8 RU-28 RU-16 RU-38 RU = TSSOP, CP = LFCSP, RM = MSOP, UJ = TSOT. Rev. C | Page 28 of 32 Features 10 MHz BW, 17 ns CS pulse width 10 MHz BW, 50 MHz serial 10 MHz BW, 17 ns CS pulse width 10 MHz BW, 50 MHz serial 10 MHz BW, 50 MHz serial 10 MHz BW, 50 MHz serial 10 MHz BW, 17 ns CS pulse width 10 MHz BW, 50 MHz serial 10 MHz BW, 17 ns CS pulse width 10 MHz BW, 50 MHz serial 10 MHz BW, 50 MHz serial 10 MHz BW, 50 MHz serial 10 MHz BW, 50 MHz serial 10 MHz BW, 17 ns CS pulse width 10 MHz BW, 17 ns CS pulse width 10 MHz BW, 17 ns CS pulse width 10 MHz BW, 50 MHz serial 10 MHz BW, 50 MHz serial 10 MHz BW, 50 MHz serial 10 MHz BW, 50 MHz serial 4 MHz BW, 50 MHz serial clock 4 MHz BW, 20 ns WR pulse width 4 MHz BW, 50 MHz serial clock 4 MHz BW, 20 ns WR pulse width 4 MHz BW, 50 MHz serial clock 4 MHz BW, 20 ns WR pulse width 4 MHz BW, 50 MHz serial clock 4 MHz BW, 20 ns WR pulse width AD5429/AD5439/AD5449 OUTLINE DIMENSIONS 5.10 5.00 4.90 16 9 4.50 4.40 4.30 6.40 BSC 1 8 PIN 1 1.20 MAX 0.15 0.05 0.65 BSC 0.30 0.19 COPLANARITY 0.10 0.20 0.09 SEATING PLANE 0.75 0.60 0.45 8° 0° COMPLIANT TO JEDEC STANDARDS MO-153-AB Figure 60. 16-Lead Thin Shrink Small Outline Package [TSSOP] (RU-16) Dimensions shown in millimeters ORDERING GUIDE Model 1 AD5429YRU AD5429YRU-REEL AD5429YRU-REEL7 AD5429YRUZ AD5429YRUZ-REEL AD5429YRUZ-REEL7 AD5439YRU AD5439YRU-REEL AD5439YRU-REEL7 AD5439YRUZ AD5439YRUZ-REEL AD5439YRUZ-REEL7 AD5449YRU AD5449YRU-REEL AD5449YRU-REEL7 AD5449YRUZ AD5449YRUZ-REEL AD5449YRUZ-REEL7 EVAL-AD5429EBZ EVAL-AD5439EB EVAL-AD5449EBZ 1 Resolution 8 8 8 8 8 8 10 10 10 10 10 10 12 12 12 12 12 12 INL (LSB) ±0.5 ±0.5 ±0.5 ±0.5 ±0.5 ±0.5 ±0.5 ±0.5 ±0.5 ±0.5 ±0.5 ±0.5 ±1 ±1 ±1 ±1 ±1 ±1 Temperature Range −40°C to +125°C −40°C to +125°C −40°C to +125°C −40°C to +125°C −40°C to +125°C −40°C to +125°C −40°C to +125°C −40°C to +125°C −40°C to +125°C −40°C to +125°C −40°C to +125°C −40°C to +125°C −40°C to +125°C −40°C to +125°C −40°C to +125°C −40°C to +125°C −40°C to +125°C −40°C to +125°C Z = RoHS Compliant Part. Rev. C | Page 29 of 32 Package Description 16-Lead TSSOP 16-Lead TSSOP 16-Lead TSSOP 16-Lead TSSOP 16-Lead TSSOP 16-Lead TSSOP 16-Lead TSSOP 16-Lead TSSOP 16-Lead TSSOP 16-Lead TSSOP 16-Lead TSSOP 16-Lead TSSOP 16-Lead TSSOP 16-Lead TSSOP 16-Lead TSSOP 16-Lead TSSOP 16-Lead TSSOP 16-Lead TSSOP Evaluation Board Evaluation Board Evaluation Board Package Option RU-16 RU-16 RU-16 RU-16 RU-16 RU-16 RU-16 RU-16 RU-16 RU-16 RU-16 RU-16 RU-16 RU-16 RU-16 RU-16 RU-16 RU-16 AD5429/AD5439/AD5449 NOTES Rev. C | Page 30 of 32 AD5429/AD5439/AD5449 NOTES Rev. C | Page 31 of 32 AD5429/AD5439/AD5449 NOTES ©2004–2010 Analog Devices, Inc. All rights reserved. Trademarks and registered trademarks are the property of their respective owners. D04464-0-4/10(C) Rev. C | Page 32 of 32