TC1027 Linear Building Block – Quad Low Power Comparator and Voltage Reference Features General Description • Combines Four Comparators and a Voltage Reference in a Single Package • Optimized for Single Supply Operation • Small Package: 16-Pin SOIC, 16-Pin QSOP or 16-Pin PDIP (Narrow) • Ultra Low Input Bias Current: Less than 100pA • Low Quiescent Current: 18µA (Typ.) • Operates Down to VDD = 1.8V Min The TC1027 is a mixed-function device combining four general purpose comparators and a voltage reference in a single 16-pin package. This increased integration allows the user to replace two packages, which saves space, lowers supply current, and increases system performance. Applications • Power Management Circuits • Battery Operated Equipment • Consumer Products Packaged in a 16-Pin QSOP, 16-Pin SOIC (0.150 wide) or 16-Pin PDIP, the TC1027 is ideal for applications requiring high integration, small size and low power. Device Selection Table Functional Block Diagram 16-Pin PDIP -40°C to +85°C TC1027CEQR 16-Pin QSOP -40°C to +85°C TC1027CEOR 16-Pin SOIC -40°C to +85°C OUTC OUTA 2 15 OUTD VDD 3 14 VSS INA- 4 13 IND+ INA+ 5 12 IND- INB- 6 11 INC+ INB+ 7 10 INC- REF+ 8 9 GND TC1027CEPR TC1027CEQR TC1027CEOR 2002 Microchip Technology Inc. INA+ 13 5 12 B INB- INB+ REF+ 6 11 10 7 8 OUTD VSS IND+ IND- C + 16 14 4 + 1 3 OUTC D + INA- OUTB 15 A VDD 16-Pin PDIP 16-Pin QSOP 16-Pin SOIC 16 2 + Package Types OUTA TC1027 1 – TC1027CEPR OUTB – Package – Temperature Range – Part Number The TC1027 is optimized for low supply voltage and very low supply current operation (18µA typ), making it ideal for battery-operated applications. The comparators have rail-to-rail inputs and outputs which allows operation from low supply voltages with large input and output signal swings. Voltage Reference 9 INC+ INC- GND DS21284B-page 1 TC1027 1.0 ELECTRICAL CHARACTERISTICS *Stresses above those listed under "Absolute Maximum Ratings" may cause permanent damage to the device. These are stress ratings only and functional operation of the device at these or any other conditions above those indicated in the operation sections of the specifications is not implied. Exposure to Absolute Maximum Rating conditions for extended periods may affect device reliability. ABSOLUTE MAXIMUM RATINGS* Supply Voltage ......................................................6.0V Voltage on Any Pin .......... (V SS – 0.3V) to (VDD + 0.3V) Junction Temperature....................................... +150°C Operating Temperature Range............. -40°C to +85°C Storage Temperature Range .............. -55°C to +150°C TC1027 ELECTRICAL SPECIFICATIONS Electrical Characteristics: Typical values apply at 25°C and VDD = 3.0V. Minimum and maximum values apply for TA = -40° to +85°C, and VDD = 1.8V to 5.5V, unless otherwise specified. Symbol Parameter Min Typ Max Units VDD Supply Voltage 1.8 — 5.5 V IQ Supply Current — 18 26 µA Test Conditions All outputs unloaded Comparator VICMR Common Mode Input Voltage Range VSS – 0.2 — VDD + 0.2 V VOS Input Offset Voltage -5 -5 — +5 +5 mV mV VDD = 3V, VCM = 1.5V, TA = 25°C TA = -40°C to 85°C IB Input Bias Current — — ±100 pA TA = 25°C, IN+,IN- = VDD to VSS VOH Output High Voltage VDD – 0.3 — — V RL = 10kΩ to VSS VOL Output Low Voltage — — 0.3 V RL = 10kΩ to VDD CMRR Common Mode Rejection Ratio 66 — — dB TA = 25°C, VDD = 5V VCM = VDD to VSS PSRR Power Supply Rejection Ratio 60 — — dB TA = 25°C, VCM = 1.2V VDD = 1.8V to 5V ISRC Output Source Current 1 — — mA IN+ = VDD , IN- = VSS, Output Shorted to VSS VDD = 1.8V ISINK Output Sink Current 2 — — mA IN+ = VSS, IN- = VDD, Output Shorted to VDD VDD = 1.8V tPD1 Response Time — 4 — µsec 100mV Overdrive, CL = 100pF tPD2 Response Time — 6 — µsec 10mV Overdrive, CL = 100pF 1.176 1.200 1.224 V 50 — — µA 50 — — µA Voltage Reference VREF Reference Voltage IREF(SOURCE) Source Current IREF(SINK) Sink Current CL(REF) Load Capacitance — — 100 PF EVREF Noise Voltage — 20 — µVRMS 100Hz to 100kHz eVREF Noise Voltage Density — 1.0 — µV/√Hz 1kHz DS21284B-page 2 2002 Microchip Technology Inc. TC1027 2.0 PIN DESCRIPTION The description of the pins are listed in Table 2-1. TABLE 2-1: PIN FUNCTION TABLE Pin No. (16-Pin PDIP) (16-Pin QSOP) (16-Pin SOIC) Symbol 1 OUTB 2 OUTA 3 VDD Description Comparator output. Comparator output. Positive power supply. 4 INA- Inverting comparator input. 5 INA+ Non-Inverting comparator input. 6 INB- Inverting comparator input. 7 INB+ Non-Inverting comparator input. 8 REF+ Voltage reference output voltage. 9 GND Voltage reference ground; must be tied to VSS. 10 INC- Inverting comparator input. 11 INC+ Non-Inverting comparator input. 12 IND- Inverting comparator input. 13 IND+ Non-Inverting comparator input. Negative power supply. 14 VSS 15 OUTD Comparator output. 16 OUTC Comparator output. 2002 Microchip Technology Inc. DS21284B-page 3 TC1027 3.0 DETAILED DESCRIPTION 4.0 TYPICAL APPLICATIONS The TC1027 is one of a series of very low-power, linear building block products targeted at low-voltage, singlesupply applications. The TC1027 minimum operating voltage is 1.8V, and typical supply current is only 18µA. It combines four comparators and a voltage reference in a single package. The TC1027 lends itself to a wide variety of applications, particularly in battery-powered systems. It Typically it finds application in power management, processor supervisory and interface circuitry. 3.1 Hysteresis can be set externally with two resistors using positive feedback techniques (see Figure 4-1). The design procedure for setting external comparator hysteresis is as follows: Comparators The TC1027 contains four comparators. The comparator's input range extends beyond both supply voltages by 200mV and the outputs will swing to within several millivolts of the supplies depending on the load current being driven. 4.1 1. The comparators exhibit propagation delay and supply current which are largely independent of supply voltage. The low input bias current and offset voltage make them suitable for high impedance precision applications. 2. 3.2 3. Voltage Reference A 2.0% tolerance, internally biased, 1.20V bandgap voltage reference is included in the TC1027. It has a push pull output capable of sourcing and sinking at least 50µA. GND (Pin 9) is connected to VSS (Pin 14) through the substrate of the integrated circuit. Large currents can flow between GND and V SS if the pins are not at the same voltage. External Hysteresis (Comparator) Choose the feedback resistor RC. Since the input bias current of the comparator is at most 100pA, the current through RC can be set to 100nA (i.e., 1000 times the input bias current) and retain excellent accuracy. The current through RC at the comparator’s trip point is VR/ RC where VR is a stable reference voltage. Determine the hysteresis voltage (VHY) between the upper and lower thresholds. Calculate RA as follows: EQUATION 4-1: VH Y R A = R C ----------- V DD 4. 5. Choose the rising threshold voltage for VSRC (VTHR). Calculate RB as follows: EQUATION 4-2: 1 R B = ----------------------------------------------------------V THR 1 1 -------------------- – ------ – ------V × R R R A A RC 6. Verify the formulas: threshold voltages with these VSRC rising: EQUATION 4-3: 1 1 1 V TH R = ( V R ) ( R A ) ------- + ------- + ------- R R R A B C VSRC falling: EQUATION 4-4: V THF = V THR – DS21284B-page 4 R A × V DD ----------------------- RC 2002 Microchip Technology Inc. TC1027 4.2 Precision Battery Monitor Figure 4-2 is a precision battery low/battery dead monitoring circuit. Typically, the battery low output warns the user that a battery dead condition is imminent. Battery dead typically initiates a forced shutdown to prevent operation at low internal supply voltages (which can cause unstable system operation). The circuit of Figure 4-2 uses a single TC1027, one additional op amp, and only six external resistors. AMP 1 is a simple buffer while CMPTR1 and CMPTR2 provide precision voltage detection using VR as a reference. Resistors R2 and R4 set the detection threshold for BATT LOW while resistors R1 and R3 set the detection threshold for BATT FAIL. The component values shown assert BATT LOW at 2.2V (typical) and BATT FAIL at 2.0V (typical). Total current consumed by this circuit is typically 24µA at 3V. Resistors R5 and R6 provide hysteresis for comparators CMPTR1 and CMPTR2, respectively. 4.3 32.768 kHz “Time of Day Clock” Crystal Controlled Oscillator A very stable oscillator driver can be designed by using a crystal resonator as the feedback element. Figure 4-3 shows a typical application circuit using this technique to develop clock driver for a Time Of Day (TOD) clock chip. The value of RA and RB determine the DC voltage level at which the comparator trips – in this case onehalf of VDD. The RC time constant of RC and CA should be set several times greater than the crystal oscillator’s period, which will ensure a 50% duty cycle by maintaining a DC voltage at the inverting comparator input equal to the absolute average age of the output signal. 4.4 Non-Retriggerable One Shot Multivibrator Using two comparators, a non-retriggerable one shot multivibrator can be designed using the circuit configuration of Figure 4-4. A key feature of this design is that the pulse width is independent of the magnitude of the supply voltage because the charging voltage and the intercept voltage are a fixed percentage of VDD. In addition, this one shot is capable of pulse width with as much as a 99% duty cycle and exhibits input lockout to ensure that the circuit will not retrigger before the output pulse has completely timed out. The trigger level is the voltage required at the input to raise the voltage at node A higher than the voltage at node B, and is set by the resistive divider R4 and R10 and the impedance network composed of R1, R2 and R3. When the one shot has been triggered, the output of CMPTR2 is high, causing the reference voltage at the non-inverting input of CMPTR1 to go to V DD. This prevents any additional input pulses from disturbing the circuit until the output pulse has timed out. 2002 Microchip Technology Inc. The value of the timing capacitor C1 must be small enough to allow CMPTR1 to discharge C1 to a diode voltage before the feedback signal from CMPTR2 (through R10) switches CMPTR1 to its high state and allows C1 to start an exponential charge through R5. Proper circuit action depends upon rapidly discharging C1 through the voltage set by R6, R9 and D2 to a final voltage of a small diode drop. Two propagation delays after the voltage on C1 drops below the level on the non-inverting input of CMPTR2, the output of CMPTR1 switches to the positive rail and begins to charge C1 through R5. The time delay which sets the output pulse width results from C1 charging to the reference voltage set by R6, R9 and D2, plus four comparator propagation delays. When the voltage across C1 charges beyond the reference, the output pulse returns to ground and the input is again ready to accept a trigger signal. 4.5 Oscillators and Pulse Width Modulators Microchip’s linear building block comparators adapt well to oscillator applications for low frequencies (less than 100kHz). Figure 4-5 shows a symmetrical square wave generator using a minimum number of components. The output is set by the RC time constant of R4 and C1, and the total hysteresis of the loop is set by R1, R2 and R3. The maximum frequency of the oscillator is limited only by the large signal propagation delay of the comparator in addition to any capacitive loading at the output which degrades the slew rate. To analyze this circuit, assume that the output is initially high. For this to occur, the voltage at the inverting input must be less than the voltage at the non-inverting input. Therefore, capacitor C1 is discharged. The voltage at the non-inverting input (VH) is: EQUATION 4-5: R2 ( V DD ) V H = -------------------------------------------[ R2 + ( R1 || R3 ) ] where, if R1 = R2 = R3, then: EQUATION 4-6: 2 ( V DD ) V H = ------------------3 DS21284B-page 5 TC1027 Capacitor C1 will charge up through R4. When the voltage at the comparator’s inverting input is equal to VH, the comparator output will switch. With the output at ground potential, the value at the non-inverting input terminal (V L) is reduced by the hysteresis network to a value given by: is basically the same as described for the free-running oscillator. If the input control voltage is moved above or below one-half VDD, the duty cycle of the output square wave will be altered. This is because the addition of the control voltage at the input has now altered the trip points. The equations for these trip points are shown in Figure 4-6 (see VH and VL). EQUATION 4-7: Pulse width sensitivity to the input voltage variations can be increased by reducing the value of R6 from 10kΩ and conversely, sensitivity will be reduced by increasing the value of R6. The values of R1 and C1 can be varied to produce the desired center frequency. V DD V L = ---------3 Using the same resistors as before, capacitor C1 must now discharge through R4 toward ground. The output will return to a high state when the voltage across the capacitor has discharged to a value equal to VL. The period of oscillation will be twice the time it takes for the RC circuit to charge up to one half its final value. The period can be calculated from: FIGURE 4-1: COMPARATOR EXTERNAL HYSTERESIS CONFIGURATION RC TC1027 EQUATION 4-8: RA 1 ----------------- = 2 ( 0.694 ) ( R4 ) ( C1 ) FREQ + VSRC VOUT – The frequency stability of this circuit should only be a function of the external component tolerances. 1/4 RB Figure 4-6 shows the circuit for a pulse width modulator circuit. It is essentially the same as in Figure 4-4, but with the addition of an input control voltage. When the input control voltage is equal to one-half VDD, operation FIGURE 4-2: VDD VR PRECISION BATTERY MONITOR To System DC/DC Converter R4, 470k, 1% R5, 7.5M VDD VDD + TC1034 R2, 330k, 1% + AMP1 – 3V Alkaline CMPTR1 – BATTLOW 1/4 + TC1027 VDD R1, 270k, 1% VR – 1/4 CMPTR2 BATTFAIL + R6, 7.5M R3, 470k, 1% DS21284B-page 6 2002 Microchip Technology Inc. TC1027 FIGURE 4-3: 32.768 kHz “TIME OF DAY” CLOCK OSCILLATOR 32.768kHz VDD TC1027 VDD RA 150k 1/4 + VOUT – RB 150k RC 1M CA 100pF FIGURE 4-4: Vper = 30.52µsec NON-RETRIGGERABLE MULTIVIBRATOR VDD TC1027 R3 1M R4 1M R1 R5 10M A – IN 100k TC1025 C C1 100pF + B D1 GND R10 61.9k t0 R7 1M VDD OUT – CMPTR1 R2 100k IN R6 562k OUT CMPTR2 R8 R9 243k GND + C VDD GND 10M D2 FIGURE 4-5: SQUARE WAVE GENERATOR VDD R1 100k TC1027 1/4 R4 VDD – C1 + VH = R2 (VDD) R2 + (R1||R3) (VDD) (R2||R3) R1 + (R2||R3) 1 FREQ = 2(0.694)(R4)(C1) VL = R2 100k 2002 Microchip Technology Inc. R3 100k DS21284B-page 7 TC1027 FIGURE 4-6: PULSE WIDTH MONITOR VDD VC R6 10k TC1027 R1 100k 1/4 R4 VDD – + C1 VH = VDD (R1R2R6 + R2R3R6) + VC (R1R2R3) R1R2R6 + R1R3R6 + R2R3R6 + R1R2R3 VL = VDD (R2R3R6) + VC (R1R2R3) R1R2R6 + R1R3R6 + R2R3R6 + R1R2R3 FREQ = 1 2 (0.694) (R4) (C1) For Square Wave Generation Select R1 = R2 = R3 R2 100k DS21284B-page 8 R3 100k VC = VDD 2 2002 Microchip Technology Inc. TC1027 5.0 TYPICAL CHARACTERISTICS The graphs and tables provided following this note are a statistical summary based on a limited number of samples and are provided for informational purposes only. The performance characteristics listed herein are not tested or guaranteed. In some graphs or tables, the data presented may be outside the specified operating range (e.g., outside specified power supply range) and therefore outside the warranted range. Comparator Propagation Delay vs. Supply Voltage 7 TA = 25°C CL = 100pF DELAY TO FALLING EDGE (µsec) 6 Overdrive = 10mV 5 4 Overdrive = 50mV 3 2 6 Overdrive = 10mV 5 Overdrive = 100mV Overdrive = 50mV 4 3 2 2.5 3 3.5 4 4.5 5 1.5 5.5 2 6 VDD = 5V 5 VDD = 4V VDD = 2V 4 VDD = 3V 2.5 3 3.5 4 4.5 5 5.5 -40°C SUPPLY VOLTAGE (V) 2.5 7 2.5 VDD = 4V VDD = 3V VDD = 2V 4 VOUT - VSS (V) VDD - VOUT (V) VDD = 5V TA = 25°C 2.0 2.0 6 85°C Comparator Output Swing vs. Output Sink Current TA = 25°C Overdrive = 100mV 25°C TEMPERATURE (°C) Comparator Output Swing vs. Output Source Current Comparator Propagation Delay vs. Temperature 5 Overdrive = 100mV 3 SUPPLY VOLTAGE (V) DELAY TO FALLING EDGE (µsec) 7 TA = 25°C CL = 100pF 2 1.5 VDD = 3V 1.5 VDD = 1.8V 1.0 VDD = 5.5V .5 1.5 VDD = 3V 1.0 VDD = 1.8V .5 VDD = 5.5V 3 -40°C 0 0 25°C 0 85°C 3 2 4 ISOURCE (mA) 1 TEMPERATURE (°C) Comparator Output Short-Circuit Current vs. Supply Voltage 5 TA = -40°C 50 TA = 25°C 40 TA = 85°C C 0° 30 TA 20 Sinking 10 Sourcing 0 0 = -4 TA = 25°C TA = 85°C 3 1 2 4 5 SUPPLY VOLTAGE (V) 2002 Microchip Technology Inc. VDD = 1.8V VDD = 3V 1.220 VDD = 5.5V Sinking 1.200 Sourcing 1.180 VDD = 5.5V 1.160 VDD = 1.8V VDD = 3V 1.140 6 0 2 4 6 1 2 3 4 5 6 ISINK (mA) 1.240 60 0 6 Reference Voltage vs. Load Current REFERENCE VOLTAGE (V) OUTPUT SHORT-CIRCUIT CURRENT (mA) Comparator Propagation Delay vs. Temperature 8 LOAD CURRENT (mA) 10 SUPPLY AND REFERENCE VOLTAGES (V) DELAY TO RISING EDGE (µsec) 7 Comparator Propagation Delay vs. Supply Voltage DELAY TO RISING EDGE (µsec) Note: Line Transient Response of VREF 4 VDD 3 2 VREF 1 0 0 100 200 300 400 TIME (µsec) DS21284B-page 9 TC1027 5.0 TYPICAL CHARACTERISTICS (CONTINUED) Reference Voltage vs. Supply Voltage Supply Current vs. Supply Voltage 20 SUPPLY CURRENT (µA) REFERENCE VOLTAGE (V) 1.25 1.20 1.15 1.10 TA = 85°C 18 16 TA = 25°C TA = -40°C 14 12 10 1.05 8 1 4 2 3 SUPPLY VOLTAGE (V) DS21284B-page 10 5 0 1 2 3 4 5 SUPPLY VOLTAGE (V) 6 2002 Microchip Technology Inc. TC1027 6.0 PACKAGING INFORMATION 6.1 Package Marking Information Package marking data not available at this time. 6.2 Taping Form Component Taping Orientation for 16-Pin SOIC (Narrow) Devices User Direction of Feed PIN 1 W P Standard Reel Component Orientation for TR Suffix Device Carrier Tape, Reel Size, and Number of Components Per Reel Package 16-Pin SOIC (N) Carrier Width (W) Pitch (P) Part Per Full Reel Reel Size 16 mm 8 mm 2500 13 in Component Taping Orientation for 16-Pin QSOP (Narrow) Devices User Direction of Feed PIN 1 W P Standard Reel Component Orientation for TR Suffix Device Carrier Tape, Reel Size, Number of Components Per Reel and Reel Size Package 16-Pin QSOP (N) 2002 Microchip Technology Inc. Carrier Width (W) Pitch (P) Part Per Full Reel Reel Size 12 mm 8 mm 2500 13 in DS21284B-page 11 TC1027 6.3 Package Dimensions 16-Pin PDIP (Narrow) PIN 1 .270 (6.86) .240 (6.10) .045 (1.14) .030 (0.76) .770 (19.56) .740 (18.80) .310 (7.87) .290 (7.37) .200 (5.08) .140 (3.56) .040 (1.02) .020 (0.51) .150 (3.81) .115 (2.92) .014 (0.36) .008 (0.20) 10° MAX. .400 (10.16) .310 (7.87) .110 (2.79) .090 (2.29) .070 (1.78) .045 (1.14) .022 (0.56) .015 (0.38) Dimensions: inches (mm) 16-Pin QSOP (Narrow) PIN 1 .157 (3.99) .150 (3.81) .244 (6.20) .228 (5.80) .196 (4.98) .189 (4.80) .010 (0.25) .004 (0.10) .069 (1.75) .053 (1.35) .025 (0.635) TYP. .012 (0.31) .008 (0.21) 8° MAX. .010 (0.25) .007 (0.19) .050 (1.27) .016 (0.41) Dimensions: inches (mm) DS21284B-page 12 2002 Microchip Technology Inc. TC1027 6.3 Package Dimensions (Continued) 16-Pin SOIC (Narrow) PIN 1 .157 (3.99) .150 (3.81) .244 (6.20) .228 (5.79) .050 (1.27) TYP .394 (10.00) .385 (9.78) .069 (1.75) .053 (1.35) .018 (0.46) .014 (0.36) .010 (0.25) .004 (0.10) 8° MAX. .010 (0.25) .007 (0.18) .050 (1.27) .016 (0.40) Dimensions: inches (mm) 2002 Microchip Technology Inc. DS21284B-page 13 TC1027 NOTES: DS21284B-page 14 2002 Microchip Technology Inc. TC1027 Sales and Support Data Sheets Products supported by a preliminary Data Sheet may have an errata sheet describing minor operational differences and recommended workarounds. To determine if an errata sheet exists for a particular device, please contact one of the following: 1. 2. 3. Your local Microchip sales office The Microchip Corporate Literature Center U.S. FAX: (480) 792-7277 The Microchip Worldwide Site (www.microchip.com) Please specify which device, revision of silicon and Data Sheet (include Literature #) you are using. New Customer Notification System Register on our web site (www.microchip.com/cn) to receive the most current information on our products. 2002 Microchip Technology Inc. DS21284B-page15 TC1027 NOTES: DS21284B-page16 2002 Microchip Technology Inc. TC1027 Information contained in this publication regarding device applications and the like is intended through suggestion only and may be superseded by updates. It is your responsibility to ensure that your application meets with your specifications. No representation or warranty is given and no liability is assumed by Microchip Technology Incorporated with respect to the accuracy or use of such information, or infringement of patents or other intellectual property rights arising from such use or otherwise. Use of Microchip’s products as critical components in life support systems is not authorized except with express written approval by Microchip. No licenses are conveyed, implicitly or otherwise, under any intellectual property rights. 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Le Colleoni 1 20041 Agrate Brianza Milan, Italy Tel: 39-039-65791-1 Fax: 39-039-6899883 United Kingdom Arizona Microchip Technology Ltd. 505 Eskdale Road Winnersh Triangle Wokingham Berkshire, England RG41 5TU Tel: 44 118 921 5869 Fax: 44-118 921-5820 03/01/02 *DS21284B* DS21284B-page 18 2002 Microchip Technology Inc.