AD AD8044AN

a
Quad 150 MHz
Rail-to-Rail Amplifier
AD8044
FEATURES
Single AD8041 and Dual AD8042 Also Available
Fully Specified at +3 V, +5 V, and ⴞ5 V Supplies
Output Swings to Within 25 mV of Either Rail
Input Voltage Range Extends 200 mV Below Ground
No Phase Reversal with Inputs 1 V Beyond Supplies
Low Power of 2.75 mA/Amplifier
High Speed and Fast Settling on +5 V
150 MHz –3 dB Bandwidth (G = +1)
170 V/␮s Slew Rate
40 ns Settling Time to 0.1%
Good Video Specifications (RL = 150 ⍀, G = +2)
Gain Flatness of 0.1 dB to 12 MHz
0.06% Differential Gain Error
0.15ⴗ Differential Phase Error
Low Distortion
–68 dBc Total Harmonic @ 5 MHz
Outstanding Load Drive Capability
Drives 30 mA 0.5 V from Supply Rails
APPLICATIONS
Active Filters
Video Switchers
Distribution Amplifiers
A/D Driver
Professional Cameras
CCD Imaging Systems
Ultrasound Equipment (Multichannel)
CONNECTION DIAGRAM
14-Lead Plastic DIP and SOIC
OUT A
1
14 OUT D
–IN A
2
13 –IN D
+IN A
3
V+
4
+IN B
5
10 +IN C
–IN B
6
9
–IN C
OUT B
7
8
OUT C
12 +IN D
AD8044
11 V–
TOP VIEW
The output voltage swing extends to within 25 mV of each rail,
providing the maximum output dynamic range. Additionally, it
features gain flatness of 0.1 dB to 12 MHz while offering differential gain and phase error of 0.04% and 0.22° on a single +5 V
supply. This makes the AD8044 useful for video electronics
such as cameras, video switchers or any high speed portable
equipment. The AD8044’s low distortion and fast settling make
it ideal for active filter applications.
The AD8044 offers low power supply current of 13.1 mA max
and can run on a single +3.3 V power supply. These features are
ideally suited for portable and battery powered applications
where size and power are critical.
The AD8044 is a quad low power, voltage feedback, high speed
amplifier designed to operate on +3 V, +5 V or ± 5 V supplies.
It has true single-supply capability with an input voltage range
extending 200 mV below the negative rail and within 1 V of the
positive rail.
VS = +5V
5V
2.5V
18
VS = +5V
G = +1
15
12
NORMALIZED GAIN – dB
PRODUCT DESCRIPTION
The wide bandwidth of 150 MHz along with 170 V/µs of slew
rate on a single +5 V supply make the AD8044 useful in many
general purpose, high speed applications where dual power
supplies of up to ±6 V and single supplies from +3 V to +12 V
are needed. The AD8044 is available in 14-lead plastic DIP and
SOIC.
9
6
3
0
–3
–6
–9
0V
1V
2ms
Figure 1. Output Swing: Gain = –1, RL = 2 kΩ
–12
100k
1M
10M
FREQUENCY – Hz
100M
Figure 2. Frequency Response: Gain = +1, VS = +5 V
REV. A
Information furnished by Analog Devices is believed to be accurate and
reliable. However, no responsibility is assumed by Analog Devices for its
use, nor for any infringements of patents or other rights of third parties
which may result from its use. No license is granted by implication or
otherwise under any patent or patent rights of Analog Devices.
One Technology Way, P.O. Box 9106, Norwood, MA 02062-9106, U.S.A.
Tel: 781/329-4700
World Wide Web Site: http://www.analog.com
Fax: 781/326-8703
© Analog Devices, Inc., 1999
AD8044–SPECIFICATIONS (@ T = +25ⴗC, V = +5 V, R = 2 k⍀ to 2.5 V, unless otherwise noted)
A
S
L
Parameter
Conditions
Min
DYNAMIC PERFORMANCE
–3 dB Small Signal Bandwidth, VO < 0.5 V p-p
Bandwidth for 0.1 dB Flatness
Slew Rate
Full Power Response
Settling Time to 1%
Settling Time to 0.1%
G = +1
G = +2, RL = 150 Ω
G = –1, VO = 4 V Step
VO = 2 V p-p
G = –1, VO = 2 V Step
80
NOISE/DISTORTION PERFORMANCE
Total Harmonic Distortion
Input Voltage Noise
Input Current Noise
Differential Gain Error (NTSC)
Differential Phase Error (NTSC)
Crosstalk
AD8044A
Typ
140
fC = 5 MHz, VO = 2 V p-p, G = +2, RL = 1 kΩ
f = 10 kHz
f = 10 kHz
G = +2, RL = 150 Ω to 2.5 V
G = +2, RL = 150 Ω to 2.5 V
f = 5 MHz, RL = 1 kΩ, G = +2
DC PERFORMANCE
Input Offset Voltage
MHz
MHz
V/µs
MHz
ns
ns
–68
16
850
0.04
0.22
–60
dB
nV/√Hz
fA/√Hz
%
Degrees
dB
1.0
8
2
TMIN –TMAX
Input Offset Current
Open-Loop Gain
INPUT CHARACTERISTICS
Input Resistance
Input Capacitance
Input Common-Mode Voltage Range
Common-Mode Rejection Ratio
OUTPUT CHARACTERISTICS
Output Voltage Swing
Output Voltage Swing:
Output Voltage Swing:
Output Current
Short Circuit Current
Capacitive Load Drive
POWER SUPPLY
Operating Range
Quiescent Current
Power Supply Rejection Ratio
RL = 1 kΩ
TMIN –TMAX
82
VCM = 0 V to 3.5 V
80
RL = 10 kΩ to 2.5 V
RL = 1 kΩ to 2.5 V
RL = 150 Ω to 2.5 V
TMIN –TMAX, VOUT = 0.5 V to 4.5 V
Sourcing
Sinking
G = +2
0.25 to 4.75
0.55 to 4.4
0.2
94
88
70
OPERATING TEMPERATURE RANGE
–40
6
8
4.5
4.5
1.2
mV
mV
µV/°C
µA
µA
µA
dB
dB
225
1.6
–0.2 to 4
90
kΩ
pF
V
dB
0.03 to 4.975
0.075 to 4.91
0.25 to 4.65
30
45
85
40
V
V
V
mA
mA
mA
pF
3
VS = 0, +5 V, ±1 V
Units
150
12
170
26
30
40
TMIN –TMAX
Offset Drift
Input Bias Current
Max
11
80
12
13.1
V
mA
dB
+85
°C
Specifications subject to change without notice.
–2–
REV. A
SPECIFICATIONS (@ T = +25ⴗC, V = +3 V, R = 2 k⍀ to 1.5 V, unless otherwise noted)
A
S
Parameter
Conditions
Min
DYNAMIC PERFORMANCE
–3 dB Small Signal Bandwidth, VO < 0.5 V p-p
Bandwidth for 0.1 dB Flatness
Slew Rate
Full Power Response
Settling Time to 1%
Settling Time to 0.1%
G = +1
G = +2, RL = 150 Ω
G = –1, VO = 2 V Step
VO = 2 V p-p
G = –1, VO = 2 V Step
80
NOISE/DISTORTION PERFORMANCE
Total Harmonic Distortion
Input Voltage Noise
Input Current Noise
Differential Gain Error (NTSC)
Differential Phase Error (NTSC)
Crosstalk
AD8044
L
110
fC = 5 MHz, VO = 2 V p-p, G = –1, RL = 100 Ω
f = 10 kHz
f = 10 kHz
G = +2, RL = 150 Ω to 1.5 V, Input VCM = 0.5 V
G = +2, RL = 150 Ω to 1.5 V, Input VCM = 0.5 V
f = 5 MHz, RL = 1 kΩ, G = +2
DC PERFORMANCE
Input Offset Voltage
AD8044A
Typ
MHz
MHz
V/µs
MHz
ns
ns
–48
16
600
0.13
0.3
–60
dB
nV/√Hz
fA/√Hz
%
Degrees
dB
1.5
8
2
TMIN –TMAX
Input Offset Current
Open-Loop Gain
INPUT CHARACTERISTICS
Input Resistance
Input Capacitance
Input Common-Mode Voltage Range
Common-Mode Rejection Ratio
OUTPUT CHARACTERISTICS
Output Voltage Swing
Output Voltage Swing:
Output Voltage Swing:
Output Current
Short Circuit Current
Capacitive Load Drive
POWER SUPPLY
Operating Range
Quiescent Current
Power Supply Rejection Ratio
RL = 1 kΩ
TMIN –TMAX
80
RL = 10 kΩ to 1.5 V
RL = 1 kΩ to 1.5 V
RL = 150 Ω to 1.5 V
TMIN –TMAX, VOUT = 0.5 V to 2.5 V
Sourcing
Sinking
G = +2
0.025 to 2.98
0.17 to 2.82 0.06 to 2.93
0.35 to 2.55 0.15 to 2.75
25
30
50
35
3
70
0
Specifications subject to change without notice.
–3–
5.5
7.5
4.5
4.5
1.2
225
1.6
–0.2 to 2
90
76
OPERATING TEMPERATURE RANGE
REV. A
0.2
92
88
VCM = 0 V to 1.5 V
VS = 0, +3 V, +0.5 V
Units
135
10
150
22
35
55
TMIN –TMAX
Offset Drift
Input Bias Current
Max
10.5
80
mV
mV
µV/°C
µA
µA
µA
dB
dB
kΩ
pF
V
dB
V
V
V
mA
mA
mA
pF
12
12.5
V
mA
dB
+70
°C
AD8044–SPECIFICATIONS (@ T = +25ⴗC, V = ⴞ5 V, R = 2 k⍀ to 0 V, unless otherwise noted)
A
S
L
Parameter
Conditions
Min
DYNAMIC PERFORMANCE
–3 dB Small Signal Bandwidth, VO < 0.5 V p-p
Bandwidth for 0.1 dB Flatness
Slew Rate
Full Power Response
Settling Time to 0.1%
Settling Time to 0.01%
G = +1
G = +2, RL = 150 Ω
G = –1, VO = 8 V Step
VO = 2 V p-p
G = –1, VO = 2 V Step
85
NOISE/DISTORTION PERFORMANCE
Total Harmonic Distortion
Input Voltage Noise
Input Current Noise
Differential Gain Error (NTSC)
Differential Phase Error (NTSC)
Crosstalk
150
fC = 5 MHz, VO = 2 V p-p, G = +2
f = 10 kHz
f = 10 kHz
G = +2, RL = 150 Ω
G = +2, RL = 150 Ω
f = 5 MHz, RL = 1 kΩ, G = +2
DC PERFORMANCE
Input Offset Voltage
AD8044A
Typ
MHz
MHz
V/µs
MHz
ns
ns
–72
16
900
0.06
0.15
–60
dB
nV/√Hz
fA/√Hz
%
Degrees
dB
1.4
10
2
TMIN –TMAX
Input Offset Current
Open-Loop Gain
INPUT CHARACTERISTICS
Input Resistance
Input Capacitance
Input Common-Mode Voltage Range
Common-Mode Rejection Ratio
OUTPUT CHARACTERISTICS
Output Voltage Swing
Output Voltage Swing:
Output Voltage Swing:
Output Current
Short Circuit Current
Capacitive Load Drive
POWER SUPPLY
Operating Range
Quiescent Current
Power Supply Rejection Ratio
RL = 1 kΩ
TMIN –TMAX
82
VCM = –5 V to 3.5 V
RL = 10 kΩ
RL = 1 kΩ
RL = 150 Ω
TMIN –TMAX, VOUT = –4.5 V to +4.5 V
Sourcing
Sinking
G = +2
76
–4.6 to +4.6
–4.0 to +3.8
0.2
96
92
OPERATING TEMPERATURE RANGE
70
–40
6.5
9
4.5
4.5
1.2
mV
mV
µV/°C
µA
µA
µA
dB
dB
225
1.6
–5.2 to 4
90
kΩ
pF
V
dB
–4.97 to +4.97
–4.85 to +4.85
–4.5 to +4.5
30
60
100
40
V
V
V
mA
mA
mA
pF
3
VS = –5, +5 V, ±1 V
Units
160
15
190
29
30
40
TMIN –TMAX
Offset Drift
Input Bias Current
Max
11.5
80
12
13.6
V
mA
dB
+85
°C
Specifications subject to change without notice.
–4–
REV. A
AD8044
Supply Voltage . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . +12.6 V
Internal Power Dissipation2
Plastic DIP Package (N) . . . . . . . . . . . . . . . . . . . 1.6 Watts
Small Outline Package (R) . . . . . . . . . . . . . . . . . . 1.0 Watts
Input Voltage (Common Mode) . . . . . . . . . . . . . . ± VS ± 0.5 V
Differential Input Voltage . . . . . . . . . . . . . . . . . . . . . . . ± 3.4 V
Output Short Circuit Duration
. . . . . . . . . . . . . . . . . . . . . . Observe Power Derating Curves
Storage Temperature Range (N, R) . . . . . . . –65°C to +125°C
Lead Temperature Range (Soldering 10 sec) . . . . . . . . +300°C
While the AD8044 is internally short circuit protected, this may
not be sufficient to guarantee that the maximum junction temperature (+150°C) is not exceeded under all conditions. To
ensure proper operation, it is necessary to observe the maximum
power derating curves.
2.5
MAXIMUM POWER DISSIPATION – Watts
ABSOLUTE MAXIMUM RATINGS 1
NOTES
1
Stresses above those listed under Absolute Maximum Ratings may cause permanent damage to the device. This is a stress rating only; functional operation of the
device at these or any other conditions above those indicated in the operational
section of this specification is not implied. Exposure to absolute maximum rating
conditions for extended periods may affect device reliability.
2
Specification is for the device in free air:
14-Lead Plastic Package: θ JA = 75°C/W
14-Lead SOIC Package: θJA = 120°C/W
2.0
14-LEAD PLASTIC DIP PACKAGE
1.5
14-LEAD SOIC
1.0
0.5
–50 –40 –30 –20 –10 0 10 20 30 40 50 60 70
AMBIENT TEMPERATURE – 8C
MAXIMUM POWER DISSIPATION
The maximum power that can be safely dissipated by the
AD8044 is limited by the associated rise in junction temperature. The maximum safe junction temperature for plastic encapsulated devices is determined by the glass transition temperature
of the plastic, approximately +150°C. Exceeding this limit
temporarily may cause a shift in parametric performance due to
a change in the stresses exerted on the die by the package.
Exceeding a junction temperature of +175°C for an extended
period can result in device failure.
TJ = +150°C
80 90
Figure 3. Maximum Power Dissipation vs. Temperature
ORDERING GUIDE
Model
AD8044AN
AD8044AN
AD8044AR-14
AD8044AR-14
AD8044AR-14-REEL
AD8044AR-14-REEL7
Supply
Voltages
Temperature
Range
Package
Description
Package
Option
+5, ± 5
+3
+5, ± 5
+3
–40°C to +85°C
0°C to +70°C
–40°C to +85°C
0°C to +70°C
–40°C to +85°C
–40°C to +85°C
14-Lead Plastic DIP
14-Lead Plastic DIP
14-Lead Plastic SOIC
14-Lead Plastic SOIC
13" Tape and REEL
7" Tape and REEL
N-14
N-14
R-14
R-14
CAUTION
ESD (electrostatic discharge) sensitive device. Electrostatic charges as high as 4000 V readily
accumulate on the human body and test equipment and can discharge without detection.
Although the AD8016 features proprietary ESD protection circuitry, permanent damage may
occur on devices subjected to high energy electrostatic discharges. Therefore, proper ESD
precautions are recommended to avoid performance degradation or loss of functionality.
REV. A
–5–
WARNING!
ESD SENSITIVE DEVICE
AD8044–Typical Performance Characteristics
100
11
VS = +5V
TA = +258C
62 PARTS
MEAN = 350mV
STD DEVIATION = 560mV
NUMBER OF PARTS IN BIN
9
8
95
OPEN-LOOP GAIN – dB
10
7
6
5
4
3
2
90
85
VS = +5V
T = +258C
80
75
1
0
–3 –2.5 –2 –1.5 –1 –0.5 0 0.5
VOS – mV
70
1
1.5
2
2.5
0
3
Figure 4. Typical Distribution of VOS
500
750
1000 1250
1500
LOAD RESISTANCE – V
1750
2000
Figure 7. Open-Loop Gain vs. RL to +2.5 V
100
15
VS = +5V
RL = 1kV TO +2.5V
MEAN = 7.9mV/8C
STD DEV = 2.3mV/8C
SAMPLE SIZE = 62
VS = +5
97
OPEN-LOOP GAIN – dB
12
NUMBER OF PARTS IN BIN
250
9
6
94
91
3
88
0
2.0 3.0
85
–40
4.0 5.0 6.0 7.0 8.0 9.0 10.0 11.0 12.0 13.0 14.0
VOS DRIFT – mV/8C
Figure 5. VOS Drift Over –40 °C to +85 °C
–20
0
20
40
60
TEMPERATURE – 8C
80
100
Figure 8. Open-Loop Gain vs. Temperature
2.4
100
VS = +5V
VS = +5V
90
RL = 500V
OPEN-LOOP GAIN – dB
INPUT BIAS CURRENT – mA
80
2.2
2.0
1.8
70
RL = 50V
60
50
40
30
20
10
0
–45 –35 –25 –15 –5
5 15 25 35 45 55
TEMPERATURE – 8C
65
0
75 85
Figure 6. IB vs. Temperature
0 0.15 0.35 0.75 1.25 1.75 2.25 2.75 3.25 3.75 4.45 4.65 4.85 5
OUTPUT VOLTAGE – Volts
Figure 9. Open-Loop Gain vs. Output Voltage
–6–
REV. A
AD8044
DIFF GAIN – %
100
30
0.03
0.02
0.01
0.00
–0.01
–0.02
–0.03
–0.04
10
3
1
10
100
1k
10k
100k
FREQUENCY – Hz
1M
10M
0.20
0.15
0.10
0.05
0.00
–0.05
–0.10
–0.15
–0.20
0
–30
–40
VS = +3V,
RL = 100V
AV = –1
–50
VS = +5V,
RL = 100V
AV = +2
–80
60
70
80
90
100
VS = +5V
G = +2
RL = 150V
10
20
30
40
50
60 70
80
MODULATING RAMP LEVEL – IRE
90
100
VS = +5V,
RL = 1kV
AV = +2
VS = +5V,
RL = 1kV
AV = +1
2
3
4
5
6 7
FUNDAMENTAL FREQUENCY – MHz
11.6MHz
–0.1
–0.2
–0.3
–0.5
VS = +5V
RF = 200V
RL = 150V TO 2.5V
G = +2
Vi = 0.2V p-p
–0.6
1M
8 9 10
Figure 11. Total Harmonic Distortion
10M
FREQUENCY – Hz
100M
Figure 14. 0.1 dB Gain Flatness
–30
80
VS = +5V
RL = 2kV
CL = 5pF
70
10MHz
–50
60
OPEN-LOOP GAIN – dB
–60
–70
–80
5MHz
–90
1MHz
–100
–110
VS = +5V
RL = 2kV TO 2.5V
G = +2
–120
50
40
90
0
45
–140
–20
30k
1
1.5
2
2.5
3
3.5
OUTPUT VOLTAGE – V p-p
4
4.5
5
135
PHASE
10
–130
0.5
180
20
–10
0
GAIN
30
80MHz
100k
10M
1M
FREQUENCY – Hz
0
100M
Figure 15. Open-Loop Gain and Phase Margin
vs. Frequency
Figure 12. Worst Harmonic vs. Output Voltage
–7–
PHASE MARGIN – Degrees
–40
WORST HARMONIC – dBc
50
0.0
–0.4
REV. A
40
0.1
–70
–100
1
30
0.2
–60
–90
20
0.3
VS = +5V,
RL = 100V
AV = +1
NORMALIZED GAIN – dB
VO = 2V p-p
10
Figure 13. Differential Gain and Phase Errors
Figure 10. Input Voltage Noise vs. Frequency
TOTAL HARMONIC DISTORTION – dBc
VS = +5V
G = +2
RL = 150V
0
DIFF PHASE – Degrees
INPUT VOLTAGE NOISE – nV/
Hz
300
AD8044–Typical Performance Characteristics
4
CLOSED-LOOP GAIN – dB
2
1
G = –1
RL = 2kV
60
VS = +3V, 0.1%
VS = +5V, 0.1% AND
VS = 65V, 0.1%
50
TIME – ns
3
70
+858C
+258C
–408C
VS = +5V
RL = 2kV TO 2.5V
CL = 5pF
G = +1
VO = 0.2V p-p
0
–1
40
30
–2
VS = +3V, 1%
20
VS = +5V, 1% AND
VS = 65V, 1%
–3
10
–4
–5
1M
10M
FREQUENCY – Hz
0
0.5
100M
6
3
0
G = +1
RL = 2kV
CL = 5pF
VO = 0.2V p-p
+3V
–10
VS = 65V
+5V
–20
65V
2
CMRR – dB
CLOSED-LOOP GAIN – dB
4
2
Figure 19. Settling Time vs. Input Step
Figure 16. Closed-Loop Frequency Response
vs. Temperature
5
1
1.5
INPUT STEPS – Volts p-p
1
0
–30
VS = +3V
–40
–50
65V
–1
–60
–2
+3V
–70
–3
+5V
–4
100k
1M
10M
FREQUENCY – Hz
–80
0.03
100M
0.1
1
10
FREQUENCY – MHz
100
500
Figure 20. CMRR vs. Frequency
Figure 17. Closed-Loop Frequency Response vs. Supply
1.00
OUTPUT RESISTANCE – V
100
OUTPUT SATURATION VOLTAGE – Volts
RBT = 50V
G = +1
VS = +5V
10
RBT
VOUT
1
RBT = 0V
0.1
0.01
0.03
VS = +5V
0.875
+5V –VOH (+1258C)
0.750
+5V –VOH (+258C)
0.625
+5V –VOH (–558C)
0.500
0.375
0.250
VOL (+1258C)
0.125
VOL (–558C)
0.1
1
10
FREQUENCY – MHz
100
0.00
500
0
3
6
9
VOL (+258C)
12
15
18
21
LOAD CURRENT – mA
24
27
30
Figure 21. Output Saturation Voltage vs. Load Current
Figure 18. Output Resistance vs. Frequency
–8–
REV. A
AD8044
60
12.0
G = +2, RS = 0V,
VO = 100mV STEP
RF = RG = 750V
G = +1, RS = 20V,
VO = 100mV STEP
VS = 65V
50
VS = +5V
11.0
% OVERSHOOT
SUPPLY CURRENT – mA
11.5
VS = +3V
10.5
40
RF = 0, RG =
G = +1, RS = 40V,
VO = 100mV STEP
30
G = +3, RS = 0V,
VO = 150mV STEP
RF = 750V
RG = 375V
RG
RF = 0, RG =
RF
+2.5V
VOUT
20
10.0
VIN
50V
10
RS
–2.5V
9.5
0
9.0
–40
–20
0
20
40
60
TEMPERATURE – 8C
80
Figure 22. Supply Current vs. Temperature
2
VS = +5V
NORMALIZED OUTPUT – dB
1
–10
PSRR – dB
–PSRR
–20
–30
+PSRR
–40
–50
–60
0.1
1
10
FREQUENCY – MHz
100
250
G = +2
G = +5
–1
–2
–3
–4
–7
100k
500
VS = +5V
RL = 5kV TO 2.5V
RF = 2kV
G = +10
1M
10M
FREQUENCY – Hz
100M
500M
Figure 26. Frequency Response vs. Closed-Loop Gain
10
–10
VS = 65V
RL = 2kV
9
–20
8
–30
7
–40
CROSSTALK – dB
VOUT p-p – Volts
G = +2
RL = 150V TO 2.5V
RF = 200V
–6
Figure 23. PSRR vs. Frequency
6
5
4
VS = 65V
VIN = 1V p-p
G = +2
RF = 1kV
RL = 100V
–50
–60
–70
RL = 1kV
–80
3
2
–90
1
–100
1
10
FREQUENCY – MHz
100
–110
0.1
500
Figure 24. Output Voltage Swing vs. Frequency
REV. A
200
0
–5
–70
0
0.1
100
150
LOAD CAPACITANCE – pF
3
10
–80
0.01
50
Figure 25. % Overshoot vs. Capacitive Load
20
0
0
100
1
10
FREQUENCY – MHz
100
400
Figure 27. Crosstalk (Output to Output) vs. Frequency
–9–
AD8044–Typical Performance Characteristics
5V
4.656V
2.6V
VS = +5V
G = +1
RL = 2kV
CL = 5pF
VS = +5V
RL = 150V TO +2.5V
2.55V
CL = 5pF
G = –1
2.5V
2.5V
2.45V
0.211V
500mV
2.4V
100ms
50mV
40ns
0V
a.
Figure 30. 100 mV Step Response, VS = +5 V, G = +1
5V
3V
4.309V
+2.920V
VS = +5V
RL = 150V TO GND
CL = 5pF
G = –1
VIN = 3V p-p
RL = 2kV
CL = 5pF
VS = +3V
G = –1
2.5V
2V
2.5V
1.5V
1V
0.5V
500mV
+10mV
+22mV
100ms
500mV
200ms
0V
b.
Figure 28a, b. Output Swing vs. Load Reference Voltage,
VS = +5 V, G = –1
Figure 31. Output Swing, VS = +3 V
4.5V
3.5V
1.60V
VS = +5V
G = +2
RL = 2kV
VIN = 1V p-p
CL = 5pF
VIN = 0.1V p-p
RL = 2kV
CL = 5pF
VS = +3V
1.58V
1.56V
1.54V
G = +1
1.52V
2.5V
1.50V
1.48V
1.46V
1.5V
1.44V
500mV
1.42V
20ns
0.5V
20mV
20ns
1.40V
Figure 29. One Volt Step Response, VS = +5 V, G = +2
Figure 32. Step Response, G = +1, VIN = 100 mV
–10–
REV. A
AD8044
Overdrive Recovery
Driving Capacitance Loads
Overdrive of an amplifier occurs when the output and/or input
range are exceeded. The amplifier must recover from this overdrive condition. As shown in Figure 33, the AD8044 recovers
within 50 ns from negative overdrive and within 25 ns from
positive overdrive.
The capacitive load drive of the AD8044 can be increased by
adding a low valued resistor in series with the load. Figure 35
shows the effects of a series resistor on capacitive drive for varying voltage gains. As the closed-loop gain is increased, the larger
phase margin allows for larger capacitive loads with less overshoot. Adding a series resistor with lower closed-loop gains
accomplishes this same effect. For large capacitive loads, the
frequency response of the amplifier will be dominated by the
roll-off of the series resistor and capacitive load.
VS = +5V
AV = +2
RF = 2kV
RL = 2kV
VOUT
1V/DIV
VCC
I1
VIN
2V/DIV
I10
R26
I2
I3
R39
Q4
Q25
Q36
Q5
Q51
Q39
I5
Q23
Q40
R15 R2
Q22
VEE
VINP
1V
SIP
50ns
The AD8044 is fabricated on Analog Devices’ proprietary
eXtra-Fast Complementary Bipolar (XFCB) process which
enables the construction of PNP and NPN transistors with
similar fTs in the 2 GHz–4 GHz region. The process is dielectrically isolated to eliminate the parasitic and latch-up problems
caused by junction isolation. These features allow the construction of high frequency, low distortion amplifiers with low supply
currents. This design uses a differential output input stage to
maximize bandwidth and headroom (see Figure 34). The
smaller signal swings required on the first stage outputs (nodes
S1P, S1N) reduce the effect of nonlinear currents due to
junction capacitances and improve the distortion performance.
With this design harmonic distortion of better than –85 dB
@ 1 MHz into 100 Ω with VOUT = 2 V p-p (Gain = +2) on a
single 5 volt supply is achieved.
The AD8044’s rail to rail output range is provided by a complementary common-emitter output stage. High output drive capability is provided by injecting all output stage predriver currents
directly into the bases of the output devices Q8 and Q36. Biasing of Q8 and Q36 is accomplished by I8 and I5, along with a
common-mode feedback loop (not shown). This circuit topology allows the AD8044 to drive 50 mA of output current with
the outputs within 0.5 V of the supply rails.
On the input side, the device can handle voltages from –0.2 V
below the negative rail to within 1.2 V of the positive rail. Exceeding these values will not cause phase reversal; however, the
input ESD devices will begin to conduct if the input voltages
exceed the rails by greater than 0.5 V.
REV. A
C9
Q11
Q3
C7
–11–
VOUT
Q27
SIN
Q2
Figure 33. Overdrive Recovery, VS + 5 V, VIN = 4 V Step
Circuit Description
C3
Q31
Q21
VINN
2V
VEE
R23 R27
Q7
Q17
Q13
I9
Q50
R5
Q8
Q24
R21
R3
I7
Q47
I8
I11
VEE
Figure 34. AD8044 Simplified Schematic
VCC
AD8044
+5V
1000
GRAPHICS
IC
CAPACITIVE LOAD – pF
VS = +5V
< 30% OVERSHOOT
RS
R
0V
=1
RS
V
=0
75V
G
75V
100
B
75V
RG
RS
VIN
100mV STEP
10
1
75V
RF
CL
75V
AD8044
2
3
4
5
RGB
MONITOR #1
+3V OR +5V
75V
VOUT
0.1mF
6
ACL – V/V
A
Figure 35. Capacitive Load Drive vs. Closed-Loop Gain
10mF
75V
V+
1kV
APPLICATIONS
RGB Buffer
1kV
The AD8044 can provide buffering of RGB signals that include
ground while operating from a single +3 V or +5 V supply.
75V
AD8044
75V
B
When driving two monitors from the same RGB video source it
is necessary to provide an additional driver for one of the monitors to prevent the double termination situation that the second
monitor presents. This has usually required a dual supply op
amp because the level of the input signal from the video driver
goes all the way to ground during horizontal blanking. In single
supply systems it can be a major inconvenience and expense to
add an additional negative supply.
75V
1kV
1kV
75V
AD8044
75V
C
During horizontal blanking, the current output from the DACs
is turned off and the RGB outputs are pulled to ground by the
termination resistors. If voltage sources were used for the RGB
signals, then the termination resistors near the graphics IC
would be in series and the rest of the circuit would remain the
same. This is because a voltage source is an ac short circuit, so a
series resistor is required to make the drive end of the line see
75 Ω to ac ground. On the other hand, a current source has a
very high output impedance, so a shunt resistor is required to
make the drive end of the line see 75 Ω to ground. In either
case, the monitor terminates its end of the line with 75 Ω.
RGB
MONITOR #2
1kV
A single AD8044 can provide the necessary drive capability and
yet does not require a negative supply in this application. Figure 36 is a schematic that uses three amplifiers out of a single
AD8044 to provide buffering for a second monitor.
The source of the RGB signals is shown to be from a set of three
current output DACs that are within a single supply graphics
IC. This is typically the situation in most PCs and workstations
which might use either a stand-alone triple DAC or DACs that
are integrated into a larger graphics chip.
V–
1kV
Figure 36. Single Supply RGB Video Driver
Figure 37 is an oscilloscope photo of the circuit in Figure 36
operating from a +3 V supply and driven by the Blue signal of a
color bar pattern. Note that the input and output are at ground
during the horizontal blanking interval. The RGB signals are
specified to output a maximum of 700 mV peak. The output of
the AD8044 is 1.4 V with the termination resistors providing a
divide-by-two.
500mV
VIN
5ms
100
90
GND
VOUT
GND
10
The circuit of Figure 36 shows minimum signal degradation
when using a single supply for the AD8044. The circuit performs equally well on either a +3 V or +5 V supply.
0%
500mV
Figure 37. +3 V, RGB Buffer
–12–
REV. A
AD8044
Active Filters
Layout Considerations
Active filters at higher frequencies require wider bandwidth op
amps to work effectively. Excessive phase shift produced by
lower frequency op amps can significantly impact active filter
performance.
The specified high speed performance of the AD8044 requires
careful attention to board layout and component selection.
Proper RF design techniques and low-pass parasitic component
selection are necessary.
Figure 38 shows an example of a 2 MHz biquad bandwidth
filter that uses three op amps of an AD8044 package. Such
circuits are sometimes used in medical ultrasound systems to
lower the noise bandwidth of the analog signal before A/D
conversion.
The PCB should have a ground plane covering all unused portions of the component side of the board to provide a low impedance path. The ground plane should be removed from the
area near the input pins to reduce the stray capacitance.
R6
1kV
C1
50pF
R2
2kV
R1
3kV
VIN
R4
2kV
2
1
C2
50pF
R3
2kV 6
3
7
R5
2kV
9
8
5
AD8044
10
AD8044
VOUT
AD8044
Figure 38. 2 MHz Biquad Bandpass Filter Using AD8044
The frequency response of the circuit is shown in Figure 39.
Chip capacitors should be used for the supply bypassing. One
end should be connected to the ground plane and the other
within 1/8 inch of each power pin. An additional large (0.47 µF
– 10 µF) tantalum electrolytic capacitor should be connected in
parallel, but not necessarily so close, to supply current for fast,
large signal changes at the output.
The feedback resistor should be located close to the inverting
input pin in order to keep the stray capacitance at this node to a
minimum. Capacitance variations of less than 1 pF at the inverting input will significantly affect high speed performance.
Stripline design techniques should be used for long signal traces
(greater than about 1 inch). These should be designed with a
characteristic impedance of 50 Ω or 75 Ω and be properly terminated at each end.
0
GAIN – dB
–10
–20
–30
–40
10k
100k
1M
FREQUENCY – Hz
10M
100M
Figure 39. Frequency Response of 2 MHz Bandpass
Biquad Filter
REV. A
–13–
AD8044
OUTLINE DIMENSIONS
Dimensions shown in inches and (mm).
14-Lead Plastic DIP
(N-14)
14
8
1
7
0.280 (7.11)
0.240 (6.10)
0.060 (1.52)
0.015 (0.38)
PIN 1
0.210 (5.33)
MAX
0.325 (8.25)
0.300 (7.62) 0.195 (4.95)
0.115 (2.93)
0.130
(3.30)
MIN
0.160 (4.06)
0.115 (2.93)
0.022 (0.558)
0.014 (0.356)
C2075a–10–8/99
0.795 (20.19)
0.725 (18.42)
0.100 0.070 (1.77)
(2.54) 0.045 (1.15)
BSC
0.015 (0.381)
0.008 (0.204)
SEATING
PLANE
14-Lead SOIC
(R-14)
0.3444 (8.75)
0.3367 (8.55)
14
8
1
7
PIN 1
0.0098 (0.25)
0.0040 (0.10)
SEATING
PLANE
0.0500
(1.27)
BSC
0.2440 (6.20)
0.2284 (5.80)
0.0688 (1.75)
0.0532 (1.35)
0.0192 (0.49)
0.0138 (0.35)
0.0098 (0.25)
0.0075 (0.19)
0.0196 (0.50)
x 45°
0.0099 (0.25)
8°
0°
0.0500 (1.27)
0.0160 (0.41)
PRINTED IN U.S.A.
0.1574 (4.00)
0.1497 (3.80)
–14–
REV. A