LTC3103 1.8µA Quiescent Current, 15V, 300mA Synchronous Step-Down DC/DC Converter DESCRIPTION FEATURES n n n n n n n n n n n Ultralow Quiescent Current: 1.8µA Synchronous Rectification: Efficiency Up to 95% Wide VIN Range: 2.5V to 15V Wide VOUT Range: 0.6V to 13.8V 300mA Output Current User-Selectable Automatic Burst Mode® or Forced Continuous Operation Accurate and Programmable RUN Pin Threshold 1.2MHz Fixed Frequency PWM Internal Compensation Power Good Status Output for VOUT Available in Thermally Enhanced 3mm × 3mm × 0.75mm, 10-Pin DFN and 10-Pin MSOP Packages APPLICATIONS n n n n n n Remote Sensor Networks Distributed Power Systems Multicell Battery or SuperCap Regulator Energy Harvesters Portable Instruments Low Power Wireless Systems The LTC®3103 is a high efficiency, monolithic synchronous step-down converter using a current mode architecture capable of supplying 300mA of output current. The LTC3103 offers two operational modes: automatic Burst Mode operation and forced continuous mode allowing the user the ability to optimize output voltage ripple, noise and light load efficiency. With Burst Mode operation enabled, the typical DC input supply current at no load drops to 1.8µA maximizing the efficiency for light loads. Selection of forced continuous mode provides very low noise constant frequency, 1.2MHz operation. Additionally, the LTC3103 includes an accurate RUN comparator, thermal overload protection, a power good output and an integrated soft-start feature to guarantee that the power system start-up is well controlled. L, LT, LTC, LTM, Burst Mode, Linear Technology and the Linear logo are registered trademarks of Linear Technology Corporation. All other trademarks are the property of their respective owners. TYPICAL APPLICATION Efficiency vs Output Current 100 BST MODE 0.022µF 10µH SW 10µF RUN PGOOD FB VCC GND 1.78M 12pF 47µF 1µF 665k 90 85 75 70 1 65 60 3103 TA01a 10 80 55 50 0.0001 VIN = 3V VIN = 5V VIN = 10V VIN = 15V 0.01 0.1 0.001 OUTPUT CURRENT (A) 1 POWER LOSS (mW) LTC3103 100 95 2.2V 300mA EFFICIENCY (%) VIN 3V TO 15V 0.1 3103 TA01b 3103f 1 LTC3103 ABSOLUTE MAXIMUM RATINGS (Note 1) VIN.............................................................. –0.3V to 18V SW................................................. –0.3V to (VIN + 0.3V) FB................................................................. –0.3V to 6V BST......................................... (SW – 0.3V) to (SW + 6V) RUN, MODE ................................................ –0.3V to VIN VCC, PGOOD.................................................. –0.3V to 6V Operating Junction Temperature Range (Notes 2, 3)............................................. –40°C to 125°C Storage Temperature Range................... –65°C to 150°C Lead Temperature (Soldering, 10 sec) MSE Only........................................................... 300°C PIN CONFIGURATION TOP VIEW VIN 1 SW 2 BST 3 GND 4 PGOOD 5 TOP VIEW 10 MODE 11 GND VIN SW BST GND PGOOD 9 NC 8 FB 7 RUN 6 VCC DD PACKAGE 10-LEAD (3mm × 3mm) PLASTIC DFN TJMAX = 125°C, θJA = 58°C/W, θJC = 10°C/W EXPOSED PAD (PIN 11) IS GND, MUST BE SOLDERED TO PCB 1 2 3 4 5 10 9 8 7 6 11 GND MODE NC FB RUN VCC MSE PACKAGE 10-LEAD PLASTIC MSOP TJMAX = 125°C, θJA = 40°C/W, θJC = 5.0°C/W EXPOSED PAD (PIN 11) IS GND, MUST BE SOLDERED TO PCB ORDER INFORMATION LEAD FREE FINISH TAPE AND REEL PART MARKING* PACKAGE DESCRIPTION TEMPERATURE RANGE LTC3103EDD#PBF LTC3103EDD#TRPBF LFXH 10-Lead (3mm × 3mm) Plastic DFN –40°C to 125°C LTC3103IDD#PBF LTC3103IDD#TRPBF LFXH 10-Lead (3mm × 3mm) Plastic DFN –40°C to 125°C LTC3103EMSE#PBF LTC3103EMSE#TRPBF LTFXJ 10-Lead Plastic MSOP –40°C to 125°C LTC3103IMSE#PBF LTC3103IMSE#TRPBF LTFXJ 10-Lead Plastic MSOP –40°C to 125°C Consult LTC Marketing for parts specified with wider operating temperature ranges. *The temperature grade is identified by a label on the shipping container. Consult LTC Marketing for information on non-standard lead based finish parts. For more information on lead free part marking, go to: http://www.linear.com/leadfree/ For more information on tape and reel specifications, go to: http://www.linear.com/tapeandreel/ The l denotes the specifications which apply over the full operating ELECTRICAL CHARACTERISTICS junction temperature range, otherwise specifications are at TA = 25°C (Note 2). VIN = 10V unless otherwise noted. PARAMETER CONDITIONS MIN TYP MAX UNITS Step-Down Converter Input Voltage Range l Input Undervoltage Lockout Threshold VIN Rising VIN Rising, TJ = 0°C to 85°C (Note 4) Input Undervoltage Lockout Hysteresis (Note 4) l 2.5 2.1 2.1 0.4 15 V 2.6 2.5 V V V 3103f 2 LTC3103 ELECTRICAL CHARACTERISTICS The l denotes the specifications which apply over the full operating junction temperature range, otherwise specifications are at TA = 25°C (Note 2). VIN = 10V unless otherwise noted. PARAMETER CONDITIONS Feedback Voltage (Note 5) Feedback Voltage Line Regulation VIN = 2.5V to 15V (Note 5) Feedback Input Current (Note 5) Oscillator Frequency MIN l 0.588 l l TJ = 0°C to 85°C (Note 4) 0.930 1 TYP MAX 0.6 0.612 V 0.02 0.05 %/V 1 20 1.2 1.2 1.55 1.45 UNITS nA MHz MHz Quiescent Current, VIN—Active RUN = VIN, MODE = 0V, FB > 0.612 Nonswitching Quiescent Current, VIN— Sleep RUN = VIN, FB > 0.612, MODE = VIN, TJ = 0°C to 85°C (Note 4) RUN = VIN, FB > 0.612, MODE = VIN l 1.8 1.8 2.6 3.3 µA µA RUN = 0V, TJ = 0°C to 85°C (Note 4) RUN = 0V l 1 1.8 1.7 3.3 µA µA Quiescent Current, VIN—Shutdown 600 µA N-Channel MOSFET Synchronous Rectifier Leakage Current VIN = VSW = 15V, VRUN = 0V 0.01 0.3 µA N-Channel MOSFET Switch Leakage Current VIN = 15V, VSW = 0V, VRUN = 0V 0.01 0.3 µA N-Channel MOSFET Synchronous Rectifier RDS(ON) ISW = 200mA 0.85 N-Channel MOSFET Switch RDS(ON) ISW = –200mA Peak Current Limit 0.65 l Ω 0.40 0.50 0.75 A –14 –10 –5 % PGOOD Threshold FB Falling, Percentage Below FB PGOOD Hysteresis Percentage of FB PGOOD Voltage Low IPGOOD = 100µA 0.2 PGOOD Leakage Current VPGOOD = 5V 0.01 Maximum Duty Cycle Ω 2 V 0.3 µA 92 % Switch Minimum Off Time (tOFF(MIN)) (Note 4) 65 ns Synchronous Rectifier Minimum On Time (tON(MIN)) (Note 4) 70 ns RUN Pin Threshold RUN Pin Rising l l 89 % 0.76 RUN Pin Hysteresis RUN Input Current 0.85 0.06 RUN = 1.2V MODE Threshold MODE Input Current 0.80 l l 0.5 MODE = 1.2V Soft-Start Time Note 1: Stresses beyond those listed under Absolute Maximum Ratings may cause permanent damage to the device. Exposure to any Absolute Maximum Rating condition for extended periods may affect device reliability and lifetime. Note 2: The LTC3103 is tested under pulsed load conditions such that TJ ≈ TA. The LTC3103E is guaranteed to meet specifications from 0°C to 85°C junction temperature. Specifications over the –40°C to 125°C operating junction temperature range are assured by design, characterization and correlation with statistical process controls. The LTC3103I is guaranteed over the full –40°C to 125°C operating junction temperature range. The junction temperature (TJ) is calculated from the ambient temperature (TA) and power dissipation (PD) according to the formula: TJ = TA + (PD)(θJA°C/W) 0.7 V V 0.01 0.4 µA 0.8 1.2 V 0.1 4 µA 1.4 2.5 ms where θJA is the package thermal impedance. Note the maximum ambient temperature consistent with these specifications is determined by specific operating conditions in conjunction with board layout, the rated package thermal resistance and other environmental factors. Note 3: This IC includes overtemperature protection that is intended to protect the device during momentary overload conditions. The maximum rated junction temperature will be exceeded when this protection is active. Continuous operation above the specified absolute maximum operating junction temperature may impair device reliability or permanently damage the device. Note 4: Specification is guaranteed by design. Note 5: The LTC3103 has a proprietary test mode that allows testing in a feedback loop which servos VFB to the balance point for the error amplifier. 3103f 3 LTC3103 TYPICAL PERFORMANCE CHARACTERISTICS Efficiency vs Output Current 100 90 85 85 80 75 70 65 VIN = 4V VIN = 7V VIN = 10V VIN = 15V 0.01 0.1 0.001 OUTPUT CURRENT (A) 75 70 65 ILOAD = 300mA ILOAD = 100mA ILOAD = 10mA ILOAD = 1mA ILOAD = 100µA 60 55 50 1 12 10 8 INPUT VOLTAGE (V) 4 2 6 14 3103 G01 100 80 80 70 70 60 50 40 0 0.0001 VIN = 3.7V VIN = 5V VIN = 7V VIN = 10V VIN = 15V 0.001 0.01 0.1 OUTPUT CURRENT (A) 50 40 30 10 8 FREQUENCY CHANGE (%) CHANGE IN VFB (%) 1.5 1.0 0.5 3 5 9 7 11 INPUT VOLTAGE (V) 13 0 15 50 NORMALIZED TO 25°C 40 6 4 2 0 –2 –4 –6 2 4 10 8 12 6 INPUT VOLTAGE (V) –10 –50 –25 14 16 RDS(ON) vs Temperature NORMALIZED TO 25°C VIN = 10V 30 20 SYNCHRONOUS RECTIFIER 10 MAIN SWITCH 0 –10 –20 –8 3103 G07 FRONT PAGE APPLICATION LDO ENABLED 3103 G06 CHANGE IN RESISTANCE (%) NORMALIZED TO 25°C 18 2.0 Oscillator Frequency vs Temperature –0.50 – 60 – 40 – 20 0 20 40 60 80 100 120 140 TEMPERATURE (°C) 16 2.5 3103 G05 Feedback Voltage vs Temperature –0.25 6 8 10 12 14 INPUT VOLTAGE (V) 3.0 60 0 1 0 4 3.5 10 0.25 2 3103 G03 20 0.50 0 Application No-Load Input Current vs Supply Voltage (Forced Continuous Operation) ILOAD = 300mA ILOAD = 100mA ILOAD = 10mA ILOAD = 1mA 3103 G04 0.75 1.6 16 VOUT = 3.3V, L = 10µH 90 EFFICIENCY (%) EFFICIENCY (%) VOUT = 3.3V 90 L = 10µH 10 1.8 Efficiency vs Input Voltage (Forced Continuous Operation) 100 20 1.9 3103 G02 Efficiency vs Output Current (Forced Continuous Operation) 30 2.0 1.7 INPUT CURRENT (mA) 50 0.0001 80 FRONT PAGE APPLICATION 2.1 INPUT CURRENT (µA) 90 2.2 VOUT = 2.2V L = 10µH 95 EFFICIENCY (%) EFFICIENCY (%) VOUT = 3.3V 95 L = 15µH 55 Application No-Load Input Current vs Supply Voltage (Automatic Burst Mode Operation) Efficiency vs Input Voltage (Automatic Burst Mode Operation) 100 60 TA = 25°C unless otherwise noted 0 25 50 75 100 125 150 TEMPERATURE (°C) 3103 G08 –30 –50 –25 75 50 25 TEMPERATURE (°C) 0 100 125 3103 G09 3103f 4 LTC3103 TYPICAL PERFORMANCE CHARACTERISTICS PEAK CURRENT LIMIT CHANGE (%) LEAKAGE CURRENT (nA) 350 SYNCHRONOUS RECTIFIER 250 MAIN SWITCH 200 150 100 50 0 –50 –25 0 25 50 75 100 125 150 TEMPERATURE (°C) 10.0 3.0 7.5 2.8 2.5 0 –2.5 –5.0 –20 10 70 40 TEMPERATURE (°C) RUN 5V/DIV VOUT 1V/DIV PGOOD 5V/DIV IL 100mA/DIV 100 130 Forced Continuous Operation 3103 G13 Start-Up into Pre-Biased Output (Forced Continuous Operation) VBST REFRESH CURRENT PULSES ILOAD = 2mA VIN = 10V L = 10µH VOUT = 2.5V 500µs/DIV 1.6 1.0 –50 –30 –10 10 30 50 70 TEMPERATURE (°C) Start-Up into Pre-Biased Output (Automatic Burst Mode Operation) VBST REFRESH CURRENT PULSES SOFT-START PERIOD BURST CURRENT PULSES IL 100mA/DIV ILOAD = 25mA VIN = 10V CIN = 10µF L = 10µH VOUT = 2.5V COUT = 22µF RUN 5V/DIV PGOOD 5V/DIV VOUT 1V/DIV 110 90 3103 G12 PGOOD 5V/DIV 1µs/DIV 3103 G14 ILOAD = 2mA VIN = 10V CIN = 10µF L = 10µH VOUT = 2.5V COUT = 47µF 500µs/DIV 3103 G15 Start-Up from Shutdown (Forced Continuous Operation) Start-Up from Shutdown (Automatic Burst Mode Operation) RUN 5V/DIV VOUT 1V/DIV SOFT-START FOLDBACK PERIOD IL 100mA/DIV IL 100mA/DIV 3103 G16 1.8 RUN 5V/DIV VOUT 1V/DIV IL 100mA/DIV 10µs/DIV 2.0 3103 G11 VOUT 20mV/DIV AC-COUPLED ILOAD = 25mA VIN = 10V CIN = 10µF L = 10µH VOUT = 2.5V COUT = 22µF 2.2 1.2 –10.0 –50 Automatic Burst Mode Operation IL 100mA/DIV 2.4 1.4 –7.5 3103 G10 VOUT 50mV/DIV AC-COUPLED VIN = 10V VOUT = 2.5V 2.6 5.0 INPUT CURRENT (µA) VIN = 10V 300 Application No-Load Input Current vs Temperature (Automatic Burst Mode Operation) Peak Current Limit Change vs Temperature SW Leakage vs Temperature 400 TA = 25°C unless otherwise noted ILOAD = 25mA VIN = 10V L = 10µH VOUT = 2.5V 500µs/DIV 3103 G17 ILOAD = 5mA VIN = 10V L = 10µH VOUT = 2.5V 500µs/DIV 3103 G18 3103f 5 LTC3103 TYPICAL PERFORMANCE CHARACTERISTICS VOUT 200mV/DIV AC-COUPLED VOUT 50mV/DIV AC-COUPLED IL 200mA/DIV IL 100mA/DIV 3103 G19 200µs/DIV ILOAD = LOAD STEP, 5mA TO 300mA VIN = 10V CIN = 10µF L = 10µH VOUT = 2.2V COUT = 47µF VOUT = 9V 9 150 200 100 LOAD CURRENT (mA) 250 –2.0 300 –1.0 COUT = 68µF COUT = 47µF COUT = 22µF 0 10 20 30 ILOAD (mA) 50 40 –1.0 –1.5 –2.0 COUT = 100µF COUT = 68µF COUT = 47µF –2.5 0 20 40 60 ILOAD (mA) 80 100 3103 G25 COUT = 68µF COUT = 47µF COUT = 33µF –1.5 –2.0 0 10 20 30 40 50 ILOAD (mA) 60 Automatic Burst Mode Threshold vs Supply Voltage 100 160 95 140 IOUT = 1mA 90 IOUT = 300mA 85 80 75 70 65 2 3 6 5 7 4 INPUT VOLTAGE (V) 80 70 3103 G24 BURST THRESHOLD (ILOAD, mA) CHANGE IN VOUT (%) –0.5 NORMALIZED AT ILOAD = 100mA VIN = 10V VOUT = 3.3V CFF = 12pF 0 Maximum Duty Cycle vs Input Voltage MAXIMUM DUTY CYCLE (%) NORMALIZED AT ILOAD = 100mA VIN = 10V VOUT = 1.8V CFF = 12pF 0 300 Load Regulation (Automatic Burst Mode Operation) 3103 G23 Load Regulation (Automatic Burst Mode Operation) 0.5 250 –0.5 3103 G22 1.0 100 150 200 LOAD CURRENT (mA) 50 0.5 0 –1.5 VOUT = 5V 50 0 1.0 –1.0 8 –3.0 2.5 –0.5 10 0 3.5 CHANGE IN VOUT (%) CHANGE IN VOUT (%) 12 6 VOUT = 2.2V VOUT = 1.8V VOUT = 1.5V 3.0 NORMALIZED AT ILOAD = 100mA VIN = 10V VOUT = 5V CFF = 12pF 0.5 13 7 4.0 Load Regulation (Automatic Burst Mode Operation) VOUT = 12V 11 3103 G20 VOUT = 4.2V VOUT = 3.3V VOUT = 2.5V 4.5 3103 G21 1.0 15 14 INPUT VOLTAGE (V) 5.0 200µs/DIV ILOAD = LOAD STEP, 50mA TO 200mA VIN = 10V L = 10µH VOUT = 2.5V COUT = 22µF Minimum Input Voltage at Maximum Duty Cycle vs Load Current 5 5.5 ILOAD 100mA/DIV ILOAD 200mA/DIV Minimum Input Voltage at Maximum Duty Cycle vs Load Current Load Step (Forced Continuous Operation) INPUT VOLTAGE (V) Load Step (Automatic Burst Mode Operation) TA = 25°C unless otherwise noted 8 9 3103 G26 VOUT = 1.2V VOUT = 1.8V VOUT = 2.5V VOUT = 3.3V VOUT = 5V 120 100 80 60 40 20 0 0 2 4 8 6 10 12 INPUT VOLTAGE (V) 14 16 3103 G27 3103f 6 LTC3103 PIN FUNCTIONS VIN (Pin 1): Main Supply Pin. Decouple with a 10µF or larger ceramic capacitor. The capacitor should be as close to the part as possible. SW (Pin 2): Switch Pin Connects to the Inductor. This pin connects to the drains of the internal main and synchronous power MOSFET switches. BST (Pin 3): Bootstrapped Floating Supply for the High Side Gate Drive. Connect to SW through a 22nF (minimum) capacitor. The capacitor must be connected between BST and SW and be located as close as possible to the part as possible. GND (Pin 4): Power Ground. PGOOD (Pin 5): Open-drain output that is pulled to ground when the feedback voltage falls 10% (typical) below the regulation point, during a thermal shutdown event or if the converter is disabled. The PGOOD output is valid 1ms after the buck converter is enabled. VCC (Pin 6): Internally Regulated Supply Rail. Internal power rail regulated off of VIN to power control circuitry. Decouple with a 1µF or larger ceramic capacitor placed as close to the part as possible. RUN (Pin 7): Run Pin Comparator Input. A voltage greater than 0.84V will enable the IC. Tie this pin to VIN to enable the IC or connect to an external resistor divider from VIN to provide an accurate undervoltage lockout threshold. 60mV of hysteresis is provided internally. FB (Pin 8): Feedback Input to Error Amplifier. The resistor divider connected to this pin sets the buck converter output voltage. NC (Pin 9): No Connect Pin Must be Tied to GND. MODE (Pin 10): Logic-Controlled Input to Select Mode of Operation. Forcing this pin high commands high efficiency automatic Burst Mode operation where the buck will automatically transition from PWM operation at heavy load to Burst Mode operation at light loads. Forcing this pin low commands low noise, fixed frequency, forced continuous operation. GND (Exposed Pad Pin 11): Backpad Ground Common. This pad must be soldered to the PC board and connected to the ground plane for optimal thermal performance. 3103f 7 LTC3103 BLOCK DIAGRAM C2 1 VIN VCC 6 VCC PRE-REG VCC C3 VCC IBIAS UVLO OSC IPEAK(REF) IPEAK 0.6V 0.8V + UVLO R6 7 RUN VREF + R5 0.8V 10 MODE BURST ENABLE BST 3 CBST IPEAK COMP TOP_ON VREF_GOOD SHUTDOWN SD LOGIC – BOOST CONTROL LOGIC BOT_ON SW ANTICROSS CONDUCT – + TSD – THERMAL SHUTDOWN 9 NC PWM PWM COMP IZERO COMP SLOPE COMP – gm + – VOUT C1 + + SLEEP COMP L1 2 + + – 0.6V SS FB R2 8 R1 SLEEP REF – 0.6V – 10% PGOOD 5 + GND 4 3103 BD 3103f 8 LTC3103 OPERATION The LTC3103 step-down DC/DC converter is capable of supplying 300mA to the load. The output voltage is adjustable over a broad range and can be set as low as 0.6V. Both the power and the synchronous rectifier switches are internal N-channel MOSFETs. The converter uses a constant-frequency, current mode architecture and may be configured using automatic Burst Mode operation for highly efficient light load operation or configured for low noise forced conduction continuous operation where the converter is optimized to operate over a broad range of step-down ratios without pulse skipping. With the automatic Burst Mode feature enabled the typical DC supply current drops to only 1.8µA with no load. Main Control Loop During normal operation, the internal top power MOSFET is turned on at the beginning of each cycle and turned off when the PWM current comparator trips. The peak inductor current at which the comparator trips is controlled by the voltage on the output of the error amplifier. The FB pin allows the internally compensated error amplifier to receive an output feedback voltage from an external resistive divider from VOUT . When the load current increases, the output begins to fall causing a slight decrease in the feedback voltage relative to the 0.6V reference, this in turn causes the control voltage to increase until the average inductor current matches the new load current. While the top MOSFET is off, the bottom MOSFET is turned on until either the inductor current starts to reverse as indicated by the current reversal comparator, IZERO, or the beginning of the next clock cycle. IZERO is set to 40mA (typical) in automatic Burst Mode operation and –110mA (typical) in forced continuous mode. Forced Continuous Mode Grounding MODE enables forced continuous operation and disables Burst Mode operation. At light loads, forced continuous mode minimizes output voltage ripple and noise but is less efficient than Burst Mode operation. Forced continuous operation may be desirable for use in applications that are sensitive to the Burst Mode output voltage ripple or its harmonics. The LTC3103 offers a broad range of possible step-down ratios without pulse skipping but for very small step-down ratios, the minimum on-time of the main switch will be reached and the converter will begin turning off for multiple cycles in order to maintain regulation. Burst Mode Operation Holding the MODE pin above 1.2V will enable automatic Burst Mode operation and disable forced continuous operation. As the load transitions current increases the converter will automatically transition between Burst Mode and PWM operation. Conversely the converter will automatically transition from PWM operation to Burst Mode operation as the load decreases. Between bursts the converter is not active (i.e., both switches are off) and most of the internal circuitry is disabled to reduce the quiescent current to 1.8µA. Burst Mode entry and exit is determined by the peak inductor current and therefore the load current at which Burst Mode operation will be entered or exited depends on the input voltage, the output voltage and the inductor value. Typical curves for Burst Mode entry threshold are provided in the Typical Performance Characteristics section of this data sheet. Soft-Start The converter has an internal closed-loop soft-start circuit with a nominal duration of 1.4ms. The converter remains in regulation during soft-start and will therefore respond to output load transients that occur during this time. In addition, the output voltage rise time has minimal dependency on the size of the output capacitor or load current. Thermal Shutdown If the die temperature exceeds 150°C (typical) the converter will be disabled. All power devices will be turned off and the switch node will be forced into a high impedance state. The soft-start circuit is reset during thermal shutdown to provide a smooth recovery once the overtemperature condition is eliminated. If enabled, the converter will restart when the die temperature drops to approximately 130°C. 3103f 9 LTC3103 OPERATION Power Good Status Output Short-Circuit Protection The PGOOD pin is an open-drain output which indicates the output voltage status of the step-down converter. If the output voltage falls 10% below the regulation voltage, the PGOOD open-drain output will pull low. A built-in deglitching delay prevents false trips due to voltage transients on load steps. The output voltage must rise 2% above the falling threshold before the pull-down will turn off. The PGOOD output will also pull low during overtemperature shutdown and undervoltage lockout to indicate these fault conditions. The PGOOD output is valid 1ms after the buck converter is enabled. When the converter is disabled the open-drain device is forced on into a low impedance state. The PGOOD pull-up voltage must be below the 6V absolute maximum voltage rating of the pin. When the output is shorted to ground, the error amplifier will saturate high and the high side switch will turn on at the start of each cycle and remain on until the current limit trips. During this minimum on-time, the inductor current will increase rapidly and will decrease very slowly during the remainder of the period due to the very small reverse voltage produced by a hard output short. To eliminate the possibility of inductor current runaway in this situation, the switching frequency is reduced to approximately 300kHz when the voltage on FB falls below 0.3V. Current Limit The peak inductor current limit comparator shuts off the buck switch once the internal limit threshold is reached. Peak switch current is no less than 400mA. Slope Compensation Current mode control requires the use of slope compensation to prevent sub-harmonic oscillations in the inductor current waveform at high duty cycle operation. In some current mode ICs, current limiting is performed by clamping the error amplifier voltage to a fixed maximum which leads to a reduced output current capability at low step-down ratios. Slope compensation is accomplished on the LTC3103 internally through the addition of a compensating ramp to the current sense signal. The current limiting function is completed prior to the addition of the compensation ramp and therefore achieves a peak inductor current limit that is independent of duty cycle. BST Pin Function The input switch driver operates from the voltage generated on the BST pin. An external capacitor between the SW and BST pins and an internal synchronous PMOS boost switch are used to generate a voltage that is higher than the input voltage. When the synchronous rectifier is on (SW is low) the internal boost switch connects one side of the capacitor to VCC replenishing its charge. When the synchronous rectifier is turned off the input switch is turned on forcing SW high and the BST pin is at a potential equal to VCC + SW relative to ground. A comparator ensures there is sufficient voltage across the boost capacitor to guarantee start-up after long sleep periods or if starting up into a pre-biased output. Undervoltage Lockout The LTC3103 has an internal UVLO which disables the converter if the supply voltage decreases below 2.1V (typical), the converter will be disabled. The soft-start for the converter will be reset during undervoltage lockout to provide a smooth restart once the input voltage increases above the undervoltage lockout threshold. The RUN pin can alternatively be configured as a precise undervoltage lockout (UVLO) on the VIN supply with a resistive divider connected to the RUN pin. 3103f 10 LTC3103 APPLICATIONS INFORMATION The basic LTC3103 application circuit is shown as the Typical Application on the front page of this data sheet. The external component selection is determined by the desired output voltage, output current, desired noise immunity and ripple voltage requirements for each particular application. However, basic guidelines and considerations for the design process are provided in this section. in discontinuous conduction for a wider range of output loads and efficiency will be reduced. In addition, there is a minimum inductor value required to maintain stability of the current loop (given the fixed internal slope compensation). Specifically, if the buck converter is going to be utilized at duty cycles greater than 40%, the inductance value must be at least LMIN as given by the following equation: Inductor Selection LMIN ≥ 2.5 • VOUT (µH) The choice of inductor value influences both the efficiency and the magnitude of the output voltage ripple. Larger inductance values will reduce inductor current ripple and will therefore lead to lower output voltage ripple. For a fixed DC resistance, a larger value inductor will yield higher efficiency by lowering the peak current to be closer to the average. However, a larger value inductor within the same family will generally have a greater series resistance, thereby offsetting this efficiency advantage. Given a desired peak-to-peak current ripple, ∆IL(A), the required inductance can be calculated via the following expression: L≥ VOUT 1.2 • ∆IL V • 1– OUT (µH) VIN A reasonable choice for ripple current is ∆IL = 120mA which represents 40% of the maximum 300mA load current. The DC current rating of the inductor should be at least equal to the maximum load current plus half the ripple current in order to prevent core saturation and loss of efficiency during operation. To optimize efficiency the inductor should have a low series resistance. In particularly space restricted applications it may be advantageous to use a much smaller value inductor at the expense of larger ripple current. In such cases, the converter will operate Table 1 depicts the minimum required inductance for several common output voltages using standard inductor values. Table 1. Minimum Inductance OUTPUT VOLTAGE (V) MINIMUM INDUCTANCE (µH) 0.8 2.2 1.2 3.3 2.0 5.6 2.7 6.8 3.3 8.3 5.0 15 A large variety of low ESR, power inductors are available that are well suited to the LTC3103 converter applications. The trade-off generally involves PCB area, application height, required output current and efficiency. Table 2 provides a representative sampling of small surface mount inductors that are well suited for use with the LTC3103. The inductor specifications listed are for comparison purposes but other values within these inductor families are generally well suited to this application as well. Within each family (i.e., at a fixed inductor size), the DC resistance generally increases and the maximum current generally decreases with increased inductance. 3103f 11 LTC3103 APPLICATIONS INFORMATION Table 2. Representative Inductor Selection PART NUMBER VALUE (µH) DCR (Ω) MAX DC CURRENT (A) SIZE (MM) W×L×H Coilcraft EPL3015 6.8 0.19 1.00 3.0 × 3.0 × 1.5 LPS3314 10 0.33 0.70 3.3 × 3.3 × 1.3 LPS4018 15 0.26 1.12 4.0 × 4.0 × 1.8 SD3114 6.8 0.30 0.98 3.1 × 3.1 × 1.4 SD3118 10 0.3 0.75 3.2 × 3.2 × 1.8 Cooper-Bussman Murata LQH3NPN 6.8 0.20 1.25 3.0 × 3.0 × 1.4 LQH44PN 10 0.16 1.10 4.0 × 4.0 × 1.7 CDRH3D16 6.8 0.17 0.73 3.8 × 3.8 × 1.8 CDRH3D16 10 0.21 0.55 3.8 × 3.8 × 1.8 Sumida Taiyo-Yuden CBC3225 6.8 0.16 0.93 3.2 × 2.5 × 2.5 NR3015 10 0.23 0.70 3.0 × 3.0 × 1.5 NR4018 15 0.30 0.65 4.0 × 4.0 × 1.8 744029006 6.8 0.25 0.95 2.8 × 2.8 × 1.4 744031006 6.8 0.16 0.85 3.8 × 3.8 × 1.7 Würth 744031100 10 0.19 0.74 3.8 × 3.8 × 1.7 744031100 15 0.26 0.62 3.8 × 3.8 × 1.7 Panasonic ELLVGG6R8N 6.8 0.23 1.00 3.0 × 3.0 × 1.5 ELL4LG100MA 10 0.20 0.80 3.8 × 3.8 × 1.8 VLF3012 6.8 0.18 0.78 3.0 × 2.8 × 1.2 VLC4018 10 0.16 0.85 4.0 × 4.0 × 1.8 TDK Output Capacitor Selection A low ESR output capacitor should be utilized at the buck output in order to minimize voltage ripple. Multilayer ceramic capacitors are an excellent choice as they have low ESR and are available in small footprints. In addition to controlling the output ripple magnitude, the value of the output capacitor also sets the loop crossover frequency and therefore can impact loop stability. There is both a minimum and maximum capacitance value required to ensure stability of the loop. If the output capacitance is too small, the loop crossover frequency will increase to the point where switching delay and the high frequency parasitic poles of the error amplifier will degrade the phase margin. In addition, the wider bandwidth produced by a small output capacitor will make the loop more susceptible to switching noise. At the other extreme, if the output capacitor is too large, the crossover frequency can decrease too far below the compensation zero and also lead to degraded phase margin. Table 3 provides a guideline for the range of allowable values of low ESR output capacitors assuming a feedforward capacitor is used. See the Output Voltage Programming section for details on selecting a feedforward capacitor. Larger value output capacitors can be accommodated provided they have sufficient ESR to stabilize the loop, or by increasing the value of the feedforward capacitor in parallel with the upper resistor divider resistor. In Burst Mode operation, the output capacitor stores energy to satisfy the load current when the LTC3103 is in a low current sleep state between the burst pulses. It can take several cycles to respond to a large load step during a sleep period. If large transient load currents are required then a larger capacitor can be used at the output to minimize output voltage droop until the part transitions from Burst Mode operation to continuous mode operation. Note that even X5R and X7R type ceramic capacitors have a DC bias effect which reduces their capacitance when a DC voltage is applied. It is not uncommon for capacitors offered in the smallest case sizes to lose more than 50% of their capacitance when operated near their rated voltage. As a result it is sometimes necessary to use a larger capacitance value or use a higher voltage rating in order to realize the intended capacitance value. Consult the manufacturer’s data for the capacitor you select to be assured of having the necessary capacitance in your application. Table 3. Recommended Output Capacitor Limits OUTPUT VOLTAGE (V) CMIN (µF) CMAX (µF) 0.8 22.0 220 1.2 15.0 220 2.0 12.0 100 2.7 6.8 68 3.3 4.7 47 5.0 4.7 47 3103f 12 LTC3103 APPLICATIONS INFORMATION Input Capacitor Selection Minimum Off-Time/On-Time Considerations The VIN pin provides current to the power stages of the buck converter. It is recommended that a low ESR ceramic capacitor with a value of at least 10µF be used to bypass the pin. These capacitors should be placed as close to the pin as possible and should have a short return path to the GND pin. The maximum duty cycle is limited in the LTC3103 by the boost capacitor refresh time, the rise/fall times of the switch as well as propagation delays in the PWM comparator, the level shifts and the gate drive. This minimum off time is typically 65ns which imposes a maximum duty cycle of: Output Voltage Programming where f is the 1.2MHz switching frequency and tOFF(MIN) is the minimum off-time. If the maximum duty cycle is surpassed, due to a dropping input voltage for example, the output will drop out of regulation. The minimum input voltage to avoid this dropout condition is: The output voltage is set by a resistive divider according to the following formula: R2 VOUT = 0.6V • 1+ R1 The external divider is connected to the output as shown in Figure 1. Note that FB divider current is not included in the LTC3103 quiescent current specification. For improved transient response, a feedforward capacitor, CFF , may be placed in parallel with resistor R2. The capacitor modifies the loop dynamics by adding a pole-zero pair to the loop dynamics which generates a phase boost that can improve the phase margin and increase the speed of the transient response, resulting in smaller voltage deviation on load transients. The zero frequency depends not only on the value of the feed forward capacitor, but also on the upper resistor divider resistor. Specifically, the zero frequency, fZERO, is given by the following equation: fZERO = 1 2 • π •R2 • CFF1 For R2 resistor values of ~1M a 12pF ceramic capacitor will suffice, however that value may be increased or decreased to optimize the converter’s response for a given set of application parameters. VOUT R2 CFF FB LTC3103 R1 GND 3103 F01 Figure 1. Setting the Output Voltage DCMAX = 1 – (f • tOFF(MIN)) VIN(MIN) = ( VOUT 1– f • tOFF(MIN) ) Conversely, the minimum on-time is the smallest duration of time in which the buck switch can be in its “on” state. This time is limited by similar factors and is typically 70ns. In forced continuous operation, the minimum on-time limit imposes a minimum duty cycle of: DCMIN = f • tON(MIN) where tON(MIN) is the minimum on-time. In extreme stepdown ratios where the minimum duty cycle is surpassed, the output voltage will still be in regulation but the rectifier switch will remain on for more than one cycle and subharmonic switching will occur to provide a higher effective duty cycle. The result is higher output voltage ripple. This is an acceptable result in many applications so this constraint may not be of critical importance in some cases. Precise Undervoltage Lockout The LTC3103 is in shutdown when the RUN pin is low and active when the pin is higher than the RUN pin threshold. The rising threshold of the RUN pin comparator is an accurate 0.8V, with 60mV of hysteresis. This threshold is enabled when VIN is above the 2.5V minimum value. If VIN is lower than 2.5V, an internal undervoltage monitor puts the part in shutdown independent of the RUN pin state. The RUN pin can be configured as a precise undervoltage lockout (UVLO) on the VIN supply with a resistive divider 3103f 13 LTC3103 APPLICATIONS INFORMATION tied to the RUN pin as shown in Figure 2 to meet specific VIN voltage requirements. If used, note that the external divider current is not included in the LTC3103 quiescent current specification. The rising UVLO threshold can be calculated using the following equation: R4 VUVLO = 0.8V • 1+ R3 Internal VCC Regulator The LTC3103 uses an internal NMOS source follower regulator off of VIN to generate a low voltage internal rail, VCC. The regulator is designed to deliver current only to the internal drivers and other internal control circuits and not to an external load. The VCC pin should be bypassed with a 1µF or larger ceramic capacitor. Boost Capacitor Selection The LTC3103 uses a bootstrapped supply to power the buck switch gate drivers. When the synchronous rectifier turns on, an internal PMOS switch turns on synchronously to charge the boost capacitor, CBST , to the voltage on VCC. For most applications a 0.022µF will suffice. The capacitor should be placed as close to their respective pins as possible. VIN R4 RUN R3 LTC3103 GND 3103 F02 Figure 2. Setting the Undervoltage Lockout Threshold VIN VOUT VIA GROUND PLANE VIN 1 10 MODE SW 2 9 NC BST 3 8 FB GND 4 7 RUN PGOOD 5 6 VCC KELVIN TO VOUT UNINTERRUPTED GROUND PLANE SHOULD EXIST UNDER ALL COMPONENTS SHOWN AND UNDER THE TRACES CONNECTING THOSE COMPONENTS 3103 F03 Figure 3. PCB Layout Recommendations 3103f 14 LTC3103 TYPICAL APPLICATIONS Portable LF RFID Reader, Dual Lithium-Ion to 3.3V/300mA Regulator with Ultralow IQ VIN BST MODE SW 95 CBST 0.022µF LTC3103 PGOOD RUN PGOOD L1 10µH 1M VOUT 3.3V 300mA R2 2M 10µF VCC 100 FB 90 EFFICIENCY (%) VIN 5V TO 9V Efficiency vs Output Current CFF 12pF GND 1µF VIN = 5V 85 VIN = 9V 80 75 70 65 47µF R1 442k 60 0.0001 3103 TA02a L1: TDK VLC4018 0.001 0.01 0.1 LOAD CURRENT (A) 1 3103 TA02b 12V to 2.2V/300mA Regulator with 9V Accurate UVLO VIN 12V VIN R4 2.05M 10µF R3 200k BST MODE SW LTC3103 RUN PGOOD VCC FB GND 1µF CBST 0.022µF L1 10µH PGOOD 1M VOUT 2.2V 300mA R2 1.78M VIN 5V/DIV VOUT 1V/DIV IL 100mA/DIV CFF 12pF R1 665k Start-Up with Ramped Input Power 47µF 20ms/DIV 3103 TA03b 3103 TA03a L1: MURATA LQH44PN1 3103f 15 LTC3103 TYPICAL APPLICATIONS Slolar-Powered 2.2V Supply with Li Battery Backup and Run Threshold Set to Battery Minimum Voltage SDM20E-40C R4 3.09M + + 3.6V TADIRAN AA LITHIUM BATTERY 4.8V, 0.5W SOLAR PANEL MPT4.8-150 (6.5VOC) + CBULK 100µF BST VIN 3.2V RUN THRESHOLD SW RUN R3 715k CIN 10µF CBST 22nF LTC3103 MODE PGOOD FB VCC GND C1 1µF L1 15µH VOUT 2.2V R2 1.78M CFF 22pF R1 665k COUT 22µF 3103 TA04 L1: COILCRAFT LP54018 3103f 16 LTC3103 TYPICAL APPLICATIONS 5V to 1.2V/300mA Low Noise Regulator Using Forced Continuous Operation VIN 5V VIN BST MODE SW LTC3103 ON OFF RUN PGOOD FB PGOOD 1M VOUT 1.2V 300mA CFF 22pF GND 1µF L1 4.7µH R2 402k 10µF VCC CBST 0.022µF 10µF R1 402k 3103 TA05a L1: SUMIDA CDRH4D11NP-4R7N Efficiency vs Output Current 100 90 EFFICIENCY (%) 80 70 60 50 40 30 20 10 0 0.0001 VIN = 2.5V VIN = 3.3V VIN = 5V 0.001 0.01 0.1 OUTPUT CURRENT (A) 1 3103 TA05b 3103f 17 LTC3103 PACKAGE DESCRIPTION Please refer to http://www.linear.com/designtools/packaging/ for the most recent package drawings. DD Package 10-Lead Plastic DFN (3mm × 3mm) (Reference LTC DWG # 05-08-1699 Rev C) 0.70 ±0.05 3.55 ±0.05 1.65 ±0.05 2.15 ±0.05 (2 SIDES) PACKAGE OUTLINE 0.25 ± 0.05 0.50 BSC 2.38 ±0.05 (2 SIDES) RECOMMENDED SOLDER PAD PITCH AND DIMENSIONS 3.00 ±0.10 (4 SIDES) R = 0.125 TYP 6 0.40 ± 0.10 10 1.65 ± 0.10 (2 SIDES) PIN 1 NOTCH R = 0.20 OR 0.35 × 45° CHAMFER PIN 1 TOP MARK (SEE NOTE 6) 0.200 REF 0.75 ±0.05 0.00 – 0.05 5 1 (DD) DFN REV C 0310 0.25 ± 0.05 0.50 BSC 2.38 ±0.10 (2 SIDES) BOTTOM VIEW—EXPOSED PAD NOTE: 1. DRAWING TO BE MADE A JEDEC PACKAGE OUTLINE M0-229 VARIATION OF (WEED-2). CHECK THE LTC WEBSITE DATA SHEET FOR CURRENT STATUS OF VARIATION ASSIGNMENT 2. DRAWING NOT TO SCALE 3. ALL DIMENSIONS ARE IN MILLIMETERS 4. DIMENSIONS OF EXPOSED PAD ON BOTTOM OF PACKAGE DO NOT INCLUDE MOLD FLASH. MOLD FLASH, IF PRESENT, SHALL NOT EXCEED 0.15mm ON ANY SIDE 5. EXPOSED PAD SHALL BE SOLDER PLATED 6. SHADED AREA IS ONLY A REFERENCE FOR PIN 1 LOCATION ON THE TOP AND BOTTOM OF PACKAGE 3103f 18 LTC3103 PACKAGE DESCRIPTION Please refer to http://www.linear.com/designtools/packaging/ for the most recent package drawings. MSE Package 10-Lead Plastic MSOP, Exposed Die Pad (Reference LTC DWG # 05-08-1664 Rev H) BOTTOM VIEW OF EXPOSED PAD OPTION 1.88 ± 0.102 (.074 ± .004) 5.23 (.206) MIN 1 0.889 ± 0.127 (.035 ± .005) 0.05 REF 10 0.305 ± 0.038 (.0120 ± .0015) TYP RECOMMENDED SOLDER PAD LAYOUT 3.00 ± 0.102 (.118 ± .004) (NOTE 3) DETAIL “B” CORNER TAIL IS PART OF DETAIL “B” THE LEADFRAME FEATURE. FOR REFERENCE ONLY NO MEASUREMENT PURPOSE 10 9 8 7 6 DETAIL “A” 0° – 6° TYP 1 2 3 4 5 GAUGE PLANE 0.53 ± 0.152 (.021 ± .006) DETAIL “A” 0.18 (.007) 0.497 ± 0.076 (.0196 ± .003) REF 3.00 ± 0.102 (.118 ± .004) (NOTE 4) 4.90 ± 0.152 (.193 ± .006) 0.254 (.010) 0.29 REF 1.68 (.066) 1.68 ± 0.102 3.20 – 3.45 (.066 ± .004) (.126 – .136) 0.50 (.0197) BSC 1.88 (.074) SEATING PLANE 0.86 (.034) REF 1.10 (.043) MAX 0.17 – 0.27 (.007 – .011) TYP 0.50 (.0197) BSC NOTE: 1. DIMENSIONS IN MILLIMETER/(INCH) 2. DRAWING NOT TO SCALE 3. DIMENSION DOES NOT INCLUDE MOLD FLASH, PROTRUSIONS OR GATE BURRS. MOLD FLASH, PROTRUSIONS OR GATE BURRS SHALL NOT EXCEED 0.152mm (.006") PER SIDE 4. DIMENSION DOES NOT INCLUDE INTERLEAD FLASH OR PROTRUSIONS. INTERLEAD FLASH OR PROTRUSIONS SHALL NOT EXCEED 0.152mm (.006") PER SIDE 5. LEAD COPLANARITY (BOTTOM OF LEADS AFTER FORMING) SHALL BE 0.102mm (.004") MAX 6. EXPOSED PAD DIMENSION DOES INCLUDE MOLD FLASH. MOLD FLASH ON E-PAD SHALL NOT EXCEED 0.254mm (.010") PER SIDE. 0.1016 ± 0.0508 (.004 ± .002) MSOP (MSE) 0911 REV H 3103f Information furnished by Linear Technology Corporation is believed to be accurate and reliable. However, no responsibility is assumed for its use. Linear Technology Corporation makes no representation that the interconnection of its circuits as described herein will not infringe on existing patent rights. 19 LTC3103 TYPICAL APPLICATION 12V to 5V/300mA Regulator with High Efficiency, Ultralow IQ (1.8µA with VOUT in Regulation, No Load) VIN 12V VIN BST MODE SW LTC3103 CBST 0.022µF L1 10µH PGOOD 1M RUN PGOOD R2 1.87M 10µF VCC FB CFF 10pF GND 1µF VOUT 5V 300mA 47µF R1 255k 3103 TA06 L1: SUMIDA CDRH4D16FB RELATED PARTS PART NUMBER DESCRIPTION COMMENTS LTC3104 15V, 300mA Synchronous Step-Down DC/DC Converter with Ultralow Quiescent Current and 10mA LDO VIN: 2.5V to 15V, VOUT(MIN) = 0.6V, IQ = 2.8µA, ISD = 1µA, 3mm × 3mm DFN-10, MSOP-10 LTC3642 45V (Transient to 60V) 50mA Synchronous Step-Down DC/DC Converter VIN: 4.5V to 45V, VOUT(MIN) = 0.8V, IQ = 12µA, ISD < 1µA, 3mm × 3mm DFN-8, MSOP-8 LTC3631 45V (Transient to 60V) 100mA Synchronous Step-Down DC/DC Converter VIN: 4.5V to 45V, VOUT(MIN) = 0.8V, IQ = 12µA, ISD < 1µA, 3mm × 3mm DFN-8, MSOP-8 LTC3632 50V (Transient to 60V) 20mA Synchronous Step-Down DC/DC Converter VIN: 4.5V to 50V, VOUT(MIN) = 0.8V, IQ = 12µA, ISD < 1µA, 3mm × 3mm DFN-8, MSOP-8 LTC3388-1/LTC3388-3 20V, 50mA High Efficiency Nano Power Step-Down Regulators VIN: 2.7V to 20V, VOUT(MIN) Fixed 1.1V to 5.5V, IQ = 720nA, ISD = 400nA, 3mm × 3mm DFN-10, MSOP-10 LTC3108/LTC3108-1 Ultralow Voltage Step-Up Converter and Power Managers VIN: 0.02V to 1V, VOUT(MIN) Fixed 2.35V to 5V, IQ = 6µA, ISD < 1µA, 3mm × 4mm DFN-12, SSOP-16 LTC3109 Auto-Polarity, Ultralow Voltage Step-Up Converter and Power Manager VIN: 0.03V to 1V, VOUT(MIN) Fixed 2.35V to 5V, IQ = 7µA, ISD < 1µA, 4mm × 4mm QFN-20, SSOP-20 LTC4071 Li-Ion/Polymer Shunt Battery Charger System with Low Battery Disconnect Charger Plus Pack Protection in One IC Low Operating Current (550nA), 50mA Internal Shunt Current, Pin Selectable Float Voltages (4.0V, 4.1V, 4.2V), 8-Lead, 2mm × 3mm, DFN and MSOP Packages LTC4070 Li-Ion/Polymer Low Current Shunt Battery Charger System Selectable VFLOAT = 4.0V, 4.1V, 4.2V, Max Shunt Current = 50mA, ICCQ = 450nA to 1.04mA, ICCQLB = 300nA, 2mm × 3mm DFN-8, MSOP-8 LTC1877 10V, 600mA High Efficiency Synchronous Step-Down DC/DC Converter LTC3105 5V, 400mA, MPPC Step-Up Converter with 250mV Start-Up VIN: 0.225V to 5V, VOUT(MAX) = 5.25V, IQ = 24µA, ISD = 10µA, 3mm × 3mm DFN-10, MSOP-12 VIN: 2.65V to 10V, VOUT(MIN) = 0.8V, IQ = 10µA, ISD < 1µA, MSOP-8 3103f 20 Linear Technology Corporation LT 1111 • PRINTED IN USA 1630 McCarthy Blvd., Milpitas, CA 95035-7417 (408) 432-1900 ● FAX: (408) 434-0507 ● www.linear.com LINEAR TECHNOLOGY CORPORATION 2011