ONSEMI NCP1729SN35T1

NCP1729
Switched Capacitor
Voltage Inverter
The NCP1729 is a CMOS charge pump voltage inverter that is
designed for operation over an input voltage range of 1.15 V to 5.5 V
with an output current capability in excess of 50 mA. The operating
current consumption is only 122 mA, and a power saving shutdown
input is provided to further reduce the current to a mere 0.4 mA. The
device contains a 35 kHz oscillator that drives four low resistance
MOSFET switches, yielding a low output resistance of 26 W and a
voltage conversion efficiency of 99%. This device requires only two
external 3.3 mF capacitors for a complete inverter making it an ideal
solution for numerous battery powered and board level applications.
The NCP1729 is available in the space saving TSOP−6 package.
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MARKING
DIAGRAM
TSOP−6
(SOT23−6)
SN SUFFIX
CASE 318G
1
6
EADAYW G
G
1
Features
•
•
•
•
•
•
•
•
Operating Voltage Range of 1.15 V to 5.5 V
Output Current Capability in Excess of 50 mA
Low Current Consumption of 122 mA
Power Saving Shutdown Input for a Reduced Current of 0.4 mA
Operation at 35 kHz
Low Output Resistance of 26 W
Space Saving TSOP−6 Package
Pb−Free Package is Available
Typical Applications
•
•
•
•
•
•
•
•
LCD Panel Bias
Cellular Telephones
Pagers
Personal Digital Assistants
Electronic Games
Digital Cameras
Camcorders
Hand Held Instruments
Vin
6
2
5
3
4
= Device Code
= Assembly Location
= Year
= Work Week
= Pb−Free Package
(Note: Microdot may be in either location)
PIN CONNECTIONS
Vout
1
6
C+
Vin
2
5
SHDN
C−
3
4
GND
(Top View)
ORDERING INFORMATION
Device
Package
Shipping †
NCP1729SN35T1
TSOP−6
3000 /
Tape & Reel
TSOP−6
(Pb−Free)
3000 /
Tape & Reel
NCP1729SN35T1G
−Vout
1
EAD
A
Y
W
G
†For information on tape and reel specifications,
including part orientation and tape sizes, please
refer to our Tape and Reel Packaging Specifications
Brochure, BRD8011/D.
This device contains 77 active transistors.
Figure 1. Typical Application
© Semiconductor Components Industries, LLC, 2006
March, 2006 − Rev. 4
1
Publication Order Number:
NCP1729/D
NCP1729
MAXIMUM RATINGS*
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Symbol
Value
Unit
Input Voltage Range (Vin to GND)
Rating
Vin
−0.3 to 6.0
V
Output Voltage Range (Vout to GND)
Vout
−6.0 to 0.3
V
Output Current
Iout
100
mA
Output Short Circuit Duration (Vout to GND)
tSC
Indefinite
sec
Operating Junction Temperature
TJ
150
°C
Power Dissipation and Thermal Characteristics
Thermal Resistance, Junction−to−Air
Maximum Power Dissipation @ TA = 70°C
RqJA
PD
256
313
°C/W
mW
Storage Temperature
Tstg
−55 to 150
°C
Stresses exceeding Maximum Ratings may damage the device. Maximum Ratings are stress ratings only. Functional operation above the
Recommended Operating Conditions is not implied. Extended exposure to stresses above the Recommended Operating Conditions may affect
device reliability.
*ESD Ratings
ESD Machine Model Protection up to 200 V, Class B
ESD Human Body Model Protection up to 2000 V, Class 2
ELECTRICAL CHARACTERISTICS (Vin = 5.0 V, C1 = 3.3 mF, C2 = 3.3 mF, TA = −40°C to 85°C, typical values shown are for
TA = 25°C unless otherwise noted. See Figure 14 for Test Setup.)
Characteristic
Symbol
Min
Typ
Max
Operating Supply Voltage Range (SHDN = Vin, RL = 10 k)
Vin
1.5 to 5.5
1.15 to 6.0
−
Supply Current Device Operating (SHDN = 5.0 V, RL = R)
TA = 25°C
TA = 85°C
Iin
Unit
V
mA
−
−
122
128
200
200
−
−
0.4
1.7
−
−
24.5
19
33.5
−
45.6
54
mA
Supply Current Device Shutdown (SHDN = 0 V)
TA = 25°C
TA = 85°C
ISHDN
Oscillator Frequency
TA = 25°C
TA = −40°C to 85°C
fOSC
Output Resistance (Iout = 25 mA, Note 1)
Rout
−
26
50
W
Voltage Conversion Efficiency (RL = R)
VEFF
99
99.9
−
%
Power Conversion Efficiency (RL = 1.0 k)
PEFF
−
96
−
%
−
−
0.6 Vin
0.5 Vin
−
−
Shutdown Input Threshold Voltage (Vin = 1.5 V to 5.5 V)
High State, Device Operating
Low State, Device Shutdown
Vth(SHDN)
Shutdown Input Bias Current
High State, Device Operating, SHDN = 5.0 V
TA = 25°C
TA = 85°C
Low State, Device Shutdown, SHDN = 0 V
TA = 25°C
TA = 85°C
Wake−Up Time from Shutdown (RL = 1.0 k)
kHz
V
pA
IIH
−
−
5.0
100
−
−
−
−
5.0
100
−
−
−
1.0
−
IIL
tWKUP
1. Capacitors C1 and C2 contribution is approximately 20% of the total output resistance.
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2
ms
NCP1729
100
90
Rout, OUTPUT RESISTANCE (W)
Rout, OUTPUT RESISTANCE (W)
100
Figure 14 Test Setup
TA = 25°C
80
70
60
50
40
30
20
1.0
1.5
2.0
2.5
3.0
3.5
4.0
4.5
5.0
Figure 14 Test Setup
90
80
Vin = 1.5 V
70
Vin = 2.0 V
60
50
40
30
20
−50
5.5
Vin, SUPPLY VOLTAGE (V)
30
Vin = 4.75 V
Vout = −4.00 V
20
Vin = 3.15 V
Vout = −2.50 V
10
Vin = 1.90 V
Vout = −1.50 V
5
0
0
10
20
Figure 14 Test Setup
TA = 25°C
30
40
150
Vin = 3.15 V
Vout = −2.50 V
100
Vin = 1.90 V
Vout = −1.50 V
50
0
10
20
30
40
Figure 4. Output Current vs. Capacitance
Figure 5. Output Voltage Ripple vs.
Capacitance
fOSC, OSCILLATOR FREQUENCY (kHz)
Iin, SUPPLY CURRENT (mA)
200
C1, C2, C3, CAPACITANCE (mF)
Figure 14 Test Setup
RL = ∞
TA = 85°C
90
TA = 25°C
TA = −40°C
70
60
50
2.0
2.5
3.0
3.5
4.0
100
Vin = 4.75 V
Vout = −4.00 V
250
C1, C2, C3, CAPACITANCE (mF)
100
40
1.5
75
Figure 14 Test Setup
TA = 25°C
300
0
110
80
50
350
50
130
120
25
0
Figure 3. Output Resistance vs. Ambient
Temperature
Vout, OUTPUT VOLTAGE RIPPLE (mVp−p)
Iout, OUTPUT CURRENT (mA)
35
15
−25
TA, AMBIENT TEMPERATURE (°C)
Figure 2. Output Resistance vs. Supply Voltage
25
Vin = 3.3 V
Vin = 5.0 V
4.5
5.0
39
Figure 14 Test Setup
38
Vin = 1.5 V
37
36
Vin = 3.3 V
35
Vin = 5.0 V
34
33
32
−50
−25
0
25
50
75
Vin, SUPPLY VOLTAGE (V)
TA, AMBIENT TEMPERATURE (°C)
Figure 6. Supply Current vs. Supply Voltage
Figure 7. Oscillator Frequency vs. Ambient
Temperature
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3
50
100
Vout, OUTPUT VOLTAGE (V)
0.0
Figure 14 Test Setup
TA = 25°C
Vin = 2.0 V
−1.0
−2.0
Vin = 3.3 V
−3.0
Vin = 5.0 V
−4.0
−5.0
−6.0
10
20
30
40
50
Vin = 5.0 V
80
70
Vin = 3.3 V
60
Vin = 1.5 V
Vin = 2.0 V
50
40
0
10
20
30
40
Figure 9. Power Conversion Efficiency vs.
Output Current
OUTPUT VOLTAGE RIPPLE AND
NOISE = 10 mV / Div. AC COUPLED
1.50
RL = 10 kW
SHDN = GND
Vin = 5.0 V
1.25
Vin = 3.3 V
1.00
0.75
Vin = 1.5 V
0.50
0.25
−50
−25
0
25
50
75
TA, AMBIENT TEMPERATURE (°C)
Figure 10. Output Voltage Ripple and Noise
Figure 11. Shutdown Supply Current vs.
Ambient Temperature
WAKEUP TIME FROM SHUTDOWN
4.5
4.0
Low State,
Device Shutdown
High State,
Device Operating
3.0
2.5
2.0
1.0
1.5
2.0
2.5
SHDN = 5.0V/Div.
Vin = 5.0 V
RL = 1.0 kW
TA = 25°C
Vout = 1.0 V/Div.
3.0
TIME = 400 ms / Div.
Vth(SHND), SHUTDOWN INPUT VOLTAGE THRESHOLD (V)
Figure 13. Wakeup Time From Shutdown
Figure 12. Supply Voltage vs. Shutdown Input
Voltage Threshold
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4
50
1.75
TIME = 10 ms / Div.
TA = 25°C
Vin, SUPPLY VOLTAGE (V)
90
Figure 8. Output Voltage vs. Output Current
5.0
1.5
0.5
Figure 14 Test Setup
TA = 25°C
Iout, OUTPUT CURRENT (mA)
Figure 14 Test Setup
Vin = 3.3 V
Iout = 5.0 mA
TA = 25°C
3.5
100
Iout, OUTPUT CURRENT (mA)
ISHDN, SHUTDOWN SUPPLY CURRENT (mA)
0
h, POWER CONVERSION EFFICIENCY (%)
NCP1729
100
NCP1729
Charge Pump Efficiency
−Vout
C
+ 2
6
1
The overall power conversion efficiency of the charge
pump is affected by four factors:
1. Losses from power consumed by the internal
oscillator, switch drive, etc. (which vary with input
voltage, temperature and oscillator frequency).
2. I2R losses due to the on−resistance of the MOSFET
switches on−board the charge pump.
3. Charge pump capacitor losses due to
Equivalent Series Resistance (ESR).
4. Losses that occur during charge transfer from the
commutation capacitor to the output capacitor when
a voltage difference between the two capacitors
exists.
Most of the conversion losses are due to factors 2, 3 and 4.
These losses are given by Equation 1.
RL
OSC
Vin
+
2
5
3
4
+
C1
C3
C1 = C2 = C3 = 3.3 mF
Figure 14. Test Setup/Voltage Inverter
DETAILED OPERATING DESCRIPTION
The NCP1729 charge pump converter inverts the voltage
applied to the Vin pin. Conversion consists of a two−phase
operation (Figure 15). During the first phase, switches S2
and S4 are open and S1 and S3 are closed. During this time,
C1 charges to the voltage on Vin and load current is supplied
from C2. During the second phase, S2 and S4 are closed, and
S1 and S3 are open. This action connects C1 across C2,
restoring charge to C2.
S1
ƪ
P
+ I out 2
LOSS(2,3,4)
1
(f
OSC
)C1
) 8R
SWITCH
R out ^ I out 2
) 4ESR
C1
) ESR
C2
ƫ
(eq. 1)
The 1/(fOSC)(C1) term in Equation 1 is the effective output
resistance of an ideal switched capacitor circuit (Figures 16
and 17).
The losses due to charge transfer above are also shown in
Equation 2. The output voltage ripple is given by Equation 3.
S2
Vin
PLOSS + [ 0.5C 1 (Vin 2 * Vout 2)
C1
) 0.5C2 (VRIPPLE 2 * 2VoutVRIPPLE)]
fOSC
(eq. 2)
C2
V
S3
S4
RIPPLE
+
Iout
(f
−Vout
From OSC
)(C )
OSC 2
) 2(I out)(ESR )
C2
(eq. 3)
f
Vin
Vout
Figure 15. Ideal Switched Capacitor Charge Pump
C1
C2
RL
APPLICATIONS INFORMATION
Figure 16. Ideal Switched Capacitor Model
Output Voltage Considerations
The NCP1729 performs voltage conversion but does not
provide regulation. The output voltage will drop in a linear
manner with respect to load current. The value of this
equivalent output resistance is approximately 26 W nominal
at 25°C with Vin = 5.0 V. Vout is approximately −5.0 V at
light loads, and drops according to the equation below:
VDROP + Iout
REQUIV
Vin
Vout
R
Rout
EQUIV
+
f
1
C1
C2
RL
Vout + * (Vin * VDROP)
Figure 17. Equivalent Output Resistance
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NCP1729
Capacitor Selection
Vout to GND, it is recommended that a large value capacitor
(at least equal to C1) be connected from Vin to GND. If the
device is loaded from Vin to Vout, a small (0.7 mF) capacitor
between the pins is sufficient.
In order to maintain the lowest output resistance and
output ripple voltage, it is recommended that low ESR
capacitors be used. Additionally, larger values of C1 will
lower the output resistance and larger values of C2 will
reduce output voltage ripple. (See Equation 3).
Table 1 shows various values of C1, C2 and C3 with the
corresponding output resistance values at 25°C. Table 2
shows the output voltage ripple for various values of C1, C2
and C3. The data in Tables 1 and 2 was measured not
calculated.
Voltage Inverter
The most common application for a charge pump is the
voltage inverter (Figure 14). This application uses two or
three external capacitors. The C1 (pump capacitor) and C2
(output capacitor) are required. The input bypass capacitor
C3, may be necessary depending on the application. The
output is equal to −Vin plus any voltage drops due to loading.
Refer to Tables 1 and 2 for capacitor selection. The test setup
used for the majority of the characterization is shown in
Figure 14.
Table 1. Output Resistance vs. Capacitance
(C1 = C2 = C3), Vin = 4.75 V and Vout = −4.0 V
C1 = C2 = C3 (mF)
Rout (W)
0.68
55.4
1.3
36.9
3.3
26.0
7.3
25.8
10
25.5
24
25.0
50
24.0
Layout Considerations
As with any switching power supply circuit, good layout
practice is recommended. Mount components as close
together as possible to minimize stray inductance and
capacitance. Also use a large ground plane to minimize
noise leakage into other circuitry.
Capacitor Resources
Selecting the proper type of capacitor can reduce
switching loss. Low ESR capacitors are recommended. The
NCP1729 was characterized using the capacitors listed in
Table 3. This list identifies low ESR capacitors for the
voltage inverter application.
Table 2. Output Voltage Ripple vs. Capacitance
(C1 = C2 = C3), Vin = 4.75 V and Vout = −4.0 V
C1 = C2 = C3
(mF)
Output Voltage Ripple
(mV)
0.68
322
1.3
205
3.3
120
7.3
69
10
56
24
32
50
20
Table 3. Capacitor Types
Manufacturer/Contact
AVX
843−448−9411
www.avxcorp.com
Cornell Dubilier
508−996−8561
www.cornell−dubilier.com
Input Supply Bypassing
The input voltage, Vin should be capacitively bypassed to
reduce AC impedance and minimize noise effects due to the
switching internals in the device. If the device is loaded from
TPS
ESRD
Sanyo/Os−con
619−661−6835
www.sanyovideo.com/oscon.htm
SN
SVP
Vishay
603−224−1961
www.vishay.com
593D
594
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6
Part Types/Series
NCP1729
−Vout
6
1
OSC
+
Vin
2
+
5
+
3
4
Capacitors = 3.3 mF
Figure 18. Voltage Inverter
The NCP1729 primary function is a voltage inverter. The device will convert 5.0 V into −5.0 V with light loads. Two
capacitors are required for the inverter to function. A third capacitor, the input bypass capacitor, may be required depending
on the power source for the inverter. The performance for this device is illustrated below.
0
Vout, OUTPUT VOLTAGE (V)
TA = 25°C
−1.0
Vin = 3.3 V
−2.0
−3.0
Vin = 5.0 V
−4.0
−5.0
−6.0
0
10
20
30
40
Iout, OUTPUT CURRENT (mA)
Figure 19. Voltage Inverter Load Regulation,
Output Voltage vs. Output Current
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50
NCP1729
Vin
−Vout
6
1
+
+
OSC
+
2
6
1
OSC
5
+
2
5
3
4
+
3
4
Capacitors = 3.3 mF
Figure 20. Cascaded Devices for Increased Negative Output Voltage
Two or more devices can be cascaded for increased output voltage. Under light load conditions, the output voltage is
approximately equal to −Vin times the number of stages. The converter output resistance increases dramatically with each
additional stage. This is due to a reduction of input voltage to each successive stage as the converter output is loaded. Note that
the ground connection for each successive stage must connect to the negative output of the previous stage. The performance
characteristics for a converter consisting of two cascaded devices are shown below.
−1.0
Vout, OUTPUT VOLTAGE (V)
−2.0
−3.0
B
−4.0
−5.0
−6.0
A
−7.0
Curve
Vin (V)
Rout (W)
−8.0
A
5.0
145
B
3.0
180
TA = 25°C
−9.0
−10.0
0
10
20
30
40
Iout, OUTPUT CURRENT (mA)
Figure 21. Cascade Load Regulation, Output
Voltage vs. Output Current
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NCP1729
6
1
OSC
Vin
−Vout
+
2
5
+
+
3
+
+
4
Capacitors = 3.3 mF
Figure 22. Negative Output Voltage Doubler
A single device can be used to construct a negative voltage doubler. The output voltage is approximately equal to −2.0 Vin
minus the forward voltage drop of each external diode. The performance characteristics for the above converter are shown
below. Note that curves A and C show the circuit performance with economical 1N4148 diodes, while curves B and D are with
lower loss MBRA120E Schottky diodes.
Vout, OUTPUT VOLTAGE (V)
0
TA = 25°C
−2.0
A
−4.0
B
−6.0
C
−8.0
Curve
Vin (V)
All Diodes
Rout (W)
A
3.0
1N4148
118
B
3.0
MBRA120E
107
C
5.0
1N4148
91
D
5.0
MBRA120E
85
D
−10.0
0
10
20
30
40
Iout, OUTPUT CURRENT (mA)
Figure 23. Doubler Load Regulation,
Output Voltage vs. Output Current
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NCP1729
6
1
OSC
Vin
−Vout
2
+
5
+
+
3
+
+
+
+
4
Capacitors = 3.3 mF
Figure 24. Negative Output Voltage Tripler
A single device can be used to construct a negative voltage tripler. The output voltage is approximately equal to −3.0 Vin
minus the forward voltage drop of each external diode. The performance characteristics for the above converter are shown
below. Note that curves A and C show the circuit performance with economical 1N4148 diodes, while curves B and D are with
lower loss MBRA120E Schottky diodes.
0
Vout, OUTPUT VOLTAGE
−2.0
A
−4.0
B
−6.0
C
−8.0
D
−10.0
−12.0
−14.0
TA = 25°C
−16.0
0
10
20
30
40
50
Iout, OUTPUT CURRENT
Figure 25. Tripler Load Regulation, Output
Voltage vs. Output Current
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Curve
Vin (V)
All Diodes
Rout (W)
A
3.0
1N4148
247
B
3.0
MBRA120E
228
C
5.0
1N4148
198
D
5.0
MBRA120E
188
NCP1729
6
1
OSC
+
Vin
+
2
5
3
4
+
Vout
Capacitors = 3.3 mF
Figure 26. Positive Output Voltage Doubler
A single device can be used to construct a positive voltage doubler. The output voltage is approximately equal to 2.0 Vin
minus the forward voltage drop of each external diode. The performance characteristics for the above converter are shown
below. Note that curves A and C show the circuit performance with economical 1N4148 diodes, while curves B and D are with
lower loss MBRA120E Schottky diodes.
10.0
Vout, OUTPUT VOLTAGE (V)
D
8.0
C
6.0
Curve
Vin (V)
All Diodes
Rout (W)
A
3.0
1N4148
32
B
3.0
MBRA120E
25
C
5.0
1N4148
24
D
5.0
MBRA120E
19.3
B
4.0
A
2.0
TA = 25°C
0
0
10
20
30
40
Iout, OUTPUT CURRENT (mA)
Figure 27. Doubler Load Regulation, Output
Voltage vs. Output Current
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NCP1729
6
1
OSC
+
Vin
+
2
+
Vout
5
+
3
+
4
Capacitors = 3.3 mF
Figure 28. Positive Output Voltage Tripler
A single device can be used to construct a positive voltage tripler. The output voltage is approximately equal to 3.0 Vin minus
the forward voltage drop of each external diode. The performance characteristics for the above converter are shown below.
Note that curves A and C show the circuit performance with economical 1N4148 diodes, while curves B and D are with lower
loss MBRA120E Schottky diodes.
14.0
Vout, OUTPUT VOLTAGE (V)
D
12.0
10.0
C
Curve
Vin (V)
All Diodes
Rout (W)
A
3.0
1N4148
110
B
3.0
MBRA120E
95
C
5.0
1N4148
88
D
5.0
MBRA120E
78
8.0
B
6.0
4.0
A
2.0
TA = 25°C
0
0
10
20
30
40
50
Iout, OUTPUT CURRENT (mA)
Figure 29. Tripler Load Regulation, Output
Voltage vs. Output Current
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NCP1729
−Vout
+
6
1
OSC
Vin
+
2
5
+
100 k
3
4
Capacitors = 3.3 mF
Figure 30. Load Regulated Negative Output Voltage
A zener diode can be used with the shutdown input to provide closed loop regulation performance. This significantly reduces
the converter’s output resistance and dramatically enhances the load regulation. For closed loop operation, the desired
regulated output voltage must be lower in magnitude than −Vin. The output will regulate at a level of −VZ + Vth(SHDN). Note
that the shutdown input voltage threshold is typically 0.5 Vin and therefore, the regulated output voltage will change
proportional to the converter’s input. This characteristic will not present a problem when used in applications with constant
input voltage. In this case the zener breakdown was measured at 25 mA. The performance characteristics for the above
converter are shown below. Note that the dashed curve sections represent the converter’s open loop performance.
−1.0
Vout, OUTPUT VOLTAGE (V)
TA = 25°C
A
−2.0
−3.0
B
−4.0
−5.0
0
10
20
30
40
50
60
70
Iout, OUTPUT CURRENT (mA)
Figure 31. Load Regulation, Output Voltage vs.
Output Current
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Curve
Vin (V)
Vz (V)
Vout (V)
A
3.3
3.9
−2.1
B
5.0
6.5
−3.8
NCP1729
−Vout
R1
6
1
+
OSC
Vin
+
2
5
3
4
+
R2
10 k
Capacitors = 3.3 mF
Figure 32. Line and Load Regulated Negative Output Voltage
An adjustable shunt regulator can be used with the shutdown input to give excellent closed loop regulation performance. The
shunt regulator acts as a comparator with a precise input offset voltage which significantly reduces the converter’s output
resistance and dramatically enhances the line and load regulation. For closed loop operation, the desired regulated output
voltage must be lower in magnitude than −Vin. The output will regulate at a level of −Vref (R2/R1 + 1). The adjustable shunt
regulator can be from either the TLV431 or TL431 families. The comparator offset or reference voltage is 1.25 V or 2.5 V
respectively. The performance characteristics for the converter are shown below. Note that the dashed curve sections represent
the converter’s open loop performance.
−0.5
TA = 25°C
Vout, OUTPUT VOLTAGE (V)
Vout, OUTPUT VOLTAGE (V)
−1.0
A
−2.0
−3.0
B
−4.0
−5.0
0
10
20
30
40
50
60
Iout = 25 mA
R1 = 10 k
R2 = 24 k
TA = 25°C
−1.5
−2.5
−3.5
−4.5
1.0
70
2.0
3.0
4.0
5.0
6.0
Iout, OUTPUT CURRENT (mA)
Vin, INPUT VOLTAGE (V)
Figure 33. Load Regulation, Output Voltage vs.
Output Current
Figure 34. Line Regulation, Output Voltage vs.
Input Current
Curve
Vin (V)
R1 (W)
R2 (W)
Vout (V)
A
3.0
10 k
5.0 k
−1.8
B
5.0
10 k
24 k
−4.2
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NCP1729
−Vout
+
6
1
1
OSC
Vin
+
6
OSC
2
5
2
5
3
4
3
4
+
+
Capacitors = 3.3 mF
Figure 35. Paralleling Devices for Increased Negative Output Current
An increase in converter output current capability with a reduction in output resistance can be obtained by paralleling two
or more devices. The output current capability is approximately equal to the number of devices paralleled. A single shared
output capacitor is sufficient for proper operation but each device does require its own pump capacitor. Note that the output
ripple frequency will be complex since the oscillators are not synchronized. The output resistance is approximately equal to
the output resistance of one device divided by the total number of devices paralleled. The performance characteristics for a
converter consisting of two paralleled devices is shown below.
Vout, OUTPUT VOLTAGE (V)
−1.0
TA = 25°C
−2.0
B
−3.0
A
−4.0
−5.0
0
10
20
30
40
50
60
70
80
90
100
Iout, OUTPUT CURRENT (mA)
Figure 36. Parallel Load Regulation, Output
Voltage vs. Output Current
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Curve
Vin (V)
Rout (W)
A
5.0
14
B
3.0
17
NCP1729
Q2
6
1
+
−Vout
+
OSC
Vin
C1
Q1
2
5
3
4
C3
+
C2
C1 = C2 = 470 mF
C3 = 220 mF
Q1 = PZT751
Q2 = PZT651
−Vout = Vin −VBE(Q1) − VBE(Q2) −2 VF
Figure 37. External Switch for Increased Negative Output Current
The output current capability of the NCP1729 can be extended beyond 600 mA with the addition of two external switch
transistors and two Schottky diodes. The output voltage is approximately equal to −Vin minus the sum of the base emitter drops
of both transistors and the forward voltage of both diodes. The performance characteristics for the converter are shown below.
Note that the output resistance is reduced to 1.0 W.
Vout, OUTPUT VOLTAGE (V)
−2.0
−2.2
−2.4
−2.6
−2.8
Vin = 5.0 V
Rout = 1.0 W
TA = 25°C
−3.0
−3.2
0
0.1
0.2
0.3
0.4
0.5
Iout, OUTPUT CURRENT (mA)
Figure 38. Current Boosted Load Regulation,
Output Voltage vs. Output Current
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0.6
NCP1729
10 k
R2
Q2
R1
C1
−Vout
6
1
+
OSC
Vin
+
Q1
+
2
5
3
4
C3
C2
C1 = C2 = 470 mF
C3 = 220 mF
Q1 = PZT751
Q2 = PZT651
Figure 39. Line and Load Regulated Negative Output Voltage with High Current Capability
This converter is a combination of Figures 37 and 32. It provides a line and load regulated output of −2.47 V at up to 300 mA
with an input voltage of 5.0 V. The output will regulate at a level of −Vref (R2/R1 + 1). The performance characteristics are
shown below. Note that the dashed line is the open loop and the solid line is the closed loop configuration for the load regulation.
−0.1
Vout, OUTPUT VOLTAGE (V)
Vout, OUTPUT VOLTAGE (V)
−2.0
−2.2
−2.4
−2.6
−2.8
Vin = 5.0 V
Rout = 1.0 W
R1 = R2 = 10 kW
TA = 25°C
−3.0
−3.2
0
0.1
0.2
0.3
0.4
0.5
0.6
Iout = 100 mA
R1 = R2 = 10 kW
TA = 25°C
−0.6
−1.1
−1.6
−2.1
−2.6
2.5
3.0
3.5
4.0
4.5
5.0
Iout, OUTPUT CURRENT (A)
Vin, INPUT VOLTAGE (V)
Figure 40. Current Boosted Load Regulation,
Output Voltage vs. Output Current
Figure 41. Current Boosted Line Regulation,
Output Voltage vs. Output Current
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5.5
NCP1729
50
Q2
C1
Vout
6
1
+
50
OSC
+
Q1
Vin
+
2
5
3
4
C2
C3
Capacitors = 220 mF
Q1 = PZT751
Q2 = PZT651
Figure 42. Positive Output Voltage Doubler with High Current Capability
The NCP1729 can be configured to produce a positive output voltage doubler with current capability of 500 mA. This is
accomplished with the addition of two external switch transistors and two Schottky diodes. The output voltage is approximately
equal to 2.0 Vin minus the sum of the base emitter drops of both transistors and the forward voltage of both diodes. The
performance characteristics for the converter is shown below. Note that the output resistance is reduced to 1.8 W.
Vout, OUTPUT VOLTAGE (V)
8.8
Vin = 5.0 V
Rout = 1.8 W
TA = 25°C
8.4
8.0
7.6
7.2
0
0.1
0.2
0.3
0.4
0.5
Iout, OUTPUT CURRENT (mA)
Figure 43. Positive Doubler with Current Boosted
Load Regulation, Output Voltage vs. Output Current
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NCP1729
R1
50
10 k
Q2
6
1
50
OSC
Q1
Vin
+
2
5
3
4
R2
+
C3
Vout
+
C1
C2
Capacitors = 220 mF
Q1 = PZT751
Q2 = PZT651
Figure 44. Line and Load Regulated Positive Output Voltage Doubler with High Current Capability
This converter is a combination of Figures 42 and the shunt regulator to close the loop. In this case the anode of the regulator
is connected to ground. It provides a line and load regulated output of 7.6 V at up to 300 mA with a input voltage of 5.0 V. The
output will regulate at a level of Vref (R2/R1 + 1). The open loop configuration is the dashed line and the closed loop is the solid
line. The performance characteristics are shown below.
8.0
Vin = 5.0 V
Rout = 1.8 W Open Loop
Rout = 0.5 W Closed Loop
R1 = 10 k
R2 = 51.3 kW
TA = 25°C
8.6
8.4
8.2
Vout, OUTPUT VOLTAGE (V)
Vout, OUTPUT VOLTAGE (V)
8.8
8.0
7.8
7.6
7.4
7.2
0
0.1
0.2
0.3
0.4
0.5
0.6
7.0
6.0
5.0
4.0
Iout = 100 mA
R1 = 10 k
R2 = 51.3 kW
TA = 25°C
3.0
2.0
1.0
1.0
2.0
3.0
4.0
5.0
Iout, OUTPUT CURRENT (A)
Vin, INPUT VOLTAGE (V)
Figure 45. Current Boosted Close Loop Load
Regulation, Output Voltage vs. Output Current
Figure 46. Current Boosted Close Loop Line
Regulation, Output Voltage vs. Input Voltage
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6.0
NCP1729
Vin = −5.0 V
+
+
OSC
C
C
+
6
1
C
2
5
3
4
Vout = −2.5 V
C
+
Capacitors = 3.3 mF
Figure 47. Negative Input Voltage Splitter
A single device can be used to split a negative input voltage. The output voltage is approximately equal to −Vin / 2.0. The
performance characteristics are shown below. Note that the converter has an output resistance of 10 W.
Vout, OUTPUT VOLTAGE (V)
−1.5
−1.7
−1.9
−2.1
−2.3
Rout = 10 W
TA = 25°C
−2.5
0
10
20
30
40
50
60
70
Iout, OUTPUT CURRENT (mA)
Figure 48. Negative Voltage Splitter Load
Regulation, Output Voltage vs. Output Current
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80
NCP1729
−Vout
R1
R2
6
1
+
OSC
Vin
2
+
5
10 k
3
4
+
+
+
+Vout
Capacitors = 10 mF
Figure 49. Combination of a Closed Loop Negative Inverter with a Positive Output Voltage Doubler
All of the previously shown converter circuits have only single outputs. Applications requiring multiple outputs can be
constructed by incorporating combinations of the former circuits. The converter shown above combines Figures 26 and 32 to
form a regulated negative output inverter with a non−regulated positive output doubler. The magnitude of −Vout is controlled
by the resistor values and follows the relationship −Vref (R2/R1 + 1). Since the positive output is not within the feedback loop,
its output voltage will increase as the negative output load increases. This cross regulation characteristic is shown in the upper
portion of Figure 50. The dashed line is the open loop and the solid line is the closed loop configuration for the load regulation.
The load regulation for the positive doubler with a constant load on the −Vout is shown in Figure 51.
10.0
Vout, OUTPUT VOLTAGE (V)
Vout, OUTPUT VOLTAGE (V)
9.0
Positive Doubler
Iout = 15 mA
8.0
−3.0
Negative Inverter
−4.0
Rout = 45 W − Open Loop
Rout = 2 W − Closed Loop
R1 = 10 k, R2 = 20 k
TA = 25°C
−5.0
9.0
8.0
Negative Inverter Iout = 15 mA
R1 = 10 kW
R2 = 20 kW
TA = 25°C
7.0
0
10
20
30
Iout, NEGATIVE INVERTER OUTPUT CURRENT (mA)
0
10
20
30
40
50
Iout, POSITIVE DOUBLER OUTPUT CURRENT (mA)
Figure 50. Load Regulation, Output Voltage
vs. Output Current
+
Figure 51. Load Regulation, Output Voltage
vs. Output Current
IC1
C1
C2
Vin
−Vout
SHDN
GND
C3
+
+
GND
0.5″
Inverter Size = 0.5 in x 0.2 in
Area = 0.10 in2, 64.5 mm2
Figure 52. Inverter Circuit Board Layout, Top View Copper Side
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NCP1729
PACKAGE DIMENSIONS
TSOP−6
CASE 318G−02
ISSUE M
NOTES:
1. DIMENSIONING AND TOLERANCING PER
ANSI Y14.5M, 1982.
2. CONTROLLING DIMENSION: MILLIMETER.
3. MAXIMUM LEAD THICKNESS INCLUDES
LEAD FINISH THICKNESS. MINIMUM LEAD
THICKNESS IS THE MINIMUM THICKNESS
OF BASE MATERIAL.
4. DIMENSIONS A AND B DO NOT INCLUDE
MOLD FLASH, PROTRUSIONS, OR GATE
BURRS.
A
L
6
S
1
5
4
2
3
B
MILLIMETERS
DIM MIN
MAX
A
2.90
3.10
B
1.30
1.70
C
0.90
1.10
D
0.25
0.50
G
0.85
1.05
H 0.013 0.100
J
0.10
0.26
K
0.20
0.60
L
1.25
1.55
M
0_
10 _
S
2.50
3.00
D
G
M
J
C
0.05 (0.002)
K
H
INCHES
MIN
MAX
0.1142 0.1220
0.0512 0.0669
0.0354 0.0433
0.0098 0.0197
0.0335 0.0413
0.0005 0.0040
0.0040 0.0102
0.0079 0.0236
0.0493 0.0610
0_
10 _
0.0985 0.1181
SOLDERING FOOTPRINT*
2.4
0.094
1.9
0.075
0.95
0.037
0.95
0.037
0.7
0.028
1.0
0.039
SCALE 10:1
mm Ǔ
ǒinches
*For additional information on our Pb−Free strategy and soldering
details, please download the ON Semiconductor Soldering and
Mounting Techniques Reference Manual, SOLDERRM/D.
ON Semiconductor and
are registered trademarks of Semiconductor Components Industries, LLC (SCILLC). SCILLC reserves the right to make changes without further notice
to any products herein. SCILLC makes no warranty, representation or guarantee regarding the suitability of its products for any particular purpose, nor does SCILLC assume any liability
arising out of the application or use of any product or circuit, and specifically disclaims any and all liability, including without limitation special, consequential or incidental damages.
“Typical” parameters which may be provided in SCILLC data sheets and/or specifications can and do vary in different applications and actual performance may vary over time. All
operating parameters, including “Typicals” must be validated for each customer application by customer’s technical experts. SCILLC does not convey any license under its patent rights
nor the rights of others. SCILLC products are not designed, intended, or authorized for use as components in systems intended for surgical implant into the body, or other applications
intended to support or sustain life, or for any other application in which the failure of the SCILLC product could create a situation where personal injury or death may occur. Should
Buyer purchase or use SCILLC products for any such unintended or unauthorized application, Buyer shall indemnify and hold SCILLC and its officers, employees, subsidiaries, affiliates,
and distributors harmless against all claims, costs, damages, and expenses, and reasonable attorney fees arising out of, directly or indirectly, any claim of personal injury or death
associated with such unintended or unauthorized use, even if such claim alleges that SCILLC was negligent regarding the design or manufacture of the part. SCILLC is an Equal
Opportunity/Affirmative Action Employer. This literature is subject to all applicable copyright laws and is not for resale in any manner.
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NCP1729/D