EL8302 ® Data Sheet May 6, 2005 500MHz Rail-to-Rail Amplifier Features The EL8302 represents a triple rail-to-rail amplifier with a 3dB bandwidth of 500MHz and slew rate of 600V/µs. Running off a very low supply current of 5.6mA per channel, the EL8302 also features inputs that go to 0.15V below the VS- rail. • 500MHz -3dB bandwidth The EL8302 includes a fast-acting disable/power-down circuit. With a 25ns disable and a 200ns enable, the EL8302 is ideal for multiplexing applications. • Rail-to-rail output The EL8302 is designed for a number of general purpose video, communication, instrumentation, and industrial applications. The EL8302 is available in an 16-pin SO and 16-pin QSOP packages and is specified for operation over the -40°C to +85°C temperature range. Pinout FN7348.2 • 600V/µs slew rate • Low supply current = 5.6mA per amplifier • Supplies from 3V to 5.5V • Input to 0.15V below VS• Fast 25ns disable • Low cost • Pb-Free available (RoHS compliant) Applications • Video amplifiers EL8302 (16-PIN SO, QSOP) TOP VIEW INA+ 1 CEA 2 16 INA+ VS- 3 CEB 4 14 VS+ + - INB+ 5 NC 6 CEC 7 15 OUTA + - INC+ 8 • Portable/hand-held products • Communications devices Ordering Information PART NUMBER PACKAGE TAPE & REEL PKG. DWG. # EL8302IS 16-Pin SO - MDP0027 13 OUTB EL8302IS-T7 16-Pin SO 7” MDP0027 12 INB- EL8302IS-T13 16-Pin SO 13” MDP0027 11 NC EL8302ISZ (See Note) 16-Pin SO (Pb-free) - MDP0027 EL8302ISZ-T7 (See Note) 16-Pin SO (Pb-free) 7” MDP0027 EL8302ISZ-T13 (See Note) 16-Pin SO (Pb-free) 13” MDP0027 EL8302IU 16-Pin QSOP - MDP0040 EL8302IU-T7 16-Pin QSOP 7” MDP0040 EL8302IU-T13 16-Pin QSOP 13” MDP0040 EL8302IUZ (See Note) 16-Pin QSOP (Pb-free) - MDP0040 EL8302IUZ-T7 (See Note) 16-Pin QSOP (Pb-free) 7” MDP0040 EL8302IUZ-T13 (See Note) 16-Pin QSOP (Pb-free) 13” MDP0040 10 OUTC 9 INC- NOTE: Intersil Pb-free products employ special Pb-free material sets; molding compounds/die attach materials and 100% matte tin plate termination finish, which are RoHS compliant and compatible with both SnPb and Pb-free soldering operations. Intersil Pb-free products are MSL classified at Pb-free peak reflow temperatures that meet or exceed the Pb-free requirements of IPC/JEDEC J STD-020. 1 CAUTION: These devices are sensitive to electrostatic discharge; follow proper IC Handling Procedures. 1-888-INTERSIL or 1-888-352-6832 | Intersil (and design) is a registered trademark of Intersil Americas Inc. Copyright Intersil Americas Inc. 2003, 2005. All Rights Reserved All other trademarks mentioned are the property of their respective owners. EL8302 Absolute Maximum Ratings (TA = 25°C) Power Dissipation . . . . . . . . . . . . . . . . . . . . . . . . . . . . . See Curves Storage Temperature . . . . . . . . . . . . . . . . . . . . . . . .-65°C to +125°C Ambient Operating Temperature . . . . . . . . . . . . . . . .-40°C to +85°C Operating Junction Temperature . . . . . . . . . . . . . . . . . . . . . . +125°C Supply Voltage from VS+ to VS- . . . . . . . . . . . . . . . . . . . . . . . . . 5.5V Input Voltage . . . . . . . . . . . . . . . . . . . . . . . . VS+ + 0.3V to VS- -0.3V Differential Input Voltage . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .2V Continuous Output Current . . . . . . . . . . . . . . . . . . . . . . . . . . . 40mA CAUTION: Stresses above those listed in “Absolute Maximum Ratings” may cause permanent damage to the device. This is a stress only rating and operation of the device at these or any other conditions above those indicated in the operational sections of this specification is not implied. IMPORTANT NOTE: All parameters having Min/Max specifications are guaranteed. Typ values are for information purposes only. Unless otherwise noted, all tests are at the specified temperature and are pulsed tests, therefore: TJ = TC = TA Electrical Specifications PARAMETER VS+ = 5V, VS- = GND, TA = 25°C, VCM = 2.5V, RL to 2.5V, AV = 1, Unless Otherwise Specified DESCRIPTION CONDITIONS MIN TYP MAX UNIT -7 -0.8 +7 mV INPUT CHARACTERISTICS VOS Offset Voltage TCVOS Offset Voltage Temperature Coefficient Measured from TMIN to TMAX IB Input Bias Current VIN = 0V IOS Input Offset Current VIN = 0V TCIOS Input Bias Current Temperature Coefficient Measured from TMIN to TMAX CMRR Common Mode Rejection Ratio VCM = -0.15V to +3.5V CMIR Common Mode Input Range RIN Input Resistance CIN Input Capacitance AVOL Open Loop Gain -10 3 µV/°C -6 µA 0.1 70 µA 2 nA/°C 95 dB VS- -0.15 Common Mode 0.6 VS+ - 1.5 V 7 MΩ 0.5 pF 100 dB VOUT = +1.5V to +3.5V, RL = 150Ω to GND 80 dB 30 mΩ VOUT = +1.5V to +3.5V, RL = 1kΩ to GND 75 OUTPUT CHARACTERISTICS ROUT Output Resistance AV = +1 VOP Positive Output Voltage Swing RL = 1kΩ 4.85 4.9 V RL = 150Ω 4.65 4.7 V VON Negative Output Voltage Swing RL = 150Ω 150 200 mV RL = 1kΩ 50 70 mV IOUT Linear Output Current ISC (source) Short Circuit Current RL = 10Ω ISC (sink) Short Circuit Current 65 mA 50 80 mA RL = 10Ω 90 150 mA VS+ = 4.5V to 5.5V 70 95 dB POWER SUPPLY PSRR Power Supply Rejection Ratio IS-ON Supply Current - Enabled per Amplifier 5.6 6.2 mA IS-OFF Supply Current - Disabled per Amplifier 40 90 µA tEN Enable Time 200 ns tDS Disable Time 25 ns VIH-ENB ENABLE Pin Voltage for Power-up 0.8 V VIL-ENB ENABLE Pin Voltage for Shut-down 2 V ENABLE 2 EL8302 Electrical Specifications PARAMETER VS+ = 5V, VS- = GND, TA = 25°C, VCM = 2.5V, RL to 2.5V, AV = 1, Unless Otherwise Specified DESCRIPTION CONDITIONS MIN TYP MAX UNIT IIH-ENB ENABLE Pin Input Current High 8.6 µA IIL-ENB ENABLE Pin Input for Current Low 0.01 µA AV = +1, RF = 0Ω, CL = 1.5pF 500 MHz AV = -1, RF = 1kΩ, CL = 1.5pF 140 MHz AV = +2, RF = 1kΩ, CL = 1.5pF 165 MHz AV = +10, RF = 1kΩ, CL = 1.5pF 18 MHz AC PERFORMANCE BW -3dB Bandwidth BW ±0.1dB Bandwidth AV = +1, RF = 0Ω, CL = 1.5pF 36 MHz Peak Peaking AV = +1, RL = 1kΩ, CL = 1.5pF 1 dB GBWP Gain Bandwidth Product 200 MHz PM Phase Margin RL = 1kΩ, CL = 1.5pF 55 ° SR Slew Rate AV = 2, RL = 100Ω, VOUT = 0.5V to 4.5V 600 V/µs tR Rise Time 2.5VSTEP, 20% - 80% 4 ns tF Fall Time 2.5VSTEP, 20% - 80% 2 ns OS Overshoot 200mV step 10 % tPD Propagation Delay 200mV step 1 ns tS 0.1% Settling Time 200mV step 15 ns dG Differential Gain AV = +2, RF = 1kΩ, RL = 150Ω 0.01 % dP Differential Phase AV = +2, RF = 1kΩ, RL = 150Ω 0.01 ° eN Input Noise Voltage f = 10kHz 12 nV/√Hz iN+ Positive Input Noise Current f = 10kHz 1.7 pA/√Hz iN- Negative Input Noise Current f = 10kHz 1.3 pA/√Hz eS Channel Separation f = 100kHz 95 dB 500 Pin Descriptions PIN NAME 1, 5, 8 INA+, INB+, INC+ Non-inverting input for each channel 2, 4, 7 CEA, CEB, CEC Enable and disable input for each channel 3 VS- Negative power supply 6, 11 NC Not connected 9, 12, 16 INC-, INB-, INA- 10, 13, 15 OUTC, OUTB, OUTA 14 VS+ 3 FUNCTION Inverting input for each channel Amplifier output for each channel Positive power supply EL8302 Typical Performance Curves 3 2 GAIN (dB) 5 VS=5V AV=1 RL=1kΩ CL=1.5pF NORMALIZED GAIN (dB) 5 4 VOP-P=200mV 1 0 -1 VOP-P=1V -2 -3 VOP-P=2V -4 -5 1M 10M RF=RG=1kΩ -1 -3 RF=RG=500Ω VS=5V AV=2 RL=1kΩ CL=1.5pF 1M FREQUENCY (Hz) 5 NORMALIZED GAIN (dB) NORMALIZED GAIN (dB) 2 AV=2 1 AV=1 0 -1 AV=5 -2 -3 AV=10 -4 -5 1M 10M 100M 2 VS=5V CL=1.5pF RL=1kΩ RF=1kΩ AV=-1 AV=-5 -2 -4 AV=-10 -6 100K 1G 1M GAIN (dB) 9 RL=100Ω RL=1kΩ GAIN (dB) 3 2 1 0 1G -1 VS=5V AV=2 CL=1.5pF RF=RG=1kΩ RL=500Ω 7 5 RL=1kΩ, 150Ω -2 3 -3 -4 -5 1M 100M FIGURE 4. SMALL SIGNAL FREQUENCY RESPONSE FOR VARIOUS INVERTING GAINS 11 VS=5V AV=1 CL=1.5pF VOP-P=200mV 10M FREQUENCY (Hz) FIGURE 3. SMALL SIGNAL FREQUENCY RESPONSE FOR VARIOUS NON-INVERTING GAINS 5 1G 0 FREQUENCY (Hz) 4 100M FIGURE 2. SMALL SIGNAL FREQUENCY RESPONSE vs RF AND RG 4 VS=5V CL=1.5pF RL=1kΩ 3 10M FREQUENCY (Hz) FIGURE 1. FREQUENCY RESPONSE FOR VARIOUS OUTPUT VOLTAGE LEVELS 4 RF=RG=2kΩ 1 -5 100K 1G 100M 3 RL=500Ω 10M 100M 1G FREQUENCY (Hz) FIGURE 5. SMALL SIGNAL FREQUENCY RESPONSE FOR VARIOUS RLOAD 4 1 100K 1M 10M 100M 1G FREQUENCY (Hz) FIGURE 6. SMALL SIGNAL FREQUENCY RESPONSE vs VARIOUS RLOAD EL8302 Typical Performance Curves (Continued) 16 VS=5V AV=1 RL=1kΩ VOP-P=200mV 4 3 GAIN (dB) 2 12 CL=3.7pF 10 1 0 -1 CL=1.5pF -2 4 -3 -2 CL=10pF CL=1.5pF -4 1M 1G FIGURE 7. SMALL SIGNAL FREQUENCY RESPONSE vs CL 70 R =150Ω L 315 -30 30 225 RL=150Ω -10 135 RL=1kΩ -90 1K 10K GAIN (dB) -10 RL=1kΩ PHASE (°) GAIN (dB) FIGURE 8. SMALL SIGNAL FREQUENCY RESPONSE FOR VARIOUS CL 405 -50 1M 10M 100M VS=5V AV=1 RL=1kΩ -50 -70 -90 45 100K 1G 100M 10M FREQUENCY (Hz) FREQUENCY (Hz) 110 CL=13.5pF 2 100M CL=28.5pF 6 -4 10M CL=20pF 8 0 -5 1M VS=5V AV=2 RL=1kΩ RF=RG=1kΩ 14 CL=4.8pF GAIN (dB) 5 -110 1K -45 1G 10K 1M 100K 10M 100M 1G FREQUENCY (Hz) FREQUENCY (Hz) FIGURE 9. OPEN LOOP GAIN AND PHASE vs FREQUENCY FIGURE 10. DISABLED OUTPUT ISOLATION FREQUENCY RESPONSE -10 550 -30 450 BANDWIDTH (MHz) PSRR (dB) 500 PSRR- -50 -70 PSRR+ -90 RL=1kΩ CL=1.5pF 400 AV=1 350 300 250 200 AV=2 150 -110 1K 100 10K 100K 1M FREQUENCY (Hz) FIGURE 11. POWER SUPPLY REJECTION RATIO vs FREQUENCY 5 10M 100M 3 3.5 4.5 4 5 5.5 VS (V) FIGURE 12. SMALL SIGNAL BANDWIDTH vs SUPPLY VOLTAGE EL8302 Typical Performance Curves (Continued) 2.5 100 RL=1kΩ CL=1.5pF PEAKING (dB) IMPEDANCE (Ω) 2 10 1 0.1 AV=1 1.5 1 0.5 0 0.01 10K 100K 1M 10M 100M AV=2 3 4 3.5 4.5 FREQUENCY (Hz) 10 -35 8 -55 6 IS (mA) CMRR (dB) -15 -75 4 2 -95 -115 100K 1M 10M 0 100M 0.5 0 1 1.5 2 2.5 3 3.5 4.5 4 5 5.5 VS (V) FREQUENCY (Hz) FIGURE 15. COMMON-MODE REJECTION RATIO vs FREQUENCY FIGURE 16. SUPPLY CURRENT vs SUPPLY VOLTAGE (PER AMPLIFIER) -70 V VS =5V S=5V R =1kΩ RLL=1kΩ C =1.5pF CLL=1.5p F AV=2 -70 -80 HD2@5MHz H @1M HD2 -90 HD 1 -75 HD2@10MHz DISTORTION (dBc) -60 DISTORTION (dBc) 5.5 FIGURE 14. SMALL SIGNAL PEAKING vs SUPPLY VOLTAGE FIGURE 13. OUPUT IMPEDANCE vs FREQUENCY -100 5 VS (V) z Hz HD3@10M z 3@5M H 2 3 4 5 VOP-P (V) FIGURE 17. HARMONIC DISTORTION vs OUTPUT VOLTAGE 6 -80 H D 2@ AV =2 AV =1 -85 VS=5V f=5MHz -90 -95 HD3@1MHz HD2@ HD3 @ VO=1VP-P for AV=1 VO=2VP-P for AV=2 -100 100 HD3 @ AV =2 AV =1 1K 2K RLOAD (Ω) FIGURE 18. HARMONIC DISTORTION vs LOAD RESISTANCE EL8302 Typical Performance Curves (Continued) 1K -50 DISTORTION (dBc) -60 -70 HD2 @ -80 -90 -100 AV=2 VOLTAGE NOISE (nV/√Hz) CURRENT NOISE (pA/√Hz), VS=5V RL=1kΩ CL=1.5pF VO=1VP-P for AV=1 VO=2VP-P for AV=2 HD2@AV=1 HD3@AV=2 HD3 =1 @A V 10 1 100 eN 10 IN+ 1 10 40 100 IN- 1K 10K 100K 1M 10M FREQUENCY (Hz) FREQUENCY (MHz) FIGURE 19. HARMONIC DISTORTION vs FREQUENCY FIGURE 20. VOLTAGE AND CURRENT NOISE vs FREQUENCY VS=5V, AV=1, RL=1kΩ TO 2.5V, CL=1.5pF CHANNEL SEPARATION (dB) 0 -10 -20 -30 3.5 -40 -50 -60 -70 2.5 CH2-->CH1 CH2-->CH1 CH2-->CH3 -80 -90 -100 1.00E+05 1.00E+06 1.00E+07 CH3-->CH2 CH1-->CH2 CH1<=>CH3 1.00E+08 1.5 1.00E+09 2ns/DIV FREQUENCY (Hz) FIGURE 21. CHANNEL SEPARATION vs FREQUENCY FIGURE 22. LARGE SIGNAL TRANSIENT RESPONSE - RISING VS=5V, AV=1, RL=1kΩ to 2.5V, CL=1.5pF VS=5V, AV=1, RL=1kΩ TO 2.5V, CL= 1.5pF 2.6 VIN 2.5 3.5 2.4 2.5 2.6 VOUT 2.5 1.5 2.4 2ns/DIV FIGURE 23. LARGE SIGNAL TRANSIENT RESPONSE - FALLING 7 10ns/DIV FIGURE 24. SMALL SIGNAL TRANSIENT REPONSE EL8302 Typical Performance Curves (Continued) VS=5V, AV=5, RL=1kΩ TO 2.5V VS=5V, AV=5, RL=1kΩ TO 2.5V 5 5 2.5 2.5 0 0 2µs/DIV 2µs/DIV FIGURE 26. OUTPUT SWING FIGURE 25. OUTPUT SWING CH1 ENABLE INPUT ENABLE INPUT CH1 CH2 CH2 VOUT VOUT CH1, CH2, 1V/DIV, M=100ns CH1, CH2, 0.5V/DIV, M=20ns FIGURE 28. DISABLED RESPONSE FIGURE 27. ENABLED RESPONSES 1 0.6 633mW 0.4 θJ 0.2 0 SO 1 θ JA 6 ( 0 =1 . 10 150 °C ”) /W 909mW 0.8 1.4 POWER DISSIPATION (W) POWER DISSIPATION (W) 1.2 JEDEC JESD51-3 LOW EFFECTIVE THERMAL CONDUCTIVITY TEST BOARD QS A= OP 15 8° C 16 /W 1.2 25 50 75 85 100 125 150 AMBIENT TEMPERATURE (°C) FIGURE 29. PACKAGE POWER DISSIPATION vs AMBIENT TEMPERATURE 8 1.250W θ SO JA 1 0.8 893mW 0.6 θJ A= 0.4 QS 11 OP 2° 16 =8 (0 .1 0° 50” ) C/ W 16 C/ W 0.2 0 0 JEDEC JESD51-7 HIGH EFFECTIVE THERMAL CONDUCTIVITY TEST BOARD 0 25 50 75 85 100 125 150 AMBIENT TEMPERATURE (°C) FIGURE 30. PACKAGE POWER DISSIPATION vs AMBIENT TEMPERATURE EL8302 Simplified Schematic Diagram VS+ I1 I2 Q5 IN+ Q1 R8 VBIAS1 Q6 R3 R1 R7 R6 Q7 R2 Q2 DIFFERENTIAL TO SINGLE ENDED DRIVE GENERATOR IN- VBIAS2 Q3 OUT Q4 Q8 R4 R5 R9 VS- Description of Operation and Application Information Product Description The EL8302 is wide bandwidth, single supply, low power and rail-to-rail output voltage feedback operational amplifiers. The amplifiers are internally compensated for closed loop gain of +1 of greater. Connected in voltage follower mode and driving a 1kΩ load, the EL8302 has a -3dB bandwidth of 500MHz. Driving a 150Ω load, the bandwidth is about 350MHz while maintaining a 600V/us slew rate. The EL8302 is available with a power down pin for each channel to reduce power to 30µA typically while the amplifier is disabled. Input, Output and Supply Voltage Range The EL8302 has been designed to operate with a single supply voltage from 3V to 5.0V. Split supplies can also be used as long as their total voltage is within 3V to 5.0V. The amplifiers have an input common mode voltage range from 0.15V below the negative supply (VS- pin) to within 1.5V of the positive supply (VS+ pin). If the input signal is outside the above specified range, it will cause the output signal to be distorted. The output of the EL8302 can swing rail to rail. As the load resistance becomes lower, the ability to drive close to each rail is reduced. For the load resistor 1kΩ, the output swing is about 4.9V at a 5V supply. For the load resistor 150Ω, the output swing is about 4.6V. Choice of Feedback Resistor and Gain Bandwidth Product For applications that require a gain of +1, no feedback resistor is required. Just short the output pin to the inverting input pin. For gains greater than +1, the feedback resistor forms a pole with the parasitic capacitance at the inverting 9 input. As this pole becomes smaller, the amplifier’s phase margin is reduced. This causes ringing in the time domain and peaking in the frequency domain. Therefore, RF has some maximum value that should not be exceeded for optimum performance. If a large value of RF must be used, a small capacitor in the few pF range in parallel with RF can help to reduce the ringing and peaking at the expense of reducing the bandwidth. As far as the output stage of the amplifier is concerned, the output stage is also a gain stage with the load. RF and RG appear in parallel with RL for gains other than +1. As this combination gets smaller, the bandwidth falls off. Consequently, RF also has a minimum value that should not be exceeded for optimum performance. For gain of +1, RF=0 is optimum. For the gains other than +1, optimum response is obtained with RF between 300Ω to 1kΩ. The EL8302 has a gain bandwidth product of 200MHz. For gains ≥5, its bandwidth can be predicted by the following equation: Gain × BW = 200MHz Video Performance For good video performance, an amplifier is required to maintain the same output impedance and the same frequency response as DC levels are changed at the output. This is especially difficult when driving a standard video load of 150Ω, because the change in output current with DC level. Special circuitry has been incorporated in the EL8302 to reduce the variation of the output impedance with the current output. This results in dG and dP specifications of 0.01% and 0.01°, while driving 150Ω at a gain of 2. Driving high impedance loads would give a similar or better dG and dP performance. EL8302 Driving Capacitive Loads and Cables The EL8302 can drive 5pF loads in parallel with 1kΩ with less than 5dB of peaking at gain of +1. If less peaking is desired in applications, a small series resistor (usually between 5Ω to 50Ω) can be placed in series with the output to eliminate most peaking. However, this will reduce the gain slightly. If the gain setting is greater than 1, the gain resistor RG can then be chosen to make up for any gain loss which may be created by the additional series resistor at the output. When used as a cable driver, double termination is always recommended for reflection-free performance. For those applications, a back-termination series resistor at the amplifier’s output will isolate the amplifier from the cable and allow extensive capacitive drive. However, other applications may have high capacitive loads without a back-termination resistor. Again, a small series resistor at the output can help to reduce peaking. The maximum power dissipation allowed in a package is determined according to: T JMAX – T AMAX PD MAX = -------------------------------------------θ JA Where: TJMAX = Maximum junction temperature TAMAX = Maximum ambient temperature θJA = Thermal resistance of the package The maximum power dissipation actually produced by an IC is the total quiescent supply current times the total power supply voltage, plus the power in the IC due to the load, or: For sourcing: 3 PD MAX = V S × I SMAX + V OUTi ∑ ( VS – VOUTi ) × ---------------R Li i=1 Disable/Power-Down The EL8302 can be disabled and placed its output in a high impedance state. The turn off time is about 25ns and the turn on time is about 200ns. When disabled, the amplifier’s supply current is reduced to 30µA typically, thereby effectively eliminating the power consumption. The amplifier’s power down can be controlled by standard TTL or CMOS signal levels at the ENABLE pin. The applied logic signal is relative to VS- pin. Letting the ENABLE pin float or applying a signal that is less than 0.8V above VS- will enable the amplifier. The amplifier will be disabled when the signal at ENABLE pin is 2V above VS-. Output Drive Capability The EL8302 does not have internal short circuit protection circuitry. They have a typical short circuit current of 80mA sourcing and 150mA sinking for the output is connected to half way between the rails with a 10Ω resistor. If the output is shorted indefinitely, the power dissipation could easily increase such that the part will be destroyed. Maximum reliability is maintained if the output current never exceeds ±40mA. This limit is set by the design of the internal metal interconnections. Power Dissipation With the high output drive capability of the EL8302, It is possible to exceed the 125°C absolute maximum junction temperature under certain load current conditions. Therefore, it is important to calculate the maximum junction temperature for the application to determine if the load conditions or package types need to be modified for the amplifier to remain in the safe operating area. For sinking: 3 PD MAX = V S × I SMAX + ∑ ( VOUTi – VS - ) × ILOADi i=1 Where: VS = Total supply voltage ISMAX = Maximum quiescent supply current VOUTi = Maximum output voltage of the application for each channel RLOADi = Load resistance tied to ground for each channel ILOADi = Load current for eachh channel By setting the two PDMAX equations equal to each other, we can solve the output current and RLOAD to avoid the device overheat. Power Supply Bypassing and Printed Circuit Board Layout As with any high frequency device, a good printed circuit board layout is necessary for optimum performance. Lead lengths should be as short as possible. The power supply pin must be well bypassed to reduce the risk of oscillation. For normal single supply operation, where the VS- pin is connected to the ground plane, a single 4.7µF tantalum capacitor in parallel with a 0.1µF ceramic capacitor from VS+ to GND will suffice. This same capacitor combination should be placed at each supply pin to ground if split supplies are to be used. In this case, the VS- pin becomes the negative supply rail. For good AC performance, parasitic capacitance should be kept to a minimum. Use of wire wound resistors should be 10 EL8302 avoided because of their additional series inductance. Use of sockets should also be avoided if possible. Sockets add parasitic inductance and capacitance that can result in compromised performance. Minimizing parasitic capacitance at the amplifier’s inverting input pin is very important. The feedback resistor should be placed very close to the inverting input pin. Strip line design techniques are recommended for the signal traces. VIN1 is passed through to the output when the ENABLE signal is low and turns off in about 25ns when the ENABLE signal is high. About 200ns later, Amp B turns on and VIN2 is passed through to the output. The break-before-make operation ensures that more than one amplifier isn’t trying to drive the bus at the same time. +2.5V B 2MHz 1VP-P Typical Applications VIDEO SYNC PULSE REMOVER Many CMOS analog to digital converters have a parasitic latch up problem when subjected to negative input voltage levels. Since the sync tip contains no useful video information and it is a negative going pulse, we can chop it off. Figure 31 shows a gain of 2 connections for EL8302. Figure 32 shows the complete input video signal applied at the input, as well as the output signal with the negative going sync pulse removed. + 75Ω -2.5V 1K 1K 75Ω VOUT +2.5V A 2MHz 2VP-P 75Ω + - 75Ω -2.5V 1K 1K 5V VIN - VOUT VS- 75Ω ENABLE 75Ω VS+ + 75Ω 1K FIGURE 33. TWO TO ONE MULTIPLEXER 1K 0V -0.5V FIGURE 31. SYNC PULSE REMOVER ENABLE -1.5V -2.5V 1V 1V 0V 0.5V VIN 0V B A -1V 1V 0.5V VOUT 0V M = 50ns/DIV FIGURE 34. SINGLE SUPPLY VIDEO LINE DRIVER M = 10µs/DIV FIGURE 32. VIDEO SIGNAL MULTIPLEXER Besides the normal power down usage, the ENABLE pin of the EL8302 can be used for multiplexing applications. Figure 33 shows two channels with the outputs tied together, driving a back terminated 75Ω video load. A 2VP-P 2MHz sine wave is applied to Amp A and a 1VP-P 2MHz sine wave is applied to Amp B. Figure 34 shows the ENABLE signal and the resulting output waveform at VOUT. Observe the breakbefore-make operation of the multiplexing. Amp A is on and 11 The EL8302 is wideband rail-to-rail output op amplifiers with large output current, excellent dG, dP, and low distortion that allow them to drive video signals in low supply applications. Figure 35 is the single supply non-inverting video line driver configuration and Figure 36 is the inverting video ling driver configuration. The signal is AC coupled by C1. R1 and R2 are used to level shift the input and output to provide the largest output swing. RF and RG set the AC gain. C2 isolates the virtual ground potential. RT and R3 are the termination resistors for the line. C1, C2 and C3 are selected big enough to minimize the droop of the luminance signal. EL8302 5V RF 1kΩ VIN C1 47µF R1 10K + RT 75Ω R2 10K R3 C3 470µF 75Ω VOUT C1 RG 47µF 500Ω - 75Ω RG 1kΩ VIN RT 75Ω 5V 5V - R3 C3 470µF 75Ω VOUT + R1 10K 75Ω RF 1kΩ R2 10K C2 220µF NORMALIZED GAIN (dB) FIGURE 35. 5V SINGLE SUPPLY NON INVERTING VIDEO LINE DRIVER C2 220µF FIGURE 36. SINGLE SUPPLY INVERTING VIDEO LINE DRIVER 4 3 2 1 AV = 2 0 -1 -2 AV = -2 -3 -4 -5 -6 100K 1M 10M 100M 500M FREQUENCY (Hz) FIGURE 37. VIDEO LINE DRIVER FREQUENCY RESPONSE 12 EL8302 SO Package Outline Drawing 13 EL8302 QSOP Package Outline Drawing NOTE: The package drawing shown here may not be the latest version. To check the latest revision, please refer to the Intersil website at http://www.intersil.com/design/packages/index.asp All Intersil U.S. products are manufactured, assembled and tested utilizing ISO9000 quality systems. Intersil Corporation’s quality certifications can be viewed at www.intersil.com/design/quality Intersil products are sold by description only. Intersil Corporation reserves the right to make changes in circuit design, software and/or specifications at any time without notice. Accordingly, the reader is cautioned to verify that data sheets are current before placing orders. Information furnished by Intersil is believed to be accurate and reliable. However, no responsibility is assumed by Intersil or its subsidiaries for its use; nor for any infringements of patents or other rights of third parties which may result from its use. No license is granted by implication or otherwise under any patent or patent rights of Intersil or its subsidiaries. For information regarding Intersil Corporation and its products, see www.intersil.com 14