LTM4603HV 6A, 28VIN DC/DC µModule with PLL, Output Tracking and Margining DESCRIPTIO U FEATURES ■ ■ ■ ■ ■ ■ ■ ■ ■ ■ ■ ■ ■ ■ ■ ■ ■ Complete Switch Mode Power Supply Wide Input Voltage Range: 4.5V to 28V 6A DC Typical, 8A Peak Output Current 0.6V to 5V Output Voltage Output Voltage Tracking and Margining Remote Sensing for Precision Regulation Typical Operating Frequency: 1MHz PLL Frequency Synchronization 1.5% Regulation Current Foldback Protection (Disabled at Start-Up) Pin Compatible with the LTM4601/LTM4601HV/ LTM4603 Ultrafast Transient Response Current Mode Control Up to 93% Efficiency at 5VIN, 3.3VOUT Programmable Soft-Start Output Overvoltage Protection Pb-Free (e4) RoHS Compliant Package with Gold Finish Pads Small Footprint, Low Profile (15mm × 15mm × 2.8mm) Surface Mount LGA Package U APPLICATIO S ■ ■ ■ ■ The LTM®4603HV is a complete 6A step-down switch mode DC/DC power supply with onboard switching controller, MOSFETs, inductor and all support components. The μModuleTM is housed in a small surface mount 15mm × 15mm × 2.8mm LGA package. Operating over an input voltage range of 4.5 to 28V, the LTM4603HV supports an output voltage range of 0.6V to 5V as well as output voltage tracking and margining. The high efficiency design delivers 6A continuous current (8A peak). Only bulk input and output capacitors are needed to complete the design. The low profile (2.8mm) and light weight (1.7g) package easily mounts on the unused space on the back side of PC boards for high density point of load regulation. The μModule can be synchronized with an external clock for reducing undesirable frequency harmonics and allows PolyPhase® operation for high load currents. A high switching frequency and adaptive on-time current mode architecture deliver a very fast transient response to line and load changes without sacrificing stability. An onboard remote sense amplifier can be used to accurately regulate an output voltage independent of load current. , LT, LTC, LTM and PolyPhase are registered trademarks of Linear Technology Corporation. μModule is a trademark of Linear Technology Corporation. All other trademarks are the property of their respective owners. Telecom and Networking Equipment Servers Industrial Equipment Point of Load Regulation U TYPICAL APPLICATIO Efficiency vs Load Current with 24VIN 2.5V/6A with 4.5V to 28V Input μModule Regulator 100 CLOCK SYNC TRACK/SS CONTROL VIN 4.5V TO 28V VIN PGOOD ON/OFF CIN 392k RUN COMP INTVCC DRVCC MPGM SGND PLLIN TRACK/SS VOUT LTM4603HV PGND VFB MARG0 MARG1 VOUT_LCL DIFFVOUT VOSNS+ VOSNS– 100pF MARGIN CONTROL 90 VOUT 2.5V 6A COUT EFFICIENCY (%) ■ 80 70 60 19.1k 24VIN, 1.8VOUT 24VIN, 2.5VOUT 24VIN, 3.3VOUT 24VIN, 5VOUT 50 fSET 40 0 5% MARGIN 4603HV TA01a 1 4 3 5 2 LOAD CURRENT (A) 6 7 4603HV G03 4603hvf 1 LTM4603HV U W W W ABSOLUTE AXI U RATI GS PIN CONFIGURATION (Note 1) INTVCC, DRVCC, VOUT_LCL, VOUT (VOUT ≤ 3.3V with Remote Sense Amp) ............................ –0.3V to 6V PLLIN, TRACK/SS, MPGM, MARG0, MARG1, PGOOD....................................... –0.3V to INTVCC + 0.3V RUN ............................................................. –0.3V to 5V VFB, COMP ................................................ –0.3V to 2.7V VIN ............................................................. –0.3V to 28V VOSNS+, VOSNS– .................................. 0V to INTVCC – 1V Operating Temperature Range (Note 2) ... –40°C to 85°C Junction Temperature ........................................... 125°C Storage Temperature Range................... –55°C to 125°C INTVCC PLLIN TRACK/SS RUN COMP MPGM TOP VIEW VIN fSET MARG0 MARG1 DRVCC VFB PGOOD SGND VOSNS+ DIFFVOUT VOUT_LCL VOSNS– PGND VOUT LGA PACKAGE 118-LEAD (15mm ´ 15mm ´ 2.8mm) TJMAX = 125°C, θJA = 15°C/W, θJC = 6°C/W θJA DERIVED FROM 95mm × 76mm PCB WITH 4 LAYERS, WEIGHT = 1.7g ORDER INFORMATION LEAD FREE FINISH PART MARKING* PACKAGE DESCRIPTION TEMPERATURE RANGE LTM4603HVEV#PBF LTM4603HVV 118-Lead (15mm × 15mm × 2.8mm) LGA –40°C to 85°C LTM4603HVIV#PBF LTM4603HVV 118-Lead (15mm × 15mm × 2.8mm) LGA –40°C to 85°C Consult LTC Marketing for parts specified with wider operating temperature ranges. *The temperature grade is identified by a label on the shipping container. Consult LTC Marketing for information on non-standard lead based finish parts. For more information on lead free part marking, go to: http://www.linear.com/leadfree/ This product is only offered in trays. For more information go to: http://linear.com/packaging/ ELECTRICAL CHARACTERISTICS The ● denotes the specifications which apply over the –40°C to 85°C temperature range, otherwise specifications are at TA = 25°C, VIN = 12V. Per typical application (front page) configuration. SYMBOL PARAMETER VIN(DC) Input DC Voltage VOUT(DC) Output Voltage CONDITIONS CIN = 10μF ×2, COUT = 2×, 100μF/X5R/ Ceramic VIN = 5V, VOUT = 1.5V, IOUT = 0A VIN = 12V, VOUT = 1.5V, IOUT = 0A MIN ● 4.5 ● ● 1.478 1.478 TYP MAX UNITS 28 V 1.5 1.5 1.522 1.522 V V 4 V Input Specifications VIN(UVLO) Undervoltage Lockout Threshold IOUT = 0A 3.2 IINRUSH(VIN) Input Inrush Current at Startup IOUT = 0A. VOUT = 1.5V VIN = 5V VIN = 12V 0.6 0.7 A A 3.8 25 mA mA 2.5 43 mA mA IQ(VIN,NOLOAD) Input Supply Bias Current VIN = 12V, VOUT = 1.5V, No Switching VIN = 12V, VOUT = 1.5V, Switching Continuous VIN = 5V, VOUT = 1.5V, No Switching VIN = 5V, VOUT = 1.5V, Switching Continuous Shutdown, RUN = 0, VIN = 12V 22 μA 4603hvf 2 LTM4603HV ELECTRICAL CHARACTERISTICS The ● denotes the specifications which apply over the –40°C to 85°C temperature range, otherwise specifications are at TA = 25°C, VIN = 12V. Per typical application (front page) configuration. SYMBOL PARAMETER CONDITIONS IS(VIN) Input Supply Current VIN = 12V, VOUT = 1.5V, IOUT = 6A VIN = 12V, VOUT = 3.3V, IOUT = 6A VIN = 5V, VOUT = 1.5V, IOUT = 6A INTVCC VIN = 12V, RUN > 2V No Load MIN TYP MAX 0.85 1.78 2.034 4.7 5 UNITS A A A 5.3 V 6 A Output Specifications IOUTDC Output Continuous Current Range VIN = 12V, VOUT = 1.5V (See Output Current Derating Curves for Different VIN, VOUT and TA) 0 ΔVOUT(LINE) Line Regulation Accuracy VOUT = 1.5V, IOUT = 0A, VIN = 4.5V to 28V ● 0.3 % Load Regulation Accuracy VOUT = 1.5V, IOUT = 0A to 6A, VIN = 12V ● 0.25 % Output Ripple Voltage IOUT = 0A, COUT = 2×, 100μF/X5R/Ceramic VIN = 12V, VOUT = 1.5V VIN = 5V, VOUT = 1.5V VOUT ΔVOUT(LOAD) VOUT VOUT(AC) 10 10 mVP-P mVP-P fS Output Ripple Voltage Frequency IOUT = 3A, VIN = 12V, VOUT = 1.5V 1000 kHz ΔVOUT(START) Turn-On Overshoot, TRACK/SS = 10nF COUT = 2×, 100μF/X5R/Ceramic, VOUT = 1.5V, IOUT = 0A VIN = 12V VIN = 5V 20 20 mV mV COUT = 2×, 100μF/X5R/Ceramic, VOUT = 1.5V, IOUT = 1A Resisitive Load VIN = 12V VIN = 5V 0.5 0.7 ms ms Load: 0% to 50% to 0% of Full Load, COUT = 2 × 22μF/Ceramic, 470μF, 4V Sanyo POSCAP VIN = 12V VIN = 5V 35 35 mV mV tSETTLE Settling Time for Dynamic Load Step Load: 0% to 50% to 10% of Full Load VIN = 12V 25 μs IOUTPK Output Current Limit 8 8 A A tSTART ΔVOUTLS Turn-On Time, TRACK/SS = Open Peak Deviation for Dynamic Load COUT = 2×, 100μF/X5R/Ceramic VIN = 12V, VOUT = 1.5V VIN = 5V, VOUT = 1.5V Remote Sense Amp (Note 3) VOSNS+, VOSNS– CM Range Common Mode Input Voltage Range VIN = 12V, RUN > 2V 0 INTVCC – 1 0 INTVCC DIFFVOUT Range Output Voltage Range VOS Input Offset Voltage Magnitude AV Differential Gain 1 V/V GBP Gain Bandwidth Product 3 MHz SR Slew Rate 2 V/μs 20 kΩ 100 dB RIN Input Resistance CMRR Common Mode Rejection Ratio VIN = 12V, DIFFVOUT Load = 100k V 1.25 VOSNS+ to GND V mV 4603hvf 3 LTM4603HV ELECTRICAL CHARACTERISTICS The ● denotes the specifications which apply over the –40°C to 85°C temperature range, otherwise specifications are at TA = 25°C, VIN = 12V. Per typical application (front page) configuration. SYMBOL PARAMETER CONDITIONS VFB Error Amplifier Input Voltage Accuracy IOUT = 0A, VOUT = 1.5V MIN TYP MAX UNITS 0.594 0.6 0.606 V 1 1.5 1.9 V –1 –1.5 –2 μA Control Stage ● VRUN RUN Pin On/Off Threshold ISS/TRACK Soft-Start Charging Current VSS/TRACK = 0V tON(MIN) Minimum On Time (Note 4) 50 100 ns tOFF(MIN) Minimum Off Time (Note 4) 250 400 ns RPLLIN PLLIN Input Resistance IDRVCC Current into DRVCC Pin RFBHI Resistor Between VOUT_LCL and VFB VMPGM Margin Reference Voltage 1.18 V VMARG0, VMARG1 MARG0, MARG1 Voltage Thresholds 1.4 V 50 VOUT = 1.5V, IOUT = 1A, Frequency = 1MHz, DRVCC = 5V 60.098 kΩ 18 25 mA 60.4 60.702 kΩ PGOOD Output ΔVFBH PGOOD Upper Threshold VFB Rising 7 10 13 % ΔVFBL PGOOD Lower Threshold VFB Falling –7 –10 –13 % ΔVFB(HYS) PGOOD Hysteresis VFB Returning 1.5 3 % VPGL PGOOD Low Voltage IPGOOD = 5mA 0.15 0.4 V Note 1: Stresses beyond those listed under Absolute Maximum Ratings may cause permanent damage to the device. Exposure to any Absolute Maximum Rating condition for extended periods may affect device reliability and lifetime. Note 2: The LTM4603HVEV is guaranteed to meet performance specifications from 0°C to 85°C. Specifications over the –40°C to 85°C operating temperature range are assured by design, characterization and correlation with statistical process controls. The LTM4603HVIV is guaranteed over the –40°C to 85°C temperature range. Note 3: Remote sense amplifier recommended for ≤3.3V output. Note 4: 100% tested at die level only. 4603hvf 4 LTM4603HV U W TYPICAL PERFOR A CE CHARACTERISTICS (See Figure 20 for all curves) Efficiency vs Load Current with 24VIN Efficiency vs Load Current with 12VIN 100 100 90 90 90 80 80 80 70 5VIN, 0.6VOUT 5VIN, 1.2VOUT 5VIN, 1.5VOUT 5VIN, 1.8VOUT 5VIN, 2.5VOUT 5VIN, 3.3VOUT 60 50 40 0 1 4 3 2 5 LOAD CURRENT (A) 6 70 12VIN, 1.2VOUT 12VIN, 1.5VOUT 12VIN, 1.8VOUT 12VIN, 2.5VOUT 12VIN, 3.3VOUT 12VIN, 5VOUT 60 50 40 0 7 EFFICIENCY (%) 100 EFFICIENCY (%) EFFICIENCY (%) Efficiency vs Load Current with 5VIN 1 4 3 2 5 LOAD CURRENT (A) 6 70 60 24VIN, 1.8VOUT 24VIN, 2.5VOUT 24VIN, 3.3VOUT 24VIN, 5VOUT 50 7 40 0 4 3 5 2 LOAD CURRENT (A) 4603HV G02 4603HV G01 1.2V Transient Response 1.5V Transient Response LOAD STEP 1A/DIV VOUT 50mV/DIV VOUT 50mV/DIV VOUT 50mV/DIV 25μs/DIV 1.5V AT 3A/μs LOAD STEP COUT: 1x 22μF, 6.3V CERAMIC 1x 330μF, 4V SANYO POSCAP 2.5V Transient Response 4603HV G05 25μs/DIV 1.8V AT 3A/μs LOAD STEP COUT: 1x 22μF, 6.3V CERAMIC 1x 330μF, 4V SANYO POSCAP 4603HV G06 3.3V Transient Response LOAD STEP 1A/DIV LOAD STEP 1A/DIV VOUT 50mV/DIV VOUT 50mV/DIV 25μs/DIV 2.5V AT 3A/μs LOAD STEP COUT: 1x 22μF, 6.3V CERAMIC 1x 330μF, 4V SANYO POSCAP 7 1.8V Transient Response LOAD STEP 1A/DIV 4603HV G04 6 4603HV G03 LOAD STEP 1A/DIV 25μs/DIV 1.2V AT 3A/μs LOAD STEP COUT: 1x 22μF, 6.3V CERAMIC 1x 330μF, 4V SANYO POSCAP 1 4603HV G07 25μs/DIV 3.3V AT 3A/μs LOAD STEP COUT: 1x 22μF, 6.3V CERAMIC 1x 330μF, 4V SANYO POSCAP 4603HV G08 4603hvf 5 LTM4603HV U W TYPICAL PERFOR A CE CHARACTERISTICS (See Figure 20 for all curves) Short-Circuit Protection, IOUT = 0A Start-Up, IOUT = 6A (Resistive Load) Start-Up, IOUT = 0A VOUT 0.5V/DIV VOUT 0.5V/DIV VOUT 0.5V/DIV IIN 0.5A/DIV IIN 0.5A/DIV 1ms/DIV VIN = 12V VOUT = 1.5V COUT = 1x 22μF, 6.3V CERAMIC 1x 330μF, 4V SANYO POSCAP SOFT-START = 3.9nF 4603HV G09 IIN 2A/DIV 1ms/DIV VIN = 12V VOUT = 1.5V COUT = 1x 22μF, 6.3V CERAMIC 1x 330μF, 4V SANYO POSCAP SOFT-START = 3.9nF Short-Circuit Protection, IOUT = 6A 4603HV G10 100μs/DIV VIN = 12V VOUT = 1.5V COUT = 1x 22μF, 6.3V CERAMIC 1x 330μF, 4V SANYO POSCAP SOFT-START = 3.9nF VIN to VOUT Step-Down Ratio 5.5 3.3V OUTPUT WITH 82.5k FROM VOUT TO fSET 5.0 4.5 OUTPUT VOLTAGE (V) VOUT 0.5V/DIV IIN 2A/DIV 100μs/DIV VIN = 12V VOUT = 1.5V COUT = 1x 22μF, 6.3V CERAMIC 1x 330μF, 4V SANYO POSCAP SOFT-START = 3.9nF 4603HV G11 4603 G12 5V OUTPUT WITH 150k RESISTOR ADDED FROM fSET TO GND 4.0 3.5 3.0 2.0 5V OUTPUT WITH NO RESISTOR ADDED FROM fSET TO GND 1.5 2.5V OUTPUT 1.0 1.8V OUTPUT 2.5 1.5V OUTPUT 0.5 0 1.2V OUTPUT 0 4 12 16 20 8 INPUT VOLTAGE (V) 24 28 4603HV G13 4603hvf 6 LTM4603HV U U U PI FU CTIO S (See Package Description for Pin Assignment) VIN (Bank 1): Power Input Pins. Apply input voltage between these pins and PGND pins. Recommend placing input decoupling capacitance directly between VIN pins and PGND pins. VOUT (Bank 3): Power Output Pins. Apply output load between these pins and PGND pins. Recommend placing output decoupling capacitance directly between these pins and PGND pins. Review the figure below. PGND (Bank 2): Power ground pins for both input and output returns. VOSNS– (Pin M12): (–) Input to the Remote Sense Amplifier. This pin connects to the ground remote sense point. The remote sense amplifier is used for VOUT ≤3.3V. VOSNS+ (Pin J12): (+) Input to the Remote Sense Amplifier. This pin connects to the output remote sense point. The remote sense amplifier is used for VOUT ≤3.3V. DIFFVOUT (Pin K12): Output of the Remote Sense Amplifier. This pin connects to the VOUT_LCL pin. DRVCC (Pin E12): This pin normally connects to INTVCC for powering the internal MOSFET drivers. This pin can be biased up to 6V from an external supply with about 50mA capability, or an external circuit shown in Figure 16. This improves efficiency at the higher input voltages by reducing power dissipation in the modules. INTVCC (Pin A7): This pin is for additional decoupling of the 5V internal regulator. PLLIN (Pin A8): External Clock Synchronization Input to the Phase Detector. This pin is internally terminated to SGND with a 50k resistor. Apply a clock above 2V and below INTVCC. See Applications Information. TRACK/SS (Pin A9): Output Voltage Tracking and SoftStart Pin. When the module is configured as a master output, then a soft-start capacitor is placed on this pin to ground to control the master ramp rate. A soft-start capacitor can be used for soft-start turn on as a stand alone regulator. Slave operation is performed by putting a resistor divider from the master output to the ground, and connecting the center point of the divider to this pin. See Applications Information. MPGM (Pin A12): Programmable Margining Input. A resistor from this pin to ground sets a current that is equal to 1.18V/R. This current multiplied by 10kΩ will equal a value in millivolts that is a percentage of the 0.6V reference voltage. See Applications Information. To parallel LTM4603HVs, each requires an individual MPGM resistor. Do not tie MPGM pins together. fSET (Pin B12): Frequency Set Internally to 1MHz. An external resistor can be placed from this pin to ground to increase frequency. This pin can be decoupled with a 1000pF capacitor. See Applications Information for frequency adjustment. VFB (Pin F12): The Negative Input of the Error Amplifier. Internally, this pin is connected to VOUT_LCL with a 60.4k precision resistor. Different output voltages can be programmed with an additional resistor between VFB and SGND pins. See Applications Information. INTVCC PLLIN TRACK/SS RUN COMP MPGM TOP VIEW A VIN B BANK 1 C D E PGND F BANK 2 G H J VOUT K BANK 3 L M fSET MARG0 MARG1 DRVCC VFB PGOOD SGND VOSNS+ DIFFVOUT VOUT_LCL VOSNS– 1 2 3 4 5 6 7 8 9 10 11 12 4603hvf 7 LTM4603HV U U U PI FU CTIO S (See Package Description for Pin Assignment) MARG0 (Pin C12): This pin is the LSB logic input for the margining function. Together with the MARG1 pin will determine if margin high, margin low or no margin state is applied. The pin has an internal pull-down resistor of 50k. See Applications Information. ranges from 0V to 2.4V with 0.7V corresponding to zero sense voltage (zero current). PGOOD (Pin G12): Output Voltage Power Good Indicator. Open-drain logic output that is pulled to ground when the output voltage is not within ±10% of the regulation point, after a 25μs power bad mask timer expires. MARG1 (Pin D12): This pin is the MSB logic input for the margining function. Together with the MARG0 pin will determine if margin high, margin low or no margin state is applied. The pin has an internal pull-down resistor of 50k. See Applications Information. RUN (Pin A10): Run Control Pin. A voltage above 1.9V will turn on the module, and when below 1.9V, will turn off the module. A programmable UVLO function can be accomplished with a resistor from VIN to this pin that has a 5.1V zener to ground. Maximum pin voltage is 5V. SGND (Pin H12): Signal Ground. This pin connects to PGND at output capacitor point. VOUT_LCL (Pin L12): VOUT connects directly to this pin to bypass the remote sense amplifier, or DIFFVOUT connects to this pin when remote sense amplifier is used. COMP (Pin A11): Current Control Threshold and Error Amplifier Compensation Point. The current comparator threshold increases with this control voltage. The voltage W W SI PLIFIED BLOCK DIAGRA VOUT_LCL >2V = ON <0.9V = OFF MAX = 5V 1M VOUT RUN PGOOD 5.1V ZENER COMP 1.5μF VIN 4.5V TO 28V + CIN 60.4k INTERNAL COMP POWER CONTROL SGND Q1 VOUT 2.5V 6A MARG1 MARG0 22μF VFB RFB 19.1k 50k 50k + fSET COUT Q2 33.2k PGND MPGM CSS 10k PLLIN 50k INTVCC DRVCC 4.7μF INTVCC VOSNS– 10k + – TRACK/SS 10k VOSNS+ 10k DIFFVOUT 4603HV F01 Figure 1. Simplified LTM4603HV Block Diagram 4603hvf 8 LTM4603HV U W U DECOUPLI G REQUIRE E TS TA = 25°C, VIN = 12V. Use Figure 1 configuration. SYMBOL PARAMETER CONDITIONS MIN CIN External Input Capacitor Requirement (VIN = 4.5V to 28V, VOUT = 2.5V) IOUT = 6A 20 COUT External Output Capacitor Requirement (VIN = 4.5V to 28V, VOUT = 2.5V) IOUT = 6A 100 TYP MAX UNITS μF 200 μF U OPERATIO Power Module Description The LTM4603HV is a standalone nonisolated switching mode DC/DC power supply. It can deliver up to 6A of DC output current with few external input and output capacitors. This module provides precisely regulated output voltage programmable via one external resistor from 0.6VDC to 5.0VDC over a 4.5V to 28V wide input voltage. The typical application schematic is shown in Figure 20. The LTM4603HV has an integrated constant on-time current mode regulator, ultralow RDS(ON) FETs with fast switching speed and integrated Schottky diodes. The typical switching frequency is 1MHz at full load. With current mode control and internal feedback loop compensation, the LTM4603HV module has sufficient stability margins and good transient performance under a wide range of operating conditions and with a wide range of output capacitors, even all ceramic output capacitors. Current mode control provides cycle-by-cycle fast current limit. Besides, foldback current limiting is provided in an overcurrent condition while VFB drops. Internal overvoltage and undervoltage comparators pull the open-drain PGOOD output low if the output feedback voltage exits a ±10% window around the regulation point. Furthermore, in an overvoltage condition, internal top FET Q1 is turned off and bottom FET Q2 is turned on and held on until the overvoltage condition clears. Pulling the RUN pin below 1V forces the controller into its shutdown state, turning off both Q1 and Q2. At low load current, the module works in continuous current mode by default to achieve minimum output voltage ripple. When DRVCC pin is connected to INTVCC an integrated 5V linear regulator powers the internal gate drivers. If a 5V external bias supply is applied on the DRVCC pin, then an efficiency improvement will occur due to the reduced power loss in the internal linear regulator. This is especially true at the higher input voltage range. The LTM4603HV has a very accurate differential remote sense amplifier with very low offset. This provides for very accurate remote sense voltage measurement. The MPGM pin, MARG0 pin and MARG1 pin are used to support voltage margining, where the percentage of margin is programmed by the MPGM pin, and the MARG0 and MARG1 select margining. The PLLIN pin provides frequency synchronization of the device to an external clock. The TRACK/SS pin is used for power supply tracking and soft-start programming. 4603hvf 9 LTM4603HV U U W U APPLICATIO S I FOR ATIO The typical LTM4603HV application circuit is shown in Figure 20. External component selection is primarily determined by the maximum load current and output voltage. Refer to Table 2 for specific external capacitor requirements for a particular application. where %VOUT is the percentage of VOUT you want to margin, and VOUT(MARGIN) is the margin quantity in volts: VIN to VOUT Step-Down Ratios where RPGM is the resistor value to place on the MPGM pin to ground. There are restrictions in the maximum VIN and VOUT step down ratio that can be achieved for a given input voltage. These constraints are shown in the Typical Performance Characteristics curves labeled VIN to VOUT Step-Down Ratio. Note that additional thermal derating may apply. See the Thermal Considerations and Output Current Derating section of this data sheet. RPGM = The output margining will be ± margining of the value. This is controlled by the MARG0 and MARG1 pins. See the truth table below: Output Voltage Programming and Margining The PWM controller has an internal 0.6V reference voltage. As shown in the Block Diagram, a 1M and a 60.4k 0.5% internal feedback resistor connects VOUT and VFB pins together. The VOUT_LCL pin is connected between the 1M and the 60.4k resistor. The 1M resistor is used to protect against an output overvoltage condition if the VOUT_LCL pin is not connected to the output, or if the remote sense amplifier output is not connected to VOUT_LCL. The output voltage will default to 0.6V. Adding a resistor RSET from the VFB pin to SGND pin programs the output voltage: VOUT = 0.6 V 60.4k + RSET RSET MARG1 MODE LOW LOW NO MARGIN LOW HIGH MARGIN UP HIGH LOW MARGIN DOWN HIGH HIGH NO MARGIN Input Capacitors LTM4603HV module should be connected to a low AC impedance DC source. Input capacitors are required to be placed adjacent to the module. In Figure 20, the 10μF ceramic input capacitors are selected for their ability to handle the large RMS current into the converter. An input bulk capacitor of 100μF is optional. This 100μF capacitor is only needed if the input source impedance is compromised by long inductive leads or traces. D= RSET (kΩ) Open 60.4 40.2 30.1 25.5 19.1 13.3 8.25 VOUT (V) 0.6 1.2 1.5 1.8 2 2.5 3.3 5 The MPGM pin programs a current that when multiplied by an internal 10k resistor sets up the 0.6V reference ± offset for margining. A 1.18V reference divided by the RPGM resistor on the MPGM pin programs the current. Calculate VOUT(MARGIN): %VOUT • VOUT 100 MARG0 For a buck converter, the switching duty-cycle can be estimated as: Table 1. Standard 1% Resistor Values VOUT(MARGIN) = VOUT 1.18 V • • 10k 0.6 V VOUT(MARGIN) VOUT VIN Without considering the inductor current ripple, the RMS current of the input capacitor can be estimated as: ICIN(RMS) = IOUT(MAX ) η% • D • ( 1– D ) In the above equation, η% is the estimated efficiency of the power module. CIN can be a switcher-rated electrolytic aluminum capacitor, OS-CON capacitor or high volume ceramic capacitor. Note the capacitor ripple current ratings are often based on temperature and hours of life. This makes it advisable to properly derate the input capacitor, 4603hvf 10 LTM4603HV U W U U APPLICATIO S I FOR ATIO or choose a capacitor rated at a higher temperature than required. Always contact the capacitor manufacturer for derating requirements. In Figure 20, the 10μF ceramic capacitors are together used as a high frequency input decoupling capacitor. In a typical 6A output application, two very low ESR, X5R or X7R, 10μF ceramic capacitors are recommended. These decoupling capacitors should be placed directly adjacent to the module input pins in the PCB layout to minimize the trace inductance and high frequency AC noise. Each 10μF ceramic is typically good for 2A to 3A of RMS ripple current. Refer to your ceramics capacitor catalog for the RMS current ratings. Multiphase operation with multiple LTM4603HV devices in parallel will lower the effective input RMS ripple current due to the interleaving operation of the regulators. Application Note 77 provides a detailed explanation. Refer to Figure 2 for the input capacitor ripple current requirement as a function of the number of phases. The figure provides a ratio of RMS ripple current to DC load current as a function of duty cycle and the number of paralleled phases. Pick the corresponding duty cycle and the number of phases to arrive at the correct ripple current value. For example, the 2-phase parallel LTM4603HV design provides 10A at 2.5V output from a 12V input. The duty cycle is DC = 2.5V/12V = 0.21. The 2-phase curve has a ratio of ~0.25 for a duty cycle of 0.21. This 0.25 ratio of RMS ripple current to a DC load current of 10A equals ~2.5A of input RMS ripple current for the external input capacitors. Output Capacitors The LTM4603HV is designed for low output voltage ripple. The bulk output capacitors defined as COUT are chosen with low enough effective series resistance (ESR) to meet the output voltage ripple and transient requirements. COUT can be a low ESR tantalum capacitor, a low ESR polymer capacitor or a ceramic capacitor. The typical capacitance is 200μF if all ceramic output capacitors are used. Additional output filtering may be required by the system designer, if further reduction of output ripple or dynamic transient spike is required. Table 2 shows a matrix of different output voltages and output capacitors to minimize the voltage droop and overshoot during a 3A/μs transient. The table optimizes total equivalent ESR and total bulk capacitance to maximize transient performance. Multiphase operation with multiple LTM4603HV devices in parallel will lower the effective output ripple current due to the interleaving operation of the regulators. For example, each LTM4603HV’s inductor current of a 12V to 2.5V multiphase design can be read from the “Inductor Ripple vs Duty Cycle” (Figure 3). The large ripple current at low duty cycle and high output voltage can be reduced by adding an external resistor from fSET to ground which increases the frequency. If we choose the duty cycle of DC = 2.5V/12V = 0.21, the inductor ripple current for 2.5V output at 21% duty cycle is ~2A in Figure 3. 4 0.6 5V OUTPUT 1.8V OUTPUT 3 1-PHASE 2-PHASE 3-PHASE 4-PHASE 6-PHASE 0.4 0.3 1.5V OUTPUT ΔIL (A) RMS INPUT RIPPLE CURRENT DC LOAD CURRENT 2.5V OUTPUT 0.5 1.2V OUTPUT 3.3V OUTPUT WITH 82.5k ADDED FROM VOUT TO fSET 2 0.2 5V OUTPUT WITH 150k ADDED FROM fSET TO GND 1 0.1 0 0 0.1 0.2 0.3 0.4 0.5 0.6 0.7 DUTY FACTOR (VOUT/VIN) 0.8 0.9 4603HV F02 Figure 2. Normalized Input RMS Ripple Current vs Duty Factor for One to Six Modules (Phases) 0 20 40 60 DUTY CYCLE (VOUT/VIN) 80 4603HV F03 Figure 3. Inductor Ripple Current vs Duty Cycle 4603hvf 11 LTM4603HV U U W U APPLICATIO S I FOR ATIO 1.00 0.95 1-PHASE 2-PHASE 3-PHASE 4-PHASE 6-PHASE 0.90 0.85 RATIO = PEAK-TO-PEAK OUTPUT RIPPLE CURRENT DIr 0.80 0.75 0.70 0.65 0.60 0.55 0.50 0.45 0.40 0.35 0.30 0.25 0.20 0.15 0.10 0.05 0 0.1 0.15 0.2 0.25 0.3 0.35 0.4 0.45 0.5 0.55 0.6 0.65 0.7 0.75 0.8 0.85 0.9 DUTY CYCLE (VO/VIN) 4603HV F04 Figure 4. Normalized Output Ripple Current vs Duty Cycle, Dlr = VOT/LI Figure 4 provides a ratio of peak-to-peak output ripple current to the inductor current as a function of duty cycle and the number of paralleled phases. Pick the corresponding duty cycle and the number of phases to arrive at the correct output ripple current ratio value. If a 2-phase operation is chosen at a duty cycle of 21%, then 0.6 is the ratio. This 0.6 ratio of output ripple current to inductor ripple of 2A equals 1.2A of effective output ripple current. Refer to Application Note 77 for a detailed explanation of output ripple current reduction as a function of paralleled phases. The output voltage ripple has two components that are related to the amount of bulk capacitance and effective series resistance (ESR) of the output bulk capacitance. Therefore, the output voltage ripple can be calulated with the known effective output ripple current. The equation: ΔVOUT(P-P) ≈ (ΔIL/(8 • f • m • COUT) + ESR • ΔIL), where f is frequency and m is the number of parallel phases. This calclation process can be easily fulfilled using the Linear Technology μModule design tool. Fault Conditions: Current Limit and Overcurrent Foldback The LTM4603HV has a current mode controller, which inherently limits the cycle-by-cycle inductor current not only in steady-state operation, but also in transient. To further limit current in the event of an overload condition, the LTM4603HV provides foldback current limiting. If the output voltage falls by more than 50%, then the maximum output current is progressively lowered to about one sixth of its full current limit value. Soft-Start and Tracking The TRACK/SS pin provides a means to either soft-start the regulator or track it to a different power supply. A capacitor on this pin will program the ramp rate of the output voltage. A 1.5μA current source will charge up the external soft-start capacitor to 80% of the 0.6V internal voltage reference minus any margin delta. This will control 4603hvf 12 LTM4603HV U U W U APPLICATIO S I FOR ATIO the ramp of the internal reference and the output voltage. The total soft-start time can be calculated as: ( ) t SOFTSTART = 0.8 V • 0.6 V – VOUT(MARGIN) • CSS 1.5µA When the RUN pin falls below 1.5V, then the TRACK/SS pin is reset to allow for proper soft-start control when the regulator is enabled again. Current foldback and force continuous mode are disabled during the soft-start process. The soft-start function can also be used to control the output ramp up time, so that another regulator can be easily tracked to it. Output Voltage Tracking Output voltage tracking can be programmed externally using the TRACK/SS pin. The output can be tracked up and down with another regulator. The master regulator’s output is divided down with an external resistor divider that is the same as the slave regulator’s feedback divider. Figure 5 shows an example of coincident tracking. Ratiometric modes of tracking can be achieved by selecting different resistor values to change the output tracking ratio. The master output must be greater than the slave output for the tracking to work. Figure 6 shows the coincident output tracking characteristics. MASTER OUTPUT TRACK CONTROL VIN 100k CIN VIN PGOOD MPGM RUN COMP INTVCC DRVCC SGND PLLIN TRACK/SS VOUT LTM4603HV PGND 60.4k FROM VOUT TO VFB The RUN pin is used to enable the power module. The pin has an internal 5.1V zener to ground. The pin can be driven with a logic input not to exceed 5V. The RUN pin can also be used as an undervoltage lock out (UVLO) function by connecting a resistor divider from the input supply to the RUN pin: VUVLO = R1+ R2 • 1.5V R2 Power Good The PGOOD pin is an open-drain pin that can be used to monitor valid output voltage regulation. This pin monitors a ±10% window around the regulation point and tracks with margining. COMP Pin This pin is the external compensation pin. The module has already been internally compensated for most output voltages. Table 2 is provided for most application requirements. A spice model will be provided for other control loop optimization. PLLIN The power module has a phase-locked loop comprised of an internal voltage controlled oscillator and a phase detector. This allows the internal top MOSFET turn-on to be locked R1 40.2k MASTER OUTPUT SLAVE OUTPUT VFB MARG0 MARG1 COUT SLAVE OUTPUT OUTPUT VOLTAGE VOUT_LCL DIFFVOUT VOSNS+ VOSNS– fSET R2 60.4k Run Enable RSET 40.2k 4603HV F05 TIME Figure 5 4603HV F06 Figure 6 4603hvf 13 LTM4603HV U U W U APPLICATIO S I FOR ATIO to the rising edge of the external clock. The frequency range is ±30% around the operating frequency of 1MHz. A pulse detection circuit is used to detect a clock on the PLLIN pin to turn on the phase lock loop. The pulse width of the clock has to be at least 400ns and 2V in amplitude. During the start-up of the regulator, the phase-lock loop function is disabled. current sharing. This will balance the thermals on the design. The voltage feedback equation changes with the variable n as modules are paralleled: INTVCC and DRVCC Connection n is the number of paralleled modules. An internal low dropout regulator produces an internal 5V supply that powers the control circuitry and DRVCC for driving the internal power MOSFETs. Therefore, if the system does not have a 5V power rail, the LTM4603HV can be directly powered by Vin. The gate driver current through the LDO is about 20mA. The internal LDO power dissipation can be calculated as: Thermal Considerations and Output Current Derating PLDO_LOSS = 20mA • (VIN – 5V) The LTM4603HV also provides the external gate driver voltage pin DRVCC. If there is a 5V rail in the system, it is recommended to connect DRVCC pin to the external 5V rail. This is especially true for higher input voltages. Do not apply more than 6V to the DRVCC pin. A 5V output can be used to power the DRVCC pin with an external circuit as shown in Figure 18. Parallel Operation of the Module The LTM4603HV device is an inherently current mode controlled device. Parallel modules will have very good 60.4k + RSET n VOUT = 0.6 V RSET The power loss curves in Figures 7 and 8 can be used in coordination with the load current derating curves in Figures 9 to 12, and Figures 13 to 16 for calculating an approximate θJA for the module with various heat sinking methods. Thermal models are derived from several temperature measurements at the bench and thermal modeling analysis. Thermal Application Note 103 provides a detailed explanation of the analysis for the thermal models and the derating curves. Tables 3 and 4 provide a summary of the equivalent θJA for the noted conditions. These equivalent θJA parameters are correlated to the measured values, and are improved with air flow. The case temperature is maintained at 100°C or below for the derating curves. This allows for 4W maximum power dissipation in the total module with top and bottom heatsinking, and 2W power dissipation through the top of the module with an approximate θJC between 6°C/W to 9°C/W. This equates to a total of 124°C at the junction of the device. 6 3.5 2.5 24V LOSS 12V LOSS POWER LOSS (W) POWER LOSS (W) MAXIMUM LOAD CURRENT (A) 3.0 2.0 1.5 5V LOSS 1.0 2.5 2.0 12V LOSS 1.5 1.0 0.5 0.5 0 1 4 3 5 2 OUTPUT CURRENT (A) 6 7 4603HV F07 Figure 7. 1.5V Power Loss 4 3 2 5VIN, 1.5VOUT, 0LFM 5VIN, 1.5VOUT, 200LFM 5VIN, 1.5VOUT, 400LFM 1 0 0 0 5 0 1 4 3 5 2 OUTPUT CURRENT (A) 6 7 4603HV F08 Figure 8. 3.3V Power Loss 75 80 85 90 AMBIENT TEMPERATURE (°C) 95 4603HV F09 Figure 9. No Heat Sink 4603hvf 14 LTM4603HV U U W U 6 5 5 5 4 3 2 5VIN, 1.5VOUT, 0LFM 5VIN, 1.5VOUT, 200LFM 5VIN, 1.5VOUT, 400LFM 1 0 MAXIMUM LOAD CURRENT (A) 6 MAXIMUM LOAD CURRENT (A) 6 4 3 2 1 80 85 90 AMBIENT TEMPERATURE (°C) 95 4 3 2 12VIN, 1.5VOUT, 0LFM 12VIN, 1.5VOUT, 200LFM 12VIN, 1.5VOUT, 400LFM 1 0 0 70 95 75 80 85 90 AMBIENT TEMPERATURE (°C) 4603HV F10 12VIN, 1.5VOUT, 0LFM 12VIN, 1.5VOUT, 200LFM 12VIN, 1.5VOUT, 400LFM Figure 10. BGA Heat Sink 70 95 75 80 85 90 AMBIENT TEMPERATURE (°C) 4603HV F12 4603HV F11 Figure 12. BGA Heat Sink Figure 11. No Heat Sink 6 6 5 5 MAXIMUM LOAD CURRENT (A) MAXIMUM LOAD CURRENT (A) 4 3 2 12VIN, 3.3VOUT, 0LFM 12VIN, 3.3VOUT, 200LFM 12VIN, 3.3VOUT, 400LFM 1 0 70 4 3 2 12VIN, 3.3VOUT, 0LFM 12VIN, 3.3VOUT, 200LFM 12VIN, 3.3VOUT, 400LFM 1 0 95 75 80 85 90 AMBIENT TEMPERATURE (°C) 70 4603HV F14 Figure 13. No Heat Sink Figure 14. BGA Heat Sink 6 6 5 5 4 3 2 24VIN, 3.3VOUT, 0LFM 24VIN, 3.3VOUT, 200LFM 24VIN, 3.3VOUT, 400LFM 1 0 60 85 65 70 75 80 AMBIENT TEMPERATURE (°C) 4603HV F15 Figure 15. No Heat Sink 95 75 80 85 90 AMBIENT TEMPERATURE (°C) 4603HV F13 MAXIMUM LOAD CURRENT (A) 75 MAXIMUM LOAD CURRENT (A) MAXIMUM LOAD CURRENT (A) APPLICATIO S I FOR ATIO 4 3 2 24VIN, 3.3VOUT, 0LFM 24VIN, 3.3VOUT, 200LFM 24VIN, 3.3VOUT, 400LFM 1 0 60 85 70 75 80 65 AMBIENT TEMPERATURE (°C) 90 1635 G24 Figure 16. BGA Heat Sink 4603hvf 15 LTM4603HV Table 2. Output Voltage Response Versus Component Matrix (Refer to Figure 20) TYPICAL MEASURED VALUES COUT1 VENDORS TAIYO YUDEN TAIYO YUDEN TDK VOUT (V) 1.2 1.2 1.2 1.2 1.2 1.2 1.2 1.2 1.5 1.5 1.5 1.5 1.5 1.5 1.5 1.5 1.8 1.8 1.8 1.8 1.8 1.8 1.8 1.8 2.5 2.5 2.5 2.5 2.5 2.5 2.5 2.5 3.3 3.3 3.3 3.3 3.3 3.3 3.3 3.3 5 5 CIN (CERAMIC) 2 × 10μF 35V 2 × 10μF 35V 2 × 10μF 35V 2 × 10μF 35V 2 × 10μF 35V 2 × 10μF 35V 2 × 10μF 35V 2 × 10μF 35V 2 × 10μF 35V 2 × 10μF 35V 2 × 10μF 35V 2 × 10μF 35V 2 × 10μF 35V 2 × 10μF 35V 2 × 10μF 35V 2 × 10μF 35V 2 × 10μF 35V 2 × 10μF 35V 2 × 10μF 35V 2 × 10μF 35V 2 × 10μF 35V 2 × 10μF 35V 2 × 10μF 35V 2 × 10μF 35V 2 × 10μF 35V 2 × 10μF 35V 2 × 10μF 35V 2 × 10μF 35V 2 × 10μF 35V 2 × 10μF 35V 2 × 10μF 35V 2 × 10μF 35V 2 × 10μF 35V 2 × 10μF 35V 2 × 10μF 35V 2 × 10μF 35V 2 × 10μF 35V 2 × 10μF 35V 2 × 10μF 35V 2 × 10μF 35V 2 × 10μF 35V 2 × 10μF 35V PART NUMBER JMK316BJ226ML-T501 (22μF, 6.3V) JMK325BJ476MM-T (47μF, 6.3V) C3225X5R0J476M (47μF, 6.3V) CIN (BULK) 150μF 35V 150μF 35V 150μF 35V 150μF 35V 150μF 35V 150μF 35V 150μF 35V 150μF 35V 150μF 35V 150μF 35V 150μF 35V 150μF 35V 150μF 35V 150μF 35V 150μF 35V 150μF 35V 150μF 35V 150μF 35V 150μF 35V 150μF 35V 150μF 35V 150μF 35V 150μF 35V 150μF 35V 150μF 35V 150μF 35V 150μF 35V 150μF 35V 150μF 35V 150μF 35V 150μF 35V 150μF 35V 150μF 35V 150μF 35V 150μF 35V 150μF 35V 150μF 35V 150μF 35V 150μF 35V 150μF 35V 150μF 35V 150μF 35V COUT1 (CERAMIC) 1 × 22μF 6.3V 1 × 47μF 6.3V 2 × 47μF 6.3V 4 × 47μF 6.3V 1 × 22μF 6.3V 1 × 47μF 6.3V 2 × 47μF 6.3V 4 × 47μF 6.3V 1 × 22μF 6.3V 1 × 47μF 6.3V 2 × 47μF 6.3V 4 × 47μF 6.3V 1 × 22μF 6.3V 1 × 47μF 6.3V 2 × 47μF 6.3V 4 × 47μF 6.3V 1 × 22μF 6.3V 1 × 47μF 6.3V 2 × 47μF 6.3V 4 × 47μF 6.3V 1 × 22μF 6.3V 1 × 47μF 6.3V 2 × 47μF 6.3V 4 × 47μF 6.3V 1 × 22μF 6.3V 1 × 47μF 6.3V 2 × 47μF 6.3V 4 × 47μF 6.3V 1 × 22μF 6.3V 1 × 47μF 6.3V 2 × 47μF 6.3V 4 × 47μF 6.3V 1 × 22μF 6.3V 1 × 47μF 6.3V 2 × 47μF 6.3V 4 × 47μF 6.3V 1 × 22μF 6.3V 1 × 47μF 6.3V 2 × 47μF 6.3V 4 × 47μF 6.3V 4 × 47μF 6.3V 4 × 47μF 6.3V COUT2 (BULK) 330μF 4V 330μF 2.5V 220μF 6.3V NONE 330μF 4V 330μF 2.5V 220μF 6.3V NONE 330μF 4V 330μF 2.5V 220μF 6.3V NONE 330μF 4V 330μF 2.5V 220μF 6.3V NONE 330μF 4V 330μF 2.5V 220μF 6.3V NONE 330μF 4V 330μF 2.5V 220μF 6.3V NONE 330μF 4V 330μF 4V 220μF 6.3V NONE 330μF 4V 330μF 4V 220μF 6.3V NONE 330μF 4V 330μF 4V 220μF 6.3V NONE 330μF 4V 330μF 4V 220μF 6.3V NONE NONE NONE COUT2 VENDORS SANYO POSCAP SANYO POSCAP SANYO POSCAP VIN (V) 5 5 5 5 12 12 12 12 5 5 5 5 12 12 12 12 5 5 5 5 12 12 12 12 5 5 5 5 12 12 12 12 7 7 7 7 12 12 12 12 15 20 DROOP (mV) 34 22 20 32 34 22 20 29.5 35 25 24 36 35 25 24 32.6 38 29.5 28 43 38 28 27 36.4 38 37.6 39.5 66 38 34.5 35.8 50 42 47 50 75 42 47 50 69 110 110 PART NUMBER 6TPE220MIL (220μF, 6.3V) 2R5TPE330M9 (330μF, 2.5V) 4TPE330MCL (330μF, 4V) PEAK TO PEAK (mV) 68 40 40 60 68 40 39 55 70 48 47.5 68 70 48 45 61.9 76 57.5 55 80 76 55 52 70 78 74 78.1 119 78 66.3 68.8 98 86 89 94 141 86 88 94 131 215 217 RECOVERY TIME (μs) 30 26 24 18 30 26 24 18 30 30 26 26 30 30 26 26 37 30 26 26 37 30 26 26 40 34 28 12 40 34 28 18 40 32 28 14 40 32 28 22 20 20 LOAD STEP (A/μs) 3 3 3 3 3 3 3 3 3 3 3 3 3 3 3 3 3 3 3 3 3 3 3 3 3 3 3 3 3 3 3 3 3 3 3 3 3 3 3 3 3 3 RSET (kΩ) 60.4 60.4 60.4 60.4 60.4 60.4 60.4 60.4 40.2 40.2 40.2 40.2 40.2 40.2 40.2 40.2 30.1 30.1 30.1 30.1 30.1 30.1 30.1 30.1 19.1 19.1 19.1 19.1 19.1 19.1 19.1 19.1 13.3 13.3 13.3 13.3 13.3 13.3 13.3 13.3 8.25 8.25 4603hvf 16 LTM4603HV U W U U APPLICATIO S I FOR ATIO Table 3. 1.5V Output DERATING CURVE VIN (V) POWER LOSS CURVE AIR FLOW (LFM) HEAT SINK θJA (°C/W) Figures 9, 11 5, 12 Figure 7 0 None 15.2 Figures 9, 11 5, 12 Figure 7 200 None 14 Figures 9, 11 5, 12 Figure 7 400 None 12 Figures 10, 12 5, 12, 20 Figure 7 0 BGA Heat Sink 13.9 Figures 10, 12 5, 12, 20 Figure 7 200 BGA Heat Sink 11.3 Figures 10, 12 5, 12, 20 Figure 7 400 BGA Heat Sink 10.25 DERATING CURVE VIN (V) POWER LOSS CURVE AIR FLOW (LFM) HEAT SINK θJA (°C/W) Figures 13, 15 12, 24 Figure 8 0 None 15.2 Figures 13, 15 12, 24 Figure 8 200 None 14.6 Figures 13, 15 12, 24 Figure 8 400 None 13.4 Figures 14, 16 12, 24 Figure 8 0 BGA Heat Sink 13.9 Figures 14, 16 12, 24 Figure 8 200 BGA Heat Sink 11.1 Figures 14, 16 12, 24 Figure 8 400 BGA Heat Sink 10.5 Table 4. 3.3V Output Heat Sink Manufacturer Wakefield Engineering Part No: 20069 Phone: 603-635-2800 4603hvf 17 LTM4603HV U W U U APPLICATIO S I FOR ATIO Safety Considerations • Do not put vias directly on pads. The LTM4603HV modules do not provide isolation from VIN to VOUT. There is no internal fuse. If required, a slow blow fuse with a rating twice the maximum input current needs to be provided to protect each unit from catastrophic failure. • If vias are placed onto the pads, the the vias must be capped. Layout Checklist/Example • Interstitial via placement can also be used if necessary. • Use a separated SGND ground copper area for components connected to signal pins. Connect the SGND to PGND underneath the unit. The high integration of LTM4603HV makes the PCB board layout very simple and easy. However, to optimize its electrical and thermal performance, some layout considerations are still necessary. Figure 17 gives a good example of the recommended layout. • Use large PCB copper areas for high current path, including VIN, PGND and VOUT. It helps to minimize the PCB conduction loss and thermal stress. The LTM4603HV is designed to typically operate at 1MHz across most input conditions. The fSET pin is typically left open or decoupled with an optional 1000pF capacitor. The switching frequency has been optimized for maintaining constant output ripple noise over most operating ranges. The 1MHz switching frequency and the 400ns minimum off time can limit operation at higher duty cycles like 5V to 3.3V, and produce excessive inductor ripple currents for lower duty cycle applications like 28V to 5V. The 5V and 3.3V drop out curves are modified by adding an external resistor on the fSET pin to allow for wider input voltage operations. • Place high frequency ceramic input and output capacitors next to the VIN, PGND and VOUT pins to minimize high frequency noise. • Place a dedicated power ground layer underneath the unit. • To minimize the via conduction loss and reduce module thermal stress, use multiple vias for interconnection between top layer and other power layers. Frequency Adjustment VIN CIN CIN GND SIGNAL GND COUT COUT VOUT 4603HV F17 Figure 17. Recommended Layout 4603hvf 18 LTM4603HV U W U U APPLICATIO S I FOR ATIO Example for 5V Output Example for 3.3V Output LTM4603HV minimum on-time = 100ns; tON = ((4.8 • 10pf)/IfSET) LTM4603HV minimum on-time = 100ns; tON = ((3.3 • 10pF)/IfSET) LTM4603HV minimum off-time = 400ns; tOFF = t– tON, where t = 1/Frequency LTM4603HV minimum off-time = 400ns; tOFF = t – tON, where t = 1/Frequency Duty Cycle = tON/t or VOUT/VIN Duty Cycle (DC) = tON/t or VOUT/VIN Equations for setting frequency: Equations for setting frequency: IfSET = (VIN/(3 • RfSET)), for 28V input operation, IfSET = 281μA, tON = ((4.8 • 10pF)/IfSET), tON = 171ns, where the internal RfSET is 33.2k. Frequency = (VOUT/(VIN • tON)) = (5V/(28 • 171ns)) ~ 1MHz. The inductor ripple current begins to get high at the higher input voltages due to a larger voltage across the inductor. This is shown in the “Inductor Ripple Current vs Duty Cycle” graph as ~4A at 25% duty cycle. The inductor ripple current can be lowered at the higher input voltages by adding an external resistor from fSET to ground to increase the switching frequency. A 3A ripple current is chosen, and the total peak current is equal to 1/2 of the 3A ripple current plus the output current. The 5V output current is limited to 5A, so total peak current is less than 6.5A. This is below the 8A peak specified value. A 150k resistor is placed from fSET to ground, and the parallel combination of 150k and 33.2k equates to 27.2k. The IfSET calculation with 27.2k and 28V input voltage equals 343μA. This equates to a tON of 140ns. This will increase the switching frequency from 1MHz to ~1.28MHz for the 28V to 5V conversion. The minimum on time is above 100ns at 28V input. Since the switching frequency is approximately constant over input and output conditions, then the lower input voltage range is limited to 10V for the 1.28MHz operation due to the 400ns minimum off time. Equation: tON = (VOUT/VIN) • (1/Frequency) equates to a 382ns on time, and a 400ns off time. The “VIN to VOUT Step-Down Ratio” curve reflects an operating range of 10V to 28V for 1.28MHz operation with a 150k resistor to ground (shown in Figure 18), and an 8V to 16V operating range for fSET floating. These modifications are made to provide wider input voltage ranges for the 5V output designs while limiting the inductor ripple current, and maintaining the 400ns minimum off time. IfSET = (VIN/(3 • RfSET)), for 28V input operation, IfSET = 281μA, tON = ((3.3 • 10pf)/IfSET), tON = 117ns, where the internal RfSET is 33.2k. Frequency = (VOUT/(VIN • tON)) = (3.3V/(28 • 117ns)) ~ 1MHz. The minimum on-time and minimum-off time are within specification at 118ns and 882ns. But the 4.5V minimum input for converting 3.3V output will not meet the minimum off-time specification of 400ns. tON = 733ns, Frequency = 1MHz, tOFF = 267ns. Solution Lower the switching frequency at lower input voltages to allow for higher duty cycles, and meet the 400ns minimum off-time at 4.5V input voltage. The off-time should be about 500ns with 100ns guard band. The duty cycle for (3.3V/4.5) = ~73%. Frequency = (1 – DC)/tOFF or (1 – 0.73)/500ns = 540kHz. The switching frequency needs to be lowered to 540kHz at 4.5V input. tON = DC/frequency, or 1.35μs. The fSET pin voltage compliance is 1/3 of VIN, and the IfSET current equates to 45μA with the internal 33.2k. The IfSET current needs to be 24μA for 540kHz operation. A resistor can be placed from VOUT to fSET to lower the effective IfSET current out of the fSET pin to 24μA. The fSET pin is 4.5V/3 =1.5V and VOUT = 3.3V, therefore an 82.5k resistor will source 21μA into the fSET node and lower the IfSET current to 24μA. This enables the 540kHz operation and the 4.5V to 28V input operation for down converting to 3.3V output as shown in Figure 19. The frequency will scale from 540kHz to 1.27MHz over this input range. This provides for an effective output current of 5A over the input range. 4603hvf 19 LTM4603HV U W U U APPLICATIO S I FOR ATIO VOUT TRACK/SS CONTROL VIN 10V TO 28V R2 100k R4 100k MPGM RUN COMP INTVCC DRVCC 5% MARGIN R1 392k 1% C1 10μF 35V C2 10μF 35V VIN PGOOD PLLIN TRACK/SS VOUT LTM4603HV SGND PGND REVIEW TEMPERATURE DERATING CURVE C6 100pF VFB MARG0 MARG1 + VOUT_LCL DIFFVOUT VOSNS+ VOSNS– VOUT 5V 5A REFER TO TABLE 2 C3 100μF 6.3V SANYO POSCAP fSET RfSET 150k RSET 8.25k MARGIN CONTROL IMPROVE EFFICIENCY FOR ≥12V INPUT SOT-323 DUAL CMSSH-3C3 4603HV F18 Figure 18. 5V at 5A Design VOUT VIN 4.5V TO 28V TRACK/SS CONTROL R2 100k R4 100k PGOOD C2 10μF 35V VIN PGOOD MPGM RUN COMP INTVCC DRVCC PLLIN TRACK/SS VOUT LTM4603HV R1 392k C1 10μF 35V 5% MARGIN SGND PGND REVIEW TEMPERATURE DERATING CURVE C6 100pF VFB MARG0 MARG1 + VOUT_LCL DIFFVOUT VOSNS+ VOSNS– fSET MARGIN CONTROL RfSET 82.5k VOUT 3.3V 5A C3 100μF 6.3V SANYO POSCAP RSET 13.3k 4603HV F19 Figure 19. 3.3V at 5A Design 4603hvf 20 LTM4603HV U U W U APPLICATIO S I FOR ATIO CLOCK SYNC VOUT VIN 4.5V TO 28V R2 100k C5 0.01μF R4 100k PGOOD CIN BULK OPT. TABLE 2 + CIN 10μF 35V ×2 CER PLLIN TRACK/SS VOUT VIN PGOOD MPGM RUN ON/OFF COMP INTVCC DRVCC R1 392k LTM4603HV SGND PGND VFB MARG0 MARG1 REVIEW TEMPERATURE DERATING CURVE C3 100pF COUT1 22μF 6.3V MARGIN CONTROL COUT2 470μF 6.3V VOUT_LCL DIFFVOUT VOSNS+ VOSNS– fSET RSET 40.2k 100k* VIN *100k NEEDED ONLY FOR ≥20V INPUT 5% MARGIN + VOUT 1.5V 6A REFER TO TABLE 2 4603 F18 Figure 20. Typical 4.5V-28VIN, 1.5V at 6A Design VOUT VIN 4.5V TO 28V C1 10μF 35V ×2 R2 392k LTC6908-1 R9 118k C3 0.1μF R3 100k V+ OUT1 GND OUT2 SET MOD C3 0.33μF R4 100k 0° PHASE VIN PLLIN VOUT PGOOD VFB RUN VOUT_LCL COMP DIFFVOUT INTVCC LTM4603HV DRVCC VOSNS+ MPGM VOSNS– MARG0 fSET TRACK/SS MARG1 SGND PGND C8 100pF RSET 9.53k C2 100μF 6.3V C4 220μF 6.3V C7 100μF 6.3V C6 220μF 6.3V VOUT 2.5V 12A MARGIN CONTROL 2-PHASE OSCILLATOR 180° PHASE R7 100k C5 10μF 35V ×2 R6 392k PLLIN VIN VOUT PGOOD VFB RUN VOUT_LCL COMP DIFFVOUT INTVCC LTM4603HV DRVCC VOSNS+ MPGM VOSNS– MARG0 fSET TRACK/SS MARG1 SGND PGND 4603HV F21 5% MARGIN Figure 21. 2-Phase, Parallel 2.5V at 12A Design 4603hvf 21 LTM4603HV TYPICAL APPLICATIONS LTC6908-1 R9 118k V+ OUT1 GND OUT2 SET MOD C8 0.1μF 0° PHASE 2-PHASE OSCILLATOR 3.3V 3.3V VIN 5V TO 28V R4 100k R3 100k C1 10μF 35V ×2 R2 392k C3 0.15μF 180° PHASE PLLIN VIN VOUT PGOOD VFB RUN LTM4603HV COMP VOUT_LCL DIFFVOUT INTVCC DRVCC VOSNS+ MPGM VOSNS– MARG0 fSET TRACK/SS MARG1 SGND PGND C8 22pF RSET1 13.3k C2 100μF 6.3V C4 220μF 6.3V VOUT1 3.3V 6A 3.3V TRACK R16 60.4k MARGIN CONTROL R7 100k R8 100k C5 10μF 35V ×2 R2 392k R15 19.1k VIN PLLIN VOUT PGOOD VFB RUN LTM4603HV COMP VOUT_LCL DIFFVOUT INTVCC DRVCC VOSNS+ MPGM VOSNS– MARG0 fSET TRACK/SS MARG1 SGND PGND C9 22pF RSET2 19.1k C6 100μF 6.3V VOUT2 2.5V C7 6A 220μF 6.3V MARGIN CONTROL 4603HV F22 Figure 22. 2-Phase, 3.3V and 2.5V at 6A with Tracking LTC6908-1 R9 182k C8 0.1μF 1.8V V+ OUT1 GND OUT2 SET MOD 0° PHASE 2-PHASE OSCILLATOR 1.8V VIN 4.5V TO 28V R3 100k C1 10μF 35V ×2 R4 100k R2 392k C3 0.15μF 180° PHASE PLLIN VIN PGOOD VOUT VFB RUN LTM4603HV COMP VOUT_LCL INTVCC DIFFVOUT DRVCC VOSNS+ MPGM VOSNS– MARG0 fSET TRACK/SS MARG1 SGND PGND C8 100pF RSET1 30.1k MARGIN CONTROL C2 100μF 6.3V C4 220μF 6.3V VOUT1 1.8V 6A 1.8V TRACK R16 60.4k R15 40.2k R7 100k R8 100k C5 10μF 35V ×2 R6 392k VIN PLLIN PGOOD VOUT VFB RUN LTM4603HV COMP VOUT_LCL INTVCC DIFFVOUT DRVCC VOSNS+ MPGM VOSNS– MARG0 fSET TRACK/SS MARG1 SGND PGND C9 100pF RSET2 40.2k C6 100μF 6.3V VOUT2 1.5V C7 6A 220μF 6.3V MARGIN CONTROL 4603HV F23 Figure 23. 2-Phase, 1.8V and 1.5V at 6A with Tracking 4603hvf 22 Information furnished by Linear Technology Corporation is believed to be accurate and reliable. However, no responsibility is assumed for its use. Linear Technology Corporation makes no representation that the interconnection of its circuits as described herein will not infringe on existing patent rights. C(0.30) PAD 1 1.27 BSC 13.97 BSC 0.12 – 0.28 6.9850 5.7150 4.4450 3.1750 1.9050 0.6350 0.0000 0.6350 1.9050 3.1750 4.4450 5.7150 6.9850 6.9850 1 5.7150 2 4.4450 3.1750 1.9050 0.6350 0.0000 0.6350 1.9050 3.1750 4.4450 3 4 6 7 8 BOTTOM VIEW 5 13.97 BSC 9 10 SUGGESTED SOLDER PAD LAYOUT TOP VIEW 5.7150 11 12 DETAIL A 6.9850 bbb Z PADS SEE NOTES 3 A eee M X Y 0.27 – 0.37 SUBSTRATE DETAIL A 0.60 – 0.66 DETAIL B 0.60 – 0.66 B C D E F G H J K L M 2.45 – 2.55 MOLD CAP Z DETAIL B 2.72 – 2.92 aaa Z 4 PAD 1 CORNER (Reference LTM DWG # 05-05-1801 Rev Ø) LGA Package 118-Lead (15mm × 15mm) X DETAILS OF PAD #1 IDENTIFIER ARE OPTIONAL, BUT MUST BE LOCATED WITHIN THE ZONE INDICATED. THE PAD #1 IDENTIFIER MAY BE EITHER A MOLD OR MARKED FEATURE 4 SYMBOL TOLERANCE 0.10 aaa 0.10 bbb 0.03 eee LGA 118 0306 REV Ø 6. THE TOTAL NUMBER OF PADS: 118 5. PRIMARY DATUM -Z- IS SEATING PLANE LAND DESIGNATION PER JESD MO-222, SPP-010 3 2. ALL DIMENSIONS ARE IN MILLIMETERS NOTES: 1. DIMENSIONING AND TOLERANCING PER ASME Y14.5M-1994 TOP VIEW 15 BSC 15 BSC Y aaa Z LTM4603HV PACKAGE DESCRIPTIO 4603hvf 23 U LTM4603HV RELATED PARTS PART NUMBER DESCRIPTION COMMENTS LTC2900 Quad Supply Monitor with Adjustable Reset Timer Monitors Four Supplies; Adjustable Reset Timer LTC2923 Power Supply Tracking Controller Tracks Both Up and Down; Power Supply Sequencing LT3825/LT3837 Synchronous Isolated Flyback Controllers No Optocoupler Required; 3.3V, 12A Output; Simple Design LTM4600 10A DC/DC μModule Fast Transient Response LTM4601 12A DC/DC μModule with PLL, Output Tracking and Margining, LTM4603HV Pin Compatible LTM4602 6A DC/DC μModule Pin Compatible with the LTM4600 LTM4603 6A DC/DC μModule with Tracking PLL/Margining Pin Compatible with the LTM4601 4603hvf 24 Linear Technology Corporation LT 0607 • PRINTED IN USA 1630 McCarthy Blvd., Milpitas, CA 95035-7417 (408) 432-1900 ● FAX: (408) 434-0507 ● www.linear.com © LINEAR TECHNOLOGY CORPORATION 2007