Single and Quad 18 V Operational Amplifiers AD8614/AD8644 APPLICATIONS PIN CONFIGURATIONS OUT A 1 5 V+ 4 –IN AD8614 TOP VIEW (Not to Scale) +IN 3 06485-001 V– 2 Figure 1. 5-Lead SOT-23 (RJ-5) 14 OUT D OUT A 1 –IN A 2 13 –IN D LCD gamma and VCOM drivers Modems Portable instrumentation Direct access arrangement +IN A 3 –IN B 6 9 –IN C GENERAL DESCRIPTION OUT B 7 8 OUT C The AD8614 (single) and AD8644 (quad) are single-supply, 5.5 MHz bandwidth, rail-to-rail amplifiers optimized for LCD monitor applications. They are processed using the Analog Devices, Inc. high voltage, extra fast complementary bipolar (HV XFCB) process. This proprietary process includes trench-isolated transistors that lower internal parasitic capacitance, which improves gain bandwidth, phase margin, and capacitive load drive. The low supply current of 800 μA (typical) per amplifier is critical for portable or densely packed designs. In addition, the rail-to-rail output swing provides greater dynamic range and control than standard video amplifiers provide. V+ 4 AD8644 TOP VIEW (Not to Scale) +IN B 5 12 +IN D 11 V– 10 +IN C 06485-002 Unity-gain bandwidth: 5.5 MHz Low voltage offset: 1.0 mV Slew rate: 7.5 V/μs Single-supply operation: 5 V to 18 V High output current: 70 mA Low supply current: 800 μA/amplifier Stable with large capacitive loads Rail-to-rail inputs and outputs Figure 2. 14-Lead TSSOP (RU-14) OUT A 1 14 OUT D –IN A 2 13 –IN D +IN A 3 AD8644 +IN D TOP VIEW 11 V– (Not to Scale) 10 +IN C +IN B 5 12 V+ 4 –IN B 6 9 –IN C OUT B 7 8 OUT C 06485-003 FEATURES Figure 3. 14-Lead Narrow Body SOIC (R-14) These products operate from supplies of 5 V to as high as 18 V. The unique combination of an output drive of 70 mA, high slew rates, and high capacitive drive capability makes the AD8614/AD8644 an ideal choice for LCD applications. The AD8614 and AD8644 are specified over the temperature range of –20°C to +85°C. They are available in 5-lead SOT-23, 14-lead TSSOP, and 14-lead SOIC surface-mount packages in tape and reel. Rev. B Information furnished by Analog Devices is believed to be accurate and reliable. However, no responsibility is assumed by Analog Devices for its use, nor for any infringements of patents or other rights of third parties that may result from its use. Specifications subject to change without notice. No license is granted by implication or otherwise under any patent or patent rights of Analog Devices. Trademarks and registered trademarks are the property of their respective owners. One Technology Way, P.O. Box 9106, Norwood, MA 02062-9106, U.S.A. Tel: 781.329.4700 www.analog.com Fax: 781.461.3113 ©1999–2007 Analog Devices, Inc. All rights reserved. AD8614/AD8644 TABLE OF CONTENTS Features .............................................................................................. 1 Output Short-Circuit Protection.................................................9 Applications....................................................................................... 1 Input Overvoltage Protection ................................................... 10 General Description ......................................................................... 1 Output Phase Reversal............................................................... 10 Pin Configurations ........................................................................... 1 Power Dissipation....................................................................... 10 Revision History ............................................................................... 2 Unused Amplifiers ..................................................................... 10 Specifications..................................................................................... 3 Capacitive Load Drive ............................................................... 11 Electrical Characteristics............................................................. 3 Direct Access Arrangement ...................................................... 11 Absolute Maximum Ratings............................................................ 4 Thermal Resistance ...................................................................... 4 A One-Chip Headphone/Microphone Preamplifier Solution........................................................................................ 11 ESD Caution.................................................................................. 4 Outline Dimensions ....................................................................... 13 Typical Performance Characteristics ............................................. 5 Ordering Guide .......................................................................... 14 Theory of Operation ........................................................................ 9 REVISION HISTORY 9/07—Rev. A to Rev B Change to Current Noise Density in Table 1 ................................ 3 12/06—Rev. 0 to Rev. A Updated Format..................................................................Universal Deleted SPICE Model Availability Section.................................. 12 Updated Outline Dimensions ....................................................... 13 Changes to Ordering Guide .......................................................... 14 10/99—Revision 0: Initial Version Rev. B | Page 2 of 16 AD8614/AD8644 SPECIFICATIONS ELECTRICAL CHARACTERISTICS 5 V ≤ VS ≤ 18 V, VCM = VS/2, TA = 25°C, unless otherwise noted. 1 Table 1. Parameter INPUT CHARACTERISTICS Offset Voltage Symbol Conditions Min VOS Typ Max Unit 1.0 2.5 3 400 500 100 200 VS mV mV nA nA nA nA V dB V/mV −20°C ≤ TA ≤ +85°C Input Bias Current IB Input Offset Current IOS 80 −20°C ≤ TA ≤ +85°C 5 −20°C ≤ TA ≤ +85°C Input Voltage Range Common-Mode Rejection Ratio Voltage Gain OUTPUT CHARACTERISTICS Output Voltage High Output Voltage Low Output Short-Circuit Current POWER SUPPLY Power Supply Rejection Ratio Supply Current/Amplifier CMRR AVO VCM = 0 V to VS VOUT = 0.5 V to VS – 0.5 V, RL = 10 kΩ VOH VOL ISC ILOAD = 10 mA ILOAD = 10 mA PSRR ISY 0 60 10 75 150 VS − 0.15 −20°C ≤ TA ≤ +85°C 35 30 VS = ±2.25 V to ±9.25 V 80 65 70 110 0.8 −20°C ≤ TA ≤ +85°C DYNAMIC PERFORMANCE Slew Rate Gain Bandwidth Product Phase Margin Settling Time NOISE PERFORMANCE Voltage Noise Density Current Noise Density 1 SR GBP Φo tS en en in CL = 200 pF 150 1.1 1.5 V mV mA mA dB mA mA 0.01%, 10 V step 7.5 5.5 65 3 V/μs MHz Degrees μs f = 1 kHz f = 10 kHz f = 10 kHz 12 11 1 nV/√Hz nV/√Hz pA/√Hz All typical values are for VS = 18 V. Rev. B | Page 3 of 16 AD8614/AD8644 ABSOLUTE MAXIMUM RATINGS THERMAL RESISTANCE Table 2. Parameter Supply Voltage Input Voltage Storage Temperature Range Operating Temperature Range Junction Temperature Range Lead Temperature Range (Soldering, 60 sec) Rating 20 V GND to VS −65°C to +150°C −20°C to +85°C −65°C to +150°C 300°C Stresses above those listed under Absolute Maximum Ratings may cause permanent damage to the device. This is a stress rating only; functional operation of the device at these or any other conditions above those indicated in the operational section of this specification is not implied. Exposure to absolute maximum rating conditions for extended periods may affect device reliability. θJA is specified for the worst-case conditions, that is, a device soldered in a circuit board for surface-mount packages. Table 3. Thermal Resistance Package Type 5-Lead SOT-23 (RJ) 14-Lead TSSOP (RU) 14-Lead SOIC (R) ESD CAUTION Rev. B | Page 4 of 16 θJA 230 180 120 θJC 140 35 56 Unit °C/W °C/W °C/W AD8614/AD8644 TYPICAL PERFORMANCE CHARACTERISTICS 45 6.5 40 5.5 35 4.5 VOLTAGE (1V/DIV) SMALL SIGNAL OVERSHOOT (%) 7.5 VS = 18V RL = 2kΩ TA = 25°C 30 25 20 15 +OS 10 3.5 2.5 1.5 0.5 –0.5 06485-004 –OS 5 0 10 VS = 5V RL = 2kΩ CL = 200pF AV = 1 TA = 25°C 100 1k 06485-007 50 –1.5 –2.5 10k TIME (1µs/DIV) CAPACITANCE (pF) Figure 7. Large Signal Transient Response, VS = 5 V Figure 4. Small Signal Overshoot vs. Load Capacitance 29 12 25 21 0.1% 0.01% VOLTAGE (4V/DIV) 4 0 –4 0.1% 13 9 5 1 0.01% –3 06485-005 –8 –12 17 0 0.5 1.0 1.5 2.0 2.5 3.0 06485-008 OUTPUT SWING FROM 0 TO ±V 8 VS = 18V RL = 2kΩ CL = 200pF AV = 1 TA = 25°C –7 –11 3.5 TIME (1µs/DIV) SETTLING TIME (µs) Figure 8. Large Signal Transient Response, VS = 18 V Figure 5. Output Swing vs. Settling Time 80 180 VS 2 VS = 5V ≤ VS ≤ 18V RL = 2kΩ CL = 200pF AV = 1 TA = 25°C 06485-009 0 135 06485-006 GAIN (dB) 5V ≤ VS ≤ 18V RL = 1MΩ CL = 40pF TA = 25°C 20 VOLTAGE (50mV/DIV) 90 40 PHASE SHIFT (Degrees) 45 60 1k 10k 100k 1M 10M TIME (500ns/DIV) 100M FREQUENCY (Hz) Figure 9. Small Signal Transient Response Figure 6. Open-Loop Gain and Phase Shift vs. Frequency Rev. B | Page 5 of 16 AD8614/AD8644 10k 400 VS = ±9V 300 INPUT BIAS CURRENT (nA) 1k 100 SINK SOURCE 1 0.001 0.01 0.1 1 10 200 100 0 –100 –200 –300 06485-013 10 06485-010 ΔOUTPUT VOLTAGE (mV) 5V ≤ VS ≤ 18V TA = 25°C –400 –9 100 –7 –5 LOAD CURRENT (mA) Figure 10. Output Voltage to Supply Rail vs. Load Current 1 3 5 7 9 2.5V ≤ VS ≤ 9V TA = 25°C 160 QUANTITY (Amplifiers) 140 700 600 500 400 300 120 100 80 60 40 200 100 0 1 2 3 4 5 6 7 8 9 0 10 06485-014 20 06485-011 SUPPLY CURRENT/AMPLIFIER (µA) 0 180 TA = 25°C 800 0 –1 Figure 13. Input Bias Current vs. Common-Mode Voltage, VS = ±9 V 1000 900 –3 COMMON-MODE VOLTAGE (V) –2.0 –1.5 SUPPLY VOLTAGE (±V) –1.0 –0.5 0 0.5 1.0 1.5 2.0 INPUT OFFSET VOLTAGE (mV) Figure 11. Supply Current vs. Supply Voltage Figure 14. Input Offset Voltage Distribution 400 1.0 VS = ±2.5V 200 100 0 –100 –200 –400 –2.5 06485-012 –300 –1.5 –0.5 0.5 1.5 0.9 0.8 0.7 VS = 5V 0.6 0.5 –35 2.5 COMMON-MODE VOLTAGE (V) VS = 18V 06485-015 SUPPLY CURRENT/AMPLIFIER (mA) INPUT BIAS CURRENT (nA) 300 –15 5 25 45 65 TEMPERATURE (°C) Figure 12. Input Bias Current vs. Common-Mode Voltage, VS = ±2.5 V Figure 15. Supply Current vs. Temperature Rev. B | Page 6 of 16 85 AD8614/AD8644 6 5V ≤ VS ≤ 18V TA = 25°C 4 40 VS = 5V AVCL = 1 RL = 2kΩ TA = 25°C GAIN (dB) OUTPUT SWING (V p-p) 5 3 20 0 2 06485-016 0 100 06485-019 1 1k 10k 100k 1M 1k 10M 10k Figure 16. Maximum Output Swing vs. Frequency, VS = 5 V 10 8 6 06485-017 4 2 1k 10k 100k 1M 120 5V ≤ VS ≤ 18V TA = 25°C 100 80 60 40 20 0 100 10M 1k FREQUENCY (Hz) 1M 100 240 180 120 60 AV = 1 06485-018 AV = 10 AV = 100 100k 10M 1M VS = 18V TA = 25°C 80 60 PSRR+ 40 PSRR– 20 0 100 10M FREQUENCY (Hz) 06485-021 POWER SUPPLY REJECTION (dB) 5V ≤ VS ≤ 18V TA = 25°C IMPEDANCE (Ω) 100k Figure 20. Common-Mode Rejection vs. Frequency 300 10k 10k FREQUENCY (Hz) Figure 17. Maximum Output Swing vs. Frequency, VS = 18 V 0 1k 100M 06485-020 COMMON-MODE REJECTION (dB) OUTPUT SWING (V p-p) VS = 18V AVCL = 1 RL = 2kΩ TA = 25°C 12 0 100 10M 140 18 14 1M Figure 19. Closed-Loop Gain vs. Frequency 20 16 100k FREQUENCY (Hz) FREQUENCY (Hz) 1k 10k 100k 1M FREQUENCY (Hz) Figure 18. Closed-Loop Output Impedance vs. Frequency Figure 21. Power Supply Rejection vs. Frequency Rev. B | Page 7 of 16 10M AD8614/AD8644 100 9 VS = 18V TA = 25°C 6 SR– 5 4 3 2 0 0 2 4 06485-022 AV = 1 RL = 2kΩ CL = 200pF TA = 25°C 1 6 8 10 12 14 16 18 1 10 20 SUPPLY VOLTAGE (V) 06485-023 VOLTAGE NOISE DENSITY (nV/ Hz) VS = 5V TA = 25°C 100 1k Figure 24. Voltage Noise Density vs. Frequency, VS = 18 V 10 1 10 100 FREQUENCY (Hz) Figure 22. Slew Rate vs. Supply Voltage 100 10 06485-024 SR+ 7 SLEW RATE (V/µs) VOLTAGE NOISE DENSITY (nV/ Hz) 8 1k 10k FREQUENCY (Hz) Figure 23. Voltage Noise Density vs. Frequency, VS = 5 V Rev. B | Page 8 of 16 10k AD8614/AD8644 THEORY OF OPERATION Figure 26 shows a simplified schematic of the AD8614/AD8644. The input stage is rail-to-rail, consisting of two complementary differential pairs, one NPN pair and one PNP pair. The input stage is protected against avalanche breakdown by two back-toback diodes. Each input has a 1.5 kΩ resistor that limits input current during overvoltage events and furnishes phase reversal protection if the inputs are exceeded. The two differential pairs are connected to a double-folded cascode. This is the stage in the amplifier with the most gain. The double-folded cascode differentially feeds the output stage circuitry. Two complementary common emitter transistors are used as the output stage. This allows the output to swing to within 125 mV from each rail with a 10 mA load. The gain of the output stage, and thus the open-loop gain of the op amp, depends on the load resistance. OUTPUT SHORT-CIRCUIT PROTECTION To achieve a wide bandwidth and high slew rate, the output of the AD8614/AD8644 is not short-circuit protected. Shorting the output directly to ground or to a supply rail can destroy the device. The typical maximum safe output current is 70 mA. In applications where some output current protection is needed, but not at the expense of reduced output voltage headroom, a low value resistor in series with the output can be used. This is shown in Figure 25. The resistor is connected within the feedback loop of the amplifier so that if VOUT is shorted to ground and VIN swings up to 18 V, the output current does not exceed 70 mA. For 18 V single-supply applications, resistors less than 261 Ω are not recommended. The AD8614/AD8644 have no built-in short-circuit protection. The short-circuit limit is a function of high current roll-off of the output stage transistors and the voltage drop over the resistor shown on the schematic at the output stage. The voltage over this resistor is clamped to one diode during short-circuit voltage events. 18V VIN AD86x4 261Ω VOUT 06485-026 The AD8614/AD8644 are processed using Analog Devices high voltage, extra fast complementary bipolar (HV XFCB) process. This process includes trench-isolated transistors that lower parasitic capacitance. Figure 25. Output Short-Circuit Protection VCC 1.5kΩ + VCC VCC VOUT 06485-025 – 1.5kΩ VEE Figure 26. Simplified Schematic Rev. B | Page 9 of 16 AD8614/AD8644 OUTPUT PHASE REVERSAL The AD8614/AD8644 are immune to phase reversal as long as the input voltage is limited to within the supply rails. Although the device’s output does not change phase, large currents due to input overvoltage can result, damaging the device. In applications where the possibility of an input voltage exceeding the supply voltage exists, overvoltage protection should be used, as described in the previous section. TJ = PDISS × θJA + TA where: TJ is the AD8614/AD8644 junction temperature. PDISS is the AD8614/AD8644 power dissipation. θJA is the AD8614/AD8644 junction-to-ambient package thermal resistance. TA is the ambient temperature of the circuit. The power dissipated by the device can be calculated as: PDISS = ILOAD × (VS – VOUT) where: ILOAD is the AD8614/AD8644 output load current. VS is the AD8614/AD8644 supply voltage. VOUT is the AD8614/AD8644 output voltage. Figure 27 provides a convenient way to determine if the device is being overheated. The maximum safe power dissipation can be found graphically, based on the package type and the ambient temperature around the package. By using the previous equation, it is a simple matter to see if PDISS exceeds the device’s power derating curve. To ensure proper operation, it is important to observe the recommended derating curves shown in Figure 27. 1.5 POWER DISSIPATION The maximum power that can be safely dissipated by the AD8614/AD8644 is limited by the associated rise in junction temperature. The maximum safe junction temperature is 150°C, and should not be exceeded or device performance could suffer. If this maximum is momentarily exceeded, proper circuit operation is restored as soon as the die temperature is reduced. Leaving the device in an overheated condition for an extended period can result in permanent damage to the device. 14-LEAD SOIC PACKAGE θJA = 120°C/W 1.0 14-LEAD TSSOP PACKAGE θJA = 180°C/W 0.5 5-LEAD SOT-23 PACKAGE θJA = 230°C/W 0 –35 06485-027 As with any semiconductor device, whenever the condition exists for the input to exceed either supply voltage, attention needs to be paid to the input overvoltage characteristic. As an overvoltage occurs, the amplifier can be damaged, depending on the voltage level and the magnitude of the fault current. When the input voltage exceeds either supply by more than 0.6 V, internal pin junctions energize, allowing current to flow from the input to the supplies. Observing Figure 26, the AD8614/AD8644 have 1.5 kΩ resistors in series with each input, which helps to limit the current. This input current is not inherently damaging to the device as long as it is limited to 5 mA or less. If the voltage is large enough to cause more than 5 mA of current to flow, an external series resistor should be added. The size of this resistor is calculated by dividing the maximum overvoltage by 5 mA and subtracting the internal 1.5 kΩ resistor. For example, if the input voltage could reach 100 V, the external resistor should be (100 V ÷ 5 mA) – 1.5 kΩ = 18.5 kΩ. This resistance should be placed in series with either or both inputs if they are subjected to the overvoltages. To calculate the internal junction temperature of the AD8614/AD8644, the following formula can be used: MAXIMUM POWER DISSIPATION (W) INPUT OVERVOLTAGE PROTECTION –15 5 25 45 AMBIENT TEMPERATURE (°C) 65 85 Figure 27. Maximum Power Dissipation vs. Temperature (5-Lead and 14-Lead Package Types) UNUSED AMPLIFIERS It is recommended that any unused amplifiers in the quad package be configured as a unity-gain follower with a 1 kΩ feedback resistor connected from the inverting input to the output, and the noninverting input tied to the ground plane. Rev. B | Page 10 of 16 AD8614/AD8644 P1 Tx GAIN ADJUST CAPACITIVE LOAD DRIVE When driving heavy capacitive loads directly from the AD8614/AD8644 output, a snubber network can be used to improve the transient response. This network consists of a series R-C connected from the amplifier’s output to ground, placing it in parallel with the capacitive load. The configuration is shown in Figure 28. Although this network does not increase the bandwidth of the amplifier, it does significantly reduce the amount of overshoot. TO TELEPHONE LINE 2 1 A1 6.2V 5V DC T1 MIDCOM 671-8005 R6 10kΩ 6 7 A2 R7 10kΩ 5 R8 10kΩ 10µF R9 10kΩ R10 10kΩ 2 R11 10kΩ 5V A1, A2 = 1/2 AD8644 A3, A4 = 1/2 AD8644 TRANSMIT TxA 3 R5 10kΩ 6.2V ZO 600Ω C1 R1 10kΩ 0.1µF 2kΩ R3 360Ω 1:1 R2 9.09kΩ 3 1 A3 P2 Rx GAIN ADJUST R14 14.3kΩ R13 10kΩ 2kΩ 6 R12 10kΩ 5 A4 7 RECEIVE RxA C2 0.1µF 06485-029 The AD8614/AD8644 exhibit excellent capacitive load driving capabilities. Although the device is stable with large capacitive loads, there is a decrease in amplifier bandwidth as the capacitive load increases. Figure 29. A Single-Supply Direct Access Arrangement for Modems RX CX A ONE-CHIP HEADPHONE/MICROPHONE PREAMPLIFIER SOLUTION CL 06485-028 VIN VOUT Figure 28. Snubber Network Compensation for Capacitive Loads The optimum values for the snubber network should be determined empirically based on the size of the capacitive load. Table 4 shows a few sample snubber network values for a given load capacitance. Table 4. Snubber Networks for Large Capacitive Loads Load Capacitance (CL) 0.47 nF 4.7 nF 47 nF Because of its high output current performance, the AD8644 makes an excellent amplifier for driving an audio output jack in a computer application. Figure 30 shows how the AD8644 can be interfaced with an ac codec to drive headphones or speakers. 5V 5V AVDD1 25 VREFOUT 28 U1-A Snubber Network (RX, CX) 300 Ω, 0.1 μF 30 Ω, 1 μF 5 Ω, 10 μF LINE_OUT_L 35 C1 100µF + 10 2 1 4 3 R3 20Ω R1 2kΩ 5 AD1881A (AC'97) DIRECT ACCESS ARRANGEMENT 6 Figure 29 shows a schematic for a 5 V single-supply transmit/ receive telephone line interface for 600 Ω transmission systems. It allows full duplex transmission of signals on a transformercoupled 600 Ω line. Amplifier A1 provides gain that can be adjusted to meet the modem’s output drive requirements. Both A1 and A2 are configured to apply the largest possible differential signal to the transformer. The largest signal available on a single 5 V supply is approximately 4.0 V p-p into a 600 Ω transmission system. Amplifier A3 is configured as a difference amplifier to extract the receive information from the transmission line for amplification by A4. A3 also prevents the transmit signal from interfering with the receive signal. The gain of A4 can be adjusted in the same manner as A1 to meet the modem input signal requirements. Standard resistor values permit the use of single in-line package (SIP) format resistor arrays. Couple this with the AD8644 14-lead SOIC or TSSOP package and this circuit can offer a compact solution. LINE_OUT_R 36 C2 100µF + 7 U1-B AVSS1 26 9 8 R4 20Ω R2 2kΩ U1 = AD8644 NOTES 1. ADDITIONAL PINS OMITTED FOR CLARITY. Rev. B | Page 11 of 16 Figure 30. A PC-99-Compliant Headphone/Line Out Amplifier 06485-030 AD86x4 AD8614/AD8644 current from the headphones and create a high-pass filter with a corner frequency of If gain is required from the output amplifier, four additional resistors should be added as shown in Figure 31. 5V AVDD1 f −3 dB = R6 20kΩ 25 5V AVDD2 38 LINE_OUT_L 35 R5 10kΩ C1 100µF + 10 2 U1-A 1 4 3 where RL is the resistance of the headphones. R3 20Ω The remaining two amplifiers can be used as low voltage microphone preamplifiers. A single AD8614 can be used as a standalone microphone preamplifier. Figure 32 shows this implementation. R1 2kΩ 5 VREF 27 10kΩ AD1881A (AC'97) AVSS1 26 C2 100µF + 7 U1-B 9 8 R6 20kΩ 5V AV = 20dB 6 R5 10kΩ LINE_OUT_R 36 1 2πC1(R4 + R L ) 1kΩ R4 20Ω 1µF + 2.2kΩ MIC1 21 MIC 1 R2 2kΩ AD1881A (AC'97) U1 = AD8644 10kΩ 5V AV = 20dB 1kΩ R6 06485-031 AV = = +6dB WITH VALUES SHOWN R5 NOTES 1. ADDITIONAL PINS OMITTED FOR CLARITY. 1µF + 2.2kΩ MIC2 22 MIC 2 VREF 27 The gain of the AD8644 can be set as AV = 06485-032 Figure 31. A PC-99-Compliant Headphone/Speaker Amplifier with Gain Figure 32. Microphone Preamplifier R6 R5 Input coupling capacitors are not required for either circuit as the reference voltage is supplied from the AD1881A. The resistors R4 and R5 help protect the AD8644 output in case the output jack or headphone wires are accidentally shorted to ground. The output coupling capacitors C1 and C2 block dc Rev. B | Page 12 of 16 AD8614/AD8644 OUTLINE DIMENSIONS 5.10 5.00 4.90 2.90 BSC 5 4 14 2.80 BSC 1.60 BSC 1 2 PIN 1 6.40 BSC 0.95 BSC 1 1.90 BSC 1.30 1.15 0.90 7 PIN 1 1.45 MAX 0.15 MAX 8 4.50 4.40 4.30 3 0.50 0.30 0.65 BSC 1.05 1.00 0.80 0.22 0.08 10° 5° 0° SEATING PLANE 1.20 MAX 0.15 0.05 0.60 0.45 0.30 0.30 0.19 0.20 0.09 SEATING COPLANARITY PLANE 0.10 8° 0° COMPLIANT TO JEDEC STANDARDS MO-153-AB-1 COMPLIANT TO JEDEC STANDARDS MO-178-AA Figure 33. 5-Lead Small Outline Transistor Package [SOT-23] (RJ-5) Dimensions shown in millimeters Figure 34. 14-Lead Thin Shrink Small Outline Package [TSSOP] (RU-14) Dimensions shown in millimeters 8.75 (0.3445) 8.55 (0.3366) 8 14 1 7 1.27 (0.0500) BSC 0.25 (0.0098) 0.10 (0.0039) COPLANARITY 0.10 0.51 (0.0201) 0.31 (0.0122) 6.20 (0.2441) 5.80 (0.2283) 0.50 (0.0197) 0.25 (0.0098) 1.75 (0.0689) 1.35 (0.0531) SEATING PLANE 45° 8° 0° 0.25 (0.0098) 0.17 (0.0067) 1.27 (0.0500) 0.40 (0.0157) COMPLIANT TO JEDEC STANDARDS MS-012-AB CONTROLLING DIMENSIONS ARE IN MILLIMETERS; INCH DIMENSIONS (IN PARENTHESES) ARE ROUNDED-OFF MILLIMETER EQUIVALENTS FOR REFERENCE ONLY AND ARE NOT APPROPRIATE FOR USE IN DESIGN. Figure 35. 14-Lead Standard Small Outline Package [SOIC_N] Narrow Body (R-14) Dimensions shown in millimeters and (inches) Rev. B | Page 13 of 16 060606-A 4.00 (0.1575) 3.80 (0.1496) 0.75 0.60 0.45 AD8614/AD8644 ORDERING GUIDE Model AD8614ART-R2 AD8614ART-REEL AD8614ART-REEL7 AD8614ARTZ-REEL 1 AD8614ARTZ-REEL71 AD8644AR AD8644AR-REEL AD8644AR-REEL7 AD8644ARZ1 AD8644ARZ-REEL1 AD8644ARZ-REEL71 AD8644ARU AD8644ARU-REEL AD8644ARUZ1 AD8644ARUZ-REEL1 1 Temperature Range –20°C to +85°C –20°C to +85°C –20°C to +85°C –20°C to +85°C –20°C to +85°C –20°C to +85°C –20°C to +85°C –20°C to +85°C –20°C to +85°C –20°C to +85°C –20°C to +85°C –20°C to +85°C –20°C to +85°C –20°C to +85°C –20°C to +85°C Package Description 5-Lead SOT-23 5-Lead SOT-23 5-Lead SOT-23 5-Lead SOT-23 5-Lead SOT-23 14-Lead SOIC_N 14-Lead SOIC_N 14-Lead SOIC_N 14-Lead SOIC_N 14-Lead SOIC_N 14-Lead SOIC_N 14-Lead TSSOP 14-Lead TSSOP 14-Lead TSSOP 14-Lead TSSOP Z = RoHS Compliant Part. Rev. B | Page 14 of 16 Package Option RJ-5 RJ-5 RJ-5 RJ-5 RJ-5 R-14 R-14 R-14 R-14 R-14 R-14 RU-14 RU-14 RU-14 RU-14 Branding A6A A6A A6A A0Z A0Z AD8614/AD8644 NOTES Rev. B | Page 15 of 16 AD8614/AD8644 NOTES ©1999–2007 Analog Devices, Inc. All rights reserved. Trademarks and registered trademarks are the property of their respective owners. D06485-0-9/07(B) Rev. B | Page 16 of 16