ISL8225M Datasheet

DATASHEET
Dual 15A/Single 30A Step-Down Power Module
ISL8225M
Features
The ISL8225M is a fully-encapsulated step-down switching
power supply that can deliver up to 100W output power from a
small 17mm square PCB footprint. The two 15A outputs may
be used independently or combined to deliver a single 30A
output. Designing a high-performance board mounted power
supply has never been simpler -- only a few external
components are needed to create a very dense and reliable
power solution.
• Fully-encapsulated dual step-down switching power supply
Automatic current sharing and phase interleaving allow up to
six modules to be paralleled for 180A output capability. 1.5%
output voltage accuracy, differential remote voltage sensing
and fast transient response create a very high-performance
power system. Built-in output overvoltage, overcurrent and
over-temperature protection enhance system reliability.
The ISL8225M is available in a thermally-enhanced QFN
package. Excellent efficiency and low thermal resistance
permit full power operation without heat sinks or fans. In
addition, the QFN package with external leads permits easy
probing and visual solder inspection.
• AN1789 “ISL8225MEVAL2Z Evaluation Board User Guide”
• AN1790 “ISL8225MEVAL3Z Evaluation Board User Guide”
• AN1793, “ISL8225MEVAL4Z Evaluation Board User Guide”
• ISL8225M 110A Thermal Performance Video
4.5V TO 20V
4x22µF
VIN1
VIN2
OFF ON
VSEN1+
EN/FF2
VSEN2-
VSEN1ISL8225M
PGND
SGND
MODE
• Up to 95% conversion efficiency
• 4.5V to 20V input voltage range
• 0.6V to 7.5V output voltage range
• 1.5% output voltage accuracy with differential remote
sensing
• Up to six modules may be paralleled to support 180A output
current
• Output overvoltage, overcurrent and over-temperature
protection
• Full power operation without heat sinks or fans
• QFN package with exposed leads permits easy probing and
visual solder inspection
• Computing, networking and telecom infrastructure
equipment
• Industrial and medical equipment
• General purpose point-of-load (POL) power
17m
m
17
mm
1kΩ
RSET
1kΩ
5x100µF
7.5mm
VMON1
VMON2
VCC
4.7µF
1.2V AT 30A
VOUT
VOUT1
VOUT2
EN/FF1
• Dual 15A or single 30A output
Applications
Related Literature
VIN
• Up to 100W output from a 17mmx17mm square PCB
footprint
COMP1
COMP2
470pF
NOTE: ALL PINS NOT SHOWN ARE FLOATING.
FIGURE 1. COMPLETE 30A STEP-DOWN POWER SUPPLY
December 8, 2014
FN7822.2
1
FIGURE 2. SMALL FOOTPRINT WITH HIGH POWER DENSITY
CAUTION: These devices are sensitive to electrostatic discharge; follow proper IC Handling Procedures.
1-888-INTERSIL or 1-888-468-3774 | Copyright Intersil Americas LLC 2012-2014. All Rights Reserved
Intersil (and design) is a trademark owned by Intersil Corporation or one of its subsidiaries.
All other trademarks mentioned are the property of their respective owners.
ISL8225M
Table of Contents
Pinout Internal Circuit. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 3
Ordering Information . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 4
Pin Descriptions. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 6
Absolute Maximum Ratings . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 7
Thermal Information . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 7
Recommended Operating Conditions . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 7
Electrical Specifications . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 7
Typical Performance Characteristics . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
Efficiency Performance. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
Transient Response Performance . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
Start-up and Short Circuit Performance . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
10
10
11
12
Typical Application Circuits . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 13
Application Information . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
Programming the Output Voltage . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
Selection of Input Capacitor . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
Selection of Output Capacitors . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
EN/FF Turn ON/OFF. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
Thermal Considerations . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
22
22
22
23
23
23
Functional Description . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
Initialization . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
Enable and Voltage Feed-forward . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
Soft-Start. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
Power-Good . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
Current Share . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
Overvoltage Protection (OVP) . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
Over-Temperature Protection (OTP) . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
Overcurrent Protection (OCP) . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
Frequency Synchronization and Phase Lock Loop . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
Tracking Function . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
Mode Programming. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
Two Phase Parallel Mode Operation . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
Layout Guide . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
Current Derating . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
23
23
23
24
24
25
25
25
25
25
26
26
27
27
28
Package Description . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
PCB Layout Pattern Design . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
Thermal Vias. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
Stencil Pattern Design . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
28
28
28
28
Derating Curves . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 29
Reflow Parameters . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 31
Revision History. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 32
About Intersil . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 32
Package Outline Drawing . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 33
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2
FN7822.2
December 8, 2014
ISL8225M
Pinout Internal Circuit
VCC
7
FILTER
2.2µF
14
VIN1
15
EN/FF1
12
PHASE1
23
VOUT1
13
PGND
22
VSEN1+
21
VSEN1-
18
VMON1
20
COMP1
8
VIN2
16
EN/FF2
10
PHASE2
25
VOUT2
9
PGND
+
26
VSEN2+
-
1
VSEN2-
4
VMON2
2
COMP2
LDO
PGOOD
SOFT-START
AND FAULT
LOGIC
UGATE1
24
GATE
DRIVER
CLKOUT
17
ISHARE
19
Q1
L1
LGATE1
0.32µH
Q2
CURRENT
SENSING/
SHARING
10k
ISEN1B
ISEN1A
+
MODE
DIFF
AMP1
3
-
ZCOMP1
-
5
INTERNAL
REFERENCE
ERROR
AMP1
+
SYNC
ZCOMP2
SOFT-START
AND FAULT
LOGIC
UGATE2
GATE
DRIVER
Q3
L2
0.32µH
LGATE2
Q4
CURRENT ISEN2B
SENSING/
SHARING ISEN2A
SGND
DIFF
AMP2
6
ZCOMP3
ZCOMP4
-
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3
MODE
+
INTERNAL
REFERENCE
ERROR
AMP2
7.5k
FN7822.2
December 8, 2014
ISL8225M
Ordering Information
PART NUMBER
(Notes 2, 3)
PART
MARKING
TEMP RANGE (°C)
(Note 4)
PACKAGE
(RoHS Compliant)
PKG.
DWG. #
ISL8225MIRZ
ISL8225M
-40 to +125
26 Ld QFN
L26.17x17
ISL8225MIRZ-T (Note 1)
ISL8225M
-40 to +125
26 Ld QFN
L26.17x17
ISL8225MEVAL2Z
6 Phase 90A Evaluation Board
ISL8225MEVAL3Z
Dual Phase Single Output 30A Evaluation Board
ISL8225MEVAL4Z
Dual 15A/optional 30A Cascadable Evaluation Board
NOTES:
1. Please refer to TB347 for details on reel specifications.
2. These Intersil plastic packaged products are RoHS compliant by EU exemption 7C-I and employ special Pb-free material sets, molding compounds/die
attach materials, and 100% matte tin plate plus anneal (e3) termination finish which is compatible with both SnPb and Pb-free soldering operations.
Intersil RoHS compliant products are MSL classified at Pb-free peak reflow temperatures that meet or exceed the Pb-free requirements of IPC/JEDEC
J STD-020.
3. For Moisture Sensitivity Level (MSL), please see device information page for ISL8225M. For more information on MSL, please see tech brief TB363
4. The ISL8225M is guaranteed over the full -40°C to +125°C internal junction temperature range. Note that the allowed ambient temperature
consistent with these specifications is determined by specific operating conditions, including board layout, cooling scheme and other environmental
factors.
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4
FN7822.2
December 8, 2014
ISL8225M
Pin Configuration
VIN2
VCC
SGND
SYNC
VMON2
MODE
COMP2
8
7
6
5
4
3
2
PIN 1
1
VSEN2-
26
VSEN2+
25
VOUT2
24
PGOOD
23
VOUT1
22
VSEN1+
21
VSEN1-
5
13
14
15
16
17
18
19
20
CLKOUT
VMON1
ISHARE
COMP1
12
EN/FF2
PHASE1
EN/FF1
11
VIN1
10
N/C
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9
PGND
PHASE2
PGND
ISL8225M
(26 LD QFN)
TOP VIEW
FN7822.2
December 8, 2014
ISL8225M
Pin Descriptions
PIN#
PIN
NAME
TYPE
21, 1
VSEN1-, VSEN2-
I
20, 2
COMP1, COMP2 I/O Error amplifier outputs. Typically floating for dual-output use. For parallel use, a 470pF~1nF capacitor is recommended
on the COMP pins of each SLAVE phase to eliminate the coupling noise. All COMP pins of SLAVE phases need to tie to
MASTER phase COMP1 pin (first phase). Internal compensation networks are implemented for working in the full range
of I/O conditions.
3
18, 4
MODE
I
DESCRIPTION
Output voltage negative feedback. Negative input of the differential remote sense for the regulator. Connect to the
negative rail or ground of the load/processor, as shown in Figure 19. The negative feedback pins can be used to
program the module operation conditions. See Tables 3 and 5 for details.
Mode setting. Typically floating for dual-output use; tie to SGND for parallel use. See Tables 3 and 5 for details. When
VSEN2- is pulled within 700mV of VCC, the 2nd channel’s remote sensing amplifier is disabled. The MODE pin, as well
as the VSEN2+ pin, determine relative phase-shift between the two channels and the CLKOUT signal output.
VMON1, VMON2 I/O Remote sensing amplifier outputs. These pins are connected internally to OV/UV/PGOOD comparators, so they can’t
be floated when the module works in multi-phase operation. When VSEN1-, VSEN2- are pulled within 700mV of VCC,
the corresponding remote sensing amplifier is disabled; the output (VMON pin) is in high impedance. In this event, the
VMON pins can be used as an additional monitor of the output voltage, with a resistor divider to protect the system
against single point of failure. The default setting voltage is 0.6V. See Table 3 for details.
5
SYNC
6
SGND
7
VCC
14, 8
VIN1, VIN2
9, 13
PGND
12, 10
PHASE1,
PHASE2
I
Signal synchronization. An optional external resistor (RSYNC) connected from this pin to SGND increases oscillator
switching frequency (Figure 33 and Table 1). The internal default frequency is 500kHz with this pin floating. Also, the
internal oscillator can lock to an external frequency source or the CLKOUT signal from another ISL8225M. Input voltage
range for external source: 3V to 5V square wave. No capacitor is recommended on this pin.
PWR Control signal ground. Connect to PGND under the module in the quiet inner layer. Make sure to have the single location
for the connection between SGND and PGND to avoid noise coupling. See “Layout Guide” on page 27.
PWR 5V internal linear regulator output. Voltage range: 3V to 5.6V. The decoupling ceramic capacitor for the VCC pin is
recommended to be 4.7µF.
PWR Power inputs. Input voltage range: 4.5V to 20V. Tie directly to the input rail. VIN1 provides power to the internal linear
drive circuitry. When the input is 4.5V to 5.5V, VIN should be tied directly to VCC.
PWR Power ground. Power ground pins for both input and output returns.
PWR Phase node. Use for monitoring switching frequency. Phase pins should be floating or used for snubber connections.To
achieve better thermal performance, the phase planes can also be used for heat removal with thermal vias connected
to large inner layers. See “Layout Guide” on page 27
11
N/C
15, 16
EN/FF1,
EN/FF2
I/O Enable and feed-forward control. Tie a resistor divider to VIN or use the system enable signal for this pin. The voltage
turn-on threshold is 0.8V. With a voltage lower than the threshold, the corresponding channel can be disabled
independently. By connecting to VIN with a resistor divider, the input voltage can be monitored for UVLO (undervoltage
lockout) function. The voltage on each EN/FF pin is also used to adjust the internal control loop gain independently to
realize the feed-forward function. Please set the EN/FF between 1.25V to 5V. A 1nF capacitor is recommended on each
EN/FF pin. Please see Table 1 to select resistor divider and application details in “EN/FF Turn ON/OFF” on page 23.
17
CLKOUT
I/O Clock out. Provide the clock signal for the input synchronization signal of other ISL8225Ms. Typically tied to VCC for
dual-output use with 180° phase-shift. See Tables 3 and 5 when using more than one ISL8225M. When the module is
in dual-output mode, the clock-out signal is disabled. By programming the voltage level of this CLKOUT pin, the module
can work for DDR/tracking or as two independent outputs with selectable phase-shift (see Table 6).
19
ISHARE
O
Current sharing control. Tie all ISHARE pins together when multiple modules are configured for current sharing and
share a common current output. The ISHARE voltage represents the average current of all active and connected
channels. A 470pF capacitor is recommended for each ISHARE pin for multiple phase applications. Typically, the
ISHARE pin should be floating for dual-output or single module application.
22, 26
VSEN1+,
VSEN2+
I
Output voltage positive feedback. Positive inputs of differential remote sense for the regulator. A resistor divider can
be connected to this pin to program the output voltage. It is recommended to put the resistor divider close to the
module and connect the kelvin sensing traces of VOUT and VSEN- to the sensing points of the load/processor (see
Figure 19). The VSEN2+ pin can be used to program the module operation conditions. See Tables 3 and 5 for details.
23, 25
24
-
Non-connection pin. This pin is floating with no connection inside.
VOUT1, VOUT2 PWR Power Output. Apply output load between these pins and PGND pins. Output voltage range: 0.6V to 7.5V.
PGOOD
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O
Power good. Provide open-drain power-good signal when the output is within 9% of the nominal output regulation point
with 4% hysteresis (13%/9%) and soft-start complete. PGOOD monitors the outputs (VMON) of the internal differential
amplifiers.
6
FN7822.2
December 8, 2014
ISL8225M
Absolute Maximum Ratings
Thermal Information
Input Voltage, VIN . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . -0.3V to +25V
Driver Bias Voltage, VCC . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . -0.3V to +6.5V
Phase Voltage, VPHASE . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . -0.3V to +30V
Input, Output or I/O Control Voltage . . . . . . . . . . . . . . . -0.3V to VCC + 0.3V
ESD Rating
Human Body Model (Tested per JESD22-A114E) . . . . . . . . . . . . . . . . 2kV
Machine Model (Tested per JESD22-A115-A) . . . . . . . . . . . . . . . . . 200V
Charge Device Model (Tested per JESD22-C101C). . . . . . . . . . . . . . 750V
Latch-up (Tested per JESD-78B; Class 2, Level A) . . . . . . . . . . . . . . 100mA
Thermal Resistance (Typical)
JA (°C/W) JC (°C/W)
QFN Package (Notes 5, 6) . . . . . . . . . . . . . .
10.0
0.9
Maximum Storage Temperature Range . . . . . . . . . . . . . .-55°C to +150°C
Pb-free Reflow Profile . . . . . . . . . . . . . . . . . . . . . . . . . . . . Refer to Figure 48
Recommended Operating Conditions
Input Voltage, VIN1 and VIN2 . . . . . . . . . . . . . . . . . . . . . . . . . . . 4.5V to 20.0V
Output Voltage, VOUT1 and VOUT2 . . . . . . . . . . . . . . . . . . . . . . . 0.6V to 7.5V
Junction Temperature Range . . . . . . . . . . . . . . . . . . . . . . .-40°C to +125°C
CAUTION: Do not operate at or near the maximum ratings listed for extended periods of time. Exposure to such conditions may adversely impact product
reliability and result in failures not covered by warranty.
NOTES:
5. JA is measured in free air with the component mounted on a high effective thermal conductivity test board with “direct attach” features. See Tech
Brief TB379.
6. For JC, the “case temp” location is the center of the phase exposed metal pad on the package underside.
Electrical Specifications TA = +25°C, VIN = 12V, unless otherwise noted. Boldface limits apply across the internal junction
temperature range, -40°C to +125°C (Note 4).
PARAMETER
SYMBOL
TEST CONDITIONS
MIN
TYP
(Note 7) (Note 8)
MAX
(Note 7)
UNITS
VCC SUPPLY CURRENT
Nominal Supply VIN Current
IQ_VIN
VIN = 20V; no load; EN1 = EN2 = high
131
mA
VIN1 = 20V; no load; EN1 = high, EN2 = low
72
mA
71
mA
VIN1 = 12V; no load; EN1 = high, EN2 = high
VIN2 = 20V; no load; EN1 = 0, EN2 = high
134
mA
VIN = 4.5V; no load; EN1 = EN2 = high
136
mA
VIN1 = 4.5V; no load; EN1 = high, EN2 = low
73
mA
VIN2 = 4.5V; no load; EN1 = 0, EN2 = high
70
mA
250
mA
1
Ω
INTERNAL LINEAR REGULATOR (Note 9)
Maximum Current
IPVCC
VCC = 4V to 5.6V
Saturated Equivalent Impedance
RLDO
P-Channel MOSFET (VIN = 5V)
VCC Voltage Level
VCC
IVCC = 0mA
5.1
5.4
5.6
V
POWER-ON RESET (Note 9)
Rising VCC Threshold
0°C to +75°C
2.85
2.97
V
-40°C to +85°C
2.85
3.05
V
2.65
2.75
Falling VCC Threshold
System Soft-start Delay
tSS_DLY
After PLL and VCC PORs, and EN above their
thresholds
384
V
Cycles
ENABLE (Note 9)
Turn-on Threshold Voltage
Hysteresis Sink Current
IEN_HYS
Undervoltage Lockout Hysteresis
VEN_HYS
VEN_RTH = 10.6V; VEN_FTH = 9V, RUP = 53.6kΩ,
RDOWN = 5.23kΩ
Sink Current
IEN_SINK
VENFF = 1V
Sink Impedance
REN_SINK
IEN_SINK = 5mA, VENFF = 1V
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7
0.75
0.8
0.86
V
23
30
35
µA
1.6
V
15.4
mA
64
Ω
FN7822.2
December 8, 2014
ISL8225M
Electrical Specifications TA = +25°C, VIN = 12V, unless otherwise noted. Boldface limits apply across the internal junction
temperature range, -40°C to +125°C (Note 4). (Continued)
PARAMETER
SYMBOL
TEST CONDITIONS
MIN
TYP
(Note 7) (Note 8)
MAX
(Note 7)
UNITS
OSCILLATOR
Oscillator Frequency
fOSC
SYNC pin is open
VCC = 5V; -40°C < TA < +85°C
Total Variation (Note 9)
510
-9
kHz
+9
%
1500
kHz
FREQUENCY SYNCHRONIZATION AND PHASE LOCK LOOP (Note 9)
Synchronization Frequency
VCC = 5V
PLL Locking Time
VCC = 5.4V, fSW = 500kHz
Input Signal Duty Cycle Range
300
130
10
µs
90
%
PWM (Note 9)
Minimum PWM OFF Time
310
tMIN_OFF
Current Sampling Blanking Time
345
410
175
tBLANKING
ns
ns
OUTPUT CHARACTERISTICS
Output Continuous Current Range
IOUT(DC)
VIN = 12V, VOUT1 = 1.5V
0
15
A
VIN = 12V, VOUT2 = 1.5V
0
15
A
VIN = 12V, VOUT = 1.5V, in Parallel mode
0
30
A
VOUT/VIN VIN = 4.5V to 20V
Line Regulation Accuracy
VOUT1 = 1.5V, IOUT1 = 0A
0.0065
%
VOUT2 = 1.5V, IOUT2 = 0A
0.0065
%
VOUT1 = 1.5V, IOUT1 = 15A
0.01
%
VOUT2 = 1.5V, IOUT2 = 15A
0.01
%
VIN = 4.5V to 20V
VOUT/VOUT VIN = 12V, 5x22µF, 2x4.7µF ceramic capacitor and
1x330µF POSCAP
Load Regulation Accuracy
VOUT
Output Ripple Voltage
IOUT1 = 0A to 15A, VOUT1 = 1.5V
0.3
1
%
IOUT2 = 0A to 15A, VOUT2 = 1.5V
0.3
1
%
VIN = 12V, 3x100µF ceramic capacitor and
1x330µF POSCAP
IOUT1 = 0A, VOUT1 = 1.5V
11
mVP-P
IOUT2 = 0A, VOUT2 = 1.5V
11
mVP-P
IOUT1 = 15A, VOUT1 = 1.5V
14
mVP-P
IOUT2 = 15A, VOUT2 = 1.5V
14
mVP-P
IOUT1 = 0A to 7.5A
75
mVP-P
IOUT2 = 0A to 7.5A
75
mVP-P
IOUT1 = 7.5A to 0A
70
mVP-P
IOUT2 = 7.5A to 0A
70
mVP-P
DYNAMIC CHARACTERISTICS
Voltage Change for Positive Load Step
Voltage Change for Negative Load Step
VOUT-DP
VOUT-DN
Current slew rate = 2.5A/µs
VIN = 12V, VOUT = 1.5V, 2x47µF ceramic capacitor
and 1x330µF POSCAP
Current slew rate = 2.5A/µs
VIN = 12V, VOUT = 1.5V, 2x47µF ceramic capacitor
and 1x330µF POSCAP
REFERENCE (Note 9)
Reference Voltage (Include Error and
Differential Amplifier Offsets)
VREF1
Reference Voltage (Include Error and
Differential Amplifier Offsets)
VREF2
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8
TA = -40°C to +85°C
0.5958
0.6
-0.7
TA = -40°C to +85°C
0.5955
-0.75
0.6
0.6042
V
0.7
%
0.6057
V
0.95
%
FN7822.2
December 8, 2014
ISL8225M
Electrical Specifications TA = +25°C, VIN = 12V, unless otherwise noted. Boldface limits apply across the internal junction
temperature range, -40°C to +125°C (Note 4). (Continued)
PARAMETER
SYMBOL
TEST CONDITIONS
MIN
TYP
(Note 7) (Note 8)
MAX
(Note 7)
UNITS
DIFFERENTIAL AMPLIFIER (Note 9)
DC Gain
UG_DA
Unity Gain Bandwidth
Unity gain amplifier
0
UGBW_DA
VSEN+ Pin Sourcing Current
IVSEN+
Maximum Source Current for Current Sharing
IVSEN1-
Input Impedance
RVSEN+_to
_VSEN-
5
0.2
1
MHz
2.5
µA
VSEN1- Source Current for Current Sharing when
parallel multiple modules, each of which has its
own voltage loop
350
µA
VVSEN+/IVSEN+, VVSEN+ = 0.6V
-600
kΩ
Output Voltage Swing
0
Input Common Mode Range
VCC - 1.8
VCC - 1.8
-0.2
Disable Threshold
dB
VVSEN-
VMON1, 2 = tri-state
Ilimit1
VIN = 12V, VOUT1 = 1.5V, RSYNC = Open
Ilimit2
VIN = 12V, VOUT2 = 1.5V, RSYNC = Open
V
V
VCC - 0.4
V
20
A
OVERCURRENT PROTECTION (Note 9)
Channel Overcurrent Limit
Share Pin OC Threshold
VOC_SET
VCC = 5V
(comparator offset included)
I/IOUT
VIN = 12V, VOUT = 1.5V
IOUT = 30A, VSEN2- = high
20
1.16
1.20
A
1.22
V
CURRENT SHARE
Current Share Accuracy
±10
%
POWER-GOOD MONITOR (Note 9)
Undervoltage Falling Trip Point
VUVF
Undervoltage Rising Hysteresis
VUVR_HYS
Overvoltage Rising Trip Point
VOVR
Overvoltage Falling Hysteresis
VOVF_HYS
Percentage below reference point
-15
-13
11
13
Percentage above UV trip point
Percentage above reference point
IPGOOD = 2mA
Sinking Impedance
IPGOOD = 2mA
Maximum Sinking Current
VPGOOD < 0.8V
%
15
%
4
Percentage below OV trip point
PGOOD Low Output Voltage
-11
%
4
%
0.35
70
10
V
Ω
mA
OVERVOLTAGE PROTECTION (Note 9)
OV Latching-up Trip Point
EN/FF = UGATE = LATCH Low, LGATE = High
OV Non Latching-up Trip Point
EN = Low, UGATE = Low, LGATE = High
LGATE Release Trip Point
EN = Low/HIGH, UGATE = Low, LGATE = Low
118
120
122
%
113
%
87
%
Over-Temperature Trip (Controller Junction
Temperature)
150
°C
Over-Temperature Release Threshold
(Controller Junction Temperature)
125
°C
OVER-TEMPERATURE PROTECTION (Note 9)
NOTES:
7. Compliance to datasheet limits is assured by one or more methods: production test, characterization and/or design.
8. Parameters with TYP limits are not production tested, unless otherwise specified.
9. Parameters are 100% tested for internal IC prior to module assembly.
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9
FN7822.2
December 8, 2014
ISL8225M
Typical Performance Characteristics
Efficiency Performance
TA = +25°C, if not specified, as shown in Figure 18 with 2nd phase disabled. The efficiency equation is
as follows:
 V OUT xI OUT 
P OUT
Output Power
Efficiency = ----------------------------------------- = ---------------- = -------------------------------------P IN
 V IN xI IN 
Input Power
100
3.3V
95
100
1.8V
2.5V
90
EFFICIENCY (%)
EFFICIENCY (%)
90
85
1V
80
1.5V
1.2V
75
70
85
80
70
65
60
60
55
55
0
2
4
6
8
10
LOAD CURRENT (A)
12
14
50
16
2.5V AT 500kHz
75
65
50
1.8V AT 500kHz
2
95
EFFICIENCY (%)
80
75
70
1.2V AT 500kHz
1.8V AT 500kHz
2.5V AT 500kHz
1.5V AT 500kHz
1V AT 500kHz
60
55
12
14
16
2.5VOUT
1.8VOUT
95
85
65
6
8
10
LOAD CURRENT (A)
FIGURE 4. EFFICIENCY vs LOAD CURRENT (12VIN)
5V AT 900kHz
90
EFFICIENCY (%)
4
6.5V AT 750kHz
7.5V AT 750kHz
1V AT 500kHz
7.5V AT 750kHz
0
100
100
1.2V AT 500kHz
1.5V AT 500kHz
6.5V AT 750kHz
FIGURE 3. EFFICIENCY vs LOAD CURRENT (5VIN AT 500kHz)
50
5V AT 850kHz
3.3V AT 650kHz
95
90
1.2VOUT
85
1.5VOUT
1VOUT
80
75
3.3V AT 650kHz
0
2
4
6
8
10
12
14
70
0
16
5
10
15
20
25
30
LOAD CURRENT (A)
LOAD CURRENT (A)
FIGURE 5. EFFICIENCY vs LOAD CURRENT (20VIN)
FIGURE 6. EFFICIENCY vs LOAD CURRENT (PARALLEL SINGLE
OUTPUT, AS SHOWN IN Figure 19 AT 5VIN/500kHz)
95
1.8VOUT
2.5VOUT
90
EFFICIENCY (%)
85
1.5VOUT
1.2VOUT
80
1VOUT
75
70
65
60
0
5
10
15
20
25
30
LOAD CURRENT (A)
FIGURE 7. EFFICIENCY vs LOAD CURRENT (PARALLEL SINGLE OUTPUT, AS SHOWN IN Figure 19 AT 12VIN/500kHz
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FN7822.2
December 8, 2014
ISL8225M
Typical Performance Characteristics (Continued)
Transient Response Performance VIN = 12V, COUT = 1x10µF and 3x100µF ceramic capacitors, IOUT = 0A to 7.5A, current
slew rate = 2.5A/µs. TA = +25°C, if not specified, as shown in Figure 18 with 2nd phase disabled.
50mV/DIV
50mV/DIV
50mV/DIV 2A/DIV
2A/DIV
2A/DIV
200µs/DIV
200µs/DIV
200uS/DIV FIGURE 8. 1VOUT TRANSIENT RESPONSE
FIGURE 9. 1.2VOUT TRANSIENT RESPONSE
50mV/DIV
50mV/DIV 50mV/DIV
50mV/DIV
2A/DIV 2A/DIV
2A/DIV
2A/DIV
200µs/DIV
200uS/DIV FIGURE 10. 1.5VOUT TRANSIENT RESPONSE
200µs/DIV
200uS/DIV FIGURE 11. 1.8VOUT TRANSIENT RESPONSE
50mV/DIV
50mV/DIV 100mV/DIV
100mV/DIV
2A/DIV 2A/DIV
2A/DIV
2A/DIV
200µs/DIV
200uS/DIV FIGURE 12. 2.5VOUT TRANSIENT RESPONSE
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11
200µs/DIV
200uS/DIV FIGURE 13. 3.3VOUT TRANSIENT RESPONSE
FN7822.2
December 8, 2014
ISL8225M
Typical Performance Characteristics (Continued)
Start-up and Short Circuit Performance
VIN = 12V, VOUT = 1.5V, CIN = 1x180µF, 2 x 10µF/Ceramic, COUT = 2x47µF and
1x330µF POSCAP. TA = +25°C, if not specified, as shown in Figure 18 with 2nd phase disabled.
VOUT
Vout VVout
OUT
0.5V/DIV
0.5V/DIV 0.5V/DIV
0.5V/DIV IIin IN
IIN
Iin
0.1A/DIV
0.1A/DIV 0.1A/DIV
1A/DIV 1ms/DIV 1ms/DIV
1ms/DIV
1ms/DIV FIGURE 14. START-UP AT 0A
FIGURE 15. START-UP AT 15A
V
Vout
OUT
VVout OUT
0.5V/DIV
0.5V/DIV 0.5V/DIV
0.5V/DIV IIin
IN
IIin IN
0.2A/DIV
0.2A/DIV 0.5A/DIV 0.5A/DIV
100us/DIV 100µs/DIV
FIGURE 16. SHORT CIRCUIT AT 0A
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12
100µs/DIV
100us/DIV FIGURE 17. SHORT CIRCUIT AT 15A
FN7822.2
December 8, 2014
ISL8225M
Typical Application Circuits
CIN1
330µF
+
CIN2
4x22µF
8
15
R5*
16
7
R6*
17
C1
4.7µF
3
19
*SEE Table 1 on page 19 FOR R5/R6
VALUES.
5
20
2
VIN1
VOUT1
VIN2
VSEN1+
EN/FF1
VSEN1-
EN/FF2
VOUT2
VCC
VSEN2+
CLKOUT
ISL8225M
VSEN2-
MODE
VMON1
ISHARE
VMON2
SYNC
PHASE1
COMP1
PHASE2
COMP2
6
PGND
14
SGND
4.5V TO 20V
VIN
PGOOD
23
22
21
CFF
(OPTIONAL)
R2*
1kΩ
R1*
1kΩ
COUT1
2x47µF
R3*
1kΩ
1.5V AT 15A
VOUT2
+
COUT4
330µF
COUT3
2x47µF
25
26
1
CFF
(OPTIONAL)
R4*
665Ω
1.2V AT 15A
VOUT1
+
COUT2
330µF
18
*SEE Table 4 on page 22, RESISTORS SET
ON VSEN+ AND VSEN- PINS.
4
12
10
24
9
SEE “LAYOUT GUIDE” ON PAGE 27 FOR SHORTING SGND TO PGND
FIGURE 18. DUAL OUTPUTS FOR 1.2V/15A AND 1.5V/15A
CIN1
330µF
+
CIN2
4x22µF
8
15
R3*
16
7
17
R4*
C1
4.7µF
3
19
*SEE Table 1 on page 19 FOR R3/R4
VALUES.
5
20
2
C2
470pF
VIN1
VOUT1
VIN2
VSEN1+
EN/FF1
VSEN1-
EN/FF2
VOUT2
VSEN2+
VCC
CLKOUT
ISL8225M
VSEN2-
MODE
VMON1
ISHARE
VMON2
21
26
1
9
COUT
5x100µF
LOAD
KELVIN REMOTE SENSING LINES
VCC
18
4
12
PHASE2 10
6
R1
1kΩ
R2
665Ω
25
COMP1
PGOOD
VOUT
22
PHASE1
COMP2
1.5V AT 30A
23
SYNC
PGND
14
SGND
4.5V TO 20V
VIN
24
2Ω
2200pF
SIZE:1210
2Ω
SIZE:1210
2200pF
OPTIONAL SNUBBER FOR NOISE
ATTENUATION. SEE Figure 34 on page 28.
SEE “LAYOUT GUIDE” ON PAGE 27 FOR SHORTING SGND TO PGND
FIGURE 19. PARALLEL USE FOR SINGLE 1.5V/30A OUTPUT WITH 180° INTERLEAVING
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13
FN7822.2
December 8, 2014
ISL8225M
Typical Application Circuits (Continued)
+
CIN1
330µF
14
8
CIN2
4x22µF
R5*
15
16
*SEE Table 1 on page 19 FOR
R5/R6 VALUES.
7
R6*
C1
4.7µF
17
3
VDDQ
19
R7
1kΩ
5
20
R8
324Ω
C2
1nF
2
VIN1
VOUT1
VIN2
VSEN1+
EN/FF1
VSEN1-
EN/FF2
VOUT2
VCC
VSEN2+
CLKOUT
VSEN2-
ISL8225M
MODE
VMON1
ISHARE
VMON2
SYNC
PHASE1
COMP1
PHASE2
COMP2
6
PGND
4.5V TO 20V
SGND
VIN
PGOOD
2.5V
23
VDDQ
R1
22
R2 1kΩ
316Ω
21
COUT1
3x100µF
1.25V VDDQ/2
VTT
25
R3
26
R4 1kΩ
931Ω
1
COUT2
3x100µF
18
4
12
10
24
9
*SET THE CLKOUT VOLTAGE CLOSE TO 0.612V.
SEE DETAILS IN “Functional Description” on page 23
FIGURE 20. DDR/TRACKING USE
CIN1
330µF
+
8
CIN2
4x22µF
R5
7.15kΩ
15
16
7
R6
2.05kΩ
C1
4.7µF
17
3
19
5
20
R7
88.7kΩ
2
VIN1
VOUT1
VIN2
VSEN1+
EN/FF1
VSEN1-
EN/FF2
VOUT2
VCC
VSEN2+
CLKOUT
VSEN2-
ISL8225M
MODE
VMON1
ISHARE
VMON2
SYNC
PHASE1
COMP1
PHASE2
COMP2
6
PGND
14
SGND
8V TO 20V
VIN
9
PGOOD
3.3V AT 10A
VOUT1
23
R1
22
R2 1kΩ
221Ω
21
COUT1
3x100µF
5V AT 10A
VOUT2
25
R3
26
R4 1kΩ
137Ω
1
COUT2
3x100µF
18
4
*SEE Figure 27 on page 22 FOR THE
FREQUENCY SETTING FOR I/O
CONDITIONS.
12
10
24
*SEE Figure 31, “RSYNC vs SWITCHING FREQUENCY,” ON
page 24 TO SELECT R7 FOR THE DESIRED FREQUENCY
OPERATION.
FIGURE 21. 3.3V/5V VOLTAGE APPLICATION WITH THE FREQUENCY SET AT 900kHz
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14
FN7822.2
December 8, 2014
ISL8225M
Typical Application Circuits (Continued)
+
CIN1
330µF
8
CIN2
8x22µF
R5
16.5kΩ
15
16
7
R6
4.12kΩ
17
C1
4.7µF
3
19
5
20
R7
147kΩ
2
VIN1
VOUT1
VIN2
VSEN1+
EN/FF1
VSEN1-
EN/FF2
VOUT2
VCC
VSEN2+
CLKOUT
VSEN2-
ISL8225M
MODE
VMON1
ISHARE
VMON2
SYNC
PHASE1
COMP1
PHASE2
COMP2
PGND
14
SGND
11V TO 20V
VIN
6
*SEE Figure 31, “RSYNC vs SWITCHING
PGOOD
6.5V AT 10A
VOUT1
23
R1
22
R2 1kΩ
102Ω
21
COUT1
6x47µF
7.5V AT 7A
VOUT2
25
R3
26
R4 1kΩ
86.6Ω
1
COUT2
6x47µF
18
4
*SEE Figure 27 on page 22 FOR THE
FREQUENCY SETTING FOR I/O
CONDITIONS.
12
10
24
9
FREQUENCY,” ON page 24 TO SELECT R7 FOR
THEDESIRED FREQUENCY OPERATION.
FIGURE 22. HIGH OUTPUT VOLTAGE APPLICATION WITH THE FREQUENCY SET AT 750kHz
CIN1
330µF
+
CIN2
8x22µF
8
15
R3
6.04kΩ
16
7
17
R4
2.05kΩ
C1
4.7µF
3
19
5
20
R7
147kΩ
2
C2
470pF
VIN1
VOUT1
VIN2
VSEN1+
EN/FF1
VSEN1-
EN/FF2
VOUT2
VSEN2+
VCC
CLKOUT
ISL8225M
VSEN2-
MODE
VMON1
ISHARE
VMON2
9
SEE “LAYOUT GUIDE” ON PAGE 27 FOR SHORTING SGND TO PGND
COUT1
5x47µF
LOAD
COUT2
330µF
25
26
1
KELVIN REMOTE SENSING LINES
VCC
18
4
2Ω
12
COMP1
6
1kΩ
R2
21 86.6Ω
PHASE2 10
PGOOD
VOUT
R1
22
PHASE1
COMP2
7.5 AT 14A
23
SYNC
PGND
14
SGND
15V TO 20V
VIN
2200pF
SIZE:1210
24
2Ω
SIZE:1210
2200pF
R8
953Ω
C3
22nF
OPTIONAL SNUBBER FOR NOISE
ATTENUATION. SEE Figure 34 on page 28.
FIGURE 23. PARALLEL USE FOR SINGLE OUTPUT WITH 240° INTERLEAVING
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15
FN7822.2
December 8, 2014
ISL8225M
Typical Application Circuits (Continued)
+
VIN1
CIN2
4x22µF
VOUT1
VIN2
VSEN1+
EN/FF1
VSEN1-
EN/FF2
VOUT2
R4*
VCC1
*SEE Table 1 on
page 19 FOR R3/R4
VALUES.
R3*
VSEN2+
VCC
C1
4.7µF
CLKOUT
ISL8225M
1.5V/60A
MASTER PHASE
VOUT1
R1
1kΩ
R2
665Ω
COUT1
4x100µF
SLAVE
VCC1
VSEN2-
MODE
VMON1
ISHARE
VMON2
SYNC
PHASE1
COMP1
PHASE2
COMP2
PGOOD
PGND
CIN1
2x470µF
4.5V TO 20V
SGND
VIN
VCC
C6
22nF
R8
953Ω
R5
3.3kΩ
PGOOD
C3
470pF
CIN2
4x22µF
VCC2
VIN1
VOUT1
VIN2
VSEN1+
EN/FF1
VSEN1-
EN/FF2
VOUT2
CLKOUT
ISL8225M
VMON1
ISHARE
VMON2
PHASE1
COMP1
PHASE2
COMP2
PGOOD
PGND
SYNC
C5
470pF
SLAVE
VSEN2-
MODE
SGND
C4
470pF
COUT2
4x100µF
VCC2
VSEN2+
VCC
C2
4.7µF
SLAVE
R6
1kΩ
C7
22nF
R7
665Ω
R9
953Ω
FIGURE 24. 4-PHASE PARALLELED AT 1.5V/60A WITH 90° INTERLEAVING
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16
FN7822.2
December 8, 2014
ISL8225M
Typical Application Circuits (Continued)
8
CIN1
4x22µF
R4*
*SEE Table 1
on page 19
FOR R3/R4
VALUES.
15
16
VCC1
R3*
C1
4.7µF
7
17
VCC
3
19
5
20
R7
100kΩ
2
8
15
CIN2
4x22µF
16
VCC2
7
17
C3
4.7µF
3
19
5
20
C4
470pF
2
VSEN1+
VIN2
EN/FF1
VSEN1-
EN/FF2
VOUT2
VCC
VSEN2+
CLKOUT
VSEN2-
ISL8225M
MODE
VMON1
ISHARE
VMON2
SYNC
PHASE1
COMP1
PHASE2
COMP2
PGOOD
C2
470pF
14
VOUT1
6
PGND
+
VIN1
VIN1
VOUT1
VIN2
VSEN1+
EN/FF1
VSEN1-
EN/FF2
VOUT2
VCC
VSEN2+
CLKOUT
VSEN2-
ISL8225M
MODE
VMON1
ISHARE
VMON2
SYNC
PHASE1
COMP1
PHASE2
COMP2
PGOOD
6
23
VOUT1
R1
22
21
1.5V/40A
MASTER PHASE
R2 1kΩ
316Ω
25
SLAVE
26
VCC1
COUT1
4x100µF
1
18
VCC1
4
12
10
R6
C5
22nF 953Ω
R5
3.3kΩ
24
PGOOD
9
PGND
2x470µF
14
SGND
4.5V TO 20V
SGND
VIN
23
SLAVE
COUT2
2x100µF
22
21
VCC2
5V/10A
25
26
1
18
4
12
VOUT2
R8
R9 1kΩ
137Ω
COUT3
3x100µF
R10
1kΩ
R11
316Ω
10
24
9
FIGURE 25. 3-PHASE PARALLELED AT 1.5V/40A AND 1-PHASE AT 5V/10A OUTPUT WITH 90° INTERLEAVING
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FN7822.2
December 8, 2014
ISL8225M
Typical Application Circuits (Continued)
8
15
16
VCC1
R3*
7
C1
4.7µF
EN/FF1
VSEN1- 21
EN/FF2
VOUT2
VCC
17
CLKOUT
3
19
5
ISHARE
VMON2
C8
470pF
8
15
16
7
17
C2
4.7µF
3
19
5
20
2
C3
470pF
14
8
15
16
7
VCC3
17
C5
4.7µF
3
19
5
20
2
C6
470pF
C7
470pF
PHASE2
6
9
PGOOD
VIN1
VOUT1
VIN2
VSEN1+
EN/FF1
VSEN1-
EN/FF2
VOUT2
VCC
VSEN2+
CLKOUT
ISL8225M
VSEN2-
MODE
VMON1
ISHARE
VMON2
SYNC
PHASE1
COMP1
PHASE2
6
9
COMP2
C4
470pF
CIN3
4x22µF
PHASE1
COMP2
14
VSEN2VMON1
COMP1
2
VCC2
ISL8225M
MODE
SYNC
20
CIN2
4x22µF
VSEN2+
PGND
*SEE Table 1 on page 19 FOR
R3/R4 VALUES.
VSEN1+
PGND
R4*
VIN2
PGOOD
VIN1
VOUT1
VIN2
VSEN1+
EN/FF1
VSEN1-
EN/FF2
VOUT2
VCC
VSEN2+
CLKOUT
ISL8225M
VSEN2-
MODE
VMON1
ISHARE
VMON2
SYNC
PHASE1
COMP1
PHASE2
COMP2
PGND
CIN1
4x22µF
VOUT1
SGND
+
23
VIN1
SGND
2x470µF
14
SGND
4.5V TO 20V
VIN
6
9
PGOOD
26
VOUT
R1
22
25
1.2V/90A
MASTER PHASE
R2 1kΩ
1kΩ
COUT1
4x100µF
SLAVE
VCC1
1
18
4
VCC1
12
R5
3.3kΩ
10
24
23
22
PGOOD
SLAVE
VCC2
COUT2
4x100µF
21
25
SLAVE
26
1
R6*
18
4
R7*
500Ω
12
10
24
23
22
*KEEP R6/R7 THE SAME
RATIO AS R1/R2. EACH VMON
PIN CAN HAVE SEPERATE
RESISTOR DIVIDER TO
MONITOR THE OUTPUT
VOLTAGE.
SLAVE
VCC3
21
25
500Ω
COUT3
4x100µF
SLAVE
26
1
18
4
12
10
24
FIGURE 26. SIX-PHASE 90A 1.2V OUTPUT CIRCUIT
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FN7822.2
December 8, 2014
ISL8225M
TABLE 1. ISL8225M DESIGN GUIDE MATRIX (REFER TO Figure 18)
VIN VOUT R2 or R4
CASE (V) (V)
(Ω)
CIN1
(BULK)
µF
(Note 10)
CIN2
(CERAMIC)
(µF)
COUT1
(CERAMIC)
(µF)
COUT2
(BULK)
(µF)
CFF
(nF)
EN/FF (kΩ)
R5/R6
(Note 11)
FREQ.
(kHz)
RSYNC
(kΩ)
LOAD
(A)
(Note 12)
1
5
1
1.5k
1x330
1x100
1x100
1x330
None
6.04/3.01
500
None
15
2
5
1
1.5k
1x330
1x100
3x100
None
3.3
6.04/3.01
500
None
15
3
12
1
1.5k
1x330
2x22
1x100
1x330
None
6.04/1.50
500
None
15
4
12
1
1.5k
1x330
2x22
3x100
None
3.3
6.04/1.50
500
None
15
5
5
1.2
1.0k
1x330
1x100
1x100
1x330
None
6.04/3.01
500
None
15
6
5
1.2
1.0k
1x330
1x100
3x100
None
3.3
6.04/3.01
500
None
15
7
12
1.2
1.0k
1x330
2x22
1x100
1x330
None
6.04/1.50
500
None
15
8
12
1.2
1.0k
1x330
2x22
3x100
None
3.3
6.04/1.50
500
None
15
9
20
1.2
1.0k
1x330
2x22
1x100
1x330
3.3
6.04/1.50
500
None
15
10
20
1.2
1.0k
1x330
2x22
3x100
None
4.7
6.04/1.50
500
None
15
11
5
1.5
665
1x330
1x100
1x100
1x330
None
6.04/3.01
500
None
15
12
5
1.5
665
1x330
1x100
3x100
None
3.3
6.04/3.01
500
None
15
13
12
1.5
665
1x330
2x22
1x100
1x330
None
6.04/1.50
500
None
15
14
12
1.5
665
1x330
2x22
3x100
None
3.3
6.04/1.50
500
None
15
15
20
1.5
665
1x330
2x22
1x100
1x330
None
6.04/1.50
500
None
15
16
20
1.5
665
1x330
2x22
3x100
None
3.3
6.04/1.50
500
None
15
17
5
2.5
316
1x330
1x100
1x100
1x330
None
6.04/3.01
500
None
15
18
5
2.5
316
1x330
1x100
3x100
None
3.3
6.04/3.01
500
None
15
19
12
2.5
316
1x330
2x22
1x100
1x330
None
6.04/1.50
650
249
15
20
12
2.5
316
1x330
2x22
3x100
None
3.3
6.04/1.50
650
249
15
21
20
2.5
316
1x330
2x22
1x100
1x330
None
6.04/1.50
750
147
14
22
20
2.5
316
1x330
2x22
3x100
None
3.3
6.04/1.50
750
147
14
23
5
3.3
221
1x330
1x100
1x100
1x330
None
6.04/3.01
500
None
15
24
5
3.3
221
1x330
1x100
3x100
None
None
6.04/3.01
500
None
15
25
12
3.3
221
1x330
2x22
1x100
1x330
None
6.04/1.50
800
124
14
26
12
3.3
221
1x330
2x22
3x100
None
None
6.04/1.50
800
124
14
27
20
3.3
221
1x330
2x22
1x100
1x330
None
6.04/1.50
850
107
13
28
20
3.3
221
1x330
2x22
3x100
None
3.3
6.04/1.50
850
107
13
29
12
5
137
1x330
2x22
1x100
1x330
None
6.04/1.50
950
82.5
12
30
12
5
137
1x330
2x22
3x100
None
None
6.04/1.50
950
82.5
12
31
20
5
137
1x330
2x22
1x100
1x330
None
6.04/1.50
950
82.5
10
32
20
5
137
1x330
2x22
3x100
None
3.3
6.04/1.50
950
82.5
10
33
12
6.5
102
1x330
4x22
2x47
1x330
None
16.5/4.12
750
147
10
34
12
6.5
102
1x330
4x22
6x47
None
3.3
16.5/4.12
750
147
10
35
20
6.5
102
1x330
4x22
2x47
1x330
None
16.5/4.12
750
147
10
36
20
6.5
102
1x330
4x22
6x47
None
3.3
16.5/4.12
750
147
10
37
12
7.5
86.6
1x330
4x22
2x47
1x330
None
16.5/4.12
750
147
7
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FN7822.2
December 8, 2014
ISL8225M
TABLE 1. ISL8225M DESIGN GUIDE MATRIX (REFER TO Figure 18) (Continued)
VIN VOUT R2 or R4
(Ω)
CASE (V) (V)
CIN1
(BULK)
µF
(Note 10)
CIN2
(CERAMIC)
(µF)
COUT1
(CERAMIC)
(µF)
COUT2
(BULK)
(µF)
CFF
(nF)
EN/FF (kΩ)
R5/R6
(Note 11)
FREQ.
(kHz)
RSYNC
(kΩ)
LOAD
(A)
(Note 12)
38
12
7.5
86.6
1x330
4x22
6x47
None
3.3
16.5/4.12
750
147
7
39
20
7.5
86.6
1x330
4x22
2x47
1x330
None
16.5/4.12
750
147
7
40
20
7.5
86.6
1x330
4x22
6x47
None
3.3
16.5/4.12
750
147
7
NOTES:
10. CIN bulk capacitor is optional only for decoupling noise due to the long input cable. CIN2 and COUT1 ceramic capacitors are listed for one phase only.
Please double the capacitor quantity for dual-phase operations.
11. EN/FF resistor divider is tied directly to VIN. The resistors listed here are for two channels' EN/FF pins tied together. If the separate resistor divider is
used for each channel, the resistor value needs to be doubled.
12. MAX load current listed in the table is for conditions at +25°C and no air flow on a typical Intersil 4-layer evaluation board.
TABLE 2. RECOMMENDED I/O CAPACITOR IN Table 1
VENDOR
VALUE
PART NUMBER
TDK, Input and Output Ceramic
100µF, 6.3V, 1210
C3225X5R0J107M
Murata, Input and Output Ceramic
100µF, 6.3V, 1210
GRM32ER60J107M
AVX, Input and Output Ceramic
100µF, 6.3V, 1210
12106D107MAT2A
Murata, Input Ceramic
22µF, 25V, 1210
GRM32ER61E226KE15L
Taiyo Yuden, Input Ceramic
22µF, 25V, 1210
TMK325BJ226MM-T
AVX, Input Ceramic
22µF, 25V, 1210
12103D226KAT2A
Panasonic POSCAP, Output Bulk
330µF, 10V
10TPB330M
Panasonic SMT, Input Bulk
330µF, 25V
EEVHA1E331UP
Murata, Input and Output Ceramic
47µF, 10V, 1210
GRM32ER71A476KE15L
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FN7822.2
December 8, 2014
ISL8225M
TABLE 3. ISL8225M OPERATION MODES
1ST MODULE (I = INPUT; O = OUTPUT; I/O = INPUT AND OUTPUT, BI-DIRECTION)
MODE
EN1/FF1 EN2/FF
(I)
2 (I)
VSEN2(I)
1
0
0
-
2A
0
1
Active
2B
1
0
-
3A
1
1
3B
1
3C
CLKOUT/RE
MODE VSEN2+ FIN WRT 1ST VMON2
(I)
(I)
(I OR O)
(Note 14)
-
-
VMON1
OF 2ND
MODULE
(Note 14)
MODES OF OPERATION
2ND CHANNEL
WRT 1ST (O)
(Note 13)
OPERATION OPERATION
MODE
MODE
OUTPUT (SEE
OF 2ND
OF 3RD
DESCRIPTION
MODULE
MODULE FOR DETAILS)
-
-
-
-
-
-
Disabled
-
Active
-
VMON1 =
VMON2 to Keep
PGOOD Valid
-
-
Single Phase
-
-
-
VMON1 =
VMON2 to Keep
PGOOD Valid
-
-
Single Phase
<VCC -0.7V Active Active 29% to 45%
of VCC (I)
Active
-
0°
-
-
Dual
Regulator
1
<VCC -0.7V Active Active 45% to 62%
of VCC (I)
Active
-
90°
-
-
Dual
Regulator
1
1
<VCC -0.7V Active Active >62% of VCC
(I)
Active
-
180°
-
-
Dual
Regulator
4
1
1
<VCC -0.7V Active Active <29% of VCC
(I)
Active
-
-60°
-
-
DDR Mode
5A
1
1
VCC
GND
-
60°
VMON1 or
Divider
-
180°
-
-
2-Phase
5B
1
1
VCC
GND
-
60°
Divider
Divider
180°
5B
5B
6-Phase
5C
1
1
VCC
GND
-
60°
VMON1 or
Divider
Active
180°
5C
5C
3 Outputs
6
1
1
VCC
VCC
GND
120°
953Ω//
22nF
Active
240°
2B
-
3-Phase
7A
1
1
VCC
VCC
VCC
90°
953Ω//
22nF
Divider
180°
7A
-
4-Phase
7B
1
1
VCC
VCC
VCC
90°
953Ω//
22nF
Active
180°
7B
-
2 Outputs
(1st module in
Mode 7A)
7C
1
1
VCC
VCC
VCC
90°
953Ω//
22nF
Active
180°
3, 4
-
3 Outputs
(1st module in
Mode 7A)
Active Active
-
-
8
Cascaded Module Operation MODEs 5B+5B+7A+5B+5B+5B/7A, No External Clock Required
12-Phase
9
External Clock or External Logic Circuits Required for Equal Phase Interval
5, 7, 8, 9, 10,
11, or (PHASE
>12)
NOTE:
13. “2ND CHANNEL WRT 1ST” means “second channel with respect to first;” in other words, Channel 2 lags Channel 1 by the degrees specified in this
column. For example, 90° means Channel 2 lags Channel 1 by 90°; -60° means Channel 2 leads Channel 1 by 60°.
14. “VMON1” means that the pin is tied to the VMON1 pin of the same module.
“Divider” means that there is a resistor divider from VOUT to SGND; refer to Figure 26.“
953Ω//22nF” means that there are 953Ω resistor and 22nF connecting the pin to SGND; refer to Figure 24.
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ISL8225M
Application Information
Programming the Output Voltage
The ISL8225M has an internal 0.6V ±0.7% reference voltage.
Programming the output voltage requires a resistor divider (R1
and R2) between the VOUT, VSEN+, and VSEN- pins, as shown in
Figure 18. Please note that the output voltage accuracy is also
dependent on the resistor accuracy of R1 and R2. The user needs
to select a high accuracy resistor (i.e. 0.5%) in order to achieve
the overall output accuracy. The output voltage can be calculated
as shown in Equation 1:
(EQ. 1)
R1
V OUT = 0.6   1 + --------

R2
NOTE: It is recommended to use a 1kΩ value for the top resistor, R1. The
value of the bottom resistor for different output voltages is shown in
Table 4.
TABLE 4. VALUE OF BOTTOM RESISTOR FOR DIFFERENT OUTPUT
VOLTAGES (VOUT vs R2)
Selection of Input Capacitor
Selection of the input filter capacitor is based on how much
ripple the supply can tolerate on the DC input line. The larger the
capacitor, the less ripple expected, however, consideration
should be given to the higher surge current during power-up. The
ISL8225M provides a soft-start function that controls and limits
the current surge. The value of the input capacitor can be
calculated as shown in Equation 2:
IO  D  1 – D 
C IN  MIN  = ----------------------------------V P-P  f SW
R1
(Ω)
VOUT
(V)
R2
(Ω)
1k
0.6
Open
1k
0.8
3.01k
1k
1.0
1.50k
• CIN(MIN) is the minimum required input capacitance (µF)
1k
1.2
1.00k
• IO is the output current (A)
1k
1.5
665
• D is the duty cycle
1k
1.8
491
• VP-P is the allowable peak-to-peak voltage (V)
1k
2.0
422
• fSW is the switching frequency (Hz)
1k
2.5
316
1k
3.3
221
1k
5.0
137
1k
6.0
110
1k
6.5
102
1k
7.5
86.6
In addition to the bulk capacitance, some low Equivalent Series
Resistance (ESR) ceramic capacitance is recommended to
decouple between the VIN and PGND of each channel. Table 2
shows for some recommended capacitors. This capacitance
reduces voltage ringing created by the switching current across
parasitic circuit elements. All these ceramic capacitors should be
placed as closely as possible to the module pins. The estimated
RMS current should be considered in choosing ceramic capacitors.
Io D  1 – D 
I IN  RMS  = --------------------------------
1100
20VIN
1000
(EQ. 2)
where:
Due to the minimum off-time limit of 410ns, the module has a
maximum output voltage, depending on input voltage. Refer to
Figure 27 for the 5V input voltage limitation.
FREQUENCY (kHz)
At higher output voltage, the inductor ripple increases, which makes
both output ripple and inductor power loss higher. Therefore, higher
switching frequency can be used to reduce the inductor ripple.
However, higher switching frequency results in higher switching loss
and higher gate driving loss, so the overall efficiency may suffer.
Because of thermal and efficiency concerns, the optimal switching
frequency is 750KHz for 6.5V and 7.5V output. With 750kHz
switching frequency, the minimum input voltage is 10V for 6.5V
output and 11V for 7.5V. Please refer to Figure 27 for frequency
selection at different operating conditions, then refer to Figure 31 to
choose RSYNC.
15VIN
900
(EQ. 3)
Each 10µF X5R or X7R ceramic capacitor is typically good for 2A
to 3A of RMS ripple current. Refer to the capacitor vendor to
check the RMS current ratings. In a typical 15A output
application for one channel, if the duty cycle is 0.5, it needs at
least three 10µF X5R or X7R ceramic input capacitors.
12VIN
10VIN
800
700
8VIN
600
500
5VIN
0
1
2
3
4
5
VOUT (V)
FIGURE 27. RECOMMENDED FREQUENCY vs VIN AT VOUT
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FN7822.2
December 8, 2014
ISL8225M
Selection of Output Capacitors
where:
The ISL8225M is designed for low output voltage ripple. The
output voltage ripple and transient requirements can be met with
bulk output capacitors (COUT) that have adequately low ESR.
COUT can be a low ESR tantalum capacitor, a low ESR polymer
capacitor, or a ceramic capacitor. The typical capacitance is
330µF, and decoupled ceramic output capacitors are used for
each phase. See Tables 1 and 2 for more capacitor information.
Internally optimized loop compensation provides sufficient
stability margins for all ceramic capacitor applications, with a
recommended total value of 300µF per phase. Additional output
filtering may be needed if further reduction of output ripple or
dynamic transient spike is required.
• Tjunction is the module internal maximum temperature (°C)
EN/FF Turn ON/OFF
Each output of the ISL8225M can be turned on/off independently
through the EN/FF pins. For parallel use, tie all EN/FF pins together.
Since this pin has the feed-forward function, the voltage on this pin
can actively adjust the loop gain to be constant for variable input
voltage. Please refer to Table 1 to select the resistor divider for
commonly used conditions. Otherwise, use the following procedures
to finish the EN/FF design:
1. A resistor divider from VIN to GND is recommended to set the
EN/FF voltage between 1.25V to 5.0V. The resistor divider
ratio is recommended to be between 3/1 to 4/1 (as shown in
Figure 21) with a resistor divider at 7.15kΩ/2.05kΩ.
2. Check EN turn-on hysteresis (Recommend VEN_HYS > 0.3V):
• Tambient is the system ambient temperature (°C)
• P is the total power loss of the module package (W)
• JA is the thermal resistance of module junction to ambient
If the calculated temperature, Tjunction, is over the required
design target, the extra cooling scheme is required. Please refer
to “Current Derating” on page 28 for adding air flow.
Functional Description
Initialization
Initially, the Power-On Reset (POR) circuits continuously monitor
bias voltages (VCC) and voltage at the EN/FF pin. The POR
function initiates soft-start operation 384 clock cycles
after: (1) the EN pin voltage is pulled above 0.8V, (2) all input
supplies exceed their POR thresholds, and (3) the PLL locking
time expires. The Enable pin can be used as a voltage monitor
and to set the desired hysteresis, with an internal 30µA sinking
current going through an external resistor divider. The sinking
current is disengaged after the system is enabled. This feature is
specially designed for applications that require higher input rail
POR for better undervoltage protection. For example, in 12V
applications, RUP = 53.6kΩ and RDOWN = 5.23kΩ sets the
turn-on threshold (VEN_RTH) to 10.6V and the turn-off threshold
(VEN_FTH) to 9V, with 1.6V hysteresis (VEN_HYS).
where:
During shutdown or fault conditions, soft-start is quickly reset,
and the gate driver immediately changes state (<100ns) when
input drops below POR.
• RUP is the top resistor of the resistor divider
Enable and Voltage Feed-forward
• N is the total number of the EN/FF pins tied to the resistor divider
Voltage applied to the EN/FF pin is fed to adjust the sawtooth
amplitude of the channel. Sawtooth amplitude is set to 1.25 times
the corresponding FF voltage when the module is enabled. This
configuration helps maintain a constant gain. This configuration
also helps maintain input voltage to achieve optimum loop response
over a wide input voltage range.
V EN – HYS = N  R UP  3x10 – 5
(EQ. 4)
3. Set the maximum current flowing through the top pull-up
resistor RUP to below 7mA (considering EN/FF is pulled to
ground (VEN/FF = 0)). Refer to Figure 25; a 3.01kΩ/1kΩ
resistor is used to allow for the input voltage from 5V to 20V
operation. In addition, the maximum current flowing through
R5 is 6.6mA (<7mA).
4. If the EN/FF is controlled by system EN signal instead of the
input voltage, we recommend setting the fixed EN/FF voltage
to about 1/3.5 of the input voltage. If the input voltage is 12V,
a 3.3V system EN signal can be tied to EN/FF pin directly.
5. If the input voltage is below 5.5V, it is recommended to have
EN/FF voltage >1.5V to have better stability. The input voltage
can be directly tied to the VCC pin to disable the internal LDO.
6. A 1nF capacitor is recommended on the EN/FF pin to avoid
the noise injecting into the feed-forward loop.
Thermal Considerations
The ISL8225M QFN package offers typical junction to ambient
thermal resistance JA of approximately 10°C/W at natural
convection (~5.8°C/W at 400LFM) with a typical 4-layer PCB.
Therefore, use Equation 5 to estimate the module junction
temperature:
T junction = P   jA + T ambient
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23
A 384-cycle delay is added after the system reaches its rising
POR and prior to soft-start. The RC timing at the FF pin should be
small enough to ensure that the input bus reaches its static state
and that the internal ramp circuitry stabilizes before soft-start. A
large RC could cause the internal ramp amplitude not to
synchronize with the input bus voltage during output start-up or
when recovering from faults. A 1nF capacitor is recommended as
a starting value for typical applications.
In a multi-module system, with the EN pins are wired together, all
modules can immediately turn off, at one time, when a fault
condition occurs in one or more modules. A fault pulls the EN pin
low, disabling all modules, and does not create current bounce;
thus, no single channel is overstressed when a fault occurs.
Because the EN pins are pulled down under fault conditions, the
pull-up resistor (RUP) should be scaled to sink no more than 7mA
current from the EN pin. Essentially, the EN pins cannot be
directly connected to VCC.
(EQ. 5)
FN7822.2
December 8, 2014
ISL8225M
R
UP
V
V EN_HYS
= ----------------------------I
EN_HYS
EN_FTH
= V
VIN
R
²V
UP
EN_REF
R DOWN = --------------------------------------------------------------V
–V
EN_FTH
EN_REF RUP
EN_RTH
–V
EN_HYS
ON/OFF
EN
384
CLOCK
CYCLES
0.8V
SOFT-START
IEN_HYS = 30µA
RDOWN
OV, OT, OC, AND PLL LOCKING FAULTS
FIGURE 28. SIMPLIFIED ENABLE AND VOLTAGE FEED-FORWARD CIRCUIT
Soft-Start
The ISL8225M has an internal, digital, precharged soft-start
circuitry (Figures 29 to 31). The circuitry has a rise time inversely
proportional to the switching frequency. Rise time is determined
by a digital counter that increments with every pulse of the phase
clock. The full soft-start time from 0V to 0.6V can be estimated
as shown in Equation 6. The typical soft-start time is ~2.5ms.
1280
t SS = ------------f SW
(EQ. 6)
The ISL8225M is able to work under a precharged output. The
PWM outputs do not feed to the drivers until the first PWM pulse
is seen. The low-side MOSFET is on for the first clock cycle, to
provide charge for the bootstrap capacitor. If the precharged
output voltage is greater than the final target level but less than
the 113% set point, switching does not start until the output
voltage is reduced to the target voltage and the first PWM pulse
is generated. The maximum allowable precharged level is 113%.
If the precharged level is above 113% but below 120%, the
output hiccups between 113% (LGATE turns on) and 87% (LGATE
turns off), while EN is pulled low. If the precharged load voltage is
above 120% of the targeted output voltage, then the controller is
latched off and cannot power up.
OV = 113%
FIRST PWM PULSE
VOUT TARGET VOLTAGE
FIGURE 31. SOFT-START WITH VOUT BELOW 113% BUT ABOVE FINAL
TARGET VOLTAGE
Power-Good
Power-good comparators monitor voltage on the VMON pin. Trip
points are shown in Figure 32. PGOOD is not asserted until the
soft-start cycle is complete. PGOOD pulls low upon both ENs
disabling it or when the VMON voltage is out of the threshold
window. PGOOD does not pull low until the fault presents for
three consecutive clock cycles.
UV indication is not enabled until the end of soft-start. In a UV
event, if the output drops below -13% of the target level due to a
reason other than OV, OC, OT, or PLL faults (cases when EN is not
pulled low), PGOOD is pulled low.
CHANNEL 1 UV/OV
SS SETTLING AT VREF + 100mV
FIRST PWM PULSE
CHANNEL 2 UV/OV
VOUT TARGET VOLTAGE
END OF SS1
END OF SS2
0.0V
1280
t SS = ------------f SW
-100mV
t
SS_DLY
SS1_PERIOD
SS2_PERIOD
384
= -----------f SW
FIGURE 29. SOFT-START WITH VOUT = 0V
PGOOD
AND
OR
AND
+20%
VMON1, 2
+13%
+9%
FIRST PWM PULSE
VREF
SS SETTLING AT VREF + 100mV
-9%
VOUT TARGET VOLTAGE
INIT. VOUT
-13%
-100mV
FIGURE 30. SOFT-START WITH VOUT < TARGET VOLTAGE
PGOOD
PGOOD LATCH OFF
AFTER 120% OV
FIGURE 32. POWER-GOOD THRESHOLD WINDOW
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December 8, 2014
ISL8225M
Current Share
In parallel operations, the share bus voltages (ISHARE) of
different modules must tie together. The ISHARE pin voltage is
set by an internal resistor and represents the average current of
all active modules. The average current signal is compared with
the local module current, and the current share error signal is fed
into the current correction block to adjust each module’s PWM
pulse accordingly. The current share function provides at least
10% overall accuracy between modules. The current share bus
works for up to 12 phases without requiring an external clock. A
470pF ~1nF capacitor is recommended for each ISHARE pin.
In current sharing scheme, all slave channels have the feedback
loops disabled with the VSEN- pin tied to VCC. The master
channel can control all modules with COMP and ISHARE pins tied
together. For phase-shift setting, all VMON pins of slave channels
are needed to set 0.6V for monitoring use only. Typically, the
slaved VMON pins can be tied together with a resistor divider to
VOUT. However, if the MODE pin is tied to VCC for mode setting,
the related VMON2 pin is needed to tie to SGND with a 953Ω
resistor and 22nF capacitor, as shown in Figure 25 on page 17. If
there are multiple modules paralleled with the MODE pins tied to
VCC, each VMON2 pin of the slave module needs to have a 953Ω
resistor to GND while all VMON1 pins of the slave modules can be
tied together with a resistor divider from VOUT to GND, as shown
in Figure 26 on page 18. Also see Table 3 for VMON settings.
Because of the typical 5.4V VCC and 7.5kΩ resistor between
MODE pin and VMON2 pin, the 953Ω resistor maintains VMON2
pin voltage close to 0.6V, so output OVP/UVP (caused by VMON2
voltage too high or too low) will not be triggered falsely by part to
part tolerance at mass production. The 22nF capacitor is used to
avoid output UVP/OVP triggered during input start-up.
Overvoltage Protection (OVP)
The overvoltage (OV) protection indication circuitry monitors
voltage on the VMON pin. OV protection is active from the
beginning of soft-start. An OV condition (>120%) would latch the
IC off. In this condition, the high-side MOSFET (Q1 or Q3) latches
off permanently. The low-side MOSFET (Q2 or Q4) turns on
immediately at the time of OV trip and then turns off
permanently after the output voltage drops below 87%. EN and
PGOOD are also latched low in an OV event. The latch condition
can be reset only by recycling VCC.
There is another non-latch OV protection (113% of target level).
When EN is low and output is over 113% OV, the low-side
MOSFET turns on until output drops below 87%. This action
protects the power trains when even a single channel of a
multi-module system detects OV. The low-side MOSFET always
turns on when EN = LOW and the output voltage rises above
113% (all EN pins are tied together) and turns off after the output
drops below 87%. Thus, in a high phase count application
(multi-module mode), all cascaded modules can latch off
simultaneously via the EN pins (EN pins are tied together in
multi-phase mode). Each channel shares the same sink current
to reduce stress and eliminate bouncing among phases.
other cascaded channels via their EN pins. All connected ENs
stay low and then release after the module’s junction
temperature drops below +125°C (typically), a +25°C hysteresis
(typically).
Overcurrent Protection (OCP)
The OCP peak level is set to about 20A for each channel, but the OC
trip point can vary, due mainly to MOSFET rDS(ON) variations (over
process, current, and temperature). The OCP can be increased by
increasing the switching frequency since the inductor ripple is
reduced. However, the module efficiency drops accordingly with
more switching loss. When OCP is triggered, the controller pulls
EN low immediately to turn off all switches. The OCP function is
enabled at start-up and has a 7-cycle delay before it triggers.
In multi-module operation, ISHARE pins can be connected to
create VISHARE, which represents the average current of all
active channels. Total system currents are compared with a
precision threshold to determine the overcurrent condition. Each
channel also has an additional overcurrent set point with a
7-cycle delay. This scheme helps protect modules from damage
in multi-module mode by having each module carry less current
than the set point.
For overload and hard short conditions, overcurrent protection
reduces the regulator RMS output current to much less than full
load by putting the controller into hiccup mode. A delay equal to
three soft-start intervals is entered to allow time to clear the
disturbance. After the delay time, the controller initiates a
soft-start interval. If the output voltage comes up and returns to
regulation, PGOOD transitions high. If the OC trip is exceeded
during the soft-start interval, the controller pulls EN low again.
The PGOOD signal remains low, and the soft-start interval is
allowed to expire. Another soft-start interval is initiated after the
delay interval. If an overcurrent trip occurs again, this same cycle
repeats until the fault is removed. Since the output voltage may
trigger the OVP if the output current changes too fast, the module
can go into latch-off mode. In this case, the module needs to be
restarted.
Frequency Synchronization and Phase Lock
Loop
The SYNC pin has two primary capabilities: fixed frequency
operation and synchronized frequency operation. The ISL8225M
has an internally set fixed frequency of 500kHz. By tying a
resistor (RSYNC) to SGND from the SYNC pin, the switching
frequency can be set to be more than 500kHz. To increase the
switching frequency, select an externally connected resistor,
RSYNC, from SYNC to SGND according to the frequency setting
curve shown in Figure 33. See Table 1 for RSYNC at commonly
used frequency.
Over-Temperature Protection (OTP)
When the junction temperature of the internal controller is
greater than +150°C (typically), the EN pin is pulled low to inform
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FN7822.2
December 8, 2014
ISL8225M
(R1 and R2)together with the 0.612V target CLKOUT voltage as
shown in Equation 7:
800
700
R1
k =  1 + --------  1.02 – 1

R2
RSYNC (kΩ)
600
500
For Figure 20, R1 = 1kΩ, R2 = 316Ω. The resistor divider ratio of
R7/R8 is calculated as 3.083, so R8 is 324Ω with 1kΩ used as
R7.
400
300
200
Mode Programming
100
0
500
(EQ. 7)
600 700
800 900 1000 1100 1200 1300 1400 1500
FREQUENCY (kHz)
FIGURE 33. RSYNC vs SWITCHING FREQUENCY
Connecting the SYNC pin to an external square-pulse waveform
(such as the CLKOUT signal, typically 50% duty cycle from
another ISL8225M) synchronizes the ISL8225M switching
frequency to the fundamental frequency of the input waveform.
The synchronized frequency can be from 300kHz to 1500kHz.
The applied square-pulse recommended high level voltage range
is 3V to VCC+0.3V. The frequency synchronization feature
synchronizes the leading edge of the CLKOUT signal with the
falling edge of Channel 1’s PWM signal. CLKOUT is not available
until PLL locks. No capacitor is recommended on the SYNC pin.
Locking time is typically 130µs. EN is not released for a soft-start
cycle until SYNC is stabilized and PLL is locking. Connecting all
EN pins together in a multi-phase configuration is recommended.
Loss of a synchronization signal for 13 clock cycles causes the
module to be disabled until PLL returns locking, at which point, a
soft-start cycle is initiated and normal operation resumes.
Holding SYNC low disables the module.
NOTE: That the quick change of the synchronization signal can cause
module shutdown.
Tracking Function
If CLKOUT is less than 800mV, an external soft-start ramp (0.6V)
can be in parallel with the Channel 2 internal soft-start ramp for
tracking applications. Therefore, the Channel 2’s output voltage
can track the output voltage of Channel 1.
The tracking function can be applied to a typical Double Data
Rate (DDR) memory application, as shown in Figure 20 on
page 14. The output voltage (typical VTT output) of Channel 2
tracks with the input voltage [typical VDDQ/(1+k) from
Channel 1] at the CLKOUT pin. As for the external input signal
and the internal reference signal (ramp and 0.6V), the one with
the lowest voltage is used as the reference for comparing with
the FB signal. In DDR configuration, VTT channel should start up
later, after its internal soft-start ramp, such that VTT tracks the
voltage on the CLKOUT pin derived from VDDQ. This configuration
can be achieved by adding more filtering at EN/FF1 than at
EN/FF2.
ISL8225M can be programmed for dual-output, paralleled
single-output or mixed outputs (Channel 1 in parallel and
Channel 2 in dual-output). With multiple ISL8225Ms, up to 6
modules using its internal cascaded clock signal control, the
modules can supply large current up to 180A. For complete
operation, please refer to Table 3 on page 21. Commonly used
settings are listed in Table 5.
TABLE 5. PHASE-SHIFT SETTING
OPERATION
PHASE-SHIFT
BETWEEN PHASES
VSEN2- VSEN2+ CLKOUT MODE
Dual Output
(Figure 18)
180°
N/C
N/C
VCC
N/C
30A
(Figure 19)
180°
VCC
N/C
N/C
SGND
30A
(Figure 23)
240°
VCC
SGND
N/C
VCC
60A
(Figure 24)
90°
VCC
VCC
N/C
VCC
90A
(Figure 26)
60°
VCC
N/C
N/C
SGND
When the module is in the dual-output condition, depending
upon the voltage level at CLKOUT (which is set by the VCC resistor
divider output), ISL8225M operates with phase shifted as the
CLKOUT voltage shown in Table 6. The phase shift is latched as
VCC rises above POR; it cannot be changed on the fly.
TABLE 6. CLKOUT TO PROGRAM PHASE SHIFT AT DUAL-OUTPUT
CLKOUT
VOLTAGE SETTING
PHASE FOR CHANNEL 2
WRT CHANNEL 1
RECOMMENDED
CLKOUT VOLTAGE
<29% of VCC
-60°
15% VCC
29% to 45% of VCC
0°
37% VCC
45% to 62% of VCC
90°
53% VCC
62% of VCC
180°
VCC
It is suggested to scale the target CLKOUT voltage to 0.612V (2%
above 0.6V reference) with an external resistor divider. After
start-up, the internal reference takes over to maintain the good
regulation of VTT. The resistor divider ratio (k) of R7/R8 in
Figure 20 is Based on the feedback divider of VDDQ
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ISL8225M
Two Phase Parallel Mode Operation
TABLE 7. OPERATION MODE SETTING FOR 6.5V AND 7.5V OUTPUT APPLICATION
VIN
(V)
VO
(V)
OPERATION
MODE
PHASE SHIFT
BETWEEN
PHASES
VSEN2-
VSEN2+
CLKOUT
11 to 13.9
6.5
5A
180°
VCC
N/C
N/C
VMON1 OR
DIVIDER
13.9 to
15.6
6.5
6
240°
VCC
SGND
N/C
953Ω//22nF
15.6 to 20
6.5
5A
180°
VCC
N/C
N/C
VMON1 OR
DIVIDER
SGND
11 to 15
7.5
5A
180°
VCC
N/C
N/C
VMON1 OR
DIVIDER
SGND
15 to 20
7.5
6
240°
VCC
SGND
N/C
953Ω//22nF
When ISL8225M operates in 2-phase mode, the current sensing
and sharing circuit keeps each channel's current in balance.
After a typical 175nS blanking period, with respect to the falling
edge of the PWM pulse of each channel, the voltage developed
across rDS(ON) of the low side MOSFETs is filtered and sampled
as the sensed current. If the other phase's high-side MOSFET is
turned on right at the moment when current is sensed, the
switching noise can distort the sensed current signal, which may
result in low frequency output ripple. For high output voltage of
>5V, the low frequency ripple is worse due to higher switching
noise at higher input voltage. Because of the 175ns current
sensing blanking time, if the second channel has 180° phase lag
with respect to the first channel, the low frequency ripple
typically appears when the module operates at around 40% duty
cycle depending upon switching frequency. To solve this problem,
240° phase shift (Mode 6 of Table 3) can be used instead of the
180° phase shift (Mode 5A of Table 3). Figure 23 shows a typical
application with 240° phase shift.
All other conditions equal, the module with 180° phase shift has
lower input ripple and output ripple than the module with 240°
phase shift, thus the selection of the optimum operation mode
should be based on the input voltage. Table 7 shows the
operation mode selection to avoid low frequency for 6.5V and
7.5V output applications with 750kHz switching frequency.
Please refer to Table 3 on page 21 for more information about
each operation mode.
Layout Guide
To achieve stable operation, low losses, and good thermal
performance, some layout considerations are necessary
(Figure 34).
VMON2
MODE
SGND
VCC
VCC
connect the power planes in different layers under or around
the module.
• Place high-frequency ceramic capacitors between VIN, VOUT,
and PGND, as closely to the module as possible in order to
minimize high-frequency noise.
• Use remote sensed traces to the regulation point to achieve
tight output voltage regulation, and keep the sensing traces
close to each other in parallel.
• PHASE1 and PHASE2 pads are switching nodes that generate
switching noise. Keep these pads under the module. For
noise-sensitive applications, it is recommended to keep phase
pads only on the top and inner layers of the PCB. Also, do not
place phase pads exposed to the outside on the bottom layer
of the PCB.
• Avoid routing any noise-sensitive signal traces, such as the
VSEN+, VSEN-, ISHARE, COMP and VMON sensing points, near
the PHASE pins.
• Use a separated SGND ground copper area for components
connected to signal ground pins. Connect SGND to PGND with
multiple vias underneath the unit in one location to avoid the
noise coupling, as shown in Figure 34 Don't ground vias
surrounded by the noisy planes of VIN, PHASE and VOUT. For
dual output applications, the SGND to PGND vias are preferred
to be as close as possible to SGND pin.
• Optional snubbers can be put on the bottom side of the board
layout, connecting the PHASE to PGND planes, as shown in
Figure 34.
• VOUT1, VOUT2, PHASE1, PHASE2, PGND, VIN1 and VIN2
should have large, solid planes. Place enough thermal vias to
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ISL8225M
COUT2
PCB Layout Pattern Design
COUT1
PGND
PGND
VOUT2
VOUT1
R3
R1
+
R4
KELVIN CONNECTIONS
FOR THE VSENS LINES
TO LOAD
+
TO LOAD
-
R2
KELVIN CONNECTIONS
FOR THE VSENS LINES
PIN 1
SGND
VIN2
VIN1
CIN2
PHASE2
PHASE1
OPTIONAL SNUBBER
CIN1
OPTIONAL SNUBBER
PGND
FIGURE 34. RECOMMENDED LAYOUT
Current Derating
Experimental power loss curves (Figures 35 and 36), along with
JA from thermal modeling analysis, can be used to evaluate the
thermal consideration for the module. Derating curves are
derived from the maximum power allowed while maintaining
temperature below the maximum junction temperature of
+120°C (Figures 37 through 42). The maximum +120°C
junction temperature is considered for the module to load the
current consistently and it provides the 5°C margin of safety
from the rated junction temperature of +125°C. If necessary,
customers can adjust the margin of safety according to the real
applications. All derating curves are obtained from the tests on
the ISL8225MEVAL4Z evaluation board. In the actual
application, other heat sources and design margins should be
considered.
Package Description
The ISL8225M is integrated into a quad flatpack no lead
package (QFN). This package has such advantages as good
thermal and electrical conductivity, low weight, and small size.
The QFN package is applicable for surface mounting technology
and is becoming more common in the industry. The ISL8225M
contains several types of devices, including resistors, capacitors,
inductors, and control ICs. The ISL8225M is a copper lead-frame
based package with exposed copper thermal pads, which have
good electrical and thermal conductivity. The copper lead frame
and multi-component assembly are over-molded with polymer
mold compound to protect these devices.
The bottom of ISL8225M is a lead-frame footprint, which is
attached to the PCB by surface mounting. The PCB layout pattern
is shown in the L26.17x17 package outline drawing on page 33.
The PCB layout pattern is essentially 1:1 with the QFN exposed
pad and the I/O termination dimensions, except that the PCB
lands are slightly longer than the QFN terminations by about
0.2mm (0.4mm max). This extension allows for solder filleting
around the package periphery and ensures a more complete and
inspectable solder joint. The thermal lands on the PCB layout
should match 1:1 with the package exposed die pads.
Thermal Vias
A grid of 1.0mm to 1.2mm pitched thermal vias, which drops
down and connects to buried copper planes, should be placed
under the thermal land. The vias should be about 0.3mm to
0.33mm in diameter, with the barrel plated to about 2.0 ounce
copper. Although adding more vias (by decreasing pitch)
improves thermal performance, it also diminishes results as
more vias are added. Use only as many vias as are needed for
the thermal land size and as your board design rules allow.
Stencil Pattern Design
Reflowed solder joints on the perimeter I/O lands should have
about a 50µm to 75µm (2mil to 3mil) standoff height. The solder
paste stencil design is the first step in developing optimized,
reliable solder joins. The stencil aperture size to land size ratio
should typically be 1:1. Aperture width may be reduced slightly to
help prevent solder bridging between adjacent I/O lands.
To reduce solder paste volume on the larger thermal lands, an
array of smaller apertures instead of one large aperture is
recommended. The stencil printing area should cover 50% to
80% of the PCB layout pattern. A typical solder stencil pattern is
shown in the L26.17x17 package outline drawing on page 33.
The gap width between pads is 0.6mm. Consider the symmetry
of the whole stencil pattern when designing the pads.
A laser-cut, stainless-steel stencil with electropolished
trapezoidal walls is recommended. Electropolishing smooths the
aperture walls, resulting in reduced surface friction and better
paste release, which reduces voids. Using a trapezoidal section
aperture (TSA) also promotes paste release and forms a
brick-like paste deposit, which assists in firm component
placement. A 0.1mm to 0.15mm stencil thickness is
recommended for this large-pitch (1.0mm) QFN.
The package outline, typical PCB layout pattern, and typical
stencil pattern design are shown in the L26.17x17 package
outline drawing on page 28. Figure 48 shows typical reflow
profile parameters. These guidelines are general design rules.
Users can modify parameters according to specific applications.
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FN7822.2
December 8, 2014
ISL8225M
7
8
6
7
6
POWER LOSS (W)
POWER LOSS (W)
5
4
3
5VIN TO 2.5VOUT
2
5VIN TO 1VOUT
5
10
15
20
LOAD CURRENT (A)
3
12VIN TO 1VOUT
12VIN TO 1.5VOUT
1
5VIN TO 1.5VOUT
0
12VIN TO 2.5VOUT
4
2
1
0
5
25
0
30
0
20
400LFM
0LFM
LOAD CURRENT (A)
200LFM
15
10
400LFM
0LFM
25
20
200LFM
15
10
5
5
25
45
65
85
TEMPERATURE (°C)
105
0
125
25
FIGURE 37. DERATING CURVE 5V TO 1V
45
65
85
TEMPERATURE (°C)
105
125
FIGURE 38. DERATING CURVE 12V TO 1V
30
30
400LFM
25
400LFM
25
0LFM
0LFM
200LFM
LOAD CURRENT (A)
LOAD CURRENT (A)
30
All of the following curves were plotted at TJ = +125°C.
20
20
15
10
5
0
25
30
25
LOAD CURRENT (A)
15
FIGURE 36. POWER LOSS CURVES OF 12VIN
30
0
10
LOAD CURRENT (A)
FIGURE 35. POWER LOSS CURVES OF 5VIN
Derating Curves
5
200LFM
20
15
10
5
25
45
65
85
TEMPERATURE (°C)
105
FIGURE 39. DERATING CURVE 5V TO 1.5V
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29
125
0
25
45
65
85
TEMPERATURE (°C)
105
125
FIGURE 40. DERATING CURVE 12V TO 1.5V
FN7822.2
December 8, 2014
ISL8225M
Derating Curves
All of the following curves were plotted at TJ = +125°C. (Continued)
30
30
400LFM
200LFM
20
15
10
0LFM
20
200LFM
15
10
5
5
0
400LFM
25
0LFM
LOAD CURRENT (A)
LOAD CURRENT (A)
25
25
45
65
85
105
0
125
25
45
TEMPERATURE (°C)
65
85
FIGURE 41. DERATING CURVE 5V TO 2.5V
30
400LFM
400LFM
25
0LFM
200LFM
LOAD CURRENT (A)
LOAD CURRENT (A)
25
20
15
10
0LFM
20
200LFM
15
10
5
5
25
45
65
85
105
0
125
25
45
65
85
125
FIGURE 44. DERATING CURVE 12V/3.3V
FIGURE 43. DERATING CURVE 5V/3.3V
20
30
400LFM
400LFM
25
16
0LFM
LOAD CURRENT (A)
LOAD CURRENT (A)
105
TEMPERATURE (°C)
TEMPERATURE (°C)
20
200LFM
15
10
0LFM
200LFM
12
8
4
5
0
125
FIGURE 42. DERATING CURVE 12V TO 2.5V
30
0
105
TEMPERATURE (°C)
25
45
65
85
105
TEMPERATURE (°C)
FIGURE 45. DERATING CURVE 12V/5V
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30
125
0
25
45
65
85
105
125
TEMPERATURE (°C)
FIGURE 46. DERATING CURVE 12V/6.5V
FN7822.2
December 8, 2014
ISL8225M
Derating Curves
All of the following curves were plotted at TJ = +125°C. (Continued)
14
200LFM
12
LOAD CURRENT (A)
0LFM
10
8
400LFM
6
4
2
0
25
45
65
85
105
125
TEMPERATURE (°C)
FIGURE 47. DERATING CURVE 12V/7.5V
Reflow Parameters
300
PEAK TEMPERATURE +230°C~+245°C;
TYPICALLY 60s-70s ABOVE +220°C
KEEP LESS THAN 30s WITHIN 5°C OF PEAK TEMP.
250
TEMPERATURE (°C)
Due to the low mount height of the QFN, "No Clean" Type 3 solder
paste, per ANSI/J-STD-005, is recommended. Nitrogen purge is
also recommended during reflow. A system board reflow profile
depends on the thermal mass of the entire populated board, so it
is not practical to define a specific soldering profile just for the
QFN. The profile given in Figure 43 is provided as a guideline to
customize for varying manufacturing practices and applications.
200 SLOW RAMP (3°C/s MAX)
AND SOAK FROM +100°C
TO +180°C FOR 90s~120s
150
100
RAMP RATE 1.5°C FROM +70°C TO +90°C
50
0
0
100
150
200
250
300
350
DURATION (s)
FIGURE 48. TYPICAL REFLOW PROFILE
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in the quality certifications found at www.intersil.com/en/support/qualandreliability.html
Intersil products are sold by description only. Intersil Corporation reserves the right to make changes in circuit design, software and/or specifications at any time
without notice. Accordingly, the reader is cautioned to verify that data sheets are current before placing orders. Information furnished by Intersil is believed to be
accurate and reliable. However, no responsibility is assumed by Intersil or its subsidiaries for its use; nor for any infringements of patents or other rights of third
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31
FN7822.2
December 8, 2014
ISL8225M
Revision History
The revision history provided is for informational purposes only and is believed to be accurate, but not warranted. Please go to web to make sure you
have the latest revision.
DATE
REVISION
CHANGE
December 8, 2014
FN7822.2
-Features on page 1: changed the output voltage range: from: “0.6V to 6V to: “0.6V to 7.5V.
-Features on page 1: Updated 17mm square PCB footprint to: 17mmx17mm square PCB footprint.
-Ordering information table on page 4 added part numbers: ISL8225MEVAL2Z, ISL8225MEVAL3Z,
ISL8225MEVAL4Z.
-Pin description on page 6, updated the output voltage range for pin numbers 23, 25: from: 0.6V to 6V
To: 0.6V to 7.5V.
-Recommended Operation table on page 7, updated output voltage range: from 0.6V to 6V to: 0.6V to 7.5V.
-Electrical spec table on page 7 under “VCC voltage level” section, updated Min from 5.15V to 5.1V and Max
from 5.95V to 5.6V.
-Electrical spec table on page 8 as follow:
“Synchronization frequency s” section: Updated Min from 150kHz to 300kHz.
Under Load Regulation Accuracy: Added a 0.3 typ value to IOUT1 and IOUT2 sections.
Under REFERENCE section: Added Min 0.5958 and Max 0.6042 to VREF1.
Under REFERENCE section: Added Min 0.5955 and Max 0.6057 to VREF2.
-Typical performance characteristics on page 10: Update Figures 4 and 5 with 6.5V/7.5V data.
-Updated the title for Figure 19 on page 13.
-Updated the title for Figures 21 on page 14.
-Added Figure 22 and 23 on page 15.
-Updated Table 1 on page 19: Added rows 33, 34, 35, 36, 37, 38, 39, 40.
-Table 2 on page 20: Added a row for 47µF 10V ceramic cap.
-Table 3 on page 21 under Vmon2 section: Updated mode 6, 7A, 7B and 7C: from 1kΩ to 0.953Ω/ 22nF and
updated note 14.
Updated Table 4 on page 22: Added two rows for 6.5V and 7.5V values.
-“Programming the Output Voltage” on page 22: Added a text with 6.5V and 7.5V information.
-“Current Share” on page 25: changed the VMON2 value, From: 1.0k to 953Ω.
-Section “Tracking Function” on page 26: Updated equation 7.
-Table 5 on page 26: Added a row with 240°.
-Table 6 on page 26 by Adding “CHANNEL 2” to checkout WRT and updated: “29% to 45% of VCC” section
from 90° to 0° and “45% to 62% of VCC” section from 120° to 90°.
On page 27: Added “Two Phase Parallel Mode” operation section.
-Added Table 7 on page 27.
-Updated Derating Curves on page 29.
-On page 29 the title for “Derating Curves” updated: TJ = +120°C to TJ = +125°C.
January 4, 2013
FN7822.1
“Thermal Information” on page 7:
Changed “Maximum Storage Temperature Range” from “-40°C to +150°C” to “-55°C to +150°C”
“Selection of Input Capacitor” on page 22:
Added "fSW" to Equation 2. Added "fSW is the switching frequency (Hz)"
December 3, 2012
FN7822.0
Initial Release
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For the most updated datasheet, application notes, related documentation and related parts, please see the respective product
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32
FN7822.2
December 8, 2014
ISL8225M
Package Outline Drawing
L26.17x17
26 LEAD QUAD FLAT NO-LEAD PLASTIC PACKAGE (PUNCH QFN)
Rev 4, 10/12
17.8±0.2
17.0±0.2
9
8
9
7 6 5 4 3 2
8
7 6 5 4 3 2
1
26
1
26
10
10
25
25
17.0±0.2
17.8±0.2
11
11
24
23
12
24
23
12
22
21
22
21
14
13
15 1617 18 19 20
TOP VIEW
0.10
0.10
0.10
0.10
AAA AAAAA AA
3.50
3.50
0.70
B
0.38
8.95
4.93
10
4.93
8.95
0.38
0.80
AAA AAAAA AAAAA
52x 0.50 (ALL OF LEAD TIPS)
2.37
0.25
12x 1.07 0.10
2.77
5.33
0.25
0.10
5.33
3.66
3.50
16x 0.55 (FULL LEAD)
16X 0.70 (FULL LEAD)
12
15 1617 1819 20
0.2 S AB
X4
4.00
3.50
14
PIN NO. DEFINITION (TOP VIEW)
AAAA AAAAA AAA
13
12
10
1
1
3.35
3.35
A:1.0±0.1
2.97
AAA AAAAA AAAAA
14x 0.75
16x 1.75±0.05 (FULL LEAD)
A
0.05
S AB
PIN-TO-PIN DISTANCE (BOTTOM VIEW)
BOTTOM VIEW
.2
R0
All A
ro
5
und
of 1 0
°(MA
X)
0.25
7.5±0.2
S 0.2
SIDE VIEW
S
S 0.03
Submit Document Feedback
33
FN7822.2
December 8, 2014
ISL8225M
0.25
0.40
0.65
0.75
9.30
7.98
6.35
5.65
5.35
5.24
4.65
4.35
3.65
3.35
2.65
2.35
1.65
1.35
0.65
0.25
0.00
0.55
3.10
3.25
3.75
3.90
7.15
7.25
7.70
7.96
9.30
9.30
7.83
6.53
6.50
6.13
5.73
5.33
0.75
0.65
0.40
0.25
9.30
7.15
6.35
5.65
5.35
4.65
4.35
1
10
0.75
0.35
0
0.35
0.75
12
4.35
4.65
5.35
5.65
6.35
7.15
9.30
5.33
5.73
6.13
6.50
6.53
7.83
9.30
9.30
7.98
7.15
6.35
5.93
5.65
5.35
5.24
4.65
4.35
3.65
3.35
2.65
2.35
1.65
1.35
1.35
0.65
0.25
0.05
0
0.55
3.10
3.25
3.75
3.90
7.15
7.25
7.70
7.83
7.96
9.30
TYPICAL RECOMMENDED LAND PATTERN (TOP VIEW)
9.20
7.83
7.25
6.25
5.75
5.25
4.75
4.25
3.75
3.25
2.75
2.25
1.75
1.25
0.75
0.15
0
0.25
0.75
1.25
1.75
2.25
2.75
3.15
3.85
4.25
4.75
5.25
5.75
6.25
6.75
7.15
7.83
7.93
9.20
7.38
6.60
4.05
2.70
2.40
1.05
0.00
1.05
2.40
2.70
4.05
3.36
5.03
5.43
6.43
6.83
7.38
6.60
7.38
34
*
7.38
6.03
5.54
Submit Document Feedback
7.38
7.38
6.83
6.43
5.43
5.03
3.36
2.76
0.95
0.70
0
0.70
0.95
0
0.05
1.13
1.73
2.80
4.20
5.28
5.88
6.95
9.20
7.83
7.25
6.25
5.75
5.25
4.75
4.25
3.75
3.25
2.75
2.25
1.75
1.25
0.75
0.15
0
0.25
0.75
1.25
1.75
2.25
2.75
3.15
3.85
4.25
4.75
5.25
5.75
6.25
6.75
7.15
7.83
9.20
SOLDER STENCIL PATTERN WITH SQUARE PADS 1 OF 2 (TOP VIEW)
5.54
0
0.05
0.60
1.13
1.73
1.80
2.40
2.80
3.60
4.20
5.28
5.41
5.88
6.01
6.95
7.23
7.25
6.25
5.75
5.25
4.75
4.25
3.75
3.25
2.75
2.25
1.75
1.25
0.95
0.25
0
0.25
0.95
1.25
1.75
2.25
2.75
3.25
3.75
4.25
4.75
5.25
5.75
6.25
7.25
9.20
7.93
5.25
4.75
4.25
3.75
3.25
2.75
2.25
1.75
1.25
0.85
0.15
0
0.15
0.85
1.25
1.75
2.25
2.75
3.25
3.75
4.25
4.75
5.25
7.93
SOLDER STENCIL PATTERN WITH SQUARE PADS 2 OF 2 (TOP VIEW)
FN7822.2
December 8, 2014