TND330/D Rev. 3, APR − 2009 16 W xDSL Modem AC−DC Adapter Reference Design Documentation Package © Semiconductor Components Industries, LLC, 2009 April, 2009 − Rev. 3 1 Publication Order Number: TND330/D Disclaimer: ON Semiconductor is providing this reference design documentation package “AS IS” and the recipient assumes all risk associated with the use and/or commercialization of this design package. No licenses to ON Semiconductor’s or any third party’s Intellectual Property is conveyed by the transfer of this documentation. This reference design documentation package is provided only to assist the customers in evaluation and feasibility assessment of the reference design. It is expected that users may make further refinements to meet specific performance goals. http://onsemi.com 2 TND330 TND330 16 W xDSL Modem AC-DC Adapter Reference Design Documentation Package http://onsemi.com TECHNICAL NOTE 1 Overview This reference document describes a built−and−tested, GreenPointt solution for an xDSL modem ac−dc adapter. This power supply reference design is intended for low power, off−line applications where a regulated output voltage is required. Applications would also include modems, printers, routers, hubs and/or similar consumer audio and video products that require a single output voltage in the 10 to 20 W range. The power supply design is based around ON Semiconductor’s NCP10xx family of monolithic controllers with an integrated 700 V MOSFET. In this particular design an NCP1027 is utilized in a 12 V, 1.3 A output supply with a surge capability of over 1.6 A. This design can be tailored for any output voltage from several volts up to 28 V (or higher) with power outputs to approximately 20 W (depending on the AC input requirement) by merely reconfiguring the transformer turns ratio and the voltage reference zener. The power supply will meet typical safety agency isolation and leakage current standards and comply with FCC Part 15 Level B conducted EMI requirements and has an average efficiency of greater than 75%. Figure 1 shows a simplified block diagram of the reference design circuit. 90 to 265 Vac Figure 1. 16 W DSL Modem AC−DC Adapter http://onsemi.com 3 TND330 2 Introduction In 1Q06, the number of internet broadband lines (per 100 households) reached 54% in the USA, placing the country in the top 20 ranking worldwide far behind countries such as South Korea with 83% broadband penetration (source: Point Topic). By 2010, nearly 71 million households in the United States will have broadband access, a new study by Forrester Research predicts. The growth in broadband connection will result in increasing growth of cable modems and xDSL modems. Typically, these modems are powered by an external ac−dc adapter. In most offices and households, these adapters remain plugged in the socket, continuously drawing power from the mains. For this reason, the ac−dc adapter must be designed in such a way that its power consumption in standby (no−load) mode is very low. It is estimated that, on average, 25% of the energy that passes through power supplies does so during standby−mode (source: NRDC). 3 Modem AC−DC Adapter Requirements The above paragraph showed the importance of reducing the standby power. Not only the standby power consumption of an ac−dc adapter has to be very low, but its active mode efficiency has to be very high. High active−mode efficiency saves energy when electronic devices are ‘active’, which are the times when they consume the most energy. (Examples: TV is turned on; computer is being used to play a video game.) It is estimated that 75% of the energy that passes through power supplies does so during active−mode (source: NRDC). 3.1 Regulatory Requirements for Standby (no−load) Power Consumption and Active Mode Efficiency Several regulatory bodies around the world address low standby power consumption and efficiency in active mode for external power supply (EPS). These requirements target two issues: • Get rid of the losses in a no−load situation (e.g.: when the AC−DC adapter is plugged in even when it is not connected to the cell phone). • Achieve good average active mode efficiency during various active mode load conditions (25%, 50%, 75% and 100%). Many regulations have been proposed around the world. Hereafter is the list of some of the most important ones: http://onsemi.com 4 TND330 ENERGY STAR): applicable in the US and international partners http://www.energystar.gov/index.cfm?c=ext_power_supplies.power_supplies_consumers Nameplate Output Power (Pno) Minimum Average Efficiency in Active Mode (expressed as decimal) ENERGY EFFICIENCY CRITERIA FOR ACTIVE MODE 0 to < 1 Watt ≥ 0.49 * Pno > 1 and ≤ 49 Watts ≥ [0.09 * Ln(Pno)] + 0.49 > 49 Watts ≥ 0.84 ENERGY CONSUMPTION CRITERIA FOR NO LOAD 0 to < 10 Watts ≤ 0.5 Watt ≥ 10 to ≤ 250 Watts ≤ 0.75 Watt California Energy Commission: Effective January 1, 2007 Nameplate Output Minimum Efficiency in Active Mode 0 to < 1 Watt 0.49 * Nameplate Output > 1 and ≤ 49 Watts [0.09 * Ln(Nameplate Output)] + 0.49 > 49 Watts 0.84 Maximum Energy Consumption in No−Load Mode 0 to < 10 Watts 0.5 Watt ≥10 to ≤ 250 Watts 0.75 Watt Effective July 1, 2008 Nameplate Output Minimum Efficiency in Active Mode 0 to < 1 Watt 0.5 * Nameplate Output > 1 and ≤ 51 Watts [0.09 * Ln(Nameplate Output)] + 0.5 > 51 Watts 0.85 Maximum Energy Consumption in No−Load Mode Any output 0.5 Watt Where Ln (Nameplate Output) = Natural Logarithm of the nameplate output expressed in Watts European Union’s Code of Conduct, version 2, November 24, 2004 − No−load Power Consumption No−load Power Consumption Rated Output Power Phase 1 (Jan. 1, 2005) Phase 2 (Jan. 1, 2007) > 0.3 W and < 15 W 0.30 W 0.30 W > 15 W and < 50 W 0.50 W 0.30 W > 50 W and < 60 W 0.75 W 0.30 W > 60 W and < 150 W 1.00 W 0.50 W http://onsemi.com 5 TND330 Energy−Efficiency Criteria for Active Mode for Phase 1 (for the period January 1, 2005 to December 31, 2006) Rated Output Power Minimum Four Point Average (see Annex) or 100 % Load Efficiency in Active Mode 0 < W < 1.5 30 1.5 < W < 2.5 40 2.5 < W < 4.5 50 4.5 < W < 6.0 60 6.0 < W < 10.0 70 10.0 < W < 25.0 75 25.0 < W < 150.0 80 Energy−Efficiency Criteria for Active Mode for Phase 2 (valid after January 1, 2007) Nameplate Output Power (Pno) Minimum Four Point Average (see Annex) or 100 % Load Efficiency in Active Mode (expressed as a decimal) (Note 1) 0<W<1 ≥ 0.49 * Pno 1 < W < 49 ≥ [0.09 * Ln(Pno)] + 0.49 49 < W < 150 ≥ 0.84 (Note 2) 1. “Ln” refers to the natural logarithm. The algebraic order of operations requires that the natural logarithm calculation be performed first and then multiplied by 0.09, with the resulting output added to 0.49. An efficiency of 0.84 in decimal form corresponds to the more familiar value of 84% when expressed as a percentage. 2. Power supplies that have a power factor correction (PFC) to comply with IEC61000−3−2 (above 75 W input power) have a 0.04 (4%) allowance, accordingly the minimum on mode load efficiency (100% or averaged) is relaxed to 0.80 (80%). Korea: • External Power Supply − No load: 0.8 W • Battery Charger − No load: 0.8 W Worldwide Legislation for EPS (external power supplies) Regulatory Agency/ Organization Country/State Affected Implementation Date Compliance Required (Mandatory or Voluntary) STAR® United States January 1, 2005 Voluntary http://www.energystar.gov/index.cfm?c= ext_power_supplies.power_supplies_consumers Europe January 1, 2005 Voluntary http://re.jrc.ec.europa.eu/energyefficiency/html/ standby_initiative_External%20Power%20Supplies.htm China January 1, 2005 Voluntary Harmonized with ENERGY STAR, http://www.cecp.org.cn/englishhtml/hlproductlist1.asp California January 1, 2007 Mandatory http://www.energy.ca.gov/appliances/index.html Australia, New Zealand October 1, 2008 Mandatory Harmonized with ENERGY STAR, http://www.energyrating.gov.au/eps2.html Arizona January 2008 Mandatory Source: http://www.standardsasap.org Massachusetts January 2008 Mandatory Source: http://www.standardsasap.org New York January 2008 Mandatory Source: http://www.standardsasap.org Oregon January 2008 Mandatory Source: http://www.standardsasap.org Rhode Island January 2008 Mandatory Source: http://www.standardsasap.org Vermont January 2008 Mandatory Source: http://www.standardsasap.org Washington January 2008 Mandatory Source: http://www.standardsasap.org ENERGY European Union China Standard Certification Center (CSC, ex−CECP) California Energy Commission Australia Greenhouse Office (AGO) Arizona Massachusetts New York Oregon Rhode Island Vermont Washington 3. Sources: www.psma.com, www.standardsasap.org http://onsemi.com 6 Comments TND330 4 Modem AC−DC Adapter Specification For modem OEM manufacturers, the ac−dc adapter is a commodity. So, they impose their own stringent specifications and de−rating guidelines while requiring low costs. The key performance criteria for adapters are: • Power density (driven by package size requirements) • Safety • Low case temperature Cooling: Convection Input Protection: 8 ohm inrush limiting with 1 A fuse Output Protection: Over−current, over−voltage, and over− temperature Safety Compliance: 3 kV I/O isolation EMI Compliance: FCC Part 15 conducted EMI (Level B, average profile) Input: 90 to 270 Vac, 50/60 Hz Output: 12 Vdc ±5% at 1.3 A continuous (16 W); 1.6 A surge to 10 seconds Regulation: < 2% line and load combined Output Ripple: Less than 200 mV p/p Average Efficiency: > > 0.09 * Ln (16) + 0.09 = 74% (per ENERGY STAR®) Standby (no−load) power consumption < 300 mW Operating Temperature: 0 to 50°C 5 Circuit Operation Referring to the schematic in Figure 2, the power supply is designed around a flyback converter topology with a simple zener plus optocoupler feedback circuit for output voltage sensing and regulation. The ac input is full−wave rectified by D1 through D4 and filtered by C3 and C4 to provide a dc “bulk” bus to the flyback converter stage. R1 provides inrush current limiting at turn−on while C1, C2, L1, L2 and C13 comprise both common and differential mode filtering for conducted EMI. L1 3.9 mH R1 AC input 8.2, 2W F1 C1 10 nF ”x” 1 A, 250 Vac C2 D1−D4 1N4007 100 nF ”x” C3 T1 C5 180pF 2 kV C4 L2 680 uH D6 MBRS360T 10 R2 4.7 10 uF, 400Vdc x2 R3 39K, 1W 1 5 9 6 D5 MURS160 R4 100K 0.1 C7 C6 470 uF 16V x2 2 MMSD4148A R14 omit R11 2.2M R13 omit R15 10 + R12 2.2M NCP1027 (100 kHz) 3 R10 30K C11 1 nF U1 4 7 1 8 C10 10 uF 25V 2.2nF ”Y2” 4 10 uF 25V R5 Vtrim (0 ohm) 1 nF Figure 2. 16 W, 12 V Output Adapter Supply (Rev 4) http://onsemi.com U2 1 47 R7 330 C8 NOTES: 1. L1 is Coilcraft E3491−AL common mode EMI inductor (3.9 mH) 2. L2 is Coilcraft part RFB0810−681L or similar (680 uH, 500 mA) 3. See Magnetics Data Sheet for T1 construction details. 4. R9 sets OVP trip level. 5. R8, R13, R14 for optional power limit feature (see NCP1027 data sheet.) 6. Z1 zener sets Vout: Vout = Vz + 0.85V; R5 is optional voltage trim resistor 7. R10 sets AC input brownout level. 8. R1 is optional inrush limiter. 9. U1 requires Aavid #580100W00000G clip−on DIP8 heatsink or similar. 10. Crossed schematic lines are not connected 7 Z1 MMSZ5241B (11V) C13 R6 + C9 R8 0 ohm 3 8 R9 1K 5 2 D7 3 opto 2 12V @ 1.3A C12 + _ TND330 relatively smooth dc level by C6 and C7, the main output capacitors. Capacitor C12 provides for additional high frequency noise filtering for the output. An RCD snubber network composed of R2, R3, C5, and D5 is implemented to clamp voltage spikes caused by the primary leakage inductance of T1. This network prevents potential damage to the MOSFET drain terminal (pin 5) of U1 by limiting the peak voltage and lowers potential EMI emissions. An alternate non−dissipative, resonant snubber circuit is shown in Figure 3 which will improve the efficiency of this circuit by a few percentage points depending on the nature of the transformer design and the associated parasitic parameters. The flyback converter is comprised of the NCP1027 controller/MOSFET U1, flyback transformer T1, and the secondary output rectifier/filter section of D6, C6 and C7. An auxiliary winding on T1 and associated components R15, D7, C10, R9, and C9 provide an operating bias (VCC) for the control chip and allows for low output power if the supply is short circuited, and very low standby power under no−load conditions. Since the voltage produced by the auxiliary winding tracks the main output voltage, it is also used to sense for over−voltage conditions in the event the feedback loop opens. The OVP trip level can be adjusted by the turns on the auxiliary winding and the value of R9. The main secondary voltage is rectified by Schottky diode D6 and filtered to a T1 C3 10 10 uF, 400Vdc x2 MURS160 x2 C4 L2 680 uH Lr = 1.5 mH Lr is Coilcraft RFB0810−152L Bulk common 1 Cr 180pF 2 kV 9 2 Drain terminal Figure 3. Non dissipative resonant snubber option If the output current exceeds approximately 1.8 A, the converter duty cycle will be reduced by peak current sensing of the MOSFET in U1, and the output voltage will begin to drop. Since the Vcc bias voltage on C10 will drop with the output voltage, eventually there will be insufficient voltage on VCC pin 1 to power the controller, and the supply will then go into a start−stop “hiccup” mode which will prevent high output currents into an overload and protect both the power supply and load. The network of R10 through R12 provides brownout protection for the circuit in the event the AC input voltage (and hence, the dc bulk voltage) drops below about 75 Vac. The level on pin 3 at which the chip shuts down can be adjusted via R10. C11 provides noise filtering for this input. Optional over−power compensation can also be provided via optional resistors R8, R13 and R14 if desired. With universal input supplies, the available output current will typically increase at high line due to reduced inverter duty cycle and the associated propagation delays in the control circuit. As a consequence more output power (current) is available at 230 Vac input. Adding these circuit components will compensate for this effect. Grounding pin 7 disables this feature. The details for the application of this and the brownout features, among others, is described in detail in the data sheet for the NCP1027, which is available at www.onsemi.com. As the supply’s supply output voltage and/or power level decreases, depending on the need, this incremental increase in efficiency may be critical in meeting ENERGY STAR efficiency requirements. The non−dissipative snubber circuit utilizes a resonant tank circuit composed of Lr and Cr which essentially acts as a reactive charge pump that returns the transformer’s leakage reactance energy back to the input bus (on C4) rather than burn it away in a resistor. This can be implemented for the slight cost increase of an extra fast recovery diode and the small 1.5 mH inductor Lr. Output voltage regulation is achieved by the combination of components Z1, R5, R6, R7 and optocoupler U2. When the output voltage reaches approximately 12 V, zener Z1 conducts, and when sufficient current flows through R7 to produce the 0.9 V necessary to turn the optocoupler diode on, the voltage feedback loop closes and the output will be regulated. The use of R7 forces the zener current to be in a stable part of the device’s characteristic V/I curve such that temperature effects on the output voltage are minimized. The output voltage will be equal to the rated zener voltage plus about 0.9 V. There will be some variation due to zener and optocoupler characteristics and a small negative temperature coefficient with this circuit, however, the Vout set point variations should not exceed ±5%. Optional resistor R5 allows trimming of the output voltage in the upward direction only. http://onsemi.com 8 TND330 6 Transformer Design For low power applications it is desirable to have as small a transformer as possible; however, as the transformer gets smaller, so does the core’s cross sectional area. This forces more primary turns in order to maintain an acceptable magnetic flux density limit and can cause excessive turns buildup in the bobbin such that effective primary to secondary insulation becomes prohibitive. A large number of primary turns also increases the primary leakage inductance, not to mention the dc resistance of the windings in general. Both of these factors contribute to lower efficiency in the converter. In this design an E25/10/6 (formerly E24/25) ferrite core was used with a satisfactory compromise with respect to the above mentioned parametric issues. The transformer design for a universal input is shown in Figure 4. Magnetics Design Data Sheet − Universal Input Line Voltage Project / Customer: ON Semiconductor − 16 − 20 watt, 12 vout Wallwart supply Part Description: 20 watt NCP1027 flyback transformer, 100 kHz, 12V / 1.5 A Schematic ID: T1 Core Type: E24/25 (E25/10/6); 3C90 material or similar Core Gap: Gap for 750 uH Inductance: 750 uH +/−5% Bobbin Type: 10 pin horizontal mount for E24/25 (E25/10/6) Windings (in order): Winding # / type Turns / Material / Gauge / Insulation Data Primary A (1 − 10) 25 turns of #30HN over 1 layer. Insulate for 1 kV to next winding. Self leads to pins.. Vcc (3 − 8) 5 turns of #30 HN spiral wound over 1 layer with 3 mm end margins minimum. Self leads to pins. Insulate to 3 kV to next winding 12V Secondary (5 − 6) 5 turns of three strands of #26HN (trifilar) over previous winding with 1.5 mm end margins approximately. Winding ends should be cuffed with tape to avoid edge breakdown other windings. Insulate for 3 kV to next winding. Self leads to pins. Primary B (2 − 9) Same as Primary A. Hipot: 3 kV from primaries & Vcc to secondary for 1 minute. Lead Breakout / Pinout Schematic 10 1 9 2 (Top View) 10 9 8 7 6 5 6 3 8 12 3 4 5 Figure 4. http://onsemi.com 9 Vendor: Mesa Power Systems, Escondido, CA. 760−489−8162 Part # TND330 winding. The designs shown in Figures 4 and 5 should be sufficient for any magnetics fabrication house to produce the transformer. Exact pinouts will depend on the specific layout, however, the core selection, wire sizing, inductance value and turns ratio should be adhered to for proper operation. This particular flyback transformer is designed for 100 kHz discontinuous inductor mode (DCM) operation, so the slope compensation feature of pin 2 in the NCP1027 is not necessary (see data sheet for details). Figure 5 is a design for 230 Vac input only (Europe) and will provide slightly higher efficiency and the ability to increase the available continuous power output to approximately 20 W (1.65 A). In either design, the primary is separated into two layers with the secondary and Vcc winding sandwiched in between. This configuration provides for lower leakage inductance and subsequently less voltage spiking at MOSFET turn−off. The trifilar wound 12 V secondary provides for lowest ac and dc losses in this Magnetics Design Data Sheet − European Input Line Voltage Project / Customer: ON Semiconductor − 22 watt, 12 vout adapter supply − Euro version Part Description: 22 watt NCP1027 flyback transformer, 100 kHz, 12V / 2A Schematic ID: T1 Core Type: E24/25 (E25/10/6); 3C90 material or similar Core Gap: Gap for 1.5 mH across pins 2 and 10 with pins 1 and 9 connected Inductance: 1.5 mH +/−5% (across pins 2 and 10 with pins 1 and 9 connected) Bobbin Type: 10 pin horizontal mount for E24/25 (E25/10/6) Windings (in order): Winding # / type Turns / Material / Gauge / Insulation Data Primary A (1 − 10) 38 turns of #32HN over 1 layer. Insulate for 1 kV to next winding. Self leads to pins.. Vcc (3 − 8) 6 turns of #30 HN spiral wound over 1 layer with 3 mm end margins minimum. Self leads to pins. Insulate to 3 kV to next winding 12V Secondary (5 − 6) 6 turns of three strands of #26HN (trifilar) over previous winding with 1 mm end margins approximately. Winding ends should be cuffed with tape to avoid edge breakdown other windings. Insulate for 3 kV to next winding. Self leads to pins. Primary B (2 − 9) Same as Primary A. Hipot: 3 kV from primaries & Vcc to secondary for 1 minute. Lead Breakout / Pinout Schematic (Top View) 10 10 9 8 7 6 1 9 2 Vendor: Mesa Power Systems, Escondido, CA. 760−489−8162 Part # 13−1305 5 6 12 3 4 5 3 8 Figure 5. http://onsemi.com 10 TND330 7 Test Results 7.1 Active Mode Efficiency minimum requirement of 74% at this particular power level. In the 230 Vac input case, a slight efficiency degradation occurs at light loading due to increased circuit quiescent power, mainly due to higher MOSFET switching losses at this input level. The efficiency curves with output loading at 25%, 50%, 75% and 100% for 120 and 230 Vac inputs are shown in Figures 6 and 7. Figure 7 displays the improved efficiency with the resonant snubber circuit. Note that the average efficiency in both cases easily meets the ENERGY STAR Traditional RCB Snubber Non−Dissipative Resonant Snubber Efficiency @ 255C % Load 120 Vac 230 Vac % Load 120 Vac 230 Vac 25 50 74 73 25 76.2 74.4 77 78.2 50 79 79.8 75 77.6 80 75 78 80.5 100 76.8 80.6 100 78.2 81 Average Efficiency 76.4% 78.0% Average Efficiency 78.1% 78.9% Minimum Efficiency per ENERGY STAR: [0.09 * Ln(16W)] + 0.49 74% 74% Minimum Efficiency per ENERGY STAR: [0.09 * Ln(16W)] + 0.49 74% 74% 90 90 80 80 Efficiency (%) Efficiency (%) Efficiency @ 255C 70 60 70 60 50 50 0 10 20 30 40 50 60 70 80 90 100 0 % Load 120 Vac 10 20 30 40 50 60 70 % Load 230 Vac 120 Vac Figure 6. Figure 7. 7.2 Standby (no load) Power Consumption Traditional RCD Snubber 290 mW @ 120 Vac 210 mW @ 240 Vac Non−Dissipative Resonant Snubber 240 mW @ 120 Vac 200 mW @ 240 Vac http://onsemi.com 11 230 Vac 80 90 100 TND330 7.3 EMI Profile The power supply was also tested at a local certified EMI/EMC test facility for conducted EMI on the AC input mains. The plot of Figure 8 shows the conducted EMI profile (peak and average) for 120 Vac input with an output load of 1.3 A. Note that the supply’s EMI plot meets the average boundary for FCC Level B. M. Flom Associates, Inc. EN 55022: 1998, Class B Line 1 (Neutral) 90.0 Points of Interest 80.0 Corrected Peak Data CISPRB_QP Amplitude dBuV 70.0 CISPRB_AV 60.0 50.0 40.0 30.0 20.0 10.0 0 100.0K Operator: LR 10:57:13 AM, Wednesday, March 21, 2007 1.0M 10.0M Frequency MHz 100.0M Job #: p0703008 Figure 8. 7.4 Other Results Figures 9 and 10 show the typical discontinuous flyback voltage waveforms on U1’s internal MOSFET drain for 120 and 230 Vac inputs respectively, with a 1.3 A output load. Figure 9. Drain Voltage @ 120 Vac Figure 10. Drain Voltage @ 230 Vac http://onsemi.com 12 TND330 Figure 11 is a display of the output ripple with a 1.3 A load. If necessary, lower output ripple can be achieved by placing a small 4.7 mH, 2 A rated inductor between the output capacitors C6 and C7 in the positive rail. Figure 11. Output Ripple http://onsemi.com 13 TND330 8 Bill of Materials 16 W, NCP10127 Adaptor BOM (Rev. 4) Part Qty ID Description MRA4007 4 D1 − D4 MURS160 1 MBRS360T Schottky 1 MMSZ5241B zener diode Optocoupler, SFH6156A−4 (4 pin) Comments 1 A, 800 V diode ON Semiconductor D5 1 A, 600 V UFR diode ON Semiconductor D6 3 A, 60 V Schottky ON Semiconductor 1 Z1 11 V, 250 mW zener ON Semiconductor 1 U2 Optocoupler Vishay NCP1027 (100 kHz) 1 U1 100 kHz current mode controller ON Semiconductor “X” cap, disc type 2 C1, C2 10 nF “X2” capacitor, 250 Vac Vishay “Y” cap, disc type 1 C13 2.2 nF, “Y2” capacitor, 250 Vac Vishay Ceramic cap, disc 1 C5 4.7 nF, 2 kV capacitor (snubber) Vishay Ceramic cap, monolythic 1 C12 0.1 mF, 50 V ceramic cap Vishay Ceramic cap, monolythic 2 C8, C11 1 nF, 50 V ceramic cap Vishay Electrolytic cap 2 C3, C4 10 mf, 400 Vdc UCC, Rubycon Electrolytic cap 2 C6, C7 470 mf, 16 V (low ESR) UCC, Rubycon Electrolytic cap 2 C9, C10 10 mf, 25 V UCC, Rubycon Resistor, 2 W 1 R1 8.2 W, 2 W ceramic Ohmite Resistor, 1 W 1 R3 39 K, 1 W Ohmite Resistor, 1/4 W 1 R2 4.7 W, 1/4 W Ohmite Resistor, 1/4 W 1 R8 0 W, 1/4 W (jumper − power limit) Ohmite Resistor, 1/8 W 1 R7 330, 1/8 W Ohmite Resistor, 1/8 W 1 R6 47 W, 1/8 W Ohmite Resistor, 1/4 W 1 R4 100 K, 1/4 W Ohmite Resistor, 1/8 W 1 R5 0 W, 1/8 W (jumper) Ohmite Resistor, 1/8 W 1 R15 10 W Ohmite Resistor, 1/8 W 1 R9 1 kW Ohmite Resistor, 1/8 W 1 R10 30 K Ohmite Resistor, 1/4 W 2 R11, R12 2.2 Meg Ohmite Resistor, 1/4 W 2 R13, R14 TBD (optional for power limit) Ohmite Heatsink for U1 1 Aavid 580100W00000G Aavid Inductor, 680 mH 1 L2 RFB0810−681L Coilcraft EMI Inductor, 3.9 mH 1 L1 E3491−AL Coilcraft Transformer 1 T1 Flyback Xfmr #13−1302 Mesa Power Systems http://onsemi.com 14 TND330 3.75 Inches 2.25 Inches Figure 12. PCB Layout (Top View) Figure 13. Board Picture http://onsemi.com 15 TND330 9 Appendix References: • Draft Commission Communication on Policy Instruments to Reduce Stand−by Losses of Consumer Electronic Equipment (19 February 1999) − http://energyefficiency.jrc.cec.eu.int/pdf/consumer_electronics_communication.pdf European Information & Communications Technology Industry Association − http://www.eicta.org/ • • http://standby.lbl.gov/ACEEE/StandbyPaper.pdf CSC (ex−CECP China): • http://www.cecp.org.cn/englishhtml/index.asp Energy Saving (Korea): • http://weng.kemco.or.kr/efficiency/english/main.html# Top Runner (Japan): • http://www.eccj.or.jp/top_runner/index.html EU Eco−label (Europe): • http://europa.eu.int/comm/environment/ecolabel/index_en.htm • http://europa.eu.int/comm/environment/ecolabel/product/pg_television_en.htm EU Code of Conduct (Europe): • http://energyefficiency.jrc.cec.eu.int/html/standby_initiative.htm GEEA (Europe): • http://www.efficient−appliances.org/ • http://www.efficient−appliances.org/Criteria.htm Energy Star: • http://www.energystar.gov/ • http://www.energystar.gov/index.cfm?c=ext_power_supplies.power_supplies_consumers 1 Watt Executive Order: • http://oahu.lbl.gov/ • http://oahu.lbl.gov/level_summary.html Additional Collateral from ON Semiconductor: • NCP1027/D: High−Voltage Switcher for Medium • Application Note AND8241/D: A 5 V/2 A Power • • • • • • • Power Offline SMPS Design note DN06006/D: NCP1027: 1 A, 12 W Constant Current Off−Line LED Driver Design note DN06012/D: NCP1027: 10 W, 24 V / 5 V Off−Line Power Supply Design note DN06021/D: NCP1027: 16 W, 12 Vdc Modem Power Supply Supply MBRS360/D: 3 A, 60 V Schottky Rectifier MMSD4148/D: 100 V Switching Diode MURS160/D: 1 A, 600 V Ultrafast Rectifier MMSZ5241B/D: 500 mW Zener Diode GreenPoint is a trademark of Semiconductor Components Industries, LLC (SCILLC). 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