NCP1252 Boost and CAT4026 LED Driver Board

AND8478/D
NCP1252 Boost and
CAT4026 LED Driver Board
Prepared by:
ON Semiconductor
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APPLICATION NOTE
Introduction
This document describes the NCP1252 Boost and
CAT4026 LED Driver board. This board includes a DC−DC
boost converter and a linear driver for driving up to 6 strings
of LEDs at 100 mA from a regulated 24 V supply. The LED
channel current is regulated using the ON Semiconductor
CAT4026 LED controller in conjunction with the NCP1252
PWM controller operating in Continuous Conduction Mode
(CCM). The boost stage converts the 24 V into an output
voltage of up to 130 V for driving long strings of LEDs.
Figure 1 shows a simplified block diagram of the
NCP1252 Boost and CAT4026 LED Driver board.
channel by an external resistor connected between the
regulated RSET pin (1 V nominal) and ground.
A PWM logic input (active high) allows to turn on all 6
channels together. The PWM can be used to control the
brightness of the LEDs by using a PWM signal where the
duty cycle sets the brightness. A frequency of 300 Hz is
recommended to get the best dimming resolution. The
analog dimming (ANLG input) is an optional feature that
can be left unconnected.
The board supports both open cathode−anode and short
cathode−anode fault protections which respectively outputs
an active−low signal FLT−OCA and FLT−SCA when a fault
condition occurs.
Figures 2 and 3 show pictures of the actual board. To be
in line with the requested SLIM design, the board has been
designed to be less than 8 mm on top of the PCB (12.5 mm
overall).
Board Description
The board is configured for driving LED strings at
variable currents up to 100 mA maximum.
In order to support high supply voltage of the LED anode,
each LED string cathode is connected to an external power
transistor. The LED current is set independently for each
Figure 1. Board Block Diagram
© Semiconductor Components Industries, LLC, 2011
January, 2011 − Rev. 0
1
Publication Order Number:
AND8478/D
AND8478/D
Figure 2. NCP1252 Boost and CAT4026 LED Driver Board (Top Side)
Figure 3. NCP1252 Boost and CAT4026 LED Driver (Bottom Side)
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Detailed Operation
The board includes a boost converter and an LED driver
section. Each section is described below.
When the Power MOS turns ON, the supply voltage is
applied on the Boost coil and the current ramps up.
When the switch turns OFF, the voltage rises up such that
current flows to the output cap through rectifier diode. The
inductor current ramps down until the Power MOS is switch
ON again. If the switch OFF time is long enough, the current
may go to zero with complete discharge of the inductor.
Boost Converter Operation
Most of the LCD conventional Switching Mode Power
Supplies (SMPS) provide 24 V for the CCFL backlight. In
order to reuse the same existing SMPS and allow for faster
design introduction, the new LED backlight can be designed
for 24 V supply.
If for direct LED backlight, the 24 V could be sufficient
to drive limited diodes segments, the higher numbers of
LEDs used for Edge solutions requires much higher voltage.
The LED string voltage in the backlight application is
typically between 100 V and 150 V.
ǒ Ǔ
Ǔ
(eq. 1)
Working with high voltage ratio: 120 / 24 = 5, we have
80% typical on time duty cycle (ton./ ton + toff).
Considering possible lower supply and higher output
voltages, ton may go up to 90% which is very critical for the
controller, not allowing high switching frequency and
decreasing the efficiency.
To solve that, the boost is designed with tapped coil
allowing for smaller duty cycle despite high voltage ratio.
Boost Concept
As there is no need of main isolation already provided by
the 24 V SMPS, a conventional Boost or Step Up is capable
to provide the requested higher voltage.
Figure 4. Conventional Boost Solution Schematic
Ipeak
Ics
ISUPPLY
ǒ
DI + Vin ton + Vout * Vin toff
L
L
td
Itransistor
Idiode
Ivalley
toff
ton
Figure 5. Conventional Boost Current in the Coil
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Tapped Coil Boost Concept
Tapped Coil Boost Design Consideration
The coil has an added connection point allowing the
solution to work like a transformer but without the drawback
of poor coupling.
With correct turn’s ratio, the boost coil allows to get down
to 50% duty cycle despite high boost voltage ratio (Vout /
Vin). The larger toff allows a reduction of rms current in both
output diode and capacitor.
The shorter ton for the Power MOS switch, working with
lower inductance, asks for a larger peak and rms current,
requesting for low Rds−on to avoid over power dissipation
and temperature.
The high secondary inductance Ls will limit the di/dt such
that an added diode D2 should be connected from the switch
to the output capacitor to avoid overvoltage on the Power
MOS. This diode D2 can be small thanks to the very short
conduction time.
ǒ Ǔ
ǒ
Ǔ
(eq. 2)
ǒ
ǓǒVoutVin* VinǓ
(eq. 3)
DI + Vin ton + Vout * Vin toff
Lp
Lp ) Ls
Np
ton +
Np ) Ns
toff
With Ns = 3.3 Np , for 24 Vin and 120 Vout, we are getting
ton ≈ toff (about 50% duty cycle).
Lp
Ls
D1
Vin
Vout
D2
Q
Cin
Cout
Figure 6. Tapped Coil Boost Solution Schematic
Ics
td
ISUPPLY
Idiode
Ivalley
toff
ton
Figure 7. Tapped Coil Boost Current in the Coil
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NCP1252B Controller
Power Stage
The NCP1252 controller is an improved UC384X
previous solution. With more features and much reduced
number of external surrounding parts, it offers everything
needed to build cost−effective and reliable switching
supplies or Boost converter.
Thanks to the use of an internally 10 ms fixed timer,
NCP1252 detects an output overload without relying on the
auxiliary VCC. A Brown−Out input offers protection against
low input voltages and improves the converter reliability
and safety. The switching frequency is adjustable with an
external resistance to provide highest design flexibility. The
version B allows up to 80% duty cycle avoiding too short toff
or diode conduction time. The Internal 160 ns Leading Edge
Blanking avoids possible issues with Continuous
Conduction Mode and peak current by switch ON of Power
MOS. An external capacitor defines the soft start. The wide
range of VCC allows easy supply from the 24 V input voltage
with auto−recovery UVLO by 9 V.
Finally a SOIC8 package saves PCB space and represents
a solution of choice in cost sensitive project.
To reduce power dissipation, two power MOS transistors
(Q1 and Q2) are used in parallel such that Rds−on is reduced
by half. For reduced power application, one of the MOS can
easily be disconnected to reduce the size of the special low
profile heat sink.
Despite the output voltage limit to 130 V, 200 V power
MOS should be used due to the overvoltage generated by the
tapped boost coil construction.
Additional PNP transistors Q5 and Q6 allow faster Power
MOS switch OFF with reduced impedance.
The boost diode D1 is an Ultra fast 5 A / 600 V diode
MURHD560T4G allowing Continuous Conduction Mode
with limited switching losses thanks to the low trr. The
reversed voltage applied by the tapped coil asks for a voltage
much higher than output voltage (classical boost).
To reduce peak voltage on the Power MOS switches, an
additional diode D2 is added. Thanks to the limited
conduction time, a 1 A / 200 V MURA120T3 is enough.
Tapped Boost Coil
To allow SLIM design below 8 mm height on top of the
PCB, the coil has been design on special bobbin to be
inserted within a PCB hole. Designed with PQ3811, the
primary inductance of 30 mH is able to support up to 12 A
without saturation while the secondary inductance with
270 mH allows to work with 50% duty cycle.
The 65 kHz switching frequency provides a good
compromise between switching losses, efficiency and boost
coil size.
ICs Supply
The CAT4026 is supplied through a 5 V linear regulator
IC2/MC78M05CDTG (up to 35 V input capable) connected
directly to the 24 V input voltage. Thanks to the limited
current consumption, the regulator is in a DPAK without
power dissipation issues.
Despite the NCP1252 could be directly supplied from the
24 V, we use 1 KW serial resistance (R1 + R1−1) and 15 V
zener ZD1 to avoid too high VCC, reducing the power
dissipation in the controller and avoiding Over Voltage
transients issues (VCC should not exceeds 28 V).
An additional diode D3 is connected from VCC to the
output voltage avoiding NCP1252 to start with output short
circuit to GND. To avoid safety issues if the 24 V power
supply is not capable to detect this short circuit, the added
fuse F1, in series with the output, will open−up and so
disconnect the output from the 24 V supply.
Electrolytic Capacitors
To allow low profile design, all electrolytic capacitors are
10 mm diameter type, solder flat on the board with open
holes allowing the parts to be partially below the PCB. The
high RMS currents require using multiple capacitors in
parallel for both the input and output of boost converter.
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Boost Oscillograms
Brown Out: Vstart = 21.1 V & Vstop = 19.4 V
Figure 8. Boost Coil Current Waveform
For Vin = 24 V – 10%, Vout = 125 V, Pout = 73 W
Power MOS Q1 & Q2 Drain Voltage
50 V/div VDrain Max = 171 V
Boost coil input current
5 A/div
IcoilMax = 8.1 A
5 µs/div
62.2 kHz
Figure 9. Boost Coil Current Waveform
For Vin = 24 V + 10%, Vout = 125 V, Pout = 73 W
Power MOS Q1 & Q2 Drain Voltage
50 V/div VDrain Max = 170 V
Boost coil input current
5 A/div
IcoilMax = 7.5 A
5 µs/div
63.7 kHz
Figure 10. Boost Coil Current Waveform
For Vin = 24 V − 10%, Vout = 125 V, Pout = 10 W
Power MOS Q1 & Q2 Drain Voltage
50 V/div VDrain Max = 141 V
Boost coil input current
5 A/div
IcoilMax = 3.5 A
5 µs/div
66.7 kHz
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Figure 11. Boost Coil Current Waveform
For Vin = 24 V + 10%, Vout = 125 V, Pout = 10 W
Power MOS Q1 & Q2 Drain Voltage
50 V/div VDrain Max = 141 V
Boost coil input current
5 A/div
IcoilMax = 3 A
5 µs/div
62.3 kHz
Figure 12. Boost Diode D1 Current Waveform
For Vin = 24 V + 10%, Vout = 125 V, Pout = 73 W
Boost diode D1 reversed Voltage
100 V/div VDiodeMax = 340 V
Boost diode D1 current
1 A/div
IDiodeMax = 2.6 A
5 µs/div
63.5 kHz
Figure 13. Boost Diode D1 Switch OFF Waveform
Expend of Figure 12
For Vin = 24 V + 10%, Vout = 125 V, Pout = 73 W
Boost diode D1 reversed Voltage
100 V/div VdiodeMax = 340 V
Boost diode D1 current
1 A/div
IDiodeMax = 2.6 A
100 ns/div 63.5 kHz
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Figure 14. Boost Diode D1 Switch ON
Expend of Figure 12
For Vin = 24 V + 10%, Vout = 125 V, Pout = 73 W
Boost diode D1 reversed Voltage
100 V/div VdiodeMax = 165 V
Boost diode D1 current
1 A/div
IDiodeMax = 2.6 A
100 ns/div 63.5 kHz
Figure 15. Current in the Boost Diode D1
For Vin = 24 V + 10%, Vout = 125 V, Pout = 10 W
Boost diode D1 reversed Voltage
100 V/div VDiodeMax = 309 V
Boost diode D1 current
1 A/div
IDiodeMax = 0.92 A
5 µs/div
63 kHz
Figure 16. Current in the Tapped Boost Diode D2
For Vin = 24 V + 10%, Vout = 125 V, Pout = 73 W
Tapped Boost diode D2 reversed Voltage
100 V/div VDiodeMax = 203 V
Boost diode D1 current
5 A/div
IDiodeMax = 9.9 A
5 µs/div
63.7 kHz
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Figure 17. Current in the Tapped Boost Diode D2
Expend of Figure 16
For Vin = 24 V + 10%, Vout = 125 V, Pout = 73 W
Tapped Boost diode D2 reversed Voltage
100 V/div VDiodeMax = 203 V
Boost diode D1 current
5 A/div
IDiodeMax = 9.9 A
100 ns/div 63.7 kHz
Figure 18. Current in the Boost Coil
For Vin = 24 V, Vout = 125 V, Pout = 0 W = No load
Power MOS Q1 & Q2 Drain Voltage
50 V/div VDrain Max = 73 V
Boost coil input current
0.5 A/div IcoilMax = 0.55 A
5 µs/div
62.2 kHz
Boost Efficiency
For nominal 24 V input and 123 V output, the DC−DC boost efficiency performance is as follows.
• For 10 W load, the efficiency = 100 x Pout / Pin = 100 x (VOUT x IOUT) / (VIN x IIN) = 82.5%.
• For 73 W load, the efficiency = 87%.
LED Driver Operation
feedback (IFB pin) to be interfaced to a DC/DC converter for
automatically adjusting the anode voltage to the lowest level
and therefore maximizes the power supply efficiency. The
CAT4026 also detects shorted LEDs within a string or an
open LED string fault condition. Both PWM and analog
voltage inputs are available for dimming control.
The CAT4026 controller regulates the current
independently in the 6 LED strings by using external NPN
power transistors and monitoring the voltage across the
sense resistors tied to ground. Accurate constant current is
guaranteed in each string so that the device is ideal for large
LCD backlight applications. The controller senses each
cathode string voltage and provides an output current
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LED Current Setting
The LED current is set to 100 mA independently in each
of the six channels by using 10 W resistors connected
between the CAT4026 RSET[1−7] pins and ground. For
setting the LED current to another value, the following
equation can be used to calculate the RSET resistor value.
RSET[W] + 1 V ń LED Current [A]
The LEDs can be dimmed dynamically by applying a
300 Hz PWM signal to the PWM input. Figure 19 shows the
variation of the LED current versus the PWM duty cycle.
The PWM input voltage should not exceed 5 V maximum.
The PWM logic high threshold is 2.5 V, so to enable the
CAT4026 the PWM input should be above 2.5 V.
100
Figure 21. PWM Waveforms 1% Duty Cycle Zoomed
LED CURRENT [%]
80
60
40
20
0
0
20
40
60
DUTY CYCLE [%]
80
100
Figure 19. LED Current vs. Duty Cycle
In Figure 20 to Figure 24, the waveforms can be seen for
duty cycles of 1, 50, and 95%.
Figure 22. PWM Waveforms 50% Duty Cycle
Figure 20. PWM Waveforms 1% Duty Cycle
Figure 23. PWM Waveforms 95% Duty Cycle
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Open Cathode−Anode (OCA) Fault Protection
To use the ANLG input for analog dimming, an external
1 kW resistor is needed to provide current limiting when an
SCA fault occurs, otherwise leave the pin unconnected. The
LED brightness versus ANLG input pin voltage is shown in
Figure 24.
The CAT4026 OCA input is used to detect and protect
against abnormally high LED Anode condition. An external
resistive divider connected between the LED anode and the
OCA pin will trigger a fault FLT−OCA condition once the
OCA pin voltage exceeds 1.0 V. Any open−LED channel
will automatically be disabled and removed from the
feedback loop when OCA is triggered. This method
provides an auto−recovery feature for the system to resume
normal operation by ensuring only the ‘good’ LED channels
are included in the feedback loop. A latched OCA fault
condition (FLT−OCA active low) will be set on the
connector CON31 pin P2 when the OCA threshold has been
reached.
Figure 26 shows the operation of the OCA fault
occurrence during power−up.
120
LED BRIGHTNESS (%)
100
80
60
40
20
0
0
1
2
3
4
ANLG VOLTAGE (V)
Figure 24. LED Brightness vs. ANLG Pin Voltage
Normal Operation
Figure 25 shows a power−up waveform once the PWM is
enabled for a nominal 100 V anode voltage VOUT.
Figure 26. OCA Fault During Power Up
Figure 27 shows the operation of the OCA fault
occurrence in live operation.
Figure 25. Normal Power Up
Fault Protection (Open LED, Short LED)
The board supports two fault detection open−drain output
signals FLT−OCA and FLT−SCA which are pulled low
when a fault condition occurs respectively open−LED or
shorted−LED. In normal operation, when the faults are not
present, these two signals are pulled high to the 5 V VDD
rail.
Figure 27. OCA Fault in Live Operation
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Short Cathode−Anode (SCA) Fault Protection
Performance
The CAT4026 SCA pin is used to detect a severe
mismatch in LED string voltage, such as the occurrence of
a short between several LEDs (anode to cathode) within one
string. The SCA pin is connected to each LED cathode via
a diode array and a voltage level translator. The SCA
threshold voltage of the detector is set and can be adjusted
by using an external Zener diode (ZD31) nominally set to
25 V and a series resistor (R52) 3 kW. The SCA trigger
voltage is set to about 30 V on the board. An unlatched signal
will be produced by the FLT−SCA pin. The fault FLT−SCA
output is connected to the ANLG pin through a diode and
pulls the ANLG pin lower to 0.6 V when the SCA fault is
present (FLT−SCA low), thereby limiting the current in each
channel to 20 mA.
Figure 28 shows the operation of the SCA fault
occurrence during power−up.
Figure 30 shows the overall efficiency (power in LEDs
divided by power in) versus VIN for a 100 V LED string at
about 600 mA current. The average efficiency is about 87%.
100
EFFICIENCY (%)
95
90
85
VLED = 100 V @
ILED = 597 mA
80
75
20
22
24
26
28
INPUT VOLTAGE (V)
Figure 30. Efficiency vs. VIN
This board shows very tight voltage and current line
regulation with an input voltage variation from 20 V to 28 V
of about 0.80% and 0.03% respectively.
Feedback Loop Circuit
This feedback circuit shown in Figure 31 is driven by the
CAT4026 IFB pin which is connected to the NCP1252 FB
feedback pin via an inverting current amplifier circuit
(current mirror). It also contains two 75 V zener diodes
(ZD2 and ZD3) in series tied to VOUT to limit the output
voltage to about 145 V max in case the CAT4026 IFB
becomes disconnected.
Figure 28. SCA Fault at Power Up
Figure 29 shows the operation of the SCA fault
occurrence in live operation.
Figure 31. Feedback Circuit
Figure 29. SCA Fault in Live Operation
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Test Procedure
•
•
•
•
•
Warning: Due to the high−voltage (up to 150 V) present on
the board and on the LED load, the test set−up should be
handled with care.
The following steps are needed for the installation of the
board together with the power supply and the load. The load
consists of LED strings, or an equivalent resistive load, with
a voltage drop of around 100 V when biased with a 100 mA
current per string (600 mA total).
Connect the 24 V DC external supply with a current limit
set to 4 A to the board connector CN01 P8 (VIN). Connect
the external supply Ground to connector CN01 P1 (Gnd).
Connect the PWM input to the connector CN31 P8. The
PWM input should never exceed 5 V.
Before powering−up the board, an LED load (or
equivalent resistive load) should be connected to each of the
six LED channels on connector CN30 or connect one load
with all channels in parallel. The connector CN04 includes
6 LED cathode pins and 6 anode voltage pins connected
together.
To use separate strings, connect the cathodes or one side
of the 1.2 kW resistive loads rated at 25 W to each of the
cathode pins CN04 P2, P4, P6, P8, P10, and P12 (LED1−6),
and the anode or other side of the resistive loads to CN04 P1,
P3, P5, P7, P9, and P11 (VIN).
To use one single load string, short CN04 P2, P4, P6, P8,
P10, and P12 (LED1−6) together and connect to the cathode
or one side of a 200 W load rated at 150 W, and connect
CN04 P1, P3, P5, P7, P9, and P11 (VIN) to the anode or other
end of the resistive load.
Set the DC power supply (VIN) to a low 18 V to test the
under−voltage lockout (UVLO) functionality. Ensure the
LEDs do not turn on, while the PWM input is at 5 V.
Connect the PWM input to GND (logic low).
Turn on the power supply VIN to 18 V.
Set the PWM input to 5 V (logic high).
Make sure the LEDs do not turn on.
Set the PWM to GND and turn off the power supply
VIN.
• Turn on the power supply VIN to 24 V.
• Set the PWM input to 5 V (logic high).
Make sure both the short and open cathode−anode fault
pins (FLT−SCA on CN31 P4 and FLT−OCA on CN31 P2)
are pulled high to 5 V VDD.
Measure the current in the LED string (or resistive load)
with an ammeter, the average current should be around
100 mA.
On one string, short 10 LEDs or the equivalent to bring the
cathode voltage to about 31 V, and verify that the SCA fault
FLT−SCA pin is pulled low and the LED current is dropped
down to around 20 mA per channel.
Unshort the load and verify that there once again is
100 mA of current and the SCA fault pin is not pulled to
ground.
Open the load and verify that the OCA fault FLT−OCA
pin is pulled low and stays low even after reconnecting the
load.
Using a function generator, set the PWM signal for a
300 Hz frequency, 5 Vpk−pk amplitude, 2.5 V offset, and
50% duty cycle pulse train. Measure the average current
through the load which should be around 50 mA.
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Board Schematic
Figure 32. Board Schematic Part 1 of 2 (DC−DC NCP1252 Boost Section)
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Figure 33. Board Schematic Part 2 of 2 (CAT4026 Linear LED Driver Section)
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BOARD LIST OF COMPONENTS
Table 1. BOARD LIST OF COMPONENTS FOR THE NCP1252 SECTION
Name
Manufacturer
Description
Part Number
Units
C1, C2, C3
Rubycon
Chemi−con
Electrolytic Capacitor 560 mF, 35 V, 20%
ZL 35V 560 mF 10x25
EKZE 35V 560 mF 10 x 25
3
C4, C5, C6
Rubycon
Chemi−con
Electrolytic Capacitor 100 mF, 200 V, 20%
TXW 200V 100 mF 10x40
EKXJ 200V 120 mF 10 x 40
3
C7
Vishay Roederstein
Ceramic Capacitor 10 nF, 400 V, 5%
MKP18040310404M
0/NA
C8
Vishay
Ceramic Capacitor 1 nF, 400 V, 10%
BFC237051102
1
C9
Kemet
Ceramic Capacitor 1 nF, 50 V, 10%
C0805C102K5RACTU
1
C18
Kemet
Ceramic Capacitor 47 nF, 50 V, 10%
C0805C473K5RAC
1
C11
Kemet
Ceramic Capacitor 10 nF, 50 V, 10%
C0805C103K5RACTU
1
50MS510M6357
EKMG500ELL100ME11D
2
C10, C16
Rubycon
Chemi−con
Electrolytic Capacitor 10 mF, 50 V, 20%
C12
Kemet
Ceramic Capacitor 220 pF, 50 V
C0805C221K5RACTU
1
C15, C17
Kemet
Ceramic Capacitor 100 nF, 50 V, 10%
C0805C104K5RACTU
2
Kemet
Ceramic Capacitor 470 nF, 50 V, 10%
C13, C14
C0805C474K5RACTU
2
CON1
LEAMAX Enterprise
Connector
4324−08R
1
CON3
LEAMAX Enterprise
Connector
4324−03R
0/NA
D1
ON Semiconductor
5 A, 600 V MEGAHERTZt Ultrafast Rectifier
MURHD560T4G
1
D2
ON Semiconductor
Ultrafast Power Rectifier
MURA120T3
1
D3
ON Semiconductor
Switching Diode, 250 V
MMSD103T1G
1
D4, D5
ON Semiconductor
Switching Diode, 100 V
MMSD4148T1G
2
Vishay Dale
Zero Value Resistor 5%
CRCW12060000Z0EA
1
ON Semiconductor
Switching Diode, 100 V
D8
D6, D7, D9
F1
Heatsink1
Hole 1 – Hole 6
Vishay
Columbia−Staver
Kang Yang
Fuse Resistor 0.22 Ω, 0.5 W
Aluminum Heatsink
Ground Lugs
MMSD4148T1G
0/NA
NFR25H0002207JA100
1
TP209ST, 80.0, 7.0, NA,−−, 02B
1
GND−15
6
1
IC1
ON Semiconductor
Current Mode PWM Controller
NCP1252BDR2G
IC2
ON Semiconductor
500 mA, 5 V Voltage Regulator 5%
MC78M05CDTG
1
−
10
CRCW12060000Z0EA
15
RFB0807−2R2L
1
PFC3811QM−691K
1
J1 – J10
−
J50 – J64
Vishay Dale
Wire Jumpers
Zero Value Resistor 5%
L1
Coilcraft
L2
TDK
Tapped Boost Inductor
Q1, Q2
STM
Power N−MOSFET 20 A, 200 V
STF19NF20
2
Q3, Q4
ON Semiconductor
NPN General Purpose Transistor
BC848ALT1G
2
Q5, Q6
ON Semiconductor
PNP General Purpose Transistor
BC808−25LT1G
2
Q7
ON Semiconductor
PNP General Purpose Transistor
BC858ALT1G
0/NA
R16
Vishay Draloric
Resistor SMD 33 Ω, 1%
CRCW0805133RFKEA
1
R1, R1−1
Vishay Draloric
Resistor SMD 2.2 kΩ, 1%
CRCW08052K20FKEA
2
R2
Vishay Draloric
Resistor SMD 180 kΩ, 1%
CRCW0805180KFKEA
1
R3, R17
Vishay Draloric
Resistor SMD 100 Ω, 1%
CRCW0805100RFKEA
2
R4, R4−1
Vishay Draloric
Resistor SMD 2.2 kΩ, 1%
CRCW08052K20FKEA
0/NA
CCF5510K0FKE36
1
R5
Vishay Dale
Inductor 2.2 mH, 5%
Resistor Through Hole 10 kΩ, 1%
R6
Vishay Draloric
Resistor SMD 10 kΩ, 1%
CRCW080510K0FKEA
1
R19
Vishay Draloric
Resistor SMD 1.2 kΩ, 1%
CRCW120611K2FKEA
1
R20
Vishay Draloric
Resistor SMD 3.3 kΩ, 1%
CRCW080513K3FKEA
1
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Table 1. BOARD LIST OF COMPONENTS FOR THE NCP1252 SECTION
Name
Manufacturer
Description
Resistor SMD 4.7 kΩ, 1%
Part Number
Units
CRCW080514K7FKEA
0/NA
R21
Vishay Draloric
R13
Vishay Draloric
Resistor SMD 4.7 kΩ, 1%
CRCW120614K7FKEA
1
R7, R9
Vishay Draloric
Resistor SMD 27 Ω, 1%
CRCW0805127RFKEA
2
R11, R12
Welwyn
WP2S−R1A25
2
R8, R10
Vishay Draloric
Resistor Through Hole 0.1 Ω, 5%, 2 W
Resistor SMD 47 kΩ, 1%
CRCW0805147KFKEA
2
R18
Vishay Draloric
Resistor SMD 510 Ω, 1%
CRCW0805510RFKEA
1
R15
Vishay Draloric
Resistor SMD 68 kΩ, 1%
CRCW080568K0FKEA
1
R14
−
−
0/NA
R22
Vishay Draloric
Resistor SMD 1 kΩ, 1%
RC1206FR−071KL
0/NA
R23, R24
Vishay Draloric
Resistor SMD 10 kΩ, 1%
CRCW080510K0FKEA
0/NA
ZD2, ZD3
ON Semiconductor
68 V Zener Diode 500 mW 5%
MMSZ5266BT1G
2
ZD1
ON Semiconductor
15 V Zener Diode 500 mW 5%
MMSZ5245BT1G
1
Part Number
Units
Resistor SMD
Table 2. BOARD LIST OF COMPONENTS FOR THE CAT4026 SECTION
Name
Manufacturer
Description
C30
MULTICOMP
Ceramic Capacitor 1 nF, 50 V, 10%
MCCA000350
0/NA
C31
YAGEO
Ceramic Capacitor 1 nF, 200 V, 10%
CC1206KRX7RABB102
1
C32
KEMET
Ceramic Capacitor 1 mF, 10 V, 10%
C0805C105K8RACTU
1
C33
MULTICOMP
Ceramic Capacitor 100 nF, 16 V, 10%
MCCA000274
1
C34
MULTICOMP
Ceramic Capacitor 100 pF, 50 V, 10%
MCCA000330
1
C35
MULTICOMP
Ceramic Capacitor 10 nF, 50 V, 10%
MCCA000368
0/NA
C36
MULTICOMP
Ceramic Capacitor 100 nF, 16 V, 10%
MCCA000274
0/NA
1
CON30
LEAMAX Enterprise
Connector
4324−12R
CON31
LEAMAX Enterprise
Connector
4324−08R
1
CON32
LEAMAX Enterprise
Connector
4324−07R
0/NA
D30 – D37
ON Semiconductor
Switching Diode, 250 V
BAS21LT1G
8
D38
ON Semiconductor
Switching Diode, 100 V
MMSD4148T1G
1
ZD31
ON Semiconductor
25 V Zener Diode, 500 mW 5%
MMSZ5253BT1G
1
ZD30
ON Semiconductor
15 V Zener Diode, 500 mW 5%
MSZ5245BT1G
0/NA
TP209ST,120,7.0,NA,−−,02B
1
Heatsink 30
Columbia−Staver
Aluminum Heatsink
IC30
ON Semiconductor
6−Channel LED Controller
IC31
ON Semiconductor
Low Input Bias Current, 1.8 V OpAmp
J11 – J37
J100 – J135
−
Vishay Dale
Wire Jumpers
Zero Value Resistors 1%
CAT4026V−T1
1
LMV301SQ3T2G
0/NA
−
27
CRCW12060000Z0EA
36
MJD340G
6
Q30A – Q35A
ON Semiconductor
High Voltage Power Transistors NPN
Q30 – Q35
ON Semiconductor
Bipolar Power NPN
MJF47G
6
Q36
ON Semiconductor
NPN General Purpose Transistor
BC848ALT1G
0/NA
Q37
ON Semiconductor
General Purpose High Voltage Transistor NPN
MSD42WT1G
0/NA
Q38
ON Semiconductor
General Purpose High Voltage Transistor NPN
MSD42WT1G
1
R36
Vishay Draloric
Resistor SMD 18 kΩ, 1%
CRCW080518K0FKEA
0/NA
R46
Vishay Draloric
Resistor SMD 10 kΩ, 1%
CRCW080510K0FKEA
1
R37, R44, R45
Vishay Draloric
Resistor SMD 47 kΩ, 1%
CRCW0805147KFKEA
0/NA
R90, R53
Vishay Draloric
Resistor SMD 5.1 kΩ, 1%
CRCW080510K0FKEA
2
R49
Vishay Draloric
Resistor SMD 0 Ω, 1%
CRCW08050000Z0EA
0/NA
R50, R60 – R65
Vishay Draloric
Resistor SMD 0 Ω, 1%
CRCW08050000Z0EA
7
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17
AND8478/D
Table 2. BOARD LIST OF COMPONENTS FOR THE CAT4026 SECTION
Name
Manufacturer
Description
Part Number
Units
R43
Vishay Draloric
Resistor SMD 47 kΩ, 1%
CRCW0805147KFKEA
1
R41
Vishay Draloric
Resistor SMD 1 kΩ, 1%
CRCW08051K00FKEA
0/NA
R30 – R35, R54 −
R59, R48
Vishay Draloric
Resistor SMD 1 kΩ, 1%
CRCW08051K00FKEA
16
R39, R40
Vishay Draloric
Resistor SMD 100 kΩ, 1%
CRCW0805100KFKEA
0/NA
R38
Vishay Draloric
Resistor SMD 1.8 kΩ, 1%
CRCW08051K80FKEA
0/NA
R42
Vishay Draloric
Resistor SMD 510 Ω, 1%
CRCW080510R0FKEA
1
R52
Vishay Draloric
Resistor SMD 3.0 kΩ, 1%
CRCW08053K00FKEA
1
R47
Vishay Dale
Resistor SMD 130 kΩ, 1%
CRCW1206130KFKEA
1
R51
Vishay Dale
Resistor SMD 240 kΩ, 1%
CRCW0805240KFKEA
1
R66, R67 R70, R71,
R74, R75, R78, R79,
R82, R83, R86, R87
Vishay Dale
Resistor SMD 20 Ω, 1%
CRCW080520R0FKEA
12
R68, R69, R72, R73,
R76, R77, R80, R81,
R84, R85, R88, R89
−
−
0/NA
−
ON Semiconductor and
are registered trademarks of Semiconductor Components Industries, LLC (SCILLC). SCILLC reserves the right to make changes without further notice
to any products herein. SCILLC makes no warranty, representation or guarantee regarding the suitability of its products for any particular purpose, nor does SCILLC assume any liability
arising out of the application or use of any product or circuit, and specifically disclaims any and all liability, including without limitation special, consequential or incidental damages.
“Typical” parameters which may be provided in SCILLC data sheets and/or specifications can and do vary in different applications and actual performance may vary over time. All
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associated with such unintended or unauthorized use, even if such claim alleges that SCILLC was negligent regarding the design or manufacture of the part. SCILLC is an Equal
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