MICROCHIP TC1038

TC1037/TC1038/TC1039
Linear Building Block – Single Comparator in SOT Packages
Features
General Description
•
•
•
•
The TC1037/TC1038/TC1039 are single, low-power
comparators designed for low-power applications.
•
•
•
•
Tiny SOT-23A Packages
Optimized for Single Supply Operation
Ultra Low Input Bias Current: Less than 100pA
Low Quiescent Current: 4µA (TC1037),
Shutdown Mode: 4µA, 0.05µA (TC1038),
6µA (TC1039)
Shutdown Mode (TC1038)
2.0% Accurate Independent Voltage Reference
(TC1039)
Rail-to-Rail Inputs and Outputs
Operation Down to V DD = 1.8V
Applications
• Power Management Circuits
• Battery Operated Equipment
• Consumer Products
These comparators are specifically designed for
operation from a single supply. However, operation
from dual supplies also is possible, and power supply
current is independent of the magnitude of the power
supply voltage. The TC1037/TC1038/TC1039 operate
from two 1.5V alkaline cells down to VDD = 1.8V. Active
supply current is 4µA for the TC1037/TC1038 and 6µA
for the TC1039. Input and output swing of these
devices is rail-to-rail.
An active low shutdown input, SHDN, is available on
the TC1038 and disables the comparator, placing its
output in a high-impedance state. The TC1038 draws
only 0.05µA (typical) when the shutdown mode is
active.
An internally biased 1.20V bandgap reference is
included in the TC1039. The reference is accurate to
2.0 percent tolerance. This reference is independent of
the comparator in the TC1039.
Device Selection Table
Part Number
Package
Temperature
Range
TC1037CECT
5-Pin SOT-23A
-40°C to +85°C
TC1038CECH
6-Pin SOT-23A
-40°C to +85°C
Packaged in a 5-Pin SOT-23A (TC1037) or 6-Pin
SOT-23A (TC1038/TC1039), these single comparators
are ideal for applications requiring high integration,
small size and low power.
TC1039CECH
6-Pin SOT-23A
-40°C to +85°C
Functional Block Diagram
Package Types
OUTPUT
5-Pin SOT-23A
5
6-Pin SOT-23A
IN-
VDD
SHDN
IN-
4
6
5
4
VSS
5
IN+
VDD
2
+
VDD
1
–
3
4
IN-
TC1037
TC1037ECT
1
2
1
3
2
OUTPUT VSS
IN+
3
OUTPUT
VSS
IN+
6-Pin SOT-23A
VDD
REF
IN-
6
5
4
TC1039ECH
2
OUTPUT VSS
NOTE: 5-Pin SOT-23A is equivalent to the EIAJ SC-74A.
6-Pin SOT-23A is equivalent to the EIAJ SC-74.
 2002 Microchip Technology Inc.
IN+
2
5
VDD
SHDN
–
3
4
IN-
TC1038
OUTPUT
1
VSS
2
IN+
3
3
IN+
6
Voltage
Reference
+
1
1
+
OUTPUT VSS
TC1038ECH
–
6
5
4
VDD
REF
IN-
TC1039
DS21344B-page 1
TC1037/TC1038/TC1039
1.0
ELECTRICAL
CHARACTERISTICS
*Stresses above those listed under "Absolute Maximum
Ratings" may cause permanent damage to the device. These
are stress ratings only and functional operation of the device
at these or any other conditions above those indicated in the
operation sections of the specifications is not implied.
Exposure to Absolute Maximum Rating conditions for
extended periods may affect device reliability.
ABSOLUTE MAXIMUM RATINGS*
Supply Voltage ......................................................6.0V
Voltage on Any Pin .......... (V SS – 0.3V) to (VDD + 0.3V)
Junction Temperature....................................... +150°C
Operating Temperature Range............. -40°C to +85°C
Storage Temperature Range .............. -55°C to +150°C
TC1037/TC1038/TC1039 ELECTRICAL SPECIFICATIONS
Electrical Characteristics: Typical values apply at 25°C and VDD = 3.0V. Minimum and maximum values apply for TA = -40° to
+85°C and VDD = 1.8V to 5.5V, unless otherwise specified.
Symbol
Parameter
Min
Typ
Max
Units
Test Conditions
VDD
Supply Voltage
1.8
—
5.5
V
IQ
Supply Current, Operating (TC1039)
(TC1037/TC1038)
—
—
6
4
10
8
µA
µA
All Outputs Unloaded,
SHDN = VDD for TC1038
ISHDN
Supply Current Shutdown Mode
(TC1038 Only)
—
—
0.3
µA
SHDN = VSS
Shutdown Input (TC1038 Only)
VIH
Input High Threshold
80% VDD
—
—
V
VIL
Input Low Threshold
—
—
20% VDD
V
ISI
Shutdown Input Current
—
—
±100
nA
Comparator
ROUT(SD)
Output Resistance in Shutdown
20
—
—
MΩ
COUT(SD)
Output Capacitance in Shutdown
—
—
5
pF
SHDN = VSS (TC1038 Only)
TSEL
Select Time
—
20
—
µsec
VOUT Valid from SHDN = VIH
RL = 10kΩ to VSS (TC1038 Only)
TDESEL
Deselect Time
—
500
—
nsec
VOUT Valid from SHDN = VIL
RL = 10kΩ to VSS
SHDN = VSS (TC1038 Only)
VICMR
Common Mode Input Voltage Range VSS – 0.2
—
VDD + 0.2
V
AVOL
Large Signal Voltage Gain
—
100
—
V/mV
GBWP
Gain Bandwidth Product
—
90
—
kHz
VDD = 1.8V to 5.5V;
VO = VDD to VSS
VOS
Input Offset Voltage
–5
–5
—
+5
+5
mV
mV
VDD = 3V, VCM = 1.5V, TA = 25°C,
TA = -40°C to 85°C
IB
Input Bias Current
—
—
±100
pA
TA = 25°C;
IN+, IN- = VDD to VSS
VOH
Output High Voltage
VDD – 0.3
—
—
V
RL = 10kΩ to VSS
VOL
Output Low Voltage
—
—
0.3
V
RL = 10kΩ to VDD
CMRR
Common Mode Rejection Ratio
66
—
—
dB
TA = 25°C; VDD = 5V;
VCM = VDD to VSS
PSRR
Power Supply Rejection Ratio
60
—
—
dB
TA = 25°C; VCM = 1.2V;
VDD = 1.8V to 5V
ISRC
Output Source Current
1
—
—
mA
IN+ = VDD, IN- = VSS
Output Shorted to VSS
VDD = 1.8V
ISINK
Output Sink Current
2
—
—
mA
IN+ = VSS, IN- = VSS
Output Shorted to VSS
VDD = 1.8V
TPD1
Response Time
—
4
—
µsec
100mV Overdrive, C L = 100pF
TPD2
Response Time
—
6
—
µsec
10mV Overdrive, CL = 100pF
DS21344B-page 2
RL = 10kΩ, VDD = 5V
 2002 Microchip Technology Inc.
TC1037/TC1038/TC1039
TC1037/TC1038/TC1039 ELECTRICAL SPECIFICATIONS (CONTINUED)
Electrical Characteristics: Typical values apply at 25°C and VDD = 3.0V. Minimum and maximum values apply for TA = -40° to
+85°C and VDD = 1.8V to 5.5V, unless otherwise specified.
Symbol
Parameter
Min
Typ
Max
Units
1.176
1.200
1.224
V
Test Conditions
Voltage Reference (TC1039 Only)
VREF
Reference Voltage
50
—
—
µA
IREF(SINK)
Sink Current
50
—
—
µA
CL(REF)
Load Capacitance
—
—
100
pF
E VREF
Noise Voltage
—
20
—
µVRMS
eVREF
Noise Voltage Density
—
1.0
—
µV/√Hz 1kHz
IREF(SOURCE) Source Current
 2002 Microchip Technology Inc.
100Hz to 100kHz
DS21344B-page 3
TC1037/TC1038/TC1039
2.0
PIN DESCRIPTIONS
The description of the pins are listed in Table 2-1.
TABLE 2-1:
PIN FUNCTION TABLE
Pin No.
TC1037
(5-Pin SOT-23A)
Symbol
1
OUTPUT
2
VSS
Negative power supply.
3
IN+
Comparator non-inverting input.
4
IN-
Comparator inverting input.
5
VDD
Positive power supply.
Pin No.
TC1038
(6-Pin SOT-23A)
Symbol
1
OUTPUT
2
VSS
Negative power supply.
3
IN+
Comparator non-inverting input.
4
IN-
Comparator inverting input.
5
SHDN
6
VDD
Pin No.
TC1039
(6-Pin SOT-23A)
Symbol
1
OUTPUT
2
VSS
Negative power supply.
3
IN+
Comparator non-inverting input.
4
IN-
Comparator inverting input.
5
REF
1.20V bandgap voltage reference output (TC1039 only).
6
VDD
Positive power supply.
DS21344B-page 4
Description
Comparator output.
Description
Comparator output.
Active low shutdown input (TC1038 only). A low input on this pin disables the comparator
and places the output terminal in a high impedance state.
Positive power supply.
Description
Comparator output.
 2002 Microchip Technology Inc.
TC1037/TC1038/TC1039
3.0
DETAILED DESCRIPTION
The TC1037/TC1038/TC1039 are a series of very low
power, linear building block products targeted at low
voltage, single supply applications. The TC1037/
TC1038/TC1039 minimum operating voltage is 1.8V
and typical supply current is only 4µA for the TC1037
and TC1038 (fully enabled) and 6µA for the TC1039.
4.0
The TC1037/TC1038/TC1039 family lends itself to a
wide variety of applications, particularly in battery
powered systems. It typically finds application in power
management, processor supervisory and interface
circuitry.
4.1
3.1
Comparator
The TC1037/8/9 contain one comparator. The
comparator’s input range extends beyond both supply
voltages by 200mV and the outputs will swing to within
several millivolts of the supplies depending on the load
current being driven.
1.
2.
3.
3.2
Voltage Reference
External Hysteresis (Comparator)
Hysteresis can be set externally with two resistors
using positive feedback techniques (see Figure 4-1).
The design procedure for setting external comparator
hysteresis is as follows:
The comparator exhibits a propagation delay and
supply current which is largely independent of supply
voltage. The low input bias current and offset voltage
makes it suitable for high impedance precision
applications.
The TC1038 comparator is disabled during shutdown
and has a high impedance output.
TYPICAL APPLICATIONS
Choose the feedback resistor RC. Since the
input bias current of the comparator is at most
100pA, the current through RC can be set to
100nA (i.e., 1000 times the input bias current)
and retain excellent accuracy. The current
through RC at the comparator’s trip point is VR /
RC where VR is a stable reference voltage.
Determine the hysteresis voltage (VHY) between
the upper and lower thresholds.
Calculate RA as follows:
EQUATION 4-1:
A 2.0% tolerance, internally biased, 1.20V bandgap
voltage reference is included in the TC1039. It has a
push-pull output capable of sourcing and sinking at
least 50µA.
V HY
R A = R C  -----------
V

DD
4.
3.3
Shutdown Input (TC1038 Only)
SHDN at VIL disables the comparator and reduces the
supply current to less than 0.3µA. The SHDN input
cannot be allowed to float. When not used, connect it to
VDD. The comparator’s output is in a high impedance
state when the TC1038 is disabled. The comparator’s
inputs can be driven from rail-to-rail by an external
voltage when the TC1038 is disabled. No latchup will
occur when the device is driven to its enabled state
when SHDN is set to VIH.
5.
Choose the rising threshold voltage for VSRC
(VTHR).
Calculate RB as follows:
EQUATION 4-2:
1
R B = ----------------------------------------------------------V THR  1
1
 -------------------- – ------- – ------V × R  R
R
A
A RC
6.
Verify the
formulas:
threshold
voltages
with
these
VSRC rising:
EQUATION 4-3:
1
1
1
V TH R = ( V R ) ( R A )  ------- +  ------- +  -------
RA
RB
RC
VSRC falling:
EQUATION 4-4:
V THF = V THR –
 2002 Microchip Technology Inc.
R A × V DD
 -----------------------
RC 
DS21344B-page 5
TC1037/TC1038/TC1039
4.2
Precision Battery Monitor
Figure 4-2 is a precision battery low/battery dead
monitoring circuit. Typically, the battery low output
warns the user that a battery dead condition is
imminent. Battery dead typically initiates a forced
shutdown to prevent operation at low internal supply
voltages (which can cause unstable system operation).
The circuit in Figure 4-2 uses a TC1034, a TC1037 and
a TC1039, and only six external resistors. AMP 1 is a
simple buffer, while CMPTR1 and CMPTR2 provide
precision voltage detection using VR as a reference.
Resistors R2 and R4 set the detection threshold for
BATT LOW, while resistors R1 and R3 set the detection
threshold for BATT FAIL. The component values shown
assert BATT LOW at 2.2V (typical) and BATT FAIL at
2.0V (typical). Total current consumed by this circuit is
typically 16µA at 3V. Resistors R5 and R6 provide
hysteresis for comparators CMPTR1 and CMPTR2,
respectively.
4.3
32.768 kHz “Time Of Day Clock”
Crystal Controlled Oscillator
A very stable oscillator driver can be designed by using
a crystal resonator as the feedback element. Figure 4-3
shows a typical application circuit using this technique
to develop a clock driver for a Time Of Day (TOD) clock
chip. The value of RA and RB determine the DC voltage
level at which the comparator trips – in this case onehalf of VDD. The RC time constant of RC and CA should
be set several times greater than the crystal oscillator’s
period, which will ensure a 50% duty cycle by maintaining a DC voltage at the inverting comparator input
equal to the absolute average of the output signal.
4.4
Non-Retriggerable One Shot
Multivibrator
Using two comparators, a non-retriggerable one shot
multivibrator can be designed using the circuit configuration of Figure 4-4. A key feature of this design is that
the pulse width is independent of the magnitude of the
supply voltage because the charging voltage and the
intercept voltage are a fixed percentage of VDD. In
addition, this one shot is capable of pulse width with as
much as a 99% duty cycle and exhibits input lockout to
ensure that the circuit will not re-trigger before the
output pulse has completely timed out. The trigger level
is the voltage required at the input to raise the voltage
at node A higher than the voltage at node B, and is set
by the resistive divider R4 and R10 and the impedance
network composed of R1, R2 and R3. When the one
shot has been triggered, the output of CMPTR2 is high,
causing the reference voltage at the non-inverting input
of CMPTR1 to go to V DD. This prevents any additional
input pulses from disturbing the circuit until the output
pulse has timed out.
DS21344B-page 6
The value of the timing capacitor C1 must be small
enough to allow CMPTR1 to discharge C1 to a diode
voltage before the feedback signal from CMPTR2
(through R10) switches CMPTR1 to its high state and
allows C1 to start an exponential charge through R5.
Proper circuit action depends upon rapidly discharging
C1 through the voltage set by R6, R9 and D2 to a final
voltage of a small diode drop. Two propagation delays
after the voltage on C1 drops below the level on the
non-inverting input of CMPTR2, the output of CMPTR1
switches to the positive rail and begins to charge C1
through R5. The time delay which sets the output pulse
width results from C1 charging to the reference voltage
set by R6, R9 and D2, plus four comparator propagation delays. When the voltage across C1 charges
beyond the reference, the output pulse returns to
ground and the input is again ready to accept a trigger
signal.
4.5
Oscillators and Pulse Width
Modulators
Microchip’s linear building block comparators adapt
well to oscillator applications for low frequencies (less
than 100kHz). Figure 4-5 shows a symmetrical square
wave generator using a minimum number of components. The output is set by the RC time constant of R4
and C1, and the total hysteresis of the loop is set by R1,
R2 and R3. The maximum frequency of the oscillator is
limited only by the large signal propagation delay of the
comparator in addition to any capacitive loading at the
output which degrades the slew rate.
To analyze this circuit, assume that the output is initially
high. For this to occur, the voltage at the inverting input
must be less than the voltage at the non-inverting input.
Therefore, capacitor C1 is discharged. The voltage at
the non-inverting input (VH) is:
EQUATION 4-5:
R2 ( V DD )
V H = --------------------------------------------[ R2 + ( R1 || R3 ) ]
where, if R1 = R2 = R3, then:
EQUATION 4-6:
2 ( V DD )
V H = ------------------3
 2002 Microchip Technology Inc.
TC1037/TC1038/TC1039
Capacitor C1 will charge up through R4. When the
voltage of the comparator's inverting input is equal to
VH, the comparator output will switch. With the output
at ground potential, the value at the non-inverting input
terminal (V L) is reduced by the hysteresis network to a
value given by:
basically the same as described for the free-running
oscillator. If the input control voltage is moved above or
below one-half VDD, the duty cycle of the output square
wave will be altered. This is because the addition of the
control voltage at the input has now altered the trip
points. The equations for these trip points are shown in
Figure 4-6 (see VH and VL).
EQUATION 4-7:
Pulse width sensitivity to the input voltage variations
can be increased by reducing the value of R6 from
10KΩ and conversely, sensitivity will be reduced by
increasing the value of R6. The values of R1 and C1
can be varied to produce the desired center frequency.
VL
V DD
= ---------3
Using the same resistors as before, capacitor C1 must
now discharge through R4 toward ground. The output
will return to a high state when the voltage across the
capacitor has discharged to a value equal to VL. The
period of oscillation will be twice the time it takes for the
RC circuit to charge up to one half its final value. The
period can be calculated from:
FIGURE 4-1:
COMPARATOR
EXTERNAL HYSTERESIS
CONFIGURATION
RC
TC1037
EQUATION 4-8:
1
----------------- = 2 ( 0.694 ) ( R4 ) ( C1 )
FREQ
VDD
RA
VSRC
+
RB
Figure 4-6 shows the circuit for a pulse width modulator
circuit. It is essentially the same as in Figure 4-5 with
the addition of an input control voltage. When the input
control voltage is equal to one-half V DD, operation is
FIGURE 4-2:
VOUT
–
The frequency stability of this circuit should only be a
function of the external component tolerances.
VR
PRECISION BATTERY MONITOR
To System DC/DC
Converter
R4, 470k, 1%
R5, 7.5M
VDD
VDD
+
TC1034
R2, 330k, 1%
+
AMP1
–
3V
Alkaline
CMPTR1
–
TC1037
BATTLOW
+
TC1039
VDD
R1, 270k, 1%
VR
TC1039
–
CMPTR2
BATTFAIL
+
R6, 7.5M
R3, 470k, 1%
 2002 Microchip Technology Inc.
DS21344B-page 7
TC1037/TC1038/TC1039
FIGURE 4-3:
32.768 kHz “TIME OF DAY” CLOCK OSCILLATOR
32.768kHz
VDD
TC1037
VDD
RA
150k
+
VOUT
–
RB
150k
RC
1M
CA
100pF
FIGURE 4-4:
Tper = 30.52µsec
NON-RETRIGGERABLE MULTIVIBRATOR
VDD
R3
1M
TC1037
R4
1M
R1
R5
10M
A
–
IN
100k
TC1025
C
C1
100pF
+
B
D1
GND
R10
61.9k
t0
R7
1M
VDD
OUT
–
CMPTR1
R2
100k
IN
R6
562k
OUT
CMPTR2
R8
R9
243k
GND
+
C
VDD
GND
10M
D2
FIGURE 4-5:
SQUARE WAVE GENERATOR
VDD
TC1037
R1
100k
R4
VDD
–
C1
+
VH =
R2 (VDD)
R2 + (R1||R3)
(VDD) (R2||R3)
R1 + (R2||R3)
1
FREQ =
2(0.694)(R4)(C1)
VL =
R2
100k
DS21344B-page 8
R3
100k
 2002 Microchip Technology Inc.
TC1037/TC1038/TC1039
FIGURE 4-6:
PULSE WIDTH MODULATOR
VDD
VC
R6
10k
TC1037
R1
100k
1/4
R4
VDD
–
+
C1
VH =
VDD (R1R2R6 + R2R3R6) + VC (R1R2R3)
R1R2R6 + R1R3R6 + R2R3R6 + R1R2R3
VL =
VDD (R2R3R6) + VC (R1R2R3)
R1R2R6 + R1R3R6 + R2R3R6 + R1R2R3
FREQ =
1
2 (0.694) (R4) (C1)
For Square Wave Generation
Select R1 = R2 = R3
R2
100k
 2002 Microchip Technology Inc.
R3
100k
VC = VDD
2
DS21344B-page 9
TC1037/TC1038/TC1039
TYPICAL CHARACTERISTICS
Note:
The graphs and tables provided following this note are a statistical summary based on a limited number of
samples and are provided for informational purposes only. The performance characteristics listed herein
are not tested or guaranteed. In some graphs or tables, the data presented may be outside the specified
operating range (e.g., outside specified power supply range) and therefore outside the warranted range.
Comparator Propagation Delay
vs. Supply Voltage
7
TA = 25°C
CL = 100pF
DELAY TO FALLING EDGE (µsec)
6
Overdrive = 10mV
5
4
Overdrive = 50mV
3
2
6
Overdrive = 10mV
5
Overdrive = 100mV
Overdrive = 50mV
4
3
2
2.5
3
3.5
4
4.5
5
1.5
5.5
2
6
VDD = 5V
5
VDD = 4V
VDD = 2V
4
VDD = 3V
2.5
3
3.5
4
4.5
5
5.5
-40°C
SUPPLY VOLTAGE (V)
2.5
7
2.5
VDD = 4V
VDD = 3V
VDD = 2V
4
VOUT - VSS (V)
VDD - VOUT (V)
VDD = 5V
TA = 25°C
2.0
2.0
6
85°C
Comparator Output Swing
vs. Output Sink Current
TA = 25°C
Overdrive = 100mV
25°C
TEMPERATURE (°C)
Comparator Output Swing
vs. Output Source Current
Comparator Propagation Delay
vs. Temperature
5
Overdrive = 100mV
3
SUPPLY VOLTAGE (V)
DELAY TO FALLING EDGE (µsec)
7
TA = 25°C
CL = 100pF
2
1.5
VDD = 3V
1.5
VDD = 1.8V
1.0
VDD = 5.5V
.5
1.5
VDD = 3V
1.0
VDD = 1.8V
.5
VDD = 5.5V
3
-40°C
0
0
25°C
0
85°C
3
2
4
ISOURCE (mA)
1
TEMPERATURE (°C)
Comparator Output Short-Circuit
Current vs. Supply Voltage
5
TA = -40°C
50
TA = 25°C
40
TA = 85°C
C
0°
30
TA
20
Sinking
10
Sourcing
0
0
=
-4
TA = 25°C
TA = 85°C
3
1
2
4
5
SUPPLY VOLTAGE (V)
DS21344B-page 10
VDD = 1.8V
VDD = 3V
1.220
VDD = 5.5V
Sinking
1.200
Sourcing
1.180
VDD = 5.5V
1.160
VDD = 1.8V
VDD = 3V
1.140
6
0
2
4
6
1
2
3
4
5
6
ISINK (mA)
1.240
60
0
6
Reference Voltage vs.
Load Current
REFERENCE VOLTAGE (V)
OUTPUT SHORT-CIRCUIT CURRENT (mA)
Comparator Propagation Delay
vs. Temperature
8
LOAD CURRENT (mA)
10
SUPPLY AND REFERENCE VOLTAGES (V)
DELAY TO RISING EDGE (µsec)
7
Comparator Propagation Delay
vs. Supply Voltage
DELAY TO RISING EDGE (µsec)
5.0
Line Transient
Response of VREF
4
VDD
3
2
VREF
1
0
0
100
200
300
400
TIME (µsec)
 2002 Microchip Technology Inc.
TC1037/TC1038/TC1039
TYPICAL CHARACTERISTICS (CONTINUED)
Reference Voltage
vs. Supply Voltage
1.25
Supply Current vs. Supply Voltage
Supply Current vs. Supply Voltage
3
5
SUPPLY CURRENT (µA)
REFERENCE VOLTAGE (V)
TC1037, TC1038
1.20
1.15
1.10
1.05
TC1039
TA = 85°C
SUPPLY CURRENT (µA)
5.0
TA = -40°C
2
TA = 25°C
1
4
2
3
SUPPLY VOLTAGE (V)
 2002 Microchip Technology Inc.
5
TA = -40°C
4
TA = 25°C
3
2
0
1
TA = 85°C
0
1
2
3
4
5
SUPPLY VOLTAGE (V)
6
0
1
2
3
4
5
SUPPLY VOLTAGE (V)
6
DS21344B-page 11
TC1037/TC1038/TC1039
6.0
PACKAGING INFORMATION
6.1
Package Marking Information
5-Pin SOT-23A
6-Pin SOT-23A
1 & 2 = part number code + temperature range and
voltage
Part Number
Code
TC1037CECT
AR
TC1038CECH
AS
TC1039CECH
AT
3 = year and quarter code
4 = lot ID number
6.2
Taping Form
Component Taping Orientation for 5-Pin SOT-23A (EIAJ SC-74A) Devices
User Direction of Feed
Device
Marking
W
PIN 1
P
Standard Reel Component Orientation
TR Suffix Device
(Mark Right Side Up)
Carrier Tape, Number of Components Per Reel and Reel Size
Package
5-Pin SOT-23A
DS21344B-page 12
Carrier Width (W)
Pitch (P)
Part Per Full Reel
Reel Size
8 mm
4 mm
3000
7 in
 2002 Microchip Technology Inc.
TC1037/TC1038/TC1039
6.3
Taping Form (Continued)
Component Taping Orientation for 6-Pin SOT-23A (EIAJ SC-74) Devices
User Direction of Feed
Device
Device
Device
Device
Device
Device
Marking
Marking
Marking
Marking
Marking
Marking
W
PIN 1
P
Standard Reel Component Orientation
For TR Suffix Device
(Mark Right Side Up)
Carrier Tape, Number of Components Per Reel and Reel Size
Package
6-Pin SOT-23A
 2002 Microchip Technology Inc.
Carrier Width (W)
Pitch (P)
Part Per Full Reel
Reel Size
8 mm
4 mm
3000
7 in
DS21344B-page 13
TC1037/TC1038/TC1039
6.3
Package Dimensions
SOT-23A-5
.075 (1.90)
REF.
.071 (1.80)
.059 (1.50)
.122 (3.10)
.098 (2.50)
.020 (0.50)
.012 (0.30)
PIN 1
.037 (0.95)
REF.
.122 (3.10)
.106 (2.70)
.057 (1.45)
.035 (0.90)
.010 (0.25)
.004 (0.09)
10° MAX.
.006 (0.15)
.000 (0.00)
.024 (0.60)
.004 (0.10)
Dimensions: inches (mm)
SOT-23A-6
.075 (1.90)
REF.
.069 (1.75)
.059 (1.50)
.122 (3.10)
.098 (2.50)
.020 (0.50)
.014 (0.35)
.037 (0.95)
REF.
.118 (3.00)
.110 (2.80)
.057 (1.45)
.035 (0.90)
.006 (0.15)
.000 (0.00)
.008 (0.20)
.004 (0.09)
10° MAX.
.024 (0.60)
.004 (0.10)
Dimensions: inches (mm)
DS21344B-page 14
 2002 Microchip Technology Inc.
TC1037/TC1038/TC1039
Sales and Support
Data Sheets
Products supported by a preliminary Data Sheet may have an errata sheet describing minor operational differences and recommended workarounds. To determine if an errata sheet exists for a particular device, please contact one of the following:
1.
2.
3.
Your local Microchip sales office
The Microchip Corporate Literature Center U.S. FAX: (480) 792-7277
The Microchip Worldwide Site (www.microchip.com)
Please specify which device, revision of silicon and Data Sheet (include Literature #) you are using.
New Customer Notification System
Register on our web site (www.microchip.com/cn) to receive the most current information on our products.
 2002 Microchip Technology Inc.
DS21344B-page15
TC1037/TC1038/TC1039
NOTES:
DS21344B-page16
 2002 Microchip Technology Inc.
TC1037/TC1038/TC1039
Information contained in this publication regarding device
applications and the like is intended through suggestion only
and may be superseded by updates. It is your responsibility to
ensure that your application meets with your specifications.
No representation or warranty is given and no liability is
assumed by Microchip Technology Incorporated with respect
to the accuracy or use of such information, or infringement of
patents or other intellectual property rights arising from such
use or otherwise. Use of Microchip’s products as critical components in life support systems is not authorized except with
express written approval by Microchip. No licenses are conveyed, implicitly or otherwise, under any intellectual property
rights.
Trademarks
The Microchip name and logo, the Microchip logo, FilterLab,
KEELOQ, microID, MPLAB, PIC, PICmicro, PICMASTER,
PICSTART, PRO MATE, SEEVAL and The Embedded Control
Solutions Company are registered trademarks of Microchip Technology Incorporated in the U.S.A. and other countries.
dsPIC, ECONOMONITOR, FanSense, FlexROM, fuzzyLAB,
In-Circuit Serial Programming, ICSP, ICEPIC, microPort,
Migratable Memory, MPASM, MPLIB, MPLINK, MPSIM,
MXDEV, PICC, PICDEM, PICDEM.net, rfPIC, Select Mode
and Total Endurance are trademarks of Microchip Technology
Incorporated in the U.S.A.
Serialized Quick Turn Programming (SQTP) is a service mark
of Microchip Technology Incorporated in the U.S.A.
All other trademarks mentioned herein are property of their
respective companies.
© 2002, Microchip Technology Incorporated, Printed in the
U.S.A., All Rights Reserved.
Printed on recycled paper.
Microchip received QS-9000 quality system
certification for its worldwide headquarters,
design and wafer fabrication facilities in
Chandler and Tempe, Arizona in July 1999
and Mountain View, California in March 2002.
The Company’s quality system processes and
procedures are QS-9000 compliant for its
PICmicro ® 8-bit MCUs, KEELOQ® code hopping
devices, Serial EEPROMs, microperipherals,
non-volatile memory and analog products. In
addition, Microchip’s quality system for the
design and manufacture of development
systems is ISO 9001 certified.
 2002 Microchip Technology Inc.
DS21344B-page 17
WORLDWIDE SALES AND SERVICE
AMERICAS
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Corporate Office
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03/01/02
*DS21344B*
DS21344B-page 18
 2002 Microchip Technology Inc.