TPA6047A4
www.ti.com.............................................................................................................................................................................................. SLOS601 – OCTOBER 2008
2-W STEREO AUDIO POWER AMPLIFIER
WITH DirectPath™ STEREO HEADPHONE DRIVE AND REGULATOR
FEATURES
1
• Microsoft™ Windows Vista™ Compliant
• Fully Differential Architecture and High PSRR
Provide Excellent RF Rectification Immunity
• 2.1-W, 1% THD+N Into 4-Ω Speakers and
100-mW, 10% THD+N Into 16-Ω Headphones
From 5-V Supply
• DirectPath™ Headphone Amplifier Eliminates
Output Capacitors (1)
• Internal 4-Step Speaker Gain Control: 10, 12,
15.6, 21.6 dB and Fixed –1.5-V/V Headphone
• 4.75-V Low Dropout Regulator for CODEC
• Independent Shutdown Controls for Speaker,
Headphone Amplifier, and Low Dropout
Regulator (LDO)
• Output Short-Circuit and Thermal Protection
23
DESCRIPTION
The TPA6047A4 is a stereo audio power amplifier
and DirectPath™ headphone amplifier in a thermally
enhanced, space-saving, 32-pin QFN package. The
speaker amplifier is capable of driving 2.1 W per
channel continuously into 4-Ω loads at 5 V. The
headphone amplifier achieves a minimum of 100 mW
at 10% THD+N from a 5-V supply. A built-in internal
4-step gain control for the speaker amplifier and a
fixed –1.5 V/V gain for the headphone amplifier
minimizes external components needed.
Independent shutdown control and dedicated inputs
for the speaker and headphone allow the TPA6047A4
to simultaneously drive both headphones and internal
speakers. Differential inputs to the speaker amplifiers
offer superior power-supply and common-mode noise
rejection.
APPLICATIONS
•
•
Notebook Computers
Portable DVD
SIMPLIFIED APPLICATION CIRCUIT
TPA6047A4
CODEC
SPKR
SPKR_RIN+
HPR
SPKR_RIN–
HPL
SPKL
VDD
LOUT+
LOUT–
SPKR_LIN–
SPVDD
BYPASS
SPGND
HP_EN
SPKR_EN
OUTL
HP_INR
SGND
OUTR
HP_INL
3 V – 5.5 V
GAIN1
HPVDD
CPVDD
TPA6041A4
TPA6047A4
Active Low
Active Low
Active High
4.75
3.3
4.75
Gain (dB)
6, 10, 15.6,
21.6
10, 12, 15.6,
21.6
10, 12, 15.6,
21.6
Gain
Control
HPVSS
CPVSS
CPGND
VDD
4.5 V – 5.5 V
Regulator Enable
4.5 V – 5.5 V
TPA6040A4
LDO (V)
SPKR_LIN+
GAIN0
Shutdown
Control
Speaker
Enable
ROUT+
ROUT–
C1P
C1N
REG_EN
REG_OUT
4.75 V (To CODEC)
(1)
US Patent Number 5289137
1
2
3
Please be aware that an important notice concerning availability, standard warranty, and use in critical applications of Texas
Instruments semiconductor products and disclaimers thereto appears at the end of this data sheet.
DirectPath, PowerPAD are trademarks of Texas Instruments.
Microsoft, Windows Vista are trademarks of Microsoft Corporation.
PRODUCTION DATA information is current as of publication date.
Products conform to specifications per the terms of the Texas
Instruments standard warranty. Production processing does not
necessarily include testing of all parameters.
Copyright © 2008, Texas Instruments Incorporated
TPA6047A4
SLOS601 – OCTOBER 2008.............................................................................................................................................................................................. www.ti.com
These devices have limited built-in ESD protection. The leads should be shorted together or the device placed in conductive foam
during storage or handling to prevent electrostatic damage to the MOS gates.
Functional Block Diagram
REG_EN
BYPASS
(4.75-V Output)
REG_OUT
SPKR_EN
Bias Control
0.47 mF
LDO
HP_EN
1 mF
VDD
SPVDD
1 mF
SPKR_RIN+
1 mF
+
ROUT+
–
+
SPKR_RIN–
ROUT–
–
1 mF
GAIN0
SPGND
Gain Control
GAIN1
SPVDD
SPKR_LIN+
1 mF
SPKR_LIN–
1 mF
4.5 V – 5.5 V
+
–
–
+
LOUT+
LOUT–
SPVDD
SPGND
1 mF
HPVDD
HP_INL
–
HP_OUTL
1 mF
+
HPVSS
+
HP_INR
HP_OUTR
–
3 V – 5.5 V 1 mF
HPVDD
HPVDD
CPVDD
1 mF
Charge Pump
CPGND
C1P
GND
HPVSS
C1N
CPVSS
SPGND
1 mF
1 mF
2
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AVAILABLE PACKAGE OPTIONS
(1)
TA
PACKAGED DEVICE (1) (2)
32-Pin QFN (RHB)
–40°C to 85°C
TPA6047A4RHB
The RHB package is available taped and reeled. To order a taped and reeled part, add the suffix R to
the part number (e.g., TPA6047A4RHBR).
For the most current package and ordering information, see the Package Option Addendum at the end
of this document, or see the TI website at www.ti.com.
(2)
GAIN1
GAIN0
VDD
REG_OUT
SGND
HP_INL
HP_INR
REG_EN
TPA6047A4RHB
(TOP VIEW)
32
31
30
29
28
27
26
25
24
SPKR_RIN–
1
SPKR_RIN+
2
23
SPKR_EN
SPKR_LIN+
3
22
HP_EN
SPKR_LIN–
4
21
SPGND
SPGND
5
20
ROUT+
LOUT+
6
19
ROUT–
LOUT–
7
18
SPVDD
SPVDD
8
HPVDD
10
11
12 13
14
15
C1P
CPGND
CPVSS
HPVSS
HP_OUTR
HP_OUTL
C1N
9
17
16
CPVDD
Thermal
Pad
BYPASS
TERMINAL FUNCTIONS
TERMINAL
NAME
NO.
I/O/P
DESCRIPTION
SPKR_RIN–
1
I
Right-channel negative differential audio input for speaker amplifier
SPKR_RIN+
2
I
Right-channel positive differential audio input for speaker amplifier
SPKR_LIN+
3
I
Left-channel positive differential audio input for speaker amplifier
SPKR_LIN–
4
I
Left-channel negative differential audio input for speaker amplifier
SPGND
5, 21
P
Speaker power ground
LOUT+
6
O
Left-channel positive audio output
LOUT–
7
O
Left-channel negative audio output
SPVDD
8, 18
P
Supply voltage terminal for speaker amplifier
CPVDD
9
P
Charge pump positive supply, connect to HPVDD via star connection
C1P
10
I/O
CPGND
11
P
C1N
12
I/O
CPVSS
13
P
Charge pump output (negative supply for headphone amplifier), connect to HPVSS
HPVSS
14
P
Headphone amplifier negative supply, connect to CPVSS
HP_OUTR
15
O
Right-channel capacitor-free headphone output
HP_OUTL
16
O
Left-channel capacitor-free headphone output
HPVDD
17
P
Headphone amplifier supply voltage, connect to CPVDD
ROUT–
19
O
Right-channel negative audio output
Charge pump flying capacitor positive terminal
Charge pump ground
Charge pump flying capacitor negative terminal
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TERMINAL FUNCTIONS (continued)
TERMINAL
I/O/P
DESCRIPTION
NAME
NO.
ROUT+
20
O
Right-channel positive audio output
HP_EN
22
I
Headphone channel enable logic input; active high enable. HIGH=ENABLE.
SPKR_EN
23
I
Speaker channel enable logic input; active high enable. HIGH=ENABLE.
BYPASS
24
P
Common-mode bias voltage for speaker preamplifiers
REG_EN
25
I
Enable pin (Active HIGH) for turning on/off LDO. HIGH=ENABLE
HP_INR
26
I
Headphone right-channel audio input
HP_INL
27
I
Headphone left-channel audio input
SGND
28
P
Signal ground, connect to CPGND and SPGND
REG_OUT
29
O
Regulated 4.75-V output
VDD
30
P
Positive power supply
GAIN0
31
I
Bit 0, MSB, of gain select bits
GAIN1
32
I
Bit 1, LSB, of gain select bits
Die Pad
P
Solder the thermal pad on the bottom of the QFN package to the GND plane of the PCB. It is required for
mechanical stability and will enhance thermal performance.
Thermal Pad
ABSOLUTE MAXIMUM RATINGS
over operating free-air temperature range (unless otherwise noted) (1)
Supply voltage
VI
HPVDD, VDD, SPVDD, CPVDD
Input voltage
VALUE
UNIT
–0.3 to 6
V
SPKR_LIN+, SPKR_LIN-, SPKR_RIN+, SPKR_RIN-,
HP_EN,GAIN0, GAIN1, SPK_EN, REG_EN
–0.3 to 6.3
HP_INL, HP_INR HP Enabled
–3.5 to 3.5
HP_INL, HP_INR HP not Enabled
–0.3 to 3.5
Continuous total power dissipation
V
See Dissipation Rating Table
TA
Operating free-air temperature range
–40 to 85
°C
TJ
Operating junction temperature range
–40 to 150
°C
Tstg
Storage temperature range
–65 to 150
°C
8
kV
(1)
Electrostatic discharge
HBM for HP_OUTL and HP_OUTR
Electrostatic discharge,
all other pins
CDM
500
V
HBM
2
kV
Stresses beyond those listed under absolute maximum ratings may cause permanent damage to the device. These are stress ratings
only, and functional operations of the device at these or any other conditions beyond those indicated under recommended operating
conditions is not implied. Exposure to absolute-maximum-rated conditions for extended periods may affect device reliability.
DISSIPATION RATINGS
(1)
PACKAGE (1)
TA ≤ 25°C
DERATING FACTOR
TA = 70°C
TA = 85°C
RHB
5.06 W
40 mW/°C
4.04 W
3.23 W
The PowerPAD™ must be soldered to a thermal land on the printed-circuit board. Refer to the Texas Instruments document,
PowerPAD™ Thermally Enhanced Package application report (literature number SLMA002) for more information regarding the
PowerPAD™ package.
RECOMMENDED OPERATING CONDITIONS
VIH
4
MIN
MAX
UNIT
Supply voltage
VDD, SPVDD
4.5
5.5
V
Supply voltage
HPVDD, CPVDD
3
5.5
V
High-level input voltage
SPKR_EN, HP_EN, GAIN0, GAIN1, REG_EN
2
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RECOMMENDED OPERATING CONDITIONS (continued)
MIN
VIL
Low-level input voltage
TA
Operating free-air temperature
SPKR_EN, HP_EN, GAIN0, GAIN1, REG_EN
MAX
UNIT
0.8
V
–40
85
°C
GENERAL DC ELECTRICAL CHARACTERISTICS
TA = 25°C, VDD = SPVDD = HPVDD = CPVDD = 5 V (unless otherwise noted)
PARAMETER
TEST CONDITIONS
MIN
TYP
MAX
UNIT
0.02
1
µA
0.02
1
µA
IIH
High-level input current
SPKR_EN, HP_EN, GAIN0, GAIN1,
REG_EN = VDD
IIL
Low-level input current
SPKR_EN, HP_EN, GAIN0, GAIN1,
REG_EN = 0 V
IDD(Speaker)
Supply current, speaker amplifier
ONLY enabled
SPKR_EN = 2 V, HP_EN = REG_EN = 0 V
5
12
mA
IDD(HP)
Supply current, headphone
amplifier ONLY enabled
SPKR_EN = REG_EN = 0 V, HP_EN = 2 V
7.5
14
mA
IDD(REG)
Supply current, regulator ONLY
enabled
SPKR_EN = HP_EN = 0 V, REG_EN = 2 V
0.65
1
mA
IDD(SD)
Supply current, shutdown mode
SPKR_EN = HP_EN = REG_EN = 0 V
2.5
5
µA
TYP
MAX
0.5
10
SPEAKER AMPLIFIER DC CHARACTERISTICS
TA = 25°C, VDD = SPVDD = 5 V, RL = 4 Ω, Gain = 10 dB (unless otherwise noted)
PARAMETER
TEST CONDITIONS
MIN
| VOO |
Output offset voltage (measured differentially)
Inputs AC-coupled to GND, Gain = 10
dB
PSRR
Power supply rejection ratio
VDD = SPVDD = 4.5 V to 5.5 V
–55
–65
UNIT
mV
dB
SPEAKER AMPLIFIER AC CHARACTERISTICS
TA = 25°C, VDD = SPVDD = 5 V, RL = 4 Ω, Gain = 10 dB (unless otherwise noted)
PARAMETER
PO
THD+N
Output power
Total harmonic distortion plus noise
TEST CONDITIONS
THD+N = 10%, f = 1 kHz, RL = 8 Ω
1.6
THD+N = 1%, f = 1 kHz, RL = 4 Ω
2.1
THD+N = 10%, f = 1 kHz, RL = 4 Ω
2.6
PO = 1 W, RL = 8 Ω, f = 20 Hz to 20 kHz
0.06%
PO = 1 W, RL = 4 Ω, f = 20 Hz to 20 kHz
0.1%
kSVR
Supply ripple rejection ratio
SNR
Signal-to-noise ratio
Maximum output at THD+N <1%, f = 1 kHz,
Gain = 10 dB
UNIT
W
dB
99
dB
f = 1 kHz, Po = 1 W, Gain = 10 dB
–110
dB
f = 10 kHz, Po = 1 W, Gain = 10 dB
–100
dB
Noise output voltage
CBYPASS = 0.47 µF, f = 20 Hz to 20 kHz,
Gain = 10 dB, No weighting
ZI
Input Impedance
Gain = 21.6 dB
GAIN0, GAIN1 = 0.8 V
Gain
MAX
–53
Vn
G
TYP
1.3
f = 1 kHz, CBYPASS = 0.47 µF, RL = 8 Ω
VRIPPLE = 200 mVPP
Crosstalk (Left-Right; Right-Left)
MIN
THD+N = 1%, f = 1 kHz, RL = 8 Ω
µVrms
30
15
20
9
10
kΩ
11
GAIN0 = 0.8 V; GAIN1 = 2 V
11
12
13
GAIN0 = 2 V, GAIN1 = 0.8 V
14.6
15.6
16.6
GAIN0, GAIN1 = 2 V
20.6
21.6
22.6
Gain Matching
Channel-to Channel
Start-up time from shutdown
CBYPASS = 0.47 µF
0.01
dB
25
ms
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HEADPHONE AMPLIFIER DC ELECTRICAL CHARACTERISTICS
TA = 25°C, HPVDD = CPVDD = VDD = 5 V, RL = 16 Ω (unless otherwise noted)
PARAMETER
TEST CONDITIONS
| VOS |
Output offset voltage
Inputs grounded
PSRR
Power supply rejection ratio
HPVDD = 4.5 V to 5.5 V
MIN
TYP
MAX
UNIT
1.5
mV
–75
–100
dB
MIN
TYP
HEADPHONE AMPLIFIER AC CHARACTERISTICS
TA = 25°C, HPVDD = 5 V, RL = 16 Ω (unless otherwise noted)
PARAMETER
TEST CONDITIONS
MAX
UNIT
THD+N = 10%, RL = 16 Ω, f = 1 kHz
100
THD+N = 10%, RL = 32 Ω, f = 1 kHz
50
PO = 80 mW, f = 20 Hz to 20 kHz,
RL = 16 Ω
0.1
PO = 40 mW, f = 20 Hz to 20 kHz,
RL = 32 Ω
0.1
Dynamic Range with Signal Present
A-Weighted, f = 20 Hz to 20 kHz
–89
dB FS
Supply ripple rejection ratio
f = 1 kHz, 200-mVPP ripple
-60
dB
Crosstalk
Po = 2.8 mW, f = 20 Hz to 20 kHz
-90
dB
Vn
Noise output voltage
f = 20 Hz to 20 kHz, No weighting
20
µVrms
ZI
Input Impedance
Gain
Closed-loop voltage gain
PO
THD+N
kSVR
Output power (outputs in phase)
Total harmonic distortion plus noise
RL = 16 Ω
mW
%
15
20
–1.45
–1.5
Start-up time from shutdown
kΩ
–1.55
8
V/V
ms
LDO CHARACTERISTICS
TA = 25°C, VDD = 5 V (unless otherwise noted)
PARAMETER
TEST CONDITIONS
VI
Input voltage
IO
Continuous output current
VO
Output voltage
0 < IO < 120 mA; 4.9 V < Vin < 5.5 V
Line regulation
IL = 5 mA; 4.9 V < Vin < 5.5 V
Load regulation
IL = 0 – 120 mA, Vin = 5 V
Power supply ripple rejection
VDD = 4.9 V, IL = 10 mA
6
MIN
VDD
TYP
4.5
MAX
5.5
120
4.65
f = 100 Hz
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UNIT
V
mA
4.75
4.85
1.8
10
V
mV
0.13
mV/ mA
–46
dB
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TYPICAL CHARACTERISTICS
Default graph conditions: VCC = 5 V, Freq = 1 kHz, AES17 Filter.
TOTAL HARMONIC DISTORTION + NOISE (SP)
vs
FREQUENCY
TOTAL HARMONIC DISTORTION + NOISE (SP)
vs
FREQUENCY
1
Gain = 10 dB,
RL = 4 W,
VDD = 5 V
THD+N - Total Harmonic Distortion - %
THD+N - Total Harmonic Distortion + Noise - %
1
PO = 1 W
PO = 0.25 W
0.1
PO = 1.5 W
0.01
1k
10 k
f - Frequency - Hz
100 k
0.01
PO = 1 W
0.001
100
1k
10 k
f - Frequency - Hz
TOTAL HARMONIC DISTORTION + NOISE (HP)
vs
FREQUENCY
TOTAL HARMONIC DISTORTION + NOISE (HP)
vs
FREQUENCY
Gain = 3.5 dB
RL = 16 Ω
VDD = 5 V
0.1
0.001
10
PO = 0.25 W
Figure 2.
1
0.01
PO = 0.1 W
Figure 1.
THD+N − Total Harmonic Distortion + Noise − %
THD+N − Total Harmonic Distortion + Noise − %
100
0.1
0.0001
10
0.001
10
Gain = 10 dB,
RL = 8 W,
VDD = 5 V
PO = 50 mW
PO = 25 mW
100
1k
PO = 2.8 mW
10k
100k
100 k
1
Gain = 3.5 dB
RL = 32 Ω
VDD = 5 V
0.1
PO = 25 mW
PO = 1.4 mW
PO = 12.5 mW
0.01
0.001
10
100
1k
10k
100k
f − Frequency − Hz
f − Frequency − Hz
G004
G003
Figure 3.
Figure 4.
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TYPICAL CHARACTERISTICS (continued)
TOTAL HARMONIC DISTORTION + NOISE (SP)
vs
OUTPUT POWER
TOTAL HARMONIC DISTORTION + NOISE (SP)
vs
OUTPUT POWER
100
Gain = 10 dB,
RL = 4 W
VDD = 4.5 V
10
VDD = 5 V
VDD = 5.5 V
1
0.1
0.01
0.01
0.1
1
PO - Output Power - W
Gain = 10 dB,
RL = 8 W
10
VDD = 4.5 V
VDD = 5 V
1
VDD = 5.5 V
0.1
0.01
0.01
10
0.1
1
PO - Output Power - W
Figure 5.
Figure 6.
TOTAL HARMONIC DISTORTION + NOISE (HP)
vs
OUTPUT POWER
TOTAL HARMONIC DISTORTION + NOISE (HP)
vs
OUTPUT POWER
10
THD+N − Total Harmonic Distortion + Noise − %
THD+N − Total Harmonic Distortion + Noise − %
THD+N - Total Harmonic Distortion + Noise - %
THD+N - Total Harmonic Distortion + Noise - %
100
Gain = 3.5 dB
RL = 16 Ω
VDD = 5 V
1
0.1
VDD = 5 V
In Phase
0.01
0.001
0.1m
1m
10m
100m
PO − Output Power − W
1
10
Gain = 3.5 dB
RL = 32 Ω
VDD = 5 V
1
0.1
In Phase
0.01
0.001
0.1m
G007
Figure 7.
8
10
VDD = 5 V
1m
10m
100m
PO − Output Power − W
1
G008
Figure 8.
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TYPICAL CHARACTERISTICS (continued)
CROSSTALK (SP)
vs
FREQUENCY
0
-10
-20
0
-10
Gain = 10 dB,
Power = 1 W,
RL = 4 W,
VDD = 5 V
-40
-50
-50
-60
-70
-80
-90
L to R
-100
R to L
1k
10 k
f - Frequency - Hz
100 k
10
1k
10 k
f - Frequency - Hz
CROSSTALK (LDO)
vs
FREQUENCY
CROSSTALK (HP)
vs
FREQUENCY
100 k
0
Gain = 10 dB,
PO = 2 W,
-10
RL = 4 W,
VDD = 5 V
-20
-30
Gain = 3.5 dB,
PO = 2.8 mW,
RL = 16 W,
VDD = 5 V
-40
Crosstalk - dB
Crosstalk - dB
100
Figure 10.
L to LDO
-90
-50
-60
-70
-80
R to LDO
R to L
-90
-110
-100
-120
-130
-140
10
R to L
Figure 9.
-60
-100
L to R
-140
100
-50
-80
-90
-130
-40
-70
-80
-120
0
-30
-70
-110
-120
-20
-60
-100
-110
-10
RL = 8 W,
VDD = 5 V
-30
-40
-130
-140
10
Gain = 10 dB,
PO = 1 W,
-20
Crosstalk - dB
Crosstalk - dB
-30
CROSSTALK (SP)
vs
FREQUENCY
L to R
-110
100
1k
10 k
100 k
-120
10
f - Frequency - Hz
Figure 11.
100
1k
10 k
f - Frequency - Hz
100 k
Figure 12.
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TYPICAL CHARACTERISTICS (continued)
CROSSTALK (HP)
vs
FREQUENCY
CROSSTALK (HP)
vs
FREQUENCY
0
−10
−20
RL = 32 W,
VDD = 5 V
-20
-30
−40
−50
−60
−70
Gain = 3.5 dB,
PO = 2.8 mW,
-10
Crosstalk - dB
Crosstalk − dB
−30
0
Gain = 3.5 dB
PO = 35 mW
RL = 16 Ω
VDD = 5 V
R to L
−80
-40
-50
-60
-70
-80
−90
L to R
-90
−100
-100
L to R
−110
R to L
-110
−120
10
100
1k
10k
100k
-120
10
100
1k
10 k
f - Frequency - Hz
f − Frequency − Hz
100 k
G012
Figure 13.
Figure 14.
CROSSTALK (HP)
vs
FREQUENCY
OUTPUT POWER (SP)
vs
SUPPLY VOLTAGE
0
−20
Crosstalk − dB
−30
3
−40
−50
−60
−70
−80
R to L
−90
−120
10
THD+N = 10%
2.8
2.7
2.6
2.5
THD+N = 1%
2.4
2.3
2.2
2.1
2
1.9
1.8
−100
−110
Gain = 10 dB,
RL = 4 W
2.9
PO - Output Power - W
−10
3.2
3.1
Gain = 3.5 dB
PO = 35 mW
RL = 32 Ω
VDD = 5 V
L to R
1.7
100
1k
10k
100k
1.6
4.5
4.6
f − Frequency − Hz
G013
Figure 15.
10
4.7 4.8 4.9 5 5.1 5.2 5.3
VDD - Supply Voltage - V
5.4
5.5
Figure 16.
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TYPICAL CHARACTERISTICS (continued)
SUPPLY CURRENT (SP)
vs
TOTAL OUTPUT POWER
SUPPLY CURRENT (SP)
vs
TOTAL OUTPUT POWER
1.6
Gain = 10 dB,
RL = 4 W
1.2
VDD = 5.5 V
1
0.8
0.6
VDD = 4.5 V
VDD = 5.5 V
0.6
0.5
0.4
0.3
0.2
0.2
0.1
0
0
0
1
2
3
4
PO - Output Power - W
5
0
6
0.4
0.8
1.2 1.6 2 2.4 2.8 3.2
PO - Output Power - W
Figure 17.
Figure 18.
POWER DISSIPATION (SP)
vs
TOTAL OUTPUT POWER
POWER DISSIPATION (SP)
vs
TOTAL OUTPUT POWER
3.2
3
2.8
3.6
4
1.6
VDD = 5.5 V
2.4
2.2
1.4
PD - Power Dissipation - W
2.6
PD - Power Dissipation - W
VDD = 5 V
0.7
0.4
VDD = 5 V
2
1.8
VDD = 4.5 V
1.6
1.4
1.2
1
0.8
0.6
0.4
0.2
0
Gain = 10 dB,
RL = 8 W
0.8
VDD = 4.5 V
ICC - Supply Current - A
ICC - Supply Current - A
1.4
0.9
VDD = 5 V
1.2
1
0.8
0.6
0.4
0
1
2
3
4
PO - Output Power - W
5
VDD = 5 V
VDD = 4.5 V
Gain = 10 dB,
RL = 8 W
0.2
Gain = 10 dB,
RL = 4 W
0
VDD = 5.5 V
6
0
0.5
Figure 19.
1
1.5
2
2.5
3
PO - Output Power - W
3.5
4
Figure 20.
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TYPICAL CHARACTERISTICS (continued)
OUTPUT SUPPLY VOLTAGE (LDO)
vs
LOAD CURRENT
5.0
5.0
4.9
4.8
IL = −1 mA
4.8
VDD − Output Supply Voltage - V
VDD − Regulator Output Voltage − V
REGULATOR OUTPUT VOLTAGE (LDO)
vs
SUPPLY VOLTAGE
4.7
4.6
IL = −10 mA
4.5
IL = −50 mA
4.4
IL = −120 mA
4.3
4.2
4.4
VDD = 5.5 V
4.2
VDD = 4.5 V
4.0
3.8
3.6
3.4
3.2
4.0
4.5 4.6 4.7 4.8 4.9 5.0 5.1 5.2 5.3 5.4 5.5
3.0
0
25
75
100
125
150
175
G021
Figure 21.
Figure 22.
COMMON-MODE REJECTION RATIO (SP)
vs
FREQUENCY
COMMON-MODE REJECTION RATIO (SP)
vs
FREQUENCY
200
G022
0
-10
CMRR - Common Mode Rejection Ratio - dB
Gain = 10 dB,
Input Level = 0.2 VPP,
R L = 4 W,
VDD = 5 V
-20
-30
-40
-50
-60
-70
-80
-90
-100
10
100
1k
10 k
f - Frequency - Hz
100 k
-10
Gain = 10 dB,
Input Level = 0.2 VPP,
-20
RL = 8 W,
VDD = 5 V
-30
-40
-50
-60
-70
-80
-90
-100
10
Figure 23.
12
50
IL − Load Current − mA
0
CMRR - Common Mode Rejection Ratio - dB
4.6
4.1
VDD – Supply Voltage – V
VDD = 5 V
100
1k
10 k
f - Frequency - Hz
100 k
Figure 24.
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TYPICAL CHARACTERISTICS (continued)
SUPPLY RIPPLE REJECTION RATIO (LDO)
vs
FREQUENCY
SUPPLY RIPPLE REJECTION RATIO (SP)
vs
FREQUENCY
-10
0
IO = 10 mA,
Vripple = 0.20 VPP,
VDD = 5 V
kSVR - Supply Ripple Rejection Ratio - dB
kSVR - Supply Ripple Rejection Ratio - dB
0
-20
-30
-40
-50
-60
-70
-80
10
-10
Gain = 10 dB,
R L = 8 W,
Vripple = 0.20 VPP,
VDD = 5 V
-20
-30
-40
-50
-60
-70
-80
100
1k
10 k
f - Frequency - Hz
100 k
10
100
Figure 25.
1k
10 k
f - Frequency - Hz
Figure 26.
100 k
SUPPLY RIPPLE REJECTION RATIO (HP)
vs
FREQUENCY
kSVR − Supply Ripple Rejection Ratio − dB
0
−10
−20
−30
Gain = 3.5 dB,
RL = 16 Ω,
VDD = 5 V,
Vripple = 0.20 VPP
−40
−50
−60
−70
−80
−90
−100
10
100
1k
10k
100k
f − Frequency − Hz
Figure 27.
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TYPICAL CHARACTERISTICS (continued)
14
SPEAKER SHUTDOWN - 8 Ω - 10 dB
SPEAKER STARTUP - 8 Ω - 10 dB
Figure 28.
Figure 29.
HP SHUTDOWN - 32 Ω
HP STARTUP - 32 Ω
Figure 30.
Figure 31.
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APPLICATION INFORMATION
4.75 V
(Output)
4.5 V - 5.5 V
0.1 mF
2.2 mF
HP Left Input
HP Right Input
1 mF
1 mF
1 mF
{
0.47 mF
SPKR Right Input
HP_INR
REG_EN
SGND
0.47 mF
BYPASS
SPKR_RIN+
HP_EN
SPKR_LIN–
SPGND
0.47 mF
0.47 mF
TPA6047A4
SPGND
4.5 V - 5.5 V
SPVDD
HP_OUTR
HP_OUTL
CPVSS
HPVSS
CPGND
C1N
C1P
SPVDD
Right
Speaker
ROUT-
LOUT-
4.5 V - 5.5 V
Headphone Enable
ROUT+
LOUT+
Left
Speaker
Speaker Enable
SPKR_EN
SPKR_LIN+
CPVDD
SPKR Left Input
0.47 mF
HP_INL
VDD
SPKR_RIN–
REG_OUT
GAIN0
Regulator Enable
GAIN1
4-Step
Gain Control
3 V - 5.5 V
HPVDD
1 mF
3 V - 5.5 V
10 mF
1 mF
1 mF
1 mF
Headphone
Output
Figure 32. Single-Ended Input Application Circuit
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4.75 V
(Output)
4.5 V - 5.5 V
0.1 mF
2.2 mF
HP Left Input
HP Right Input
1 mF
1 mF
1 mF
{
0.47 mF
SPKR Right (+) Input
0.47 mF
SPKR Left (+) Input
REG_EN
HP_INL
HP_INR
SGND
VDD
SPKR_RIN–
REG_OUT
SPKR Right (–) Input
GAIN0
Regulator Enable
GAIN1
SPKR_LIN–
SPGND
TPA6047A4
SPGND
ROUT+
LOUT+
Left
Speaker
SPVDD
HP_OUTL
HPVSS
HP_OUTR
CPVSS
C1N
C1P
CPVDD
SPVDD
Right
Speaker
ROUT-
LOUT-
4.5 V - 5.5 V
Headphone Enable
HP_EN
0.47 mF
0.47 mF
Speaker Enable
SPKR_EN
SPKR_LIN+
SPKR Left (–) Input
0.47 mF
BYPASS
SPKR_RIN+
CPGND
4-Step
Gain Control
3 V - 5.5 V
HPVDD
1 mF
10 mF
1 mF
1 mF
1 mF
Headphone
Output
Figure 33. Differential Input Application Circuit
Power Enable Modes
The TPA6047A4 allows the disabling of any or all of the main circuit blocks when not in use in order to reduce
operating power to an absolute minimum. The SPKR_EN control can be used to disable the speaker amplifier
while the HP_EN can be used separately to turn off the headphone amplifier. The LDO also has an independent
power control, REG_EN. With all circuit blocks disabled, the supply current in shutdown mode is only 5 µA. See
the General DC Electrical Characteristics for operating currents with each circuit block operating independently.
Speaker Amplifier Description
The speaker amplifier is capable of driving 2.1 W/ch of continuous RMS power into a 4-Ω load at 5 V.
TPA6047A4 has 4-step gain control from 10 dB to 21.6 dB.
Fully Differential Amplifier
The TPA6047A4 speaker amplifier is a fully differential amplifier with differential inputs and outputs. The fully
differential architecture consists of a differential amplifier and a common mode amplifier. The differential amplifier
ensures that the amplifier outputs a differential voltage that is equal to the differential input times the gain. The
common-mode voltage at the output is biased around VDD/2 regardless of the common-mode voltage at the
input.
16
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One of the primary advantages of the fully differential amplifier is improved RF immunity. GSM handsets save
power by turning on and off the RF transmitter at a rate of 217 Hz. The transmitted signal is picked up on input
and output traces. The fully differential amplifier cancels the signal and others of this type much better than
typical audio amplifiers.
Gain Setting via GAIN0 and GAIN1 Inputs
The gain of the TPA6047A4 is set by two terminals, GAIN0 and GAIN1. The gains listed in Table 1 are realized
by changing the taps on the input resistors and feedback resistors inside the amplifier. This causes the input
impedance (ZI) to vary as a function of the gain setting.
Table 1. Gain Setting
AMPLIFIER GAIN
(dB)
INPUT IMPEDANCE (kΩ)
TYPICAL
TYPICAL
10
78
1
12
65
0
15.6
46
1
21.6
20
GAIN1
GAIN0
0
0
0
1
1
Input Capacitor, CI
The input capacitor allows the amplifier to bias the input signal to the proper dc level for proper operation. In this
case, the input capacitor, CI, and the input impedance of the amplifier, RI, form a high-pass filter with the corner
frequency determined in Equation 1. Figure 34 shows how the input capacitor and the input resistor within the
amplifier interact.
Figure 34. Input Resistor and Input Capacitor
(1)
The value of CI is important to consider as it directly affects the low-frequency, or bass, performance of the
circuit. Furthermore, the input impedance changes with a change in volume. The higher the volume, the lower
the input impedance is. To determine the appropriate capacitor value, reconfigure Equation 1 into Equation 2.
The value of the input resistor, RI, can be determined from Equation 2.
1
CI +
2pRI f c
(2)
Low-leakage tantalum or ceramic capacitors are recommended. When polarized capacitors are used, the positive
side of the capacitor should face the amplifier input in most applications as the dc level there is held at VCC/2,
which is likely higher than the source dc level. Note that it is important to confirm the capacitor polarity in each
specific application. Recommended capacitor values are between 0.1 µF and 1 µF.
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Windows Vista™ Premium Mobile Mode Specifications
Device Type
Requirement
Windows Premium Mobile Vista
Specifications
TPA6047A4 Typical Performance
THD+N
≤ –65 dB FS [20 Hz, 20 kHz]
–88 dB FS[20 Hz, 20 kHz]
Analog Speaker Line Jack
(RL = 10 kΩ, FS = 0.707
Vrms)
Dynamic Range with Signal
Present
≤ –80 dB FS A-Weight
–88 dB FS A-Weight
Analog Headphone Out Jack
(RL = 32Ω, FS = 0.300
Vrms)
Line Output Crosstalk
≤ –60 dB [20 Hz, 20 kHz]
–105 dB [20 Hz, 20 kHz]
THD+N
≤ –45 dB FS [20 Hz, 20 kHz]
–85 dB FS [20 Hz, 20 kHz]
Dynamic Range with Signal
Present
≤ –80 dB FS A-Weight
–89 dB FS A-Weight
Headphone Output Crosstalk
≤ –60 dB [20 Hz, 20 kHz]
–100 dB [20 Hz, 20 kHz]
Bridge-Tied Load Versus Single-Ended Mode
Figure 35 shows a Class-AB audio power amplifier (APA) in a bridge-tied-load (BTL) configuration. The
TPA6047A4 speaker amplifier consists of two Class-AB differential amplifiers per channel driving the positive and
negative terminals of the load. Specifically, differential drive means that as one side of the amplifier (the positive
terminal, for example) is slewing up, the other side is slewing down, and vice versa. This doubles the voltage
swing across the load as opposed to a ground-referenced load, or a single-ended load. Power is proportional to
the square of the voltage. Plugging 2x VO(PP) into the power equation yields 4X the output power from the same
supply rail and load impedance as would have been obtained with a ground-referenced load (see Equation 3).
VO(PP)
V (RMS) +
2 Ǹ2
Power +
V (RMS)
2
RL
(3)
VDD
VO(PP)
RL
2x VO(PP)
VDD
−VO(PP)
Figure 35. Differential Output Configuration
VDD
–3 dB
VO(PP)
CC
RL
VO(PP)
fc
Figure 36. Single-Ended Configuration and Frequency Response
18
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Bridge-tying the outputs in a typical computer audio, LCD TV, or multimedia LCD monitor application drastically
increases output power. For example, if an amplifier in a single-ended configuration was capable of outputting a
maximum of 250 mW for a given load with a supply voltage of 12 V, then that same amplifier would be able to
output 1 W of power in a BTL configuration with the same supply voltage and load. In addition to the increase in
output power, the BTL configuration does not suffer from the same low-frequency issues that plague the
single-ended configuration. In a BTL configuration, there is no need for an output capacitor to block dc, so no
unwanted filtering occurs. In addition, the BTL configuration saves money and space, as the dc-blocking
capacitors needed for single-ended operation are large and expensive. For example, with an 8-Ω load in SE
operation, the user needs a 1000-µF capacitor to obtain a cutoff frequency below 20 Hz. This capacitor is
expensive and large.
Headphone Amplifier Description
The headphone amplifier has a fixed gain of –1.5 V/V. It uses single-ended (SE) inputs. The DirectPath™
amplifier architecture operates from a single supply but makes use of an internal charge pump to provide a
negative voltage rail. Combining the user-provided positive rail and the negative rail generated by the IC, the
device operates in what is effectively a split supply mode. The output voltages are now centered at zero volts
with the capability to swing to the positive rail or negative rail. The DirectPath™ amplifier requires no output dc
blocking capacitors and does not place any voltage on the sleeve. The block diagram and waveform of Figure 37
illustrate the ground-referenced headphone architecture. This is the architecture of the TPA6047A4.
Single-supply headphone amplifiers typically require dc-blocking capacitors. The capacitors are required because
most headphone amplifiers have a dc bias on the outputs pin. If the dc bias is not removed, the output signal is
severely clipped, and large amounts of dc current rush through the headphones, potentially damaging them. The
left-side drawing in Figure 37 illustrates the conventional headphone amplifier connection to the headphone jack
and output signal.
DC blocking capacitors are often large in value. The headphone speakers (typical resistive values of 16 Ω or
32 Ω) combine with the dc blocking capacitors to form a high-pass filter. Equation 4 shows the relationship
between the load impedance (RL), the capacitor (CO), and the cutoff frequency (fC).
1
fc +
2pRLC O
(4)
CO can be determined using Equation 5, where the load impedance and the cutoff frequency are known.
1
CO +
2pRLf c
(5)
If fc is low, the capacitor must then have a large value because the load resistance is small. Large capacitance
values require large package sizes. Large package sizes consume PCB area, stand high above the PCB,
increase cost of assembly, and can reduce the fidelity of the audio output signal.
Two different headphone amplifier applications are available that allow for the removal of the output dc blocking
capacitors. The capacitor-less amplifier architecture is implemented in the same manner as the conventional
amplifier with the exception of the headphone jack shield pin. This amplifier provides a reference voltage, which
is connected to the headphone jack shield pin. This is the voltage on which the audio output signals are
centered. This voltage reference is half of the amplifier power supply to allow symmetrical swing of the output
voltages. Do not connect the shield to any GND reference, or large currents will result. The scenario can happen
if, for example, an accessory other than a floating GND headphone is plugged into the headphone connector.
See the second block diagram and waveform in Figure 37.
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Conventional
VDD
CO
VOUT
CO
VDD/2
GND
Capacitor-Less
VDD
VOUT
VBIAS
GND
VBIAS
DirectPathTM
VDD
GND
VSS
Figure 37. Amplifier Applications
Input-Blocking Capacitors
DC input-blocking capacitors block the dc portion of the audio source and allow the inputs to properly bias.
Maximum performance is achieved when the inputs of the TPA6047A4 are properly biased. Performance issues
such as pop are optimized with proper input capacitors.
The dc input-blocking capacitors can be removed, provided the inputs are connected differentially and within the
input common-mode range of the amplifier, the audio signal does not exceed ±3 V, and pop performance is
sufficient.
CIN is a theoretical capacitor used for mathematical calculations only. Its value is the series combination of the dc
input-blocking capacitors, C(DCINPUT-BLOCKING). Use Equation 6 to determine the value of C(DCINPUT-BLOCKING). For
example, if CIN is equal to 0.22 µF, then C(DCINPUT-BLOCKING) is equal to about 0.47 µF.
1 C
CIN =
(DCINPUT-BLOCKING)
2
(6)
The two C(DCINPUT-BLOCKING) capacitors form a high-pass filter with the input impedance of the TPA6047A4. Use
Equation 6 to calculate CIN, then calculate the cutoff frequency using CIN and the differential input impedance of
the TPA6047A4, RIN, using Equation 7. Note that the differential input impedance changes with gain. See
Table 1 for input impedance values. The frequency and/or capacitance can be determined when one of the two
values are given.
20
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fc IN +
1
2p RIN C IN
or
C IN +
1
2p fcIN R IN
(7)
If a high-pass filter with a –3-dB point of no more than 20 Hz is desired over all gain settings, the minimum
impedance would be used in the Equation 7. The minimum input impedance for TPA6047A4 is 20 kΩ. The
capacitor value by Equation 7 would be 0.399 µF. However, this is CIN, and the desired value is for
C(DCINPUT-BLOCKING). Multiplying CIN by 2 yields 0.80 µF, which is close to the standard capacitor value of 1 µF.
Place 1-µF capacitors at each input terminal of the TPA6047A4 to complete the filter.
Charge Pump Flying Capacitor and CPVSS Capacitor
The charge pump flying capacitor serves to transfer charge during the generation of the negative supply voltage.
The CPVSS capacitor must be at least equal to the flying capacitor in order to allow maximum charge transfer.
Low ESR capacitors are an ideal selection, and a value of 1 µF is typical. Use X5R or better cermaic material.
Decoupling Capacitors
The TPA6047A4 is a DirectPath™ headphone amplifier that requires adequate power supply decoupling to
ensure that the noise and total harmonic distortion (THD) are as low as possible. To filter high-frequency
transients, spikes, and digital hash on the power line, use good low equivalent-series-resistance (ESR) ceramic
capacitors, typically 1 µF. Find the smallest package possible, and place as close as possible to the device VDD
lead. Placing the decoupling capacitors close to the TPA6047A4 is important for the performance of the amplifier.
Use a 10 µF or greater capacitor near the TPA6047A4 to filter lower frequency noise signals; however, the high
PSRR of the TPA6047A4 makes the 10-µF capacitor unnecessary in most applications.
Midrail Bypass Capacitor, CBYPASS
The midrail bypass capacitor, C(BYPASS), has several important functions. During start-up or recovery from
shutdown mode, CBYPASS determines the rate at which the amplifier starts up. A 1-µF capacitor yields a start-up
time of approximately 25 ms. CBYPASS also reduces the noise coupled into the output signal by the power supply.
This improves the power supply ripple rejection (PSRR) of the amplifier. Ceramic or polyester capacitors with low
ESR and values in the range of 0.47 µF to 1 µF are recommended.
Low Dropout Regulator (LDO) Description
The TPA6047A4 contains a 4.75-V output low dropout regulator (LDO) capable of providing 120 mA with a drop
of less than 150 mV from the 5-V supply. This can be used to power an external CODEC. A 10-µF decoupling
capacitor is recommended at the output of the LDO as well as 0.1-µF capacitor to filter high-frequency noise from
the supply line.
Layout Recommendations
Solder the exposed thermal pad (metal pad on the bottom of the part) on the TPA6047A4 QFN package to a
ground pad on the PCB. Fore more information, see the land pattern drawing.
It is important to keep the TPA6047A4 external components close to the body of the amplifier to limit noise
pickup. One should lay out the differential input leads symmetrical and close together to take advantage of the
inherent common mode rejection of the TPA6047A4. The layout of the TPA6047A4 evaluation module (EVM) is a
good example of component placement and the layout files are available at www.ti.com.
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PACKAGE MATERIALS INFORMATION
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6-Nov-2008
TAPE AND REEL INFORMATION
*All dimensions are nominal
Device
TPA6047A4RHBR
Package Package Pins
Type Drawing
QFN
RHB
32
SPQ
Reel
Reel
Diameter Width
(mm) W1 (mm)
3000
330.0
12.4
Pack Materials-Page 1
A0 (mm)
B0 (mm)
K0 (mm)
P1
(mm)
5.3
5.3
1.5
8.0
W
Pin1
(mm) Quadrant
12.0
Q2
PACKAGE MATERIALS INFORMATION
www.ti.com
6-Nov-2008
*All dimensions are nominal
Device
Package Type
Package Drawing
Pins
SPQ
Length (mm)
Width (mm)
Height (mm)
TPA6047A4RHBR
QFN
RHB
32
3000
346.0
346.0
29.0
Pack Materials-Page 2
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Following are URLs where you can obtain information on other Texas Instruments products and application solutions:
Products
Amplifiers
Data Converters
DSP
Clocks and Timers
Interface
Logic
Power Mgmt
Microcontrollers
RFID
RF/IF and ZigBee® Solutions
amplifier.ti.com
dataconverter.ti.com
dsp.ti.com
www.ti.com/clocks
interface.ti.com
logic.ti.com
power.ti.com
microcontroller.ti.com
www.ti-rfid.com
www.ti.com/lprf
Applications
Audio
Automotive
Broadband
Digital Control
Medical
Military
Optical Networking
Security
Telephony
Video & Imaging
Wireless
www.ti.com/audio
www.ti.com/automotive
www.ti.com/broadband
www.ti.com/digitalcontrol
www.ti.com/medical
www.ti.com/military
www.ti.com/opticalnetwork
www.ti.com/security
www.ti.com/telephony
www.ti.com/video
www.ti.com/wireless
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