TI TPS80010ARSMR

TPS80010
www.ti.com
SLVSAD1 A – JUNE 2010 – REVISED JUNE 2010
PMU for Alkaline Battery-Powered Applications
Check for Samples: TPS80010
FEATURES
1
•
•
•
•
•
•
•
•
DESCRIPTION
1.8-V Buck DC/DC Converter
3.1-V Boost DC/DC Converter with 3-V
Post-Regulation LDO
Over 91% Conversion Efficiency
Current-Limited Start-Up for Both DC/DC
Converters
Load Switch With Current-Limited Turnon
Battery-Level Monitor Switch
32-Pin, 4-mm × 4-mm × 1-mm VQFN Package
ESD Performance Tested per JESD 22
– 2000-V Human-Body Model (A114-B,
Class II)
– 500-V Charged-Device Model (C101)
The
TPS80010
provides
an
integrated
power-management solution for 2-cell alkaline battery
applications such as wireless mice, keyboards, and
video game controllers. The VBUCK 1.8-V output is
powered by a buck converter with a load capacity of
100 mA. A power-good (PG) signal is generated
when VBUCK is above 90% of its target output
voltage. Integrated in the TPS80010 is an 80-mΩ
load switch that can be connected to the VBUCK
output, allowing more system design flexibility when
connecting to multiple loads. The 3.1-V VBOOST
output is powered by a boost converter. The
VBOOST output voltage is post-regulated by the
integrated 3-V LDO. This post-regulation provides a
low-noise supply level through the specified battery
range.
APPLICATIONS
•
•
•
Wireless Mice
Wireless Keyboards
Game Controllers
TYPICAL APPLICATION
1.8 V–3.6 V
AA
AA
10 mF
10 mF
VIN_BOOST
BAT_FALSELOAD
VIN_BUCK
PP_BAT
10 W
10 mH
SW_BOOST
EN_BOOST
VO_BOOST
EN_LDO
FB_BOOST
3.1 V
22 mF
EN_BUCK
TPS80010
IN_VM
EN_SW1
EN_BAT_CHECK
3V
OUT_VM
4.7 mF
CONTROLLER
LED
EN_BAT_FLASELOAD
2.2 mH
PG
SW_BUCK
OPTICAL
SENSOR
1.8 V
10 mF
BAT_CHECK
MEMORY/
IO
FB_BUCK
1.8 kW
MODE_BUCK
IN_VIO
ADC
OUT_VIO
TEST1
NC
1.8 kW
1.8 V
1.8-V
PERIPHERALS
TEST2
GND
1
Please be aware that an important notice concerning availability, standard warranty, and use in critical applications of Texas
Instruments semiconductor products and disclaimers thereto appears at the end of this data sheet.
PRODUCTION DATA information is current as of publication date.
Products conform to specifications per the terms of the Texas
Instruments standard warranty. Production processing does not
necessarily include testing of all parameters.
Copyright © 2010, Texas Instruments Incorporated
TPS80010
SLVSAD1 A – JUNE 2010 – REVISED JUNE 2010
www.ti.com
This device contains circuits to protect its inputs and outputs against damage due to high static voltages or electrostatic fields.
These circuits have been qualified to protect this device against electrostatic discharges (ESD) of up to 2 kV according to
MIL-STD-883C, Method 3015; however, it is advised that precautions be taken to avoid application of any voltage higher than
maximum-rated voltages to these high-impedance circuits. During storage or handling the device leads should be shorted together
or the device should be placed in conductive foam. In a circuit, unused inputs should always be connected to an appropriate logic
voltage level, preferably either VCC or ground. Specific guidelines for handling devices of this type are contained in the publication
Guidelines for Handling Electrostatic-Discharge-Sensitive (ESDS) Devices and Assemblies available from Texas Instruments.
ORDERING INFORMATION (1)
(1)
DEVICE
TEMPERATURE
PACKAGE
ORDERING CODE
MARKING
TPS80010
–40°C to 85°C
VQFN
TPS80010ARSMR
RSM
For the most current package and ordering information, see the Package Option Addendum at the end of this document, or see the TI
Web site at www.ti.com.
ABSOLUTE MAXIMUM RATINGS (1)
over operating free-air temperature range (unless otherwise noted)
MIN
MAX
VI
Input voltage range on all pins
–0.3
3.6
V
VO
Output voltage range on all pins
–0.3
3.6
V
TJ
Junction temperature range
–40
125
°C
Tstg
Storage temperature range
–65
150
°C
–500
500
V
–2
2
kV
VESD
(1)
ESD rating
Charged-device model (CDM) on all pins
Human-body model (HBM) on all pins
UNIT
Stresses beyond those listed under Absolute Maximum Ratings may cause permanent damage to the device. These are stress ratings
only, and functional operation of the device at these or any other conditions beyond those indicated under Recommended Operating
Conditions is not implied. Exposure to absolute-maximum-rated conditions for extended periods may affect device reliability.
THERMAL INFORMATION
TPS80010
THERMAL METRIC
(1)
VQFN
UNIT
32 PINS
qJA
Junction-to-ambient thermal resistance (2)
qJC(top)
Junction-to-case (top) thermal resistance
(3)
(4)
qJB
Junction-to-board thermal resistance
yJT
Junction-to-top characterization parameter
yJB
Junction-to-board characterization parameter
Junction-to-case (bottom) thermal resistance
qJC(bottom)
(1)
(2)
(3)
(4)
(5)
(6)
(7)
2
33.9
°C/W
25.2
°C/W
8
°C/W
0.12
°C/W
(6)
7.5
°C/W
(7)
1.8
°C/W
(5)
For more information about traditional and new thermal metrics, see the IC Package Thermal Metrics application report, SPRA953.
The junction-to-ambient thermal resistance under natural convection is obtained in a simulation on a JEDEC-standard, high-K board, as
specified in JESD51-7, in an environment described in JESD51-2a.
The junction-to-case (top) thermal resistance is obtained by simulating a cold plate test on the package top. No specific
JEDEC-standard test exists, but a close description can be found in the ANSI SEMI standard G30-88.
The junction-to-board thermal resistance is obtained by simulating in an environment with a ring cold plate fixture to control the PCB
temperature, as described in JESD51-8.
The junction-to-top characterization parameter, yJT, estimates the junction temperature of a device in a real system and is extracted
from the simulation data for obtaining qJA, using a procedure described in JESD51-2a (sections 6 and 7).
The junction-to-board characterization parameter, yJB, estimates the junction temperature of a device in a real system and is extracted
from the simulation data for obtaining qJA , using a procedure described in JESD51-2a (sections 6 and 7).
The junction-to-case (bottom) thermal resistance is obtained by simulating a cold plate test on the exposed (power) pad. No specific
JEDEC standard test exists, but a close description can be found in the ANSI SEMI standard G30-88.
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SLVSAD1 A – JUNE 2010 – REVISED JUNE 2010
RECOMMENDED OPERATING CONDITIONS
TA = 0°C to 85°C; typical values are at TA = 25°C
MIN
VBAT
Input voltage, VIN BOOST, VIN_BUCK, PP_BAT pins
VIO (IN_VIO)
Digital I/O operating voltage range
TA
Ambient temperature
TYP
1.95
0
MAX
UNIT
3.6
V
1.8
VBAT
V
25
85
°C
ELECTRICAL CHARACTERISTICS
TA = 0°C to 85°C; typical values are at TA = 25°C (unless otherwise noted)
PARAMETER
TEST CONDITIONS
MIN
TYP
MAX
UNIT
SUPPLY CURRENT
IQ
Quiescent current
VBAT = 3 V, all modules enabled
IOFF
Off current
VBAT = 3 V
RPULLDOWN
Internal pulldown resistor
EN_BOOST, EN_LDO, EN_SW1,
EN_BAT_CHECK, EN_BAT_FALSELOAD
157
VIH
Input logic-high voltage
EN_BOOST, EN_LDO, EN_SW1,
EN_BAT_CHECK, EN_BAT_FALSELOAD
0.7×VIO
51
mA
1
mA
DIGITAL I/O
EN_BUCK, BUCK_MODE
VIL
Input logic-low voltage
275
V
0.3×VIO
EN_BUCK, BUCK_MODE
Output logic-high voltage
PG
VOL
Output logic-low voltage
PG
IL_DIG
Logic-output load current
kΩ
0.7×VBAT
EN_BOOST, EN_LDO, EN_SW1,
EN_BAT_CHECK, EN_BAT_FALSELOAD
VOH
383
V
0.7×VBAT
VIO – 0.2
V
0.2
1
V
mA
BUCK CONVERTER
VIN
Input voltage at VIN_BUCK
IO
Output current
VFB
Feedback voltage (output
accuracy)
VBUCK
Buck output voltage
ISW
Switch current limit
IRUSH
Inrush current
Line regulation
Load regulation
Efficiency
Quiescent current
1.95
PWM, IO = 0 mA to 100 mA,
VIN ≥ 1.85 V to 3.6 V, VBUCK = 1.8 V
PFM
V
mA
1.5%
1
1.8
0.56
VIN = 2 V
PWM, IO = 100 mA
PFM, IO = 100 mA
0.7
A
mA
0.9%
PFM, VIN = 2.4 V, IO = 0 mA to 100 mA
0.5%
PFM , IO = 100 mA, VIN = 2.4 V, VBUCK = 1.8 V
92%
PWM, IO = 100 mA, VIN = 2.4 V, VBUCK = 1.8 V
90%
PFM, IO = 0 mA, no switching
21
PFM, IO = 0 mA, switching
25
Leakage current into
SW_BUCK
0.84
0.9%
–0.5%
Shutdown current
V
150
PWM, VIN = 2.4 V, IO = 0 mA to 100 mA
PWM, IO = 0 mA
IQ
–1.5%
3.6
100
mA
5
mA
0.005
0.15
mA
0.01
1
mA
RREC
Rectifier on-resistance
VGS = 3.6 V
185
380
mΩ
RMAIN
Main SW on-resistance
VGS = 3.6 V
240
480
mΩ
ΔVLN
Line transient output variation
PFM, IO = 50 mA, VIN = 2 V → 3.6 V, Δt = 25 µs
10
20
mV
ΔVLD
Load transient output variation
PFM, VIN = 2.4 V, VBUCK = 1.8 V,
IO = 1 mA → 100 mA, Δt = 1 µs
30
40
mV
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SLVSAD1 A – JUNE 2010 – REVISED JUNE 2010
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ELECTRICAL CHARACTERISTICS (continued)
TA = 0°C to 85°C; typical values are at TA = 25°C (unless otherwise noted)
PARAMETER
TEST CONDITIONS
MIN
TYP
MAX
UNIT
BUCK CONVERTER (Continued)
PWM, IO = 100 mA, VIN = 2.4 V
1
10
10
20
2.25
2.5
VRIP
Output ripple
fSW
Switching frequency
UVLO
Undervoltage lockout
threshold
tSTART
Start-up time
CL
Load capacitance
10
mF
L
Inductor
2.2
mH
PFM, IO = 10 mA, VIN = 3.6 V
2
1.7
mVpp
MHz
V
10
ms
LOAD SWITCH
RON
Switch on-resistance
120
mΩ
Maximum load current
VGS = 1.8 V
80
360
mA
Turnon inrush current
100
mA
4
ms
Output rise time
10%–90% of final VO, CL = 100 µF
IOFF
Off-state current
Switch turned off, IO = 0 mA
2
1
mA
tON
Turnon time
CL = 100 µF
6
ms
tOFF
Turnoff time
CL = 100 µF
10
ms
POWER-GOOD RESET
VTHRESH
Power-good threshold voltage
1.68
1.7
1.72
V
ΔtPG
Power-good time-out delay
100
150
200
ms
VHYS
Power-good hysteresis
10
15
mV
BOOST CONVERTER
Boost mode
1.8
3.1
VIN > VBOOST mode, VBOOST = VIN
3.1
3.6
VIN
Input voltage at VIN_BOOST
VBOOST
Output voltage
TA = 0°C–50°C, VIN = 1.8 V to 3.1 V,
IO = 0 mA to 50 mA
IO
Output current
VIN = 1.8 V to 3.6 V
ISW
Switch current limit
IRUSH
Inrush current
VIN = 2 V
RREC
Rectifier on-resistance
VBOOST = 3.1 V
RMAIN
Main SW on-resistance
fSW
3
3.1
3.2
V
50
mA
200
350
475
mA
150
Ω
1
Ω
VIN = 2 V to 3 V, IO = 50 mA
0.5%
Load regulation
VIN = 2 V, IO = 0–50 mA
0.5%
Boost efficiency
VIN = 2.4 V, IO = 5 mA
91%
Oscillator frequency
mA
1
Line regulation
VIN = 2.4 V, IO = 50 mA
V
91
kHz
625
From VIN supply, IO = 0 mA, VIN = 1.8 V,
VBOOST = 3.1 V
1
2.5
From VBOOST, IO = 0 mA, VIN = 1.8 V,
VBOOST = 3.1 V
4
6.5
Shutdown current
0.1
1
Leakage current into
SW_BOOST
0.1
1
VUVLO
VIN decreasing
0.5
0.7
ΔVLN
Line transient output variation
ΔVLD
V = 2.4 V, VBOOST = 3.1 V, IO = 1 mA → 50 mA,
Load transient output variation IN
Δt = 1 µs
5
10
VRIP
Output ripple
4
10 mVpp
Quiescent current
IQ
4
IO = 10 mA, VIN = 1.8 V → VBOOST, ΔT = 25 µs
VIN = 1.8 V, IO = 50 mA
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10
mA
V
mV
mV
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SLVSAD1 A – JUNE 2010 – REVISED JUNE 2010
ELECTRICAL CHARACTERISTICS (continued)
TA = 0°C to 85°C; typical values are at TA = 25°C (unless otherwise noted)
PARAMETER
TEST CONDITIONS
MIN
TYP
MAX
UNIT
BOOST CONVERTER (Continued)
IOFF
Off-mode current
tSTART
Start-up time
CL
Load capacitance
L
Inductance
From enable, VBOOST = 10% → 90%
6
0.1
1
mA
0.25
10
ms
10
22
10
mF
mH
POST REGULATION LDO
VIN
Input voltage at IN_VM
VLDO
Output voltage
10 µA ≤ IO ≤ IOMAX
IO
Output current
Normal mode
ILIMIT
Current limit
VLDO > 1 V
ISHORT
Short-circuit current
Output shorted to ground
VREG
Line regulation
dVLDO/dVIN at IO = Max
0.2
%
LREG
Load regulation
VLDO (IOMIN) – VLDO(IOMAX)
40
mV
ΔVLN
Load transient response
IO = 20 mA/µs, VIN = 3.1 V
50
100
mV
IQ
Quiescent current
IO = 0 mA
16
17.6
µA
PSRR
Power-supply ripple rejection
f = 120 Hz to 1 kHz at IO = IOMAX/2, VIN = 3.1 V
VRIP_NORM
Output ripple
VBAT < 3.1 V, IO = 50 mA, VIN = VBOOST
0.1
1 mVpp
VRIP_HIBAT
Output ripple
VBAT > 3.1 V, IO = 50 mA, VIN = VBOOST
4
10 mVpp
Boost plus LDO efficiency
3.1
2.91
3.6
3
3.09
V
V
50
mA
300
400
500
mA
30
60
150
mA
40
dB
VBAT = 2.4 V, IO = 5 mA, VIN = VBOOST
87%
VBAT = 2.4 V, IO = 50 mA, VIN = VBOOST
88%
tON
Turn-on time
IO = 0 mA, VLDO = 90%, CL = 2.9 µF
130
500
µs
tOFF
Turn-off time
IO = 0 mA, VLDO < 0.5 V, CL = 2.9 µF
3.9
5
ms
CL
Load capacitance
Ceramic capacitor, ESR = 10 mΩ to 150 mΩ
10
22
µF
1.8
3.6
V
3.6
V
VIN
V
4.7
BATTERY LOAD MONITOR
VOP
Operating voltage
VIN
Input voltage at PP_BAT
VOUT
Output voltage at
BAT_CHECK
ILOAD
Load current
RON
Switch on-resistance
1.8
VIN = 1.8 V to 3.6 V
10
mA
12
15
Ω
1.8
3.6
V
3.6
V
BATTERY LOAD SWITCH
VOP
Operating voltage
VIN
Input voltage at
BAT_FALSELOAD
IIN
Input current
RON
Switch on-resistance
240
360
mA
500
mΩ
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DEVICE INFORMATION
SW_BOOST
VO_BOOST
MODE_BUCK
GND2
EN_BUCK
VIN_BUCK
SW_BUCK
GND_BUCK
RSM PACKAGE
(BOTTOM VIEW)
1
32
EN_BOOST
GND_BOOST
EN_LDO
GND
VIN_BOOST
EN_BAT_CHECK
FB_BOOST
FB_BUCK
THERMAL PAD
IN_VM
BAT_FLASELOAD_EN
OUT_VM
EN_SW1
GND_FALSELOAD
BAT_FALSELOAD
PP_BAT
GND3
PG
TEST2
TEST1
IN_VIO
OUT_VIO
BAT_CHECK
OUT_VIO
IN_VIO
PIN FUNCTIONS
PIN
NAME
NO.
I/O
DESCRIPTION
BAT_CHECK
15
O
Battery monitor switch output. Connect to ADC for battery-level check.
BAT_FALSELOAD
18
I
Battery monitor input for false-load check
BAT_FALSELOAD_
EN
28
I
Battery false load switch enable
EN_BAT_CHECK
30
I
Battery-check path enable
EN_BOOST
32
I
Boost converter enable
EN_BUCK
4
I
Buck converter enable
EN_LDO
31
I
Boost post-regulation LDO enable
EN_SW1
27
I
Buck-load switch (SW1) enable
FB_BOOST
12
I
Boost-converter feedback input
FB_BUCK
29
I
Buck converter feedback input
GND
10
–
GND
GND2
5
–
Device ground
GND3
20
–
Device ground
GND_BOOST
9
–
Boost converter ground
GND_BUCK
1
–
Buck converter ground
6
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SLVSAD1 A – JUNE 2010 – REVISED JUNE 2010
PIN FUNCTIONS (continued)
PIN
NAME
GND_FALSELOAD
NO.
I/O
DESCRIPTION
17
O
False load ground
IN_VIO
25, 26
–
Internal I/O power supply. Load switch 1 input. Connect externally to buck output
IN_VM
13
I
Boost post-regulation LDO input. Connect externally to VO_BOOST.
MODE_BUCK
6
I
Buck converter mode control. High for PWM, low for PFM
OUT_VIO
23, 24
O
Load switch 1 output
OUT_VM
14
O
Boost post-regulation LDO output
PG
21
O
Buck power-good indication output. High when VBUCK > 1.7 V
PP_BAT
19
I
Battery input for level check
SW_BOOST
8
IO
Boost converter switching node. Inductor connection
SW_BUCK
2
O
Buck converter switching output. Inductor connection
TEST1
22
IO
Test pin1 (tie to GND)
TEST2
16
O
Test pin 2 (do not connect)
VIN_BOOST
11
–
Boost-converter power supply
VIN_BUCK
3
–
Buck converter power supply
VO_BOOST
7
O
Boost converter regulated output
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FUNCTIONAL BLOCK DIAGRAM
BUCK
VIN_BUCK
EN_BUCK
MODE_BUCK
Switching
Control
SW_BUCK
GND_BUCK
+
PFM
Soft Start
-
GND
FB_BUCK
+
+
ErrAmp
-
PWM
-
VREF
PG
-
PG
Comp
1.7V
+
BUCK LOAD SW
EN_SW1
IN_VIO
Soft Turn ON
OUT_VIO
OUT_VM
ErrAmp
VREF
+
IN_VM
EN_LDO
BOOST REG. LDO
FB_BOOST
ErrAmp
+
VREF
VO_BOOST
EN_BOOST
TEST1
Regulation
&
Switching
Mode
Control
with
Soft Start
SW_BOOST
+
TEST2
I SENSE
-
GND_BOOST
VIN_BOOST
+
VIN
COMP
-
BOOST
VTH
PP_BAT
EN_BAT_CHECK
BATT
MONITOR
SWITCH
BAT_CHECK
VIO
L/S
BAT_FALSELOAD
VIO
EN_BAT_FALSELOAD
8
BATTERY
LOAD
SWITCH
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GND_FALSELOAD
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SLVSAD1 A – JUNE 2010 – REVISED JUNE 2010
TYPICAL CHARACTERISTICS
1.830
95
1.825
VBUCK - Buck Output Voltage - V
100
Efficiency - %
90
85
VIN = 2.1 V
VIN = 2.4 V
80
VIN = 2.8 V
75
VIN = 3.2 V
70
65
VIN = 3.2 V
1.820
1.815
VIN = 2.8 V
1.810
1.805
VIN = 2.4 V
1.800
VIN = 2.1 V
1.795
60
0.1
1
10
Load - mA
100
Figure 1. Buck Efficiency – MODE_BUCK = 0
1.790
0
10
20
30
40 50 60
Load - mA
70
80
90
100
Figure 2. Buck Output Voltage vs Load – MODE_BUCK = 0
1.805
VBUCK - Buck Output Voltage - V
VIN = 2.4 V
Iload = 100 mA
VIN = 3.2 V
1.803
VIN = 2.8 V
VIN = 2.4 V
1.801
1.799
VBUCK
VIN = 2.1 V
1.797
10 mV/div
1 ms/div
1.795
0
20
40
60
Load - mA
80
100
Figure 3. Buck Output Voltage vs Load – MODE_BUCK = 1
Figure 4. Buck Output-Voltage Ripple – PWM
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TYPICAL CHARACTERISTICS (continued)
VIN = 2.4 V
Iload = 20 mA
VBUCK
10 mV/div
10 ms/div
Figure 5. Buck Output-Voltage Ripple – PFM
Figure 6. Buck Output Load Transient Response
100
VIN = 2 V to 3.6 V in 25 ms
Iload = 50 mA
VIN = 3.2 V
95
VIN
VIN = 2.8 V
90
Efficiency - %
1 V/div
VBUCK
20 mV/div
400 ms/div
85
VIN = 2.4 V
80
75
VIN = 2.1 V
70
65
60
0.1
Figure 7. Buck Output Line Transient Response
10
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1
Load - mA
10
100
Figure 8. Boost With LDO Efficiency
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SLVSAD1 A – JUNE 2010 – REVISED JUNE 2010
TYPICAL CHARACTERISTICS (continued)
VIN = 2.4 V
Iload = 50 mA
VIN = 2.4 V
Iload = 0 mA
VBOOST
VBOOST
VLDO
VLDO
10 mV/div
1 ms/div
10 mV/div
1 ms/div
Figure 9. Boost Output Voltage Ripple
Figure 10. Boost Output Voltage Ripple
VIN = 1.8 V to 3.1 V
Iload = 10 mA
VBOOST
VIN
10 mV/div
1 V/div
2 ms/div
Figure 11. Boost Line Transient Response
Figure 12. Boost Load Transient Response
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TYPICAL CHARACTERISTICS (continued)
Inductor
Voltage
VIN = 1.8 V to 3.1 V
Iload = 10 mA
1 V/div
10 mV/div
400 ns/div
VBOOST
Figure 13. Boost Switching Waveform –
Continuous-Current Mode
12
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Figure 14. Boost Switching Waveform –
Discontinuous-Current Mode
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THEORY OF OPERATION
Enable
The TPS80010 includes two dc-dc converters, a load switch, post-regulation LDO, and battery monitoring switch.
Each of these circuits has a dedicated enable pin with an internal pulldown resistor, RPULLDOWN, that can be
driven by standard logic or by an open-drain driver. The EN_BUCK pin not only enables the buck converter, but
also serves as the master enable for the device. No other circuitry in the TPS80010 can operate without
EN_BUCK set high.
Buck DC-DC Converter and Load Switch
The synchronous step-down (buck) converter in the TPS80010 provides a fixed 1.8-V output with a load capacity
of 150 mA. This converter operates with a fixed switching frequency of 2.25 MHz during pulse-width-modulation
(PWM) operation at moderate to heavy loads. As the load current decreases, the converter automatically
switches to a power-save mode and operates in pulse-frequency-modulation (PFM) mode in order to maximize
power efficiency. During PFM operation, the converter positions the output at a voltage about 1% above the
nominal output voltage. This feature minimizes the output voltage drops during sudden load transients. The
power-save mode can be disabled by setting the MODE_BUCK pin high.
The buck converter has internal soft-start circuitry that limits the inrush current during startup to 150 mA, allowing
a slow and controlled output-voltage ramp. Once the output voltage reaches 1.7 V, the output monitoring circuitry
generates a power-good (PG) output signal.
The TPS80010 also includes a load switch that is to be connected externally to the buck output voltage. This
switch provides flexibility in the design and power distribution of the end application by allowing several loads
(such as memory, I/O, Bluetooth, etc.) to be connected to the same supply while being able to power down or
disconnect some of these loads selectively when the end application goes to a low-power mode of operation.
This switch has a controlled turnon in order to limit the inrush current caused by the load, and hence the load
transient to the buck converter.
Boost DC-DC Converter and Post-Regulation LDO
The TPS80010 includes a synchronous step-up (boost) converter that provides a 3.1-V fixed output at 50-mA
load current. The boost converter is controlled by a hysteretic current-mode controller. This controller regulates
the output voltage by keeping the inductor ripple current constant and adjusting the offset of this inductor current
depending on the output load. If the required average input current is lower than the average inductor current
defined by this constant ripple, the converter goes into discontinuous-current mode (DCM) to keep the efficiency
high at low-load conditions. The boost also has a soft-start circuit that limits the inrush current to 150 mA.
In order to provide a clean, low-noise supply when VBAT > 3.1 V, the output of the boost is post-regulated by a
3-V LDO. This post-regulation allows the TPS80010 to provide a solid 3-V supply rail to the end application
across the full input or battery-voltage range while minimizing the number of external components. In order to
minimize power loss through the power path, the LDO allows for 100-mV input-voltage headroom at 50-mA load.
Battery Monitoring Switch and False Load
The TPS80010 implements a battery-voltage monitor switch to briefly check battery lifetime. The integrated
false-load switch connects a specified load to the battery. When this false load is applied, the battery monitor
switch is turned on, gating the sensed battery voltage to the ADC in the system. Based on this measurement, the
system can determine the battery impedance, and hence, battery health.
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APPLICATION INFORMATION
Typical Application
1.8 V–3.6 V
AA
AA
10 mF
10 mF
VIN_BOOST
BAT_FALSELOAD
VIN_BUCK
PP_BAT
10 W
10 mH
SW_BOOST
EN_BOOST
VO_BOOST
EN_LDO
FB_BOOST
3.1 V
22 mF
EN_BUCK
TPS80010
IN_VM
EN_SW1
EN_BAT_CHECK
3V
OUT_VM
4.7 mF
CONTROLLER
LED
EN_BAT_FLASELOAD
2.2 mH
PG
SW_BUCK
OPTICAL
SENSOR
1.8 V
10 mF
BAT_CHECK
MEMORY/
IO
FB_BUCK
1.8 kW
MODE_BUCK
IN_VIO
ADC
OUT_VIO
TEST1
NC
1.8 V
1.8-V
PERIPHERALS
TEST2
1.8 kW
GND
Buck Output Filter Design
The TPS80010 buck regulator is designed to operate with inductors in the range of 1.5 µH to 4.7 µH and with
output capacitors in the range of 4.7 µF to 22 µF. The part is optimized for operation with a 2.2-µH inductor and
10-µF output capacitor.
Larger or smaller inductor values can be used to optimize the performance of the device for specific operation
conditions. For stable operation, the L and C values of the output filter must not fall below 1-µH effective
inductance and 3.5-µF effective capacitance.
Buck Inductor Selection
The inductor value has a direct effect on the ripple current. The selected inductor must be rated for its dc
resistance and saturation current. The inductor ripple current (ΔIL) decreases with higher inductance and
increases with higher VIN or VBUCK.
The inductor selection also has an impact on the output-voltage ripple in PFM mode. Higher inductor values lead
to lower output-voltage ripple and higher PFM frequency; lower inductor values lead to a higher output-voltage
ripple but lower PFM frequency.
Equation 1 calculates the maximum inductor current in PWM mode under static load conditions. The saturation
current of the inductor should be rated higher than the maximum inductor current, as calculated with Equation 2.
This is recommended because during heavy load transients, the inductor current rises above the calculated
value.
V
1- BUCK
VIN
ΔIL = VBUCK ´
L ´ f
(1)
ΔIL
ILmax = IOmax +
2
(2)
with:
f = Switching frequency (2.25 MHz typical)
14
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L = Inductor value
ΔIL = Peak-to-peak inductor ripple current
ILmax = Maximum inductor current
A more conservative approach is to select the inductor current rating just for the switch current limit, ILIMF, of the
converter.
Accepting larger values of ripple current allows the use of lower inductance values, but results in higher output
voltage ripple, greater core losses, and lower output current capability.
The total losses of the coil have a strong impact on the efficiency of the dc-dc conversion and consist of both the
losses in the dc resistance (R(DC)) and the following frequency-dependent components:
• The losses in the core material (magnetic hysteresis loss, especially at high switching frequencies)
• Additional losses in the conductor from the skin effect (current displacement at high frequencies)
• Magnetic field losses of the neighboring windings (proximity effect)
• Radiation losses
Buck Output Capacitor Selection
The advanced fast-response voltage mode control scheme of the TPS80010 buck regulator allows the use of tiny
ceramic capacitors. Ceramic capacitors with low ESR values have the lowest output voltage ripple and are
recommended. The output capacitor requires either an X7R or X5R dielectric. Y5V- and Z5U-dielectric
capacitors, aside from their wide variation in capacitance over temperature, become resistive at high frequencies.
At nominal load current, the device operates in PWM mode and the rms ripple current is calculated as:
V
1 - BUCK
VIN
1
IRMSCout = VBUCK ×
´
L ´ f
2 ´ 3
(3)
At nominal load current, the device operates in PWM mode and the overall output voltage ripple is the sum of the
voltage spike caused by the output capacitor ESR plus the voltage ripple caused by charging and discharging the
output capacitor:
V
1- BUCK
æ
ö
VIN
1
ΔVBUCK = VBUCK ×
+ ESR ÷
´ ç
L ´ f
8
×
C
f
´
OUT
è
ø
(4)
At light load currents, the converter operates in power-save mode, and the output-voltage ripple depends on the
output-capacitor and inductor values. Larger output-capacitor and inductor values minimize the voltage ripple in
PFM mode and tighten dc output accuracy in PFM mode.
Buck Input Capacitor Selection
An input capacitor is required for best input voltage filtering and for minimizing the interference with other circuits
caused by high input-voltage spikes. For most applications, a 4.7-µF to 10-µF ceramic capacitor is
recommended. Because a ceramic capacitor loses up to 80% of its initial capacitance at 5 V, it is recommended
that 10-µF input capacitors be used for input voltages > 4.5 V. The input capacitor can be increased without any
limit for better input-voltage filtering. Take care when using only small ceramic input capacitors. When a ceramic
capacitor is used at the input and the power is being supplied through long wires, such as from a wall adapter, a
load step at the output or VIN step on the input can induce ringing at the VIN_BUCK pin. This ringing can couple
to the output and be mistaken as loop instability or could even damage the part by exceeding the maximum
ratings.
Table 1. Recommended Component List for Buck Converter
Component
Value
Part#
Supplier
Size
LQM2HPN2R2MJ0L
Murata
2.5 × 2 × 1.2 (1008)
LPS3015-222ML
Coilcraft
3 × 3 × 1.5
Inductor
2.2 mH
Cacitor (IN)
10 mF
GRM188R60J106ME47D
Murata
0603
Capacitor (OUT)
10 mF
GRM188R60J106ME47D
Murata
0603
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Boost Inductor Selection
To ensure proper operation of the TPS80010 boost dc-dc converter, a suitable inductor must be connected
between pins VIN_BOOST and SW_BOOST. Inductor values of 4.7 mH show good performance over the whole
input and output voltage range.
Choosing other inductance values affects the switching frequency f proportional to 1/L as shown in Equation 5.
V ´ (VBOOST - VIN )
1
L=
´ IN
f ´ 200 mA
VBOOST
(5)
Choosing inductor values higher than 4.7 mH can improve efficiency due to reduced switching frequency and
correspondingly reduced switching losses. Using inductor values below 2.2 mH is not recommended.
Having selected an inductance value, the peak current for the inductor in steady-state operation can be
calculated. Equation 6 gives the peak current estimate.
ìV
ü
× IBOOST
IL,MAX = í BOOST
+ 100 mA ý
0.8 × VIN
î
þ
IL,MAX = 200 mA
continuous current operation
discontinuous current operation
(6)
IL,MAX is the required minimum inductor-current rating. Note that load-transient or overcurrent conditions may
require an even higher current rating.
The condition in Equation 7 provides an easy way to determine whether the device is in continuous or
discontinuous operation. As long as the condition is true, the device operates in continuous-current mode. If the
condition becomes false, discontinuous-current operation is established.
VBOOST × IO
> 0.8 ´ 100 mA
VIN
(7)
Due to the use of current hysteretic control in the TPS80010 boost, the series resistance of the inductor can
impact the operation of the main switch. There is a simple calculation that can ensure proper operation of the
TPS80010 boost converter. The relationship between the series resistance (RIN), the input voltage (VIN), and the
switch-current limit (ISW) is shown in Equation 8.
V
RIN < IN
ISW
(8)
Examples:
ISW = 400 mA, VIN = 2.5 V
(9)
In Equation 9, RIN < 2.5 V / 400 mA; therefore, RIN must be less than 6.25 Ω.
ISW = 400 mA, VIN = 1.8 V
(10)
In Equation 10, RIN < 1.8 V / 400 mA; therefore, RIN must be less than 4.5 Ω.
Boost Input Capacitor
The input capacitor should be at least 10 mF to improve transient behavior of the regulator and EMI behavior of
the total power-supply circuit. The input capacitor should be a ceramic capacitor and be placed as close as
possible to the VIN_BOOST and GND pins of the IC. These capacitors should be X7R or X5R ceramic
capacitors.
Boost Output Capacitor
For the output capacitor COUT, it is recommended to use small X7R or X5R ceramic capacitors placed as close
as possible to the VO_BOOST and GND pins of the IC. If, for any reason, the application requires the use of
large capacitors which cannot be placed close to the IC, the use of a small ceramic capacitor with a capacitance
value of around 4.7 mF in parallel with the larger one is recommended. This small capacitor should be placed as
close as possible to the VO_BOOST and GND pins of the IC.
16
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A minimum effective capacitance value of 6 mF should be used; 10 mF is recommended. If the inductor value
exceeds 4.7 mH, the value of the effective output capacitance value must be half the inductance value or higher
for stability reasons; see Equation 11.
L
mF
COUT ³
´
2
mH
(11)
When choosing the output capacitor, note the effects of bias voltage, temperature, and tolerance on the effective
capacitance of the component. A capacitor in a 0603 package size suffers more capacitance degradation than a
0805 package at a similar bias voltage. For example, either a 22-µF 0603-sized capacitor or a 10-µF 0805-sized
capacitor would be required to work with a nominal 10-µH inductor.
The TPS80010 boost is not sensitive to ESR in terms of stability. Using low-ESR capacitors, such as ceramic
capacitors, is recommended to minimize output-voltage ripple. If heavy load changes are expected, the output
capacitor value should be increased to avoid output voltage drops during fast load transients.
Table 2. Recommended Component List for Boost Converter
Component
Value
Part#
Supplier
Size
Inductor
10 mH
CBC3225T100MR
Taiyo Yuden
3.2 × 2.5 × 2.5 (1210)
DO3314-103ML
Coilcraft
Capacitor (IN)
3.3 × 3.3 × 1.4
10 mF
GRM188R60J106ME47D
Murata
Capacitor (OUT)
0603
22 mF
AMK107BJ226MA-T
Taiyo Yuden
0603
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17
PACKAGE OPTION ADDENDUM
www.ti.com
28-Jun-2010
PACKAGING INFORMATION
Orderable Device
TPS80010ARSMR
Status
(1)
ACTIVE
Package Type Package
Drawing
VQFN
RSM
Pins
Package Qty
32
3000
Eco Plan
(2)
Green (RoHS
& no Sb/Br)
Lead/
Ball Finish
MSL Peak Temp
(3)
CU NIPDAU Level-2-260C-1 YEAR
Samples
(Requires Login)
Purchase Samples
(1)
The marketing status values are defined as follows:
ACTIVE: Product device recommended for new designs.
LIFEBUY: TI has announced that the device will be discontinued, and a lifetime-buy period is in effect.
NRND: Not recommended for new designs. Device is in production to support existing customers, but TI does not recommend using this part in a new design.
PREVIEW: Device has been announced but is not in production. Samples may or may not be available.
OBSOLETE: TI has discontinued the production of the device.
(2)
Eco Plan - The planned eco-friendly classification: Pb-Free (RoHS), Pb-Free (RoHS Exempt), or Green (RoHS & no Sb/Br) - please check http://www.ti.com/productcontent for the latest availability
information and additional product content details.
TBD: The Pb-Free/Green conversion plan has not been defined.
Pb-Free (RoHS): TI's terms "Lead-Free" or "Pb-Free" mean semiconductor products that are compatible with the current RoHS requirements for all 6 substances, including the requirement that
lead not exceed 0.1% by weight in homogeneous materials. Where designed to be soldered at high temperatures, TI Pb-Free products are suitable for use in specified lead-free processes.
Pb-Free (RoHS Exempt): This component has a RoHS exemption for either 1) lead-based flip-chip solder bumps used between the die and package, or 2) lead-based die adhesive used between
the die and leadframe. The component is otherwise considered Pb-Free (RoHS compatible) as defined above.
Green (RoHS & no Sb/Br): TI defines "Green" to mean Pb-Free (RoHS compatible), and free of Bromine (Br) and Antimony (Sb) based flame retardants (Br or Sb do not exceed 0.1% by weight
in homogeneous material)
(3)
MSL, Peak Temp. -- The Moisture Sensitivity Level rating according to the JEDEC industry standard classifications, and peak solder temperature.
Important Information and Disclaimer:The information provided on this page represents TI's knowledge and belief as of the date that it is provided. TI bases its knowledge and belief on information
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TI and TI suppliers consider certain information to be proprietary, and thus CAS numbers and other limited information may not be available for release.
In no event shall TI's liability arising out of such information exceed the total purchase price of the TI part(s) at issue in this document sold by TI to Customer on an annual basis.
Addendum-Page 1
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