TK83361M NARROW BAND FM IF IC FEATURES APPLICATIONS n Wide Operating Voltage Range 2.0 to 8.0V n RF Input Frequency up to 220 MHz n Low Supply Current (2.8mA, squelch off, 3.8mA, n n n n n n n squelch on) Low External Component Count µ) Excellent Limiting Sensitivity (-3dB = 8dBµ Amateur Radio Transceivers Cordless Phones Remote Controls Wireless Data Transceivers Battery Powered Devices DESCRIPTION The TK83361M is a narrow band FM IF IC designed for cordless phones, radio transceivers, remote controls, wireless data transceivers, and other communication equipment. TK83361M It integrates the mixer, oscillator, limiting amplifier, FM demodulator, filter amplifier and squelch circuit into a single surface mount SOP-16 package. The low operating current combined with a minimum operating voltage of only 2 V makes this device ideal for battery powered devices. The TK83361M offers improved performance over the MC3361C. The operating frequency has been increased to 220MHz (vs. 60MHz) while reducing the supply current from 5.2 mA to 3.8mA (squelch on). Offered in the SOP-16 surface mount package, the TK83361M is a drop-in replacement for the MC3361C. OSC (B) 1 16 RF INPUT OSC (E) 2 15 GND MIXER OUT 3 14 SCAN CONTROL VCC 4 13 SCAN CONTROL IF INPUT 5 12 SQUELCH INPUT DECOUPLE 6 11 FILTER AMP OUTPUT DECOUPLE 7 10 FILTER AMP INPUT QUAD COIL 8 9 AF OUTPUT BLOCK DIAGRAM ORDERING INFORMATION OSC (B) 1 16 RF INPUT MIXER OSC TK83361M OSC (E) 2 Tape/Reel Code GND MIXER OUT 3 15 GND 14 SCAN CONTROL SQUELCH TAPE/REEL CODE VCC 4 IF INPUT 5 DECOUPLE 6 DECOUPLE 7 13 SCAN CONTROL VCC 12 SQUELCH INPUT TL: Tape Left LIMIT AMP FILTER AMP 11 FILTER AMP OUTPUT 10 FILTER AMP INPUT 10pF QUAD COIL December 2000 TOKO, Inc. 8 QUAL DET 9 AF OUTPUT Page 1 TK83361M ABSOLUTE MAXIMUM RATINGS Supply Voltage ........................................................ 10 V Operating Voltage ......................................... 2.0 to 8.0 V Power Dissipation (Note 1) ................................ 600 mW Storage Temperature Range ................... -55 to +150 °C Operating Temperature Range .................. -30 to +70 °C Input Frequency ............................................... 220 MHz TK83361M ELECTRICAL CHARACTERISTICS Test Conditions: VCC = 4.0 V, fRF = 10.7 MHz, VRF = +80dBµ, fm = 1kHz, fdev = ±3kHz, fOSC = 10.245MHz, Ta = 25°C, unless otherwise specified. SYMBOL PARAMETER TEST CONDITIONS MIN TYP MAX UNITS ICC1 Supply Current 1 No Signal, Squelch off 2.8 3.5 mA ICC2 Supply Current 2 No Signal, Squelch on 3.8 4.9 mA Limit -3dB Limiting Sensitivity -3dB pt.(1kHz) 8 15 dBµ VO Output Voltage VRF = +80dBµ, fdev = ±3kHz ZO Output Impedance THD 130 170 mVrms VRF = +80dBµ, fdev = ±3kHz 450 Ω Total Harmonic Distortion VRF = +80dBµ, fdev = ±3kHz 0.86 GM Mixer Conversion Gain Pin 3: terminated RIM Mixer Input Impedance DC Measurement Gf Filter Amplifier Gain fin = 10kHz, Vin = 0.3mV fOC Filter Amplifier Output Terminal Voltage SH 21 2.5 % 28 dB 3.3 kΩ 40 50 dB No Signal 0.5 0.7 Scan Control High Level Squelch Input VSQ = 0.0V 3.0 3.9 SL Scan Control Low Level Squelch Input VSQ = 2.5V SH Scan Control High Level Squelch Input VSQ = 2.5V SL Scan Control Low Level Squelch Input VSQ = 0.0V HYS Squelch Hysteresis 0.0 3.0 0.9 V V 0.4 3.9 V V 0.0 0.4 V 45 100 mV Note 1: Power dissipation must be decreased at a rate of 4.8 mW/°C for operation above 25°C. Page 2 December 2000 TOKO, Inc. TK83361M TEST CIRCUIT 10.245MHz 0.01µF 1 OSC 10µF GND 15 2 50Ω 100kΩ 120pF VCC + 16 MIXER 33pF 0.1µF CF 3 14 10kΩ VCC SQUELCH 4 VCC 13 5 12 1µF + 0.1µF 6 LIMIT AMP 0.1µF FILTER AMP 11 10 7 470kΩ 1µF + 510Ω CF = BLFC455D (TOKO) CFU455D2 (MURATA) QUAD COIL = 7MCS-13546Z 10pF 20kΩ 8 9 QUAD DET QUAD COIL 8.2kΩ 0.01µF TYPICAL PERFORMANCE CHARACTERISTICS 9 - 1. Mixer + IF Section VO(DET), AMR, N, THD vs. 7.0 -30 -40 6.0 5.0 4.0 AMR(mod=30%) -50 3.0 -60 2.0 -70 1.0 THD N -10 -20 -30 -40 -50 1kHz±3kHz Non-mod fRF = 10.7MHz f m = 1kHz fdev = ±3kHz fOSC = 10.245MHz VOSC = ±0dBm 1.5 1.0 0.5 0.0 -0.5 0.0 0.5 1.0 1.5 2.0 2.5 3.0 3.5 4.0 τR, RISE TIME (msec) December 2000 TOKO, Inc. 5.0 4.0 3.0 2.0 N -70 THD 1.0 0 RELATIVE 20dB NQ SENSITIVITY(dB) SUPPLY VOLTAGE, OUTPUT LEVEL (V) VCC 2.0 AMR (MOD.=30%) 6.0 20dB NQS vs. RF INPUT FREQUENCY 3.5 2.5 VO(DET) V =4.0V cc f =455kHz IF f =1kHz, f =±3kHz m dev -60 TRANSIENT RESPONSE 3.0 7.0 -80 0.0 -20 ±0 +20 +40 +60 +80 +100 +120 VIF, IF INPUT SIGNAL LEVEL (dBµ) -80 0.0 -20 ±0 +20 +40 +60 +80 +100 +120 VRF, RF INPUT SIGNAL LEVEL (dBµ) 4.0 RF INPUT SIGNAL LEVEL THD, TOTAL HARMONIC DISTORTION(%) VO(DET) V =4.0V cc f =10.7MHz RF f =1kHz, f =±3kHz m dev fOSC=10.245MHz -20 VO(DET), Output Level, AMR, AM REJECTION AND N, NOISE (dBV) -10 RF INPUT SIGNAL LEVEL THD, TOTAL HARMONIC DISTORTION(%) VO(DET), OUTPUT LEVEL, AMR, AM REJECTION AND N, NOISE (dBV) VO(DET), AMR, N, THD vs. -20 20dB NQS = 17.5dBµ fRF = 10.7MHz fOSC = 10.245MHz -40 -60 0 -20 20dB NQS = 18.0dBµ fRF = 58MHz fOSC = 58.545MHz -40 -60 -20 -15 -10 -5 ±0 +5 +10 +15 +20 fRF±∆f RF, RF INPUT FREQUENCY(kHz) Page 3 TK83361M TYPICAL PERFORMANCE CHARACTERISTICS (CONT.) 9 - 2. Mixer Section GM, MIXER CONVERSION GAIN (dB) VOMR, RELATIVE MIXER OUTPUT LEVEL (dB) MIXER INPUT FREQUENCY RESPONSE 32 30 28 26 VCC = 4.0V fRF VARIABLE VRF = +60dBµ fOM = 455kHz VOSC = ±0dBm 24 22 1M 10M 100M 1G fRF, RF INPUT FREQUENCY (Hz) MIXER OUTPUT FREQUENCY RESPONSE 0 -2 -4 -6 -8 -10 -12 VCC = 4.0V fRF = 10.7MHz -14 VRF = +60dBµ fOSC VARIABLE VOSC = ±0dBm -16 -18 -20 100k 1M 10M fOM, MIXER OUTPUT FREQUENCY (Hz) THE 3rd ORDER INTERCEPT POINT SINAD, GM S/N vs. LOCAL OSC INPUT SIGNAL LEVEL SINAD, 12dB SINAD SENSITIVITY (dBµ) S/N, signal to noise ratio (dB) IIP3 = 107dBµ 120 1st ORDER DESIRED fRF = 10.7MHz 100 80 60 40 3rd ORDER INTERMOD fRF1 = 10.7125MHz fRF2 = 10.725MHz 20 20 40 60 80 100 120 VRF, RF INPUT SIGNAL LEVEL (dBµ) SINAD 50 6.0 -40 4.0 -50 2.0 THD -60 0.0 -40 -30 -20 -10 ±0 +10 +20 +30 +40 455±∆f IF, IF INPUT FREQUENCY (kHz) Page 4 VO(DC), OUTPUT DC VOLTAGE (V) -30 THD, TOTAL HARMONIC DISTORTION(%) VO(DET), OUTPUT LEVEL(dBV) O(DET) 8.0 25 20 30 S/N fRF = 10.7MHz 21MHz 58MHz 83MHz 20 10 15 10 0 -70 -60 -50 -40 -30 -20 -10 0 10 20 0 VOSC, LOCAL OSC INPUT SIGNAL LEVEL (dBµ) OUTPUT DC VOLTAGE vs. IF INPUT FREQUENCY OUTPUT LEVEL, TOTAL HARMONIC DISTORTION vs. IF INPUT FREQUENCY 10.0 -10 V VCC = 4.0V VIF = ±80dBµ f m = 1kHz fdev =±3kHz 30 GM 40 9 - 3. IF Section -20 35 60 GM, MIXER CONVERSION GAIN(dB) VOM, MIXER OUTPUT LEVEL (dBµ) 140 4.0 3.5 VCC = 4.0V VIF = +80dBµ 3.0 2.5 2.0 VCC 1.5 RD = 5kΩ 1.0 QUAD COIL RD .5 8 RD = 10kΩ RD = 20kΩ 0 -80 -60 -40 -20 ±0 +20 +40 +60 +80 455±∆f IF, IF INPUT FREQUENCY (kHz) December 2000 TOKO, Inc. TK83361M TYPICAL PERFORMANCE CHARACTERISTICS (CONT.) OUTPUT LEVEL, TOTAL HARMONIC DISTORTION vs. IF DEVIATION FREQUENCY 500 5.0 400 4.0 300 3.0 200 2.0 VO(DET) 1.0 100 THD 0 0 1 2 3 4 5 6 7 8 9 10 fdev., IF DEVIATION FREQUENCY (kHz) VO(DET)R, RELATIVE OUTPUT LEVEL (dB) 6.0 VCC =4.0V fIF = 455kHz VIF = +80dBµ f m = 1kHz THD, TOTAL HARMONIC DISTORTION(%) VO(DET), OUTPUT LEVEL(mVrms) 600 OUTPUT LEVEL vs. IF MODULATION FREQUENCY ±0 RD = 20kΩ 10kΩ -10 5kΩ -20 VCC -30 -40 QUAD COIL RD 8 0.0 100 1k 10k 100k 1M f m , IF MODULATION FREQUENCY (HZ) 9 - 4. Filter Amplifer Section INPUT LEVEL RESPONSE GAIN vs. INPUT FREQUENCY 10 70 60 50 Vout , OUTPUT LEVEL(Vrms) VCC = 4.0V Vin = 0.3mV R1 = 510Ω Rf = 470kΩ 40 30 1µF + 11 20 Rf 1µF + 10 10 100 THD VOUT 1 100m VCC = 4.0V Fin = 10kHz R1 = 510Ω Rf = 470kΩ THD, TOTAL HARMONIC DISTORTION(%) Gf , FILTER AMPLIFIER GAIN (dB) VCC =4.0V fIF = 455kHz VIF = +80dBµ fdev = ±3kHz Pin 9: open 10.0 1.0 R1 0 1k 10k 100k 1M fin , FILTER AMPLIFIER INPUT FREQUENCY (Hz) 10m 0.1 1 10 0.1 100 Vin , INPUT LEVEL(mVrms) 9 - 5. Squelch Section SCAN CONTROL vs. SQUELCH INPUT VOLTAGE SC, SC, SCAN CONTROL(V) 4.0 SC SC 3.5 3.0 2.5 2.0 1.5 1.0 VCC = 4.0V 0 .60 .65 .70 .75 .80 VSQ, SQUELCH INPUT VOLTAGE(V) December 2000 TOKO, Inc. Page 5 TK83361M TYPICAL PERFORMANCE CHARACTERISTICS (CONT.) 9 - 6. Versus Supply Voltage Characteristics 14 6.0 12 ICC2: sq off 5.0 10 SINAD ICC1: sq on 4.0 8 3.0 6 2.0 4 1.0 2 0 0.0 1 2 3 4 5 6 7 8 VCC, SUPPLY VOLTAGE(V) 9 32 28 24 20 16 12 8 4 0 VO(DET), OUTPUT LEVEL(dBV) 16 7.0 0 -5 VCC = 8.5V 4.0V 2.0V 60 40 20 20 Page 6 40 60 80 100 VRF, RF INPUT SIGNAL LEVEL(dBµ) 120 VO(DET) -15 60 4 VO(DC) -20 3 -25 2 50 40 30 20 THD -30 -35 1 VTH, VTL , THRESHGf , FILTER OLD VOLTAGE(V) AMP. GAIN(dB) 80 6 2 3 4 5 6 7 8 VCC, SUPPLY VOLTAGE(V) 9 1 10 0 0 FILT. AMP. GAIN, FILT. AMP. OUTPUT DC VOLTAGE, THRESHOLD VOLTAGE, HYSTERESIS vs. SUPPLY VOLTAGE 70 1.0 fOC 60 50 0.8 0.6 Gf 0.4 40 VTH 0.8 0.6 120 90 VTL HYS 0.4 60 0.2 30 0.0 0 1 2 3 4 5 6 7 8 VCC, SUPPLY VOLTAGE(V) HYS, SQUELCH HYSTERESIS(mV) VOM, MIXER OUTPUT LEVEL(dBµ) 100 70 fOC, OUTPUT DC VOLTAGE 120 7 5 -10 MIXER OUTPUT LEVEL vs. SUPPLY VOLTAGE 140 S/N THD(%),VO(DC)(V) ICC, SUPPLY CURRENT(mA) 8.0 36 OUTPUT LEVEL, TOTAL HARMONIC DISTORTION, SIGNAL TO NOISE RATIO, OUTPUT DC VOLTAGE vs. SUPPLY VOLTAGE S/N, SIGNAL TO NOISE RATIO (dB) 18 GM GM, MIXER CONVERSION GAIN(dB) 9.0 SINAD, 12dB SINAD SENSITIVITY(dBµ) SUPPLY CURRENT, 12dB SINAD SENSITIVITY, MIXER CONVERSION GAIN vs. SUPPLY VOLTAGE 9 December 2000 TOKO, Inc. TK83361M TYPICAL PERFORMANCE CHARACTERISTICS (CONT.) 9 - 7. Versus Ambient Temperature Characteristics 14 6 12 5 SINAD ICC2: sq off 10 8 4 6 3 ICC1: sq on 2 1 4 2 0 0 -40 -20 0 20 40 60 80 100 Ta, AMBIENT TEMPERATURE (°C) 32 28 24 20 16 12 8 4 0 VO(DET), OUTPUT LEVEL(dBV) 16 0 -5 S/N -10 VO(DET) -15 -20 VO(DC) -25 -30 -35 THD Gf , FILTER AMP. GAIN(dB) Ta = +25°C +85°C -40°C 60 40 20 20 40 60 80 100 VRF, RF INPUT SIGNAL LEVEL(dBµ) December 2000 TOKO, Inc. 120 VTH, VTL , THRESHOLD VOLTAGE(V) 80 6 60 5 50 4 40 3 30 2 20 1 10 0 70 60 FILT. AMP. GAIN, FILT. AMP. OUTPUT DC VOLTAGE, THRESHOLD VOLTAGE, HYSTERESIS vs. AMBIENT TEMP. Gf 0.8 0.6 50 40 VTH fOC 0.8 0.6 0.5 120 VTL 90 60 0.4 0.2 1.0 HYS 30 0.0 0 fOC, OUTPUT DC HYS, SQUELCH VOLTAGE(V) HYSTERESIS(mV) VOM, MIXER OUTPUT LEVEL(dBµ) 140 100 70 0 -40 -20 0 20 40 60 80 100 Ta, AMBIENT TEMPERATURE(°C) MIXER OUTPUT LEVEL vs. AMBIENT TEMPERATURE 120 7 THD(%),VO(DC)(V) ICC, SUPPLY CURRENT(mA) GM 7 36 S/N, SIGNAL TO NOISE RATIO (dB) 8 OUTPUT LEVEL, TOTAL HARMONIC DISTORTION, SIGNAL TO NOISE RATIO, OUTPUT DC VOLTAGE vs. AMBIENT TEMPERATURE GM, MIXER CONVERSION GAIN(dB) 18 9 SINAD, 12dB SINAD SENSITIVITY(dBµ) SUPPLY CURRENT, 12dB SINAD SENSITIVITY, MIXER CONVERSION GAIN vs. AMBIENT TEMPERATURE -40 -20 0 20 40 60 80 100 Ta, AMBIENT TEMPERATURE(°C) Page 7 TK83361M PIN FUNCTION DESCRIPTION PIN SYMBOL 1 OSC(B) 2 OSC(E) 3 MIXER OUT TERMINAL VOLTAGE (V) INTERNAL EQUIVALENT CIRCUIT VCC DESCRIPTION The base of the Colpitts oscillator. The Colpitts oscillator is composed of Pin 1 and Pin 2. 1 4 The emitter of the Colpitts oscillator. Using an external OSC source, local level must be injected into Pin 1, and Pin 2 must be opened. 2 Output of the Mixer. VCC 4 VCC Supply Voltage. 3 5 IF INPUT 6 DECOUPLE 7 DECOUPLE Input to the IF limiter amplifier. This pin is terminated by internal 1.8kW resistor. VCC 5 1.8k 51.8K 50K IF Decoupling 6 8 IF Decoupling. QUAD COIL 7 Phase Shifter. VCC 10p 8 9 Recovered Audio Output AF OUTPUT VCC 10p 9 Page 8 December 2000 TOKO, Inc. TK83361M PIN FUNCTION DESCRIPTION (CONT.) PIN 10 SYMBOL TERMINAL VOLTAGE (V) DESCRIPTION INTERNAL EQUIVALENT CIRCUIT Filter Amplifier Input. VCC FILTER AMPLIFIER INPUT 10 11 FILTER AMPLIFIER OUTPUT Filter Amplifier Output. VCC 11 12 13 Squelch Input. SQUELCH INPUT VCC SCAN CONTROL 13 Scan Control. 14 12 20k 14 SCAN CONTROL 15 GND Scan Control. Ground VCC 16 3.3K RF INPUT Mixer Input. 3.3K 16 15 December 2000 TOKO, Inc. Page 9 TK83361M TEST BOARD Figure 1: Solder Side View (Circuit Side View) Figure 2: Component Placement View NOTES: 1. Above test board is laid out for the TEST CIRCUIT (page 3). 2. Scale 1:1 (60mmx60mm) 3. 10.245MHz Fundamental mode crystal, about 30pF load. 4. 455kHz CF, TOKO Type BLFC455D or MURATA Type CFU455D2 or equivalent. 5. COIL, TOKO Type 7MCS-13546Z or 7MC-8128Z or equivalent. APPLICATIONS INFORMATION 12-1. Mixer Section The mixer consists of a Gilbert cell and a local oscillator. The mixer conversion gain, when Pin 4 is terminated, is 28dB. The RF input is unbalanced. 12-1-1. A Local OSC The oscillator included is a general Colpitts type OSC. The drive current of OSC is 200µA. Examples of components are shown in Fig. 3. The examples are explained in the next paragraph. Figure 3: Oscillator Components i) Under Crystal Control ii) Parallel LC Components VCC Page 10 VCC 1 1 2 2 December 2000 TOKO, Inc. TK83361M APPLICATIONS INFORMATION (CONT.) (1) Using an External Oscillator Source The circuit composition using an external OSC source is shown in Fig. 4. When using an external OSC source instead of the internal OSC, the local level must be injected into Pin 1 by capacitor coupling. In this case, Pin 2 must be open. The local OSC operates as an emitter follower for a multiplier by opening Pin 2 and injecting into Pin 1. tor. It is easy to increase the drive current by connecting resistor Re between Pin 2 and GND. Being short of drive current, it makes gm increase to increase the drive current by connecting external resistor Re. In that case, the amount of drive current increase, Ie, is shown in Eq.(1). V VBE V 0.7 Ie = CC = CC Re Re Figure 4: External Injection (1) VCC 0.01µ 1 RF ~ 50Ω IF 2 open (2) For 3rd Overtone mode In general, a crystal oscillator can oscillate in the fundamental mode and overtone mode. For example, it is easy for a 30MHz-overtone crystal to oscillate at 10MHz, fundamental mode. The reason is because the impedance of the fundamental mode is the same as the impedance of the overtone. Therefore, it is necessary for the circuit to select the overtone frequency by using a tuning coil. How to oscillate a general 3rd overtone oscillator is explained. In the case of an overtone mode of 30MHz and higher, using a crystal oscillator, we recommend the circuit in Fig. 5 to suppress the fundamental mode oscillation. Figure 5: Overtone Mode Circuit VCC In order to oscillate at the 3rd overtone frequency, the values of C2, C3 and L (Fig.5) are selected. Fig.6 shows a 2-port impedance response of the C2~C3~L loop network. Regarding the condition of oscillation, the impedance characteristic is capacitive at the vacinity of the overtone frequency. It is reactive at the vicinity of the fundamental frequency. The condition of oscillation is as follows: fOSC is between fa and fb, 3 x fOSC is fb and higher. Please see Fig.6 Figure 6: 2-port Impedance Response of Resonance Network +j Reactance 50Ω fOSC fa Where: fa: series resonant freq. fb: parallel resonant freq. fOSC: fundamental mode freq. 3 x fOSC: 3rd order overtone freq. fb 3 X f OSC -j Equations of 3rd order overtone oscillation are shown below. fa = 1 2π LxC2 , fb = fa C 1+ 2 C3 (2) The series value of the equivalent capacitance at the 3rd 1 order overtone freq. of this network, which is decided in the above -mentioned, and the capacitance of C1 must be equal C C2 L 1 2 to load capacitance CL. C3 Being short of negative resistance of the circuit, increase the transistor’s bias current by decreasing Re. It is able to Re decide the OSC level for minute adjusting Re. Please refer the most suitable OSC level range to 12dB SINAD sensitivity versus local OSC input signal level in TYPICAL PERThe following explains how to decide the circuit constants of FORMANCE CHARACTERISTICS. The saturating range the overtone-crystal-oscillation fundamental circuit. is the most suitable OSC level range. It is comparatively As the operating frequency increases the oscillation ampli- easy to decide the circuit constant by examining it with a tude decreases because of a shortage of gm of the oscilla- network analyzer. X’tal December 2000 TOKO, Inc. Page 11 TK83361M APPLICATIONS INFORMATION (CONT.) 12-2. IF Section The IF section includes a 6 stage differential amplifier. The fixed internal input matching resistor is 1.8kΩ. The total gain of the limiting amplifier section is approximately 77dB. The decoupling capacitors of Pin 6~7 must be connected as near as possible to the GND pin of the IC . And, make the impedance of the connecting-to-GND line to be as small as possible. If the impedance is not small enough, the sensitivities may worsen. Note at this point to add the bias voltage at Pin 8 from external source. The signal from the phase shifter is put into the multiplier cell through the emitter follower of transistor Q1. Pin 8 is singleconnected with the base terminal. And, it is necessary for Pin 8 to add the same voltage, as the base terminal of Q2 of the opposite side of Q1 through the multiplier is connected with the supply voltage. If the base voltages differ between transistors Q1 and Q2, it alters the DC zero point or worsens the distortion of the demodulation output. Figure 7: IF Limiter Amplifier Input Block 50K 5 1.8k 51.8K 6 7 12-3. FM Demodulator A quadrature FM demodulator using a Gilbert cell is included. 12-3-1. Internal Equivalent Circuit The internal equivalent circuit is shown in Fig. 8. Figure 8: Internal Equivalent Circuit of Demodulator VCC QUAD COIL 12-3-3. Audio Output After quadrature detection, the audio signal is pulled out through Pin 9. The required signal is pulled out through the LPF. 12-3-4. For Stable Operation To prevent worsening the distortion, observe the following notes: (1) Demodulated Output Voltage Too large of a demodulated output voltage will worsen the distortion due to the dynamic range of the demodulator. (2) The Signal Level in Phase Shifter (Pin 8) If the phase shifter signal level is too small, the noise level grows worse. This will cause the distortion to grow worse. (3) Band Width of Phase Shifter (Pin 8) If the bandwidth of the phase shifter is narrower than IF bandwidth, including the demodulated element, the distortion will grow worse. RD 8 VCC Active Load VCC Q2 Q1 from IF LIM AMP Page 12 12-3-2. Phase Shifter The IF signal from the limiter amplifier is provided with 90° phase shift and drives the quadrature detector. The parallel RCL resonance circuit is capable of using the internal 10pF phase shift capacitor. 10pF Multiplier Cell 12-4. Filter Amplifier Section An inverting op amp has an output at Pin 11 and the inverting input at Pin 10. The op amp, which has a wide stable operating temperature range, may be used as an active noise filter. 12-4-1. Active BPF Application An active BPF application is shown in Fig. 9, and its Response is shown in Fig. 10. December 2000 TOKO, Inc. TK83361M APPLICATIONS INFORMATION (CONT.) VTH indicates the Hi threshold voltage, VTL indicates the Lo threshold voltage in Fig. 11. Figure 9. Active BPF C R1 12-6. Application Example R3 + R2 Figure 12: Application Example Block Digram VOUT XTAL NETWORK C 1 2 GND 15 NARROW BAND BPF VIN ~ 3 14 Figure 10. Frequency Response RF INPUT 16 MIXER OSC MUTE VCC = 4.0V Vin = 50mV 15 10 5 VCC R1 = 18kΩ R2 = 750Ω R3 = 390kΩ C = 0.001µF 0 4 VCC SCAN CONTROL to PLL 13 5 12 SQUELCH 0.1µF 6 LIMIT AMP 0.1µF R1 = R3 R1R3 Q , R2 = , R3 = πf 0C 2G0 4Q2R1-R3 (3) 12-5. Squelch Section The output, which is controlled in accordance with the noise level from the rectifier, is injected into the squelch input pin. There is about 45mV of hysteresis at the Squelch Input to prevent jitter. Figure 11. Squelch Output versus Squelch Input VTL VTH VSQ(V) December 2000 TOKO, Inc. ii) Pin 14 Output Scan Control(V) Scan Control(V) i) Pin 13 Output VTL VTH 11 10 7 PHASE SHIFTER FILTER AMP NETWORK 1k 10k 100k fin , FILTER AMPLIFIER INPUT FREQUENCY (Hz) Eq. (3) is formularized, where G0 is the gain at center frequency f0, and 3dB bandwidth Q=f0/BW. RECTIFIER GAIN (dB) 20 10pF 8 9 LPF QUAD DET AF OUTPUT 12-7. Attentions to Layout Design As this product is considered for stable operation, the mixer block and the other block that includes IF stage, OP amp and squelch are independent from each other. However in order to realize stable operation, please pay attention to the following, because of high frequency operation. (1) Bypass Capacitor A bypass capacitor must be connected with minimum distance between the VCC pin and the GND pin. (2) VCC/GND Pattern In order to make low impedance VCC/GND lines, please keep the pattern as wide as possible. (3) Pattern near Demodulator Pattern layout around the phase shifter for demodulator: please keep as short as possible. VSQ(V) Page 13 TK83361M NOTES WARNING - Life support applications policy. TOKO, Inc. products shall not be used within any life support systems without the specific written consent of TOKO, Inc. A life support system is a product or system intended to support or sustain life which, if it fails, can be reasonably expected to result in a significant personal injury or death. The contents of this application as of December 2000. The contents of this datasheet are subject to change without notice or stop manufacture. The circuits shown in this specification are intended to explain typical applications of the products concerned. Accordingly, TOKO, Inc. is not responsible for any circuit problems, or for any infringement of third party patents or any other intellectual property rights that may arise from the use of these circuits. Moreover, this specification dose not signify that TOKO, Inc. agrees implicitly or explicitly to license any patent rights or other intellectual property rights which it holds. No Ozone Depleting Substances (ODS) were used in the manufacture of these parts. Examples of characteristics given here are typical for each product and being technical data, these do not constitute a guarantee of characteristics or conditions of use. Page 14 December 2000 TOKO, Inc. TK83361M PACKAGE OUTLINE Marking Information SOP-16 Marking 0.76 83361 Mark 1.27 TOKO Mark TK83361M 9 3.9±0.2 5.4 16 YYY 1.27 1 8 Recommended Mount Pad Lot No. 1.27 0 ~ 10 1.75 max +0.15 0.1 0.5±0.2 0.2 -0.05 +0.15 0.4 -0.05 ±0.2 0 ~ 0.25 1.45 9.9±0.2 0.12 M Dimensions are shown in millimeters Tolerance: x.x = ± 0.2 mm (unless otherwise specified) 6.0±0.3 Toko America, Inc. Headquarters 1250 Feehanville Drive, Mount Prospect, Illinois 60056 Tel: (847) 297-0070 Fax: (847) 699-7864 TOKO AMERICA REGIONAL OFFICES Midwest Regional Office Toko America, Inc. 1250 Feehanville Drive Mount Prospect, IL 60056 Tel: (847) 297-0070 Fax: (847) 699-7864 Western Regional Office Toko America, Inc. 2480 North First Street , Suite 260 San Jose, CA 95131 Tel: (408) 432-8281 Fax: (408) 943-9790 Semiconductor Technical Support Toko Design Center 4755 Forge Road Colorado Springs, CO 80907 Tel: (719) 528-2200 Fax: (719) 528-2375 Visit our Internet site at http://www.tokoam.com The information furnished by TOKO, Inc. is believed to be accurate and reliable. However, TOKO reserves the right to make changes or improvements in the design, specification or manufacture of its products without further notice. TOKO does not assume any liability arising from the application or use of any product or circuit described herein, nor for any infringements of patents or other rights of third parties which may result from the use of its products. No license is granted by implication or otherwise under any patent or patent rights of TOKO, Inc. December 2000 TOKO, Inc. © 2000 Toko, Inc. All Rights Reserved Page 15 IC-231-TK11031 0798O0.0K Printed in the USA