DAC900-Q1 www.ti.com SBAS505 – JUNE 2010 10-BIT 165-MSPS DIGITAL-TO-ANALOG CONVERTER Check for Samples: DAC900-Q1 FEATURES APPLICATIONS • • • • • • • 1 • Qualified for Automotive Applications Single +5V OR +3V Operation High SFDR: 5MHz Output at 100MSPS: 68dBc Low Glitch: 3pV-s Low Power: 170mW at +5V Internal Reference: Optional External Reference Adjustable Full-Scale Range Multiplying Option Latch-Up Performance Meets 100 mA Per JESD 78, Class I • • • • Communication Transmit Channels – WLL, Cellular Base Station – Digital Microwave Links – Cable Modems Waveform Generation – Direct Digital Synthesis (DDS) – Arbitrary Waveform Generation (ARB) Medical/Ultrasound High-Speed Instrumentation and Control Video, Digital TV DESCRIPTION The DAC900 is a high-speed, Digital-to-Analog Converter (DAC) offering a 10-bit resolution option within the SpeedPlus family of high-performance converters. Featuring pin compatibility among family members, the DAC908, DAC902, and DAC904 provide a component selection option to an 8-, 12-, and 14-bit resolution, respectively. All models within this family of DACs support update rates in excess of 165MSPS with excellent dynamic performance, and are especially suited to fulfill the demands of a variety of applications. The advanced segmentation architecture of the DAC900 is optimized to provide a high Spurious-Free Dynamic Range (SFDR) for single-tone, as well as for multi-tone signals—essential when used for the transmit signal path of communication systems. The DAC900 has a high impedance (200kΩ) current output with a nominal range of 20mA and an output compliance of up to 1.25V. The differential outputs allow for both a differential or singleended analog signal interface. The close matching of the current outputs ensures superior dynamic performance in the differential configuration, which can be implemented with a transformer. Utilizing a small geometry CMOS process, the monolithic DAC900 can be operated on a wide, single-supply range of +2.7V to +5.5V. Its low power consumption allows for use in portable and batteryoperated systems. Further optimization can be realized by lowering the output current with the adjustable full-scale option. For noncontinuous operation of the DAC900, a power-down mode results in only 45mW of standby power. The DAC900 comes with an integrated 1.24V bandgap reference and edge-triggered input latches, offering a complete converter solution. Both +3V and +5V CMOS logic families can be interfaced to the DAC900. The reference structure of the DAC900 allows for additional flexibility by utilizing the on-chip reference, or applying an external reference. The full-scale output current can be adjusted over a span of 2mA to 20mA, with one external resistor, while maintaining the specified dynamic performance. The DAC900 is available in a TSSOP-28 (PW) package. 1 Please be aware that an important notice concerning availability, standard warranty, and use in critical applications of Texas Instruments semiconductor products and disclaimers thereto appears at the end of this data sheet. PRODUCTION DATA information is current as of publication date. Products conform to specifications per the terms of the Texas Instruments standard warranty. Production processing does not necessarily include testing of all parameters. Copyright © 2010, Texas Instruments Incorporated DAC900-Q1 SBAS505 – JUNE 2010 www.ti.com This integrated circuit can be damaged by ESD. Texas Instruments recommends that all integrated circuits be handled with appropriate precautions. Failure to observe proper handling and installation procedures can cause damage. ESD damage can range from subtle performance degradation to complete device failure. Precision integrated circuits may be more susceptible to damage because very small parametric changes could cause the device not to meet its published specifications. +VA +VD BW DAC900 FSA Current Sources REFIN IOUT LSB Switches IOUT BYP Segmented Switches INT/EXT Latches PD +1.24V Ref. 10-Bit Data Input AGND D9...D0 CLK DGND ORDERING INFORMATION (1) PACKAGE (2) TA –40°C to 105°C (1) (2) TSSOP – PW Reel of 2500 ORDERABLE PART NUMBER DAC900TPWRQ1 TOP-SIDE MARKING DAC900T For the most current package and ordering information, see the Package Option Addendum at the end of this document, or see the TI web site at www.ti.com. Package drawings, thermal data, and symbolization are available at www.ti.com/packaging. ABSOLUTE MAXIMUM RATINGS over operating free-air temperature range (unless otherwise noted) +VA to AGND –0.3V to +6V +VD to DGND –0.3V to +6V AGND to DGND –0.3V to +0.3V +VA to +VD –6V to +6V CLK, PD to DGND –0.3V to VD + 0.3V D0-D9 to DGND –0.3V to VD + 0.3V IOUT, IOUT to AGND –1V to VA + 0.3V BW, BYP to AGND –0.3V to VA + 0.3V REFIN, FSA to AGND –0.3V to VA + 0.3V INT/EXT to AGND –0.3V to VA + 0.3V Junction temperature +150°C Storage temperature +150°C 2 Submit Documentation Feedback Copyright © 2010, Texas Instruments Incorporated Product Folder Link(s): DAC900-Q1 DAC900-Q1 www.ti.com SBAS505 – JUNE 2010 ELECTRICAL CHARACTERISTICS At TA = -40°C to +105°C, +VA = +5V, +VD = +5V, differential transformer coupled output, 50Ω doubly terminated, unless otherwise specified PARAMETER TEST CONDITIONS MIN RESOLUTION TYP MAX UNIT 10 bits OUTPUT UPDATE RATE Output Update Rate (fCLOCK) STATIC ACCURACY (1) 2.7V to 3.3V 125 165 MSPS 4.5V to 5.5V 165 200 MSPS -0.75 ±0.3 +0.75 -1 ±0.5 +1 TA = +25°C Differential Nonlinearity (DNL) fCLOCK = 25MSPS, fOUT = 1.0MHz TA = +25°C Integral Nonlinearity (INL) TA = -40°C to +105°C DYNAMIC PERFORMANCE TA = +25°C Spurious-Free Dynamic Range (SFDR) To Nyquist fOUT = 1.0MHz, fCLOCK = 25MSPS -1.5 +1.5 TA = +25°C 70 76 TA = -40°C to +105°C 60 76 LSB LSB dBc fOUT = 2.1MHz, fCLOCK = 50MSPS 75 dBc fOUT = 5.04MHz, fCLOCK = 50MSPS 68 dBc fOUT = 5.04MHz, fCLOCK = 100MSPS 68 dBc fOUT = 20.2MHz, fCLOCK = 100MSPS 62 dBc fOUT = 25.3MHz, fCLOCK = 125MSPS 62 dBc fOUT = 41.5MHz, fCLOCK = 125MSPS 53 dBc fOUT = 27.4MHz, fCLOCK = 165MSPS 59 dBc fOUT = 54.8MHz, fCLOCK = 165MSPS 53 dBc Spurious-Free Dynamic Range within a Window fOUT = 5.04MHz, fCLOCK = 50MSPS 2MHz Span 78 dBc fOUT = 5.04MHz, fCLOCK = 100MSPS 4MHz Span 78 dBc fOUT = 2.1MHz, fCLOCK = 50MSPS -74 dBc fOUT = 2.1MHz, fCLOCK = 125MSPS -73 dBc 60 dBc 30 ns ns Total Harmonic Distortion (THD) Two Tone fOUT1 = 13.5MHz, fOUT2 = 14.5MHz, fCLOCK = 100MSPS Output Settling Time (2) to 0.1% Output Rise Time (2) 10% to 90% 2 90% to 10% 2 ns 3 pV-s Output Fall Time (2) Glitch Impulse DC-ACCURACY Full-Scale Output Range (3) (FSR) All Bits High, IOUT Output Compliance Range Gain Error With Internal Reference 2 -1 TA = +25°C -10 TA = -40°C to +105°C -25 Gain Error With External Reference -10 Gain Drift With Internal Reference Offset Error With Internal Reference (1) (2) (3) 20 +1.25 ±1 +10 +25 ±2 +10 TA = -40°C to +105°C V %FSR %FSR ppmFSR/ °C ±120 TA = +25°C mA -0.06 +0.06 -0.1 +0.1 %FSR At output IOUT, while driving a virtual ground. Measured single-ended into 50Ω Load. Nominal full-scale output current is 32x IREF; see Application Section for details. Submit Documentation Feedback Copyright © 2010, Texas Instruments Incorporated Product Folder Link(s): DAC900-Q1 3 DAC900-Q1 SBAS505 – JUNE 2010 www.ti.com ELECTRICAL CHARACTERISTICS (continued) At TA = -40°C to +105°C, +VA = +5V, +VD = +5V, differential transformer coupled output, 50Ω doubly terminated, unless otherwise specified PARAMETER TEST CONDITIONS MIN Offset Drift With Internal Reference Power-Supply Rejection, +VA -0.2 +0.2 TA = -40°C to +105°C -1.4 +1.4 -0.025 +0.025 -0.4 +0.4 IOUT = 20mA, RLOAD = 50Ω Output Resistance Output Capacitance IOUT, IOUT to Ground UNIT ppmFSR/ °C TA = +25°C TA = -40°C to +105°C Output Noise MAX ±0.1 TA = +25°C Power-Supply Rejection, +VD TYP %FSR/V %FSR/V 50 pA/√Hz 200 kΩ 12 pF REFERENCE Reference Voltage +1.24 V Reference Tolerance ±10 % Reference Voltage Drift ±50 ppmFSR/ °C Reference Output Current Reference Input Resistance Reference Input Compliance Range Reference Small-Signal Bandwidth 10 µA 1 mΩ 0.1 (4) 1.25 1.3 V MHz DIGITAL INPUTS Logic Coding Straight Binary Latch Command Rising Edge of Clock Logic High Voltage, VIH +VD = +5V Logic Low Voltage, VIL +VD = +5V 3.5 5 Logic High Voltage, VIH +v = +3V Logic Low Voltage, VIL +VD = +3V 0 Logic High Current, IIH (5) +VD = +5V ±20 V Logic Low Current, IIL +VD = +5V ±20 µA 5 pF 0 2 Input Capacitance V 1.2 3 V V 0.8 V POWER SUPPLY Supply Voltages +VA +2.7 +5 +5.5 V +VD +2.7 +5 +5.5 V IVA 24 30 mA IVA, Power-Down Mode 1.1 2 mA 8 15 mA +5V, IOUT = 20mA 170 230 mW +3V, IOUT = 2mA 50 mW Power-Down Mode 45 mW 50 °C/W Supply Current (6) IVD Power Dissipation Thermal Resistance, qJA TSSOP-28 (4) (5) (6) 4 Reference bandwidth depends on size of external capacitor at the BW pin and signal level. Typically 45mA for the PD pin, which has an internal pulldown resistor. Measured at fCLOCK = 50MSPS and fOUT = 1.0MHz. Submit Documentation Feedback Copyright © 2010, Texas Instruments Incorporated Product Folder Link(s): DAC900-Q1 DAC900-Q1 www.ti.com SBAS505 – JUNE 2010 PW PACKAGE (TOP VIEW) Bit 1 1 28 CLK Bit 2 2 27 +VD Bit 3 3 26 DGND Bit 4 4 25 NC Bit 5 5 24 +VA Bit 6 6 23 BYP Bit 7 7 22 IOUT Bit 8 8 21 IOUT Bit 9 9 20 AGND Bit 10 10 19 BW NC 11 18 FSA NC 12 17 REFIN NC 13 16 INT/EXT NC 14 15 PD Submit Documentation Feedback Copyright © 2010, Texas Instruments Incorporated Product Folder Link(s): DAC900-Q1 5 DAC900-Q1 SBAS505 – JUNE 2010 www.ti.com TERMINAL FUNCTIONS TERMINAL 6 DESCRIPTION NO. NAME 1 Bit 1 Data Bit 1 (D9), MSB 2 Bit 2 Data Bit 2 (D8) 3 Bit 3 Data Bit 3 (D7) 4 Bit 4 Data Bit 4 (D6) 5 Bit 5 Data Bit 5 (D5) 6 Bit 6 Data Bit 6 (D4) 7 Bit 7 Data Bit 7 (D3) 8 Bit 8 Data Bit 8 (D2) 9 Bit 9 Data Bit 9 (D1) 10 Bit 10 Data Bit 10 (D0), LSB 11 NC No Connection 12 NC No Connection 13 NC No Connection 14 NC No Connection 15 PD Power Down, Control Input; Active HIGH. Contains internal pull-down circuit; may be left unconnected if not used. 16 INT/EXT 17 REFIN 18 FSA Full-Scale Output Adjust 19 BW Bandwidth/Noise Reduction: Bypass with 0.1mF to +VA for Optimum Performance. 20 AGND 21 IOUT Complementary DAC Current Output 22 IOUT DAC Current Output 23 BYP Bypass Node: Use 0.1mF to AGND 24 +VA Analog Supply Voltage, 2.7V to 5.5V 25 NC No Connection 26 DGND Digital Ground 27 +VD Digital Supply Voltage, 2.7V to 5.5V 28 CLK Clock Input Reference Select Pin; Internal ( = 0) or External ( = 1) Reference Operation. Reference Input/Ouput. See Applications section for further details. Analog Ground Submit Documentation Feedback Copyright © 2010, Texas Instruments Incorporated Product Folder Link(s): DAC900-Q1 DAC900-Q1 www.ti.com SBAS505 – JUNE 2010 Typical Connection Circuit +5V +5V 0.1µF +VA +VD BW DAC900 IOUT FSA Current Sources REFIN BYP Segmented MSB Switches RSET 0.1µF 1:1 IOUT LSB Switches 50Ω 0.1µF 20pF 50Ω 20pF INT/EXT PD Latches +1.24V Ref. 10-Bit Data Input AGND CLK D9.......D0 DGND Timing Diagram t2 t1 CLOCK tS D13 D0 Data Changes tH Stable Valid Data Data Changes tPD tSET Iout or Iout SYMBOL t1 t2 tS tH tPD tSET DESCRIPTION MIN TYP Clock Pulse HIGH Time Clock Pulse LOW Time Data Setup Time Data Hold Time Propagation Delay Time Output Settling Time to 0.1% 3 3 1.5 1 1 30 MAX UNIT ns ns ns ns ns ns Submit Documentation Feedback Copyright © 2010, Texas Instruments Incorporated Product Folder Link(s): DAC900-Q1 7 DAC900-Q1 SBAS505 – JUNE 2010 www.ti.com TYPICAL CHARACTERISTICS: VD = VA = +5V At TA = +25°C, Differential IOUT = 20mA, 50Ω double-terminated load, SFDR up to Nyquist, unless otherwise specified TYPICAL INL 0.75 0.75 0.50 0.50 DAC Code 85 85 80 80 SFDR (dBc) SFDR (dBc) 1000 1024 900 800 SFDR vs fOUT AT 50MSPS 90 –6dBFS 75 70 75 –6dBFS 70 65 0dBFS 65 0dBFS 60 60 55 0 4 2 6 8 Frequency (MHz) 10 12 0 5 SFDR vs fOUT AT 100MSPS 10 15 Frequency (MHz) 20 25 SFDR vs fOUT AT 125MSPS 85 85 80 80 75 75 SFDR (dBc) SFDR (dBc) 700 DAC Code SFDR vs fOUT AT 25MSPS 70 –6dBFS 65 60 55 70 –6dBFS 65 60 55 0dBFS 50 0dBFS 50 45 45 0 10 20 30 40 50 0 Frequency (MHz) 8 600 0 1000 1024 900 600 400 200 800 –1.00 700 –1.00 500 –0.75 300 –0.50 –0.75 100 –0.50 500 –0.25 400 –0.25 0 300 0 0.25 200 0.25 100 Error (LSBs) 1.00 0 Error (LSBs) TYPICAL DNL 1.00 Submit Documentation Feedback 10 20 30 40 Frequency (MHz) 50 60 Copyright © 2010, Texas Instruments Incorporated Product Folder Link(s): DAC900-Q1 DAC900-Q1 www.ti.com SBAS505 – JUNE 2010 TYPICAL CHARACTERISTICS: VD = VA = +5V (continued) At TA = +25°C, Differential IOUT = 20mA, 50Ω double-terminated load, SFDR up to Nyquist, unless otherwise specified SFDR vs fOUT AT 165MSPS SFDR vs fOUT AT 200MSPS 80 80 75 75 70 –6dBFS 65 SFDR (dBc) SFDR (dBc) 70 60 55 65 –6dBFS 60 55 0dBFS 0dBFS 50 50 45 45 40 40 10 0 30 40 50 Frequency (MHz) 20 60 70 80 0 20 30 40 50 60 70 80 90 Frequency (MHz) DIFFERENTIAL vs SINGLE-ENDED SFDR vs fOUT AT 100MSPS SFDR vs IOUTFS and fOUT AT 100MSPS, 0dBFS 85 80 80 70 IOUT (–6dBFS) SFDR (dBc) X 70 Diff (–6dBFS) 65 2.1MHz 75 X 75 SFDR (dBc) 10 X X 60 X X 55 50 * X X 10.1MHz 5.04MHz * * 60 55 40.4MHz X 50 X IOUT (0dBFS) 65 * X 45 Diff (0dBFS) 45 40 0 10 20 30 40 50 2 20 IOUTFS (mA) SFDR vs TEMPERATURE AT 100MSPS, 0dBFS THD vs fCLOCK AT f OUT = 2.1MHz 85 –70 80 –75 2.1MHz 75 –85 SFDR (dBc) 2HD –80 THD (dBc) 10 5 Frequency (MHz) 3HD –90 70 65 10.1MHz 60 55 40.4MHz –95 50 –100 0 25 50 75 100 125 X X 45 –40 fCLOCK (MSPS) X X –20 0 X 25 50 Temperature ( °C) X X 70 85 Submit Documentation Feedback Copyright © 2010, Texas Instruments Incorporated Product Folder Link(s): DAC900-Q1 9 DAC900-Q1 SBAS505 – JUNE 2010 www.ti.com TYPICAL CHARACTERISTICS: VD = VA = +5V (continued) At TA = +25°C, Differential IOUT = 20mA, 50Ω double-terminated load, SFDR up to Nyquist, unless otherwise specified DUAL-TONE OUTPUT SPECTRUM FOUR-TONE OUTPUT SPECTRUM 0 0 –10 –10 fCLOCK = 100MSPS fOUT1 = 13.5MHz fOUT2 = 14.5MHz SFDR = 60dBc Amplitude = 0dBFS –30 –40 –50 fCLOCK = 50MSPS fOUT1 = 6.25MHz fOUT2 = 6.75MHz fOUT3 = 7.25MHz fOUT4 = 7.75MHz SFDR = 66dBc Amplitude = 0dBFS –20 Magnitude (dBm) Magnitude (dBm) –20 –60 –70 –30 –40 –50 –60 –70 –80 –80 –90 –90 –100 –100 0 5 10 15 20 25 30 35 40 45 50 0 Frequency (MHz) 10 5 10 15 20 25 Frequency (MHz) Submit Documentation Feedback Copyright © 2010, Texas Instruments Incorporated Product Folder Link(s): DAC900-Q1 DAC900-Q1 www.ti.com SBAS505 – JUNE 2010 TYPICAL CHARACTERISTICS: VD = VA = +3V At TA = +25°C, Differential IOUT = 20mA, 50Ω double-terminated load, SFDR up to Nyquist, unless otherwise specified SFDR vs fOUT AT 25MSPS SFDR vs fOUT AT 50MSPS 85 85 80 80 75 SFDR (dBc) SFDR (dBc) –6dBFS 70 0dBFS 65 75 –6dBFS 70 65 60 60 55 55 0dBFS 0 4 2 6 8 Frequency (MHz) 10 12 5 0 10 15 20 25 Frequency (MHz) SFDR vs fOUT AT 125MSPS SFDR vs fOUT AT 100MSPS 85 85 80 80 75 75 SFDR (dBc) SFDR (dBc) –6dBFS 70 –6dBFS 65 60 55 70 65 60 0dBFS 55 0dBFS 50 50 45 45 0 10 20 30 40 0 50 10 20 30 40 50 Frequency (MHz) Frequency (MHz) SFDR vs fOUT AT 165MSPS DIFFERENTIAL vs SINGLE-ENDED SFDR vs fOUT AT 100MSPS 80 85 75 80 70 75 60 X 65 SFDR (dBc) SFDR (dBc) X –6dBFS 60 55 Diff (–6dBFS) 70 X 65 X Diff (0dBFS) 60 X 55 50 0dBFS IOUT (0dBFS) 50 45 0 10 20 30 40 50 Frequency (MHz) 60 70 80 X IOUT (–6dBFS) 45 40 X 0 10 20 30 Frequency (MHz) 40 Submit Documentation Feedback Copyright © 2010, Texas Instruments Incorporated Product Folder Link(s): DAC900-Q1 50 11 DAC900-Q1 SBAS505 – JUNE 2010 www.ti.com TYPICAL CHARACTERISTICS: VD = VA = +3V (continued) At TA = +25°C, Differential IOUT = 20mA, 50Ω double-terminated load, SFDR up to Nyquist, unless otherwise specified SFDR vs IOUTFS and fOUT AT 100MSPS 80 THD vs fCLOCK AT f OUT = 2.1MHz –70 2.1MHz 2HD 75 70 X X X X –80 10.1MHz 65 THD (dBc) SFDR (dBc) –75 5.04MHz 60 55 50 * * 3HD –85 –90 40.4MHz * * –95 45 40 –100 2 10 5 0 20 25 50 100 fCLOCK (MSPS) IOUTFS (mA) SFDR vs TEMPERATURE AT 100MSPS, 0dBFS 0 2.1MHz –10 75 fCLOCK = 100MSPS fOUT1 = 13.5MHz fOUT2 = 14.5MHz SFDR = 61.5dBc Amplitude = 0dBFS –20 Magnitude (dBm) 70 SFDR (dBc) 150 DUAL-TONE OUTPUT SPECTRUM 80 10.1MHz 65 60 55 40.4MHz 50 45 125 X X X X X X X –30 –40 –50 –60 –70 –80 –90 40 –100 –40 –20 0 25 50 Temperature (° C) 70 0 85 5 10 15 20 25 30 35 40 45 50 Frequency (MHz) FOUR-TONE OUTPUT SPECTRUM 0 –10 fCLOCK = 50MSPS fOUT1 = 6.25MHz fOUT2 = 6.75MHz fOUT3 = 7.25MHz fOUT4 = 7.75MHz SFDR = 62.5dBc Amplitude = 0dBFS Magnitude (dBm) –20 –30 –40 –50 –60 –70 –80 –90 –100 0 12 5 10 15 Frequency (MHz) Submit Documentation Feedback 20 25 Copyright © 2010, Texas Instruments Incorporated Product Folder Link(s): DAC900-Q1 DAC900-Q1 www.ti.com SBAS505 – JUNE 2010 APPLICATION INFORMATION Theory of Operation The architecture of the DAC900 uses the current steering technique to enable fast switching and a high update rate. The core element within the monolithic DAC is an array of segmented current sources, which are designed to deliver a full-scale output current of up to 20mA, as shown in Figure 1. An internal decoder addresses the differential current switches each time the DAC is updated and a corresponding output current is formed by steering all currents to either output summing node, IOUT or IOUT. The complementary outputs deliver a differential output signal that improves the dynamic performance through reduction of even-order harmonics, common-mode signals (noise), and double the peak-to-peak output signal swing by a factor of two, compared to singleended operation. +3V to +5V Digital +3V to +5V Analog 0.1µF Bandwidth Control +VA DAC900 RSET 2kΩ BW +VD IOUT Full-Scale Adjust Resistor FSA Ref Control Amp Ref Input REFIN 400pF 0.1µF PMOS Current Source Array LSB Switches 1:1 VOUT IOUT Segmented MSB Switches 50Ω 0.1µF 20pF 50Ω 20pF BYP INT/EXT Ref Buffer Latches and Switch Decoder Logic PD Power Down (internal pull-down) +1.24V Ref AGND Analog Ground CLK Clock Input 10-Bit Data Input DGND D9...D0 Digital Ground NOTE: Supply bypassing not shown. Figure 1. Functional Block Diagram The segmented architecture results in a significant reduction of the glitch energy, and improves the dynamic performance (SFDR) and DNL. The current outputs maintain a very high output impedance of greater than 200kΩ. The full-scale output current is determined by the ratio of the internal reference voltage (1.24V) and an external resistor, RSET. The resulting IREF is internally multiplied by a factor of 32 to produce an effective DAC output current that can range from 2mA to 20mA, depending on the value of RSET. The DAC900 is split into a digital and an analog portion, each of which is powered through its own supply pin. The digital section includes edge-triggered input latches and the decoder logic, while the analog section comprises the current source array with its associated switches and the reference circuitry. Submit Documentation Feedback Copyright © 2010, Texas Instruments Incorporated Product Folder Link(s): DAC900-Q1 13 DAC900-Q1 SBAS505 – JUNE 2010 www.ti.com DAC Transfer Function The total output current, IOUTFS, of the DAC900 is the summation of the two complementary output currents: IOUTFS = IOUT + I OUT (1) The individual output currents depend on the DAC code and can be expressed as: IOUT = IOUTFS × Code 1024 (2) Code ö æ I = IOUTFS × ç 1023 – ÷ OUT 1024 ø è (3) Where, Code is the decimal representation of the DAC data input word. Additionally, IOUTFS is a function of the reference current IREF, which is determined by the reference voltage and the external setting resistor, RSET. IOUTFS = 32 × IREF = 32 × VREF RSET (4) In most cases the complementary outputs will drive resistive loads or a terminated transformer. A signal voltage will develop at each output according to: VOUT = IOUT × RLOAD V OUT =I OUT (5) × RLOAD (6) The value of the load resistance is limited by the output compliance specification of the DAC900. To maintain specified linearity performance, the voltage for IOUT and IOUT should not exceed the maximum allowable compliance range. The two single-ended output voltages can be combined to find the total differential output swing: VOUTDIFF = VOUT – V OUT = 2 × Code – 1023 × IOUTFS × RLOAD 1024 (7) Analog Outputs The DAC900 provides two complementary current outputs, IOUT and IOUT. The simplified circuit of the analog output stage representing the differential topology is shown in Figure 2. The output impedance of 200kΩ || 12pF for IOUT and IOUT results from the parallel combination of the differential switches, along with the current sources and associated parasitic capacitances. +VA DAC900 IOUT IOUT RL RL Figure 2. Equivalent Analog Output The signal voltage swing that may develop at the two outputs, IOUT and IOUT, is limited by a negative and positive compliance. The negative limit of –1V is given by the breakdown voltage of the CMOS process, and exceeding it 14 Submit Documentation Feedback Copyright © 2010, Texas Instruments Incorporated Product Folder Link(s): DAC900-Q1 DAC900-Q1 www.ti.com SBAS505 – JUNE 2010 will compromise the reliability of the DAC900, or even cause permanent damage. With the full-scale output set to 20mA, the positive compliance equals 1.25V, operating with +VD = 5V. Note that the compliance range decreases to about 1V for a selected output current of IOUTFS = 2mA. Care should be taken that the configuration of DAC900 does not exceed the compliance range to avoid degradation of the distortion performance and integral linearity. Best distortion performance is typically achieved with the maximum full-scale output signal limited to approximately 0.5V. This is the case for a 50Ω doubly-terminated load and a 20mA full-scale output current. A variety of loads can be adapted to the output of the DAC900 by selecting a suitable transformer while maintaining optimum voltage levels at IOUT and IOUT. Furthermore, using the differential output configuration in combination with a transformer will be instrumental for achieving excellent distortion performance. Common-mode errors, such as even-order harmonics or noise, can be substantially reduced. This is particularly the case with high output frequencies and/or output amplitudes below full-scale. For those applications requiring the optimum distortion and noise performance, it is recommended to select a full-scale output of 20mA. A lower full-scale range down to 2mA may be considered for applications that require a low power consumption, but can tolerate a reduced performance level. Table 1. Input Coding vs Analog Output Current INPUT CODE (D9 - D0) IOUT IOUT 11 1111 1111 20mA 0mA 10 0000 0000 10mA 10mA 00 0000 0000 0mA 20mA Output Configurations The current output of the DAC900 allows for a variety of configurations, some of which are illustrated in the following sections. As mentioned previously, utilizing the converter's differential outputs will yield the best dynamic performance. Such a differential output circuit may consist of an RF transformer (see Figure 3) or a differential amplifier configuration (see Figure 4). The transformer configuration is ideal for most applications with ac coupling, while op amps will be suitable for a DC-coupled configuration. The single-ended configuration (see Figure 6) may be considered for applications requiring a unipolar output voltage. Connecting a resistor from either one of the outputs to ground will convert the output current into a ground-referenced voltage signal. To improve on the DC linearity, an I-to-V converter can be used instead. This will result in a negative signal excursion and, therefore, requires a dual supply amplifier. Differential With Transformer Using an RF transformer provides a convenient way of converting the differential output signal into a single-ended signal while achieving excellent dynamic performance (see Figure 3). The appropriate transformer should be carefully selected based on the output frequency spectrum and impedance requirements. The differential transformer configuration has the benefit of significantly reducing common-mode signals, thus improving the dynamic performance over a wide range of frequencies. Furthermore, by selecting a suitable impedance ratio (winding ratio), the transformer can be used to provide optimum impedance matching while controlling the compliance voltage for the converter outputs. The model shown in Figure 3 has a 1:1 ratio and may be used to interface the DAC900 to a 50Ω load. This results in a 25Ω load for each of the outputs, IOUT and IOUT. The output signals are ac coupled and inherently isolated because of the transformer's magnetic coupling. As shown in Figure 3, the transformer's center tap is connected to ground. This forces the voltage swing on IOUT and IOUT to be centered at 0V. In this case the two resistors, RS, may be replaced with one, RDIFF, or omitted altogether. This approach should only be used if all components are close to each other, and if the VSWR is not important. A complete power transfer from the DAC output to the load can be realized, but the output compliance range should be observed. Alternatively, if the center tap is not connected, the signal swing will be centered at RS × IOUTFS / 2. However, in this case, the two resistors (RS) must be used to enable the necessary DC-current flow for both outputs. Submit Documentation Feedback Copyright © 2010, Texas Instruments Incorporated Product Folder Link(s): DAC900-Q1 15 DAC900-Q1 SBAS505 – JUNE 2010 www.ti.com ADT1-1WT (Mini-Circuits) 1:1 IOUT RS 50Ω Optional RDIFF DAC900 RL IOUT RS 50Ω Figure 3. Differential Output Configuration Using an RF Transformer Differential Configuration Using an Op Amp If the application requires a DC-coupled output, a difference amplifier may be considered, as shown in Figure 4. Four external resistors are needed to configure the voltage-feedback op amp OPA680 as a difference amplifier performing the differential to single-ended conversion. Under the shown configuration, the DAC900 generates a differential output signal of 0.5Vp-p at the load resistors, RL. The resistor values shown were selected to result in a symmetric 25Ω loading for each of the current outputs since the input impedance of the difference amplifier is in parallel to resistors RL, and should be considered. R2 402Ω R1 200Ω IOUT DAC900 IOUT OPA680 CDIFF RL 26.1Ω R3 200Ω RL 28.7Ω VOUT –5V +5V R4 402Ω Figure 4. Difference Amplifier Provides Differential to Single-Ended Conversion and DC-Coupling The OPA680 is configured for a gain of two. Therefore, operating the DAC900 with a 20mA full-scale output will produce a voltage output of ±1V. This requires the amplifier to operate off of a dual power supply (±5V). The tolerance of the resistors typically sets the limit for the achievable common-mode rejection. An improvement can be obtained by fine tuning resistor R4. This configuration typically delivers a lower level of ac performance than the previously discussed transformer solution because the amplifier introduces another source of distortion. Suitable amplifiers should be selected based on their slew-rate, harmonic distortion, and output swing capabilities. High-speed amplifiers like the OPA680 or OPA687 may be considered. The ac performance of this circuit may be improved by adding a small capacitor, CDIFF, between the outputs IOUT and IOUT, as shown in Figure 4. This will introduce a real pole to create a low-pass filter in order to slewlimit the DACs fast output signal steps that otherwise could drive the amplifier into slew-limitations or into an overload condition; both would cause excessive distortion. The difference amplifier can easily be modified to add a level shift for applications requiring the single-ended output voltage to be unipolar, i.e., swing between 0V and +2V. 16 Submit Documentation Feedback Copyright © 2010, Texas Instruments Incorporated Product Folder Link(s): DAC900-Q1 DAC900-Q1 www.ti.com SBAS505 – JUNE 2010 Dual Transimpedance Output Configuration The circuit example of Figure 5 shows the signal output currents connected into the summing junction of the OPA2680, which is set up as a transimpedance stage, or I-to-V converter. With this circuit, the DAC's output will be kept at a virtual ground, minimizing the effects of output impedance variations, and resulting in the best DC linearity (INL). However, as mentioned previously, the amplifier may be driven into slew-rate limitations, and produce unwanted distortion. This may occur especially at high DAC update rates. +5V 50Ω 1/2 OPA2680 RF1 DAC900 IOUT –VOUT = IOUT • RF CD1 CF1 RF2 CD2 IOUT CF2 1/2 OPA2680 –VOUT = IOUT • RF 50Ω –5V Figure 5. Dual Voltage-Feedback Amplifier OPA2680 Forms Differential Transimpedance Amplifier The DC gain for this circuit is equal to feedback resistor RF. At high frequencies, the DAC output impedance (CD1, CD2) will produce a zero in the noise gain for the OPA2680 that may cause peaking in the closed-loop frequency response. CF is added across RF to compensate for this noise-gain peaking. To achieve a flat transimpedance frequency response, the pole in each feedback network should be set to: 1 GBP = 2p RFCF 4p RFCD (8) Where, GBP = Gain Bandwidth Product of OPA This gives a corner frequency f-3dB of approximately: f-3dB = GBP 2p RFCD (9) The full-scale output voltage is defined by the product of IOUTFS × RF, and has a negative unipolar excursion. To improve on the ac performance of this circuit, adjustment of RF and/or IOUTFS should be considered. Further extensions of this application example may include adding a differential filter at the OPA2680's output followed by a transformer, in order to convert to a single-ended signal. Submit Documentation Feedback Copyright © 2010, Texas Instruments Incorporated Product Folder Link(s): DAC900-Q1 17 DAC900-Q1 SBAS505 – JUNE 2010 www.ti.com Single-Ended Configuration Using a single load resistor connected to the one of the DAC outputs, a simple current-to-voltage conversion can be accomplished. The circuit in Figure 6 shows a 50Ω resistor connected to IOUT, providing the termination of the further connected 50Ω cable. Therefore, with a nominal output current of 20mA, the DAC produces a total signal swing of 0V to 0.5V into the 25Ω load. IOUTFS = 20mA VOUT = 0V to +0.5V IOUT DAC900 50Ω IOUT 50Ω 25Ω Figure 6. Driving a Doubly-Terminated 50Ω Cable Directly Different load resistor values may be selected as long as the output compliance range is not exceeded. Additionally, the output current, IOUTFS, and the load resistor may be mutually adjusted to provide the desired output signal swing and performance. 18 Submit Documentation Feedback Copyright © 2010, Texas Instruments Incorporated Product Folder Link(s): DAC900-Q1 DAC900-Q1 www.ti.com SBAS505 – JUNE 2010 Internal Reference Operation The DAC900 has an on-chip reference circuit that comprises a 1.24V bandgap reference and a control amplifier. Grounding pin 16, INT/EXT, enables the internal reference operation. The full-scale output current, IOUTFS, of the DAC900 is determined by the reference voltage, VREF, and the value of resistor RSET. IOUTFS can be calculated by: IOUTFS = 32 × IREF = 32 × VREF RSET (10) As shown in Figure 7, the external resistor RSET connects to the FSA pin (Full-Scale Adjust). The reference control amplifier operates as a V-to-I converter producing a reference current, IREF, which is determined by the ratio of VREF and RSET, as shown in Equation 10. The full-scale output current, IOUTFS, results from multiplying IREF by a fixed factor of 32. CCOMPEXT +5V 0.1µF BW DAC900 IREF = +VA VREF RSET FSA REFIN RSET 2kΩ Ref Control Amp Current Sources CCOMP 400pF 0.1µF INT/EXT +1.24V Ref. Figure 7. Internal Reference Configuration Using the internal reference, a 2kΩ resistor value results in a 20mA full-scale output. Resistors with a tolerance of 1% or better should be considered. Selecting higher values, the converter output can be adjusted from 20mA down to 2mA. Operating the DAC900 at lower than 20mA output currents may be desirable for reasons of reducing the total power consumption, improving the distortion performance, or observing the output compliance voltage limitations for a given load condition. It is recommended to bypass the REFIN pin with a ceramic chip capacitor of 0.1mF or more. The control amplifier is internally compensated, and its small signal bandwidth is approximately 1.3MHz. To improve the ac performance, an additional capacitor (CCOMPEXT) should be applied between the BW pin and the analog supply, +VA, as shown in Figure 7. Using a 0.1mF capacitor, the small-signal bandwidth and output impedance of the control amplifier is further diminished, reducing the noise that is fed into the current source array. This also helps shunting feedthrough signals more effectively, and improving the noise performance of the DAC900. Submit Documentation Feedback Copyright © 2010, Texas Instruments Incorporated Product Folder Link(s): DAC900-Q1 19 DAC900-Q1 SBAS505 – JUNE 2010 www.ti.com External Reference Operation The internal reference can be disabled by applying a logic HIGH (+VA) to pin INT/EXT. An external reference voltage can then be driven into the REFIN pin, which in this case functions as an input, as shown in Figure 8. The use of an external reference may be considered for applications that require higher accuracy and drift performance, or to add the ability of dynamic gain control. While a 0.1mF capacitor is recommended to be used with the internal reference, it is optional for the external reference operation. The reference input, REFIN, has a high input impedance (1MΩ) and can easily be driven by various sources. Note that the voltage range of the external reference should stay within the compliance range of the reference input (0.1V to 1.25V). CCOMPEXT +5V 0.1µF IREF = +VA BW DAC900 VREF RSET FSA REFIN External Reference Ref Control Amp Current Sources CCOMP 400pF RSET +5V INT/EXT +1.24V Ref. Figure 8. External Reference Configuration Digital Inputs The digital inputs, D0 (LSB) through D9 (MSB) of the DAC900 accepts standard-positive binary coding. The digital input word is latched into a master-slave latch with the rising edge of the clock. The DAC output becomes updated with the following falling clock edge (refer to the specification table and timing diagram for details). The best performance will be achieved with a 50% clock duty cycle, however, the duty cycle may vary as long as the timing specifications are met. Additionally, the setup and hold times may be chosen within their specified limits. All digital inputs are CMOS compatible. The logic thresholds depend on the applied digital supply voltage such that they are set to approximately half the supply voltage; Vth = +VD/2 (±20% tolerance). The DAC900 is designed to operate over a supply range of 2.7V to 5.5V. Power-Down Mode The DAC900 features a power-down function that can be used to reduce the supply current to less than 9mA over the specified supply range of 2.7V to 5.5V. Applying a logic HIGH to the PD pin will initiate the power-down mode, while a logic LOW enables normal operation. When left unconnected, an internal active pull-down circuit will enable the normal operation of the converter. 20 Submit Documentation Feedback Copyright © 2010, Texas Instruments Incorporated Product Folder Link(s): DAC900-Q1 DAC900-Q1 www.ti.com SBAS505 – JUNE 2010 Grounding, Decoupling, and Layout Information Proper grounding and bypassing, short lead length, and the use of ground planes are particularly important for high frequency designs. Multilayer pc-boards are recommended for best performance since they offer distinct advantages such as minimization of ground impedance, separation of signal layers by ground layers, etc. The DAC900 uses separate pins for its analog and digital supply and ground connections. The placement of the decoupling capacitor should be such that the analog supply (+VA) is bypassed to the analog ground (AGND), and the digital supply bypassed to the digital ground (DGND). In most cases 0.1uF ceramic chip capacitors at each supply pin are adequate to provide a low impedance decoupling path. Keep in mind that their effectiveness largely depends on the proximity to the individual supply and ground pins. Therefore, they should be located as close as physically possible to those device leads. Whenever possible, the capacitors should be located immediately under each pair of supply/ ground pins on the reverse side of the pc-board. This layout approach will minimize the parasitic inductance of component leads and pcb runs. Further supply decoupling with surface mount tantalum capacitors (1µF to 4.7µF) may be added as needed in proximity of the converter. Low noise is required for all supply and ground connections to the DAC900. It is recommended to use a multilayer pcboard utilizing separate power and ground planes. Mixed signal designs require particular attention to the routing of the different supply currents and signal traces. Generally, analog supply and ground planes should only extend into analog signal areas, such as the DAC output signal and the reference signal. Digital supply and ground planes must be confined to areas covering digital circuitry, including the digital input lines connecting to the converter, as well as the clock signal. The analog and digital ground planes should be joined together at one point underneath the DAC. This can be realized with a short track of approximately 1/8" (3mm). The power to the DAC900 should be provided through the use of wide pcb runs or planes. Wide runs will present a lower trace impedance, further optimizing the supply decoupling. The analog and digital supplies for the converter should only be connected together at the supply connector of the pc-board. In the case of only one supply voltage being available to power the DAC, ferrite beads along with bypass capacitors may be used to create an LC filter. This will generate a low-noise analog supply voltage that can then be connected to the +VA supply pin of the DAC900. While designing the layout, it is important to keep the analog signal traces separate from any digital line, in order to prevent noise coupling onto the analog signal path. Submit Documentation Feedback Copyright © 2010, Texas Instruments Incorporated Product Folder Link(s): DAC900-Q1 21 PACKAGE OPTION ADDENDUM www.ti.com 30-Jul-2011 PACKAGING INFORMATION Orderable Device DAC900TPWRQ1 Status (1) Package Type Package Drawing ACTIVE TSSOP PW Pins Package Qty 28 2500 Eco Plan (2) Green (RoHS & no Sb/Br) Lead/ Ball Finish MSL Peak Temp (3) Samples (Requires Login) CU NIPDAU Level-2-260C-1 YEAR (1) The marketing status values are defined as follows: ACTIVE: Product device recommended for new designs. LIFEBUY: TI has announced that the device will be discontinued, and a lifetime-buy period is in effect. NRND: Not recommended for new designs. Device is in production to support existing customers, but TI does not recommend using this part in a new design. PREVIEW: Device has been announced but is not in production. Samples may or may not be available. OBSOLETE: TI has discontinued the production of the device. (2) Eco Plan - The planned eco-friendly classification: Pb-Free (RoHS), Pb-Free (RoHS Exempt), or Green (RoHS & no Sb/Br) - please check http://www.ti.com/productcontent for the latest availability information and additional product content details. TBD: The Pb-Free/Green conversion plan has not been defined. Pb-Free (RoHS): TI's terms "Lead-Free" or "Pb-Free" mean semiconductor products that are compatible with the current RoHS requirements for all 6 substances, including the requirement that lead not exceed 0.1% by weight in homogeneous materials. Where designed to be soldered at high temperatures, TI Pb-Free products are suitable for use in specified lead-free processes. Pb-Free (RoHS Exempt): This component has a RoHS exemption for either 1) lead-based flip-chip solder bumps used between the die and package, or 2) lead-based die adhesive used between the die and leadframe. The component is otherwise considered Pb-Free (RoHS compatible) as defined above. Green (RoHS & no Sb/Br): TI defines "Green" to mean Pb-Free (RoHS compatible), and free of Bromine (Br) and Antimony (Sb) based flame retardants (Br or Sb do not exceed 0.1% by weight in homogeneous material) (3) MSL, Peak Temp. -- The Moisture Sensitivity Level rating according to the JEDEC industry standard classifications, and peak solder temperature. Important Information and Disclaimer:The information provided on this page represents TI's knowledge and belief as of the date that it is provided. TI bases its knowledge and belief on information provided by third parties, and makes no representation or warranty as to the accuracy of such information. Efforts are underway to better integrate information from third parties. TI has taken and continues to take reasonable steps to provide representative and accurate information but may not have conducted destructive testing or chemical analysis on incoming materials and chemicals. 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OTHER QUALIFIED VERSIONS OF DAC900-Q1 : • Catalog: DAC900 NOTE: Qualified Version Definitions: • Catalog - TI's standard catalog product Addendum-Page 1 PACKAGE MATERIALS INFORMATION www.ti.com 14-Jul-2012 TAPE AND REEL INFORMATION *All dimensions are nominal Device DAC900TPWRQ1 Package Package Pins Type Drawing TSSOP PW 28 SPQ Reel Reel A0 Diameter Width (mm) (mm) W1 (mm) 2500 330.0 16.4 Pack Materials-Page 1 6.9 B0 (mm) K0 (mm) P1 (mm) W Pin1 (mm) Quadrant 10.2 1.8 12.0 16.0 Q1 PACKAGE MATERIALS INFORMATION www.ti.com 14-Jul-2012 *All dimensions are nominal Device Package Type Package Drawing Pins SPQ Length (mm) Width (mm) Height (mm) DAC900TPWRQ1 TSSOP PW 28 2500 367.0 367.0 38.0 Pack Materials-Page 2 IMPORTANT NOTICE Texas Instruments Incorporated and its subsidiaries (TI) reserve the right to make corrections, enhancements, improvements and other changes to its semiconductor products and services per JESD46C and to discontinue any product or service per JESD48B. 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