AGILENT MGA

Agilent MGA-53543
50 MHz to 6 GHz
High Linear Amplifier
Data Sheet
Features
• Lead-free Option Available
• Very high linearity at low DC bias
power[1]
• Low noise figure
Description
Agilent Technologies’s MGA-53543
is a high dynamic range low noise
amplifier MMIC housed in a 4-lead
SC-70 (SOT-343) surface mount
plastic package.
MGA-53543 is especially ideal for
Cellular/PCS/ W-CDMA
basestation applications. With
high IP3 and low noise figure, the
MGA-53543 may be utilized as a
driver amplifier in the transmit
chain and as a second stage LNA
in the receive chain.
Attention:
Observe precautions for
handling electrostatic
sensitive devices.
Surface Mount Package
SOT-343/4-lead SC70
• Tape-and-Reel packaging option
available
Pin Connections and
Package Marking
Specifications
1.9 GHz, 5V, 54 mA (typ)
• OIP3: 39 dBm
INPUT
3
GND
4
1
GND
2
OUTPUT
& Vd
Note:
Top View. Package marking provides orientation
and identification.
“53” = Device Code
“x” = Date code character identifies month of
manufacture.
Simplified Schematic
ESD Machine Model (Class A)
ESD Human Body Model (Class 1A)
bias
Refer to Agilent Application Note A004R:
Electrostatic Discharge Damage and Control.
• Excellent uniformity in product
specifications
• Low cost surface mount small
plastic package SOT-343 (4-lead
SC-70)
53x
The combination of high linearity, low noise figure and high gain
makes the MGA-53543 ideal for
cellular/PCS/ W-CDMA base
stations, Wireless LAN, WLL and
other systems in the 50 MHz to
6 GHz frequency range.
• Advanced enhancement mode
PHEMT technology
• Noise figure: 1.5 dB
• Gain: 15.4 dB
• P-1dB: 18.6 dBm
Applications
• Base station radio card
• High linearity LNA for base
stations, WLL, WLAN, and other
applications in the 50 MHz
to 6 GHz range
Note:
1. The MGA-53543 has a superior LFOM of
15 dB. Linearity Figure of Merit (LFOM) is
essentially OIP3 divided by DC bias power.
There are few devices in the market that can
match its combination of high linearity and
low noise figure at the low DC bias power of
5V/54 mA.
MGA-53543 Absolute Maximum Ratings [1]
Symbol
Parameter
Units
Absolute Maximum
Vin
Maximum Input Voltage
V
0.8
Vd
Supply Voltage
V
5.5
Pd
Power Dissipation [2]
mW
400
Pin
CW RF Input Power
dBm
13
θjc
Thermal Resistance [3]
°C/W
130
Tj
Junction Temperature
°C
150
TSTG
Storage Temperature
°C
-65 to 150
Notes:
1. Operation of this device in excess of any of
these limits may cause permanent damage.
2. Source lead temperature is 25°C. Derate
7.7mW/°C for TL > 98°C
3. Thermal resistance measured using 150°C
Liquid Crystal Measurement Technique.
Electrical Specifications
Tc = +25°C, Zo = 50 Ω, Vd = 5V, unless noted
Symbol
Parameter and Test Condition
Frequency
Units
Min.
Typ.
Max.
σ [3]
Id
Current Drawn
N/A
mA
40
54
70
2.7
NF [1]
Noise Figure
2.4 GHz
1.9 GHz
0.9 GHz
dB
1.9
1.5
1.3
1.9
0.06
2.4 GHz
1.9 GHz
0.9 GHz
dB
14
15.1
15.4
17.4
17.0
0.25
2.4 GHz
1.9 GHz
0.9 GHz
dBm
36
38.7
39.1
39.7
2.4 GHz
1.9 GHz
0.9 GHz
dBm
18.3
18.6
19.3
Gain [1]
OIP3 [1,2]
P1dB [1]
Gain
Output Third Order Intercept Point
Output Power at 1 dB Gain Compression
PAE [1]
Power Added Effciency at P1dB
1.9 GHz
0.9 GHz
%
%
29.7
28.3
RLin[1]
Input Return Loss
2.4 GHz
1.9 GHz
0.9 GHz
dB
-12.7
-13.2
-11.1
2.4 GHz
1.9 GHz
0.9 GHz
dB
-25.1
-14.3
-14.4
RLout [1]
ISOL [1]
Output Return Loss
Isolation |s12|2
1.9 GHz
0.9 GHz
dB
1.89
-23.4
-22.3
Notes:
1. Measurements obtained from a test circuit described in Figure 1. Input and output tuners tuned for maximum OIP3 while keeping VSWR better than 2:1.
Data corrected for board losses.
2. I) Output power level and frequency of two fundamental tones at 1.9 GHz: F1 = 5.49 dBm, F2 = 5.49 dBm, F1 = 1.905 GHz, and F2 = 1.915 GHz.
II) Output power level and frequency of two fundamental tones at 900 MHz: F1 = -0.38 dBm, F2 = -0.38 dBm, F1 = 905 MHz, and F2 = 915 MHz.
3. Standard deviation data are based on at least 500 pieces sample size taken from 8 wafer lots. Future wafers allocated to this product may have nominal
values anywhere between the upper and lower spec limits.
Input Gamma &
Transmission Line
ΓSource = 0.38 ∠ 156°
(0.7 dBm Loss)
Vd
53x
RF
Input
Figure 1. Block Diagram of 1.9 GHz Test Fixture.
2
Output Gamma &
Transmission Line with
Bias Tee
ΓLoad = 0.05 ∠ 45°
(0.85 dBm Loss)
RF
Output
MGA-53543 Typical Performance
All data measured at Tc = 25°C, Vd = 5 V with input and output tuners tuned for maximum OIP3 while keeping
VSWR better than 2:1 unless stated otherwise.
45
45
-40°C
+25°C
+85°C
40
35
30
-40°C
+25°C
+85°C
20
P1dB (dBm)
OIP3 (dBm)
OIP3 (dBm)
40
24
35
30
16
12
25
25
20
20
0
1
2
3
4
5
6
8
-5
7
-1
3
7
11
0
15
Figure 2. Output Third Order Intercept Point
vs. Frequency and Temperature.
S11 & S22 (dB)
Fmin (dB)
|S21|2 (dB)
2.8
10
1.8
5
5
0.8
6
0
1
2
3
4
5
6
FREQUENCY (GHz)
Figure 5. |S21|2 vs. Frequency and
Temperature.
60
-21
Id (mA)
ISOLATION (dB)
50
-23
-25
40
30
20
-27
-40°C
+25°C
+85°C
10
0
-29
2
3
4
FREQUENCY (GHz)
Figure 8. Isolation vs. Frequency.
3
5
6
-15
0
1
2
3
4
-25
0
1
2
3
4
5
6
Figure 7. S11 and S22 (50Ω) vs. Frequency.
70
S12
-10
FREQUENCY (GHz)
Figure 6. Fmin vs. Frequency and
Temperature.
-19
1
7
S22
S11
FREQUENCY (GHz)
0
6
-20
-40°C
+25°C
+85°C
4
5
-5
15
3
4
0
-40°C
+25°C
+85°C
2
3
Figure 4. Output Power at 1dB Compression
vs. Frequency and Temperature.
3.8
1
2
FREQUENCY (GHz)
Figure 3. Output Third Order Intercept Point
vs. Output Power at 2 GHz.
20
0
1
Pout (dBm)
FREQUENCY (GHz)
5
6
Vd (V)
Figure 9. Current vs. Voltage and Temperature.
MGA-53543 Typical Scattering Parameters
TC = 25°C, Vd = 5.0V, Id = 54 mA, ZO = 50 Ω, (in ICM test fixture)
Freq
(GHz)
S11
Mag.
S11
Ang.
S21
dB
S21
Mag.
S21
Ang.
S12
dB
S12
Mag.
S12
Ang.
S22
Mag.
S22
Ang.
K
0.05
0.1
0.2
0.3
0.4
0.5
0.6
0.7
0.8
0.9
1.0
1.1
1.2
1.3
1.4
1.5
1.6
1.7
1.8
1.9
2.0
2.1
2.2
2.3
2.4
2.5
3.0
3.5
4.0
4.5
5.0
5.5
6.0
6.5
7.0
7.5
8.0
8.5
9.0
9.5
10.0
0.823
0.641
0.439
0.349
0.305
0.251
0.233
0.22
0.212
0.207
0.201
0.198
0.196
0.194
0.195
0.197
0.199
0.201
0.205
0.212
0.216
0.221
0.229
0.235
0.241
0.25
0.293
0.342
0.394
0.445
0.497
0.534
0.565
0.595
0.615
0.635
0.662
0.682
0.715
0.752
0.754
-38.8
-66.7
-98.7
-116.8
-128.9
-135.6
-142.5
-147.5
-151.1
-153.6
-155.3
-157.3
-158.2
-158.4
-159.4
-160
-160.1
-160.5
-161.5
-162.6
-163.1
-164.8
-166.1
-167.2
-169.2
-171.4
176.8
162.2
148.2
133.9
121.6
109.9
99.5
88.2
77.5
65.2
53.9
43.4
32.3
24.9
16
26.26
24.39
21.55
20.14
19.39
18.92
18.6
18.34
18.12
17.9
17.7
17.51
17.31
17.1
16.9
16.7
16.48
16.26
16.04
15.82
15.59
15.36
15.14
14.9
14.67
14.43
13.28
12.13
10.99
9.84
8.7
7.56
6.46
5.38
4.31
3.3
2.29
1.37
0.45
-0.31
-1.12
20.56
16.584
11.954
10.165
9.317
8.826
8.509
8.261
8.053
7.854
7.674
7.505
7.335
7.165
7
6.836
6.666
6.498
6.341
6.179
6.017
5.862
5.714
5.56
5.412
5.265
4.611
4.039
3.544
3.105
2.721
2.388
2.105
1.857
1.643
1.462
1.301
1.171
1.053
0.965
0.879
161.3
148.9
142.7
141.8
140.7
139.3
136.7
133.6
130.2
126.7
123
119.2
115.4
111.6
107.7
103.9
100.1
96.3
92.6
88.9
85.3
81.7
78.3
74.7
71.2
67.8
51.5
36.2
21.6
7.8
-5.2
-17.5
-28.8
-39.6
-49.8
-59.6
-68.8
-77.6
-86
-93.5
-101.7
-27.96
-24.29
-22.50
-22.05
-21.94
-21.83
-21.72
-21.72
-21.72
-21.62
-21.62
-21.62
-21.62
-21.62
-21.62
-21.62
-21.72
-21.72
-21.72
-21.83
-21.83
-21.94
-21.94
-22.05
-22.16
-22.16
-22.50
-22.73
-22.62
-22.27
-21.51
-20.72
-19.83
-18.94
-18.27
-17.72
-17.27
-16.77
-16.31
-15.86
-15.55
0.04
0.061
0.075
0.079
0.08
0.081
0.082
0.082
0.082
0.083
0.083
0.083
0.083
0.083
0.083
0.083
0.082
0.082
0.082
0.081
0.081
0.08
0.08
0.079
0.078
0.078
0.075
0.073
0.074
0.077
0.084
0.092
0.102
0.113
0.122
0.13
0.137
0.145
0.153
0.161
0.167
59.7
40.6
22.9
15.4
11.2
9
7
5.4
4
2.8
1.7
0.7
-0.2
-1.1
-2
-2.8
-3.6
-4.3
-4.9
-5.6
-6.2
-6.7
-7.3
-7.6
-7.9
-8.2
-8.6
-7.3
-5.3
-3.4
-2.7
-3.5
-5.9
-10.4
-16
-22.1
-28.2
-34.2
-40.9
-47.5
-55.3
0.72
0.558
0.344
0.235
0.176
0.097
0.087
0.094
0.11
0.129
0.148
0.169
0.186
0.203
0.219
0.235
0.248
0.261
0.273
0.283
0.293
0.301
0.31
0.316
0.322
0.327
0.338
0.333
0.313
0.287
0.256
0.229
0.204
0.185
0.162
0.127
0.084
0.033
0.028
0.081
0.129
-33
-61.5
-95.3
-118.3
-138.2
-167.4
159.7
131.8
110.7
95.4
84.1
74.8
66.6
59.6
53.1
47.6
42.2
37.1
32.4
28
23.8
19.8
16
12.3
8.8
5.5
-9.4
-22.6
-34.9
-48
-62.1
-77.8
-94.1
-108.7
-120.2
-128.8
-132.9
-145.4
57.9
51.3
50.1
0.3
0.4
0.7
0.9
0.9
1
1
1.1
1.1
1.1
1.1
1.1
1.1
1.1
1.1
1.1
1.1
1.1
1.1
1.2
1.2
1.2
1.2
1.2
1.3
1.3
1.4
1.5
1.6
1.6
1.6
1.6
1.5
1.5
1.5
1.6
1.6
1.6
1.6
1.5
1.6
4
MGA-53543 Typical Noise Parameters
TC = 25°C, Vd = 5.0V, Id = 54 mA, ZO = 50 Ω, (in ICM test fixture)
Freq
(GHz)
Fmin
(dB)
Γopt
Mag
Γopt
Ang
Rn/Zo
Ga
(dB)
0.5
0.8
0.9
1.0
1.1
1.5
1.8
1.9
2.0
2.1
2.2
2.3
2.4
2.5
3.0
3.5
3.8
3.9
4.0
4.5
5.0
5.5
5.7
5.8
5.9
6.0
6.5
7.0
7.5
8.0
8.5
9.0
9.5
10.0
1.07
1.11
1.12
1.14
1.14
1.22
1.3
1.31
1.34
1.36
1.35
1.4
1.44
1.49
1.59
1.64
1.71
1.74
1.76
1.96
2.11
2.38
2.49
2.51
2.54
2.61
2.81
3.14
3.48
3.81
4.07
4.16
4.18
4.62
0.108
0.144
0.159
0.171
0.213
0.238
0.223
0.229
0.237
0.243
0.254
0.255
0.264
0.272
0.298
0.369
0.4
0.41
0.417
0.469
0.521
0.555
0.563
0.568
0.583
0.579
0.613
0.63
0.652
0.673
0.694
0.741
0.778
0.771
156.5
173.2
175.3
173.9
166.3
-179
-175.2
-172
-169.3
-167.3
-165
-163.2
-159.9
-158
-142.3
-131.2
-123.8
-123
-120.2
-108
-99.4
-90.1
-87.3
-84.3
-82.7
-81.7
-72.1
-63.1
-52
-42
-32.5
-22.7
-16.7
-8.9
0.1
0.09
0.09
0.09
0.08
0.08
0.09
0.09
0.09
0.09
0.09
0.09
0.09
0.1
0.12
0.13
0.16
0.17
0.18
0.26
0.35
0.49
0.56
0.6
0.64
0.66
0.9
1.17
1.56
2.05
2.56
3.21
3.89
4.48
19.13
18.28
18.08
17.89
17.71
16.99
16.45
16.27
16.07
15.88
15.69
15.49
15.29
15.09
14.12
13.14
12.56
12.39
12.19
11.23
10.34
9.42
9.04
8.84
8.7
8.52
7.66
6.71
5.78
4.92
4.11
3.47
3.2
2.41
MGA-53543 Typical Linearity Parameters
TC = 25°C, Vd = 5V, ZO = 50 Ω
Freq
ΓSource[1]
Mag
ΓSource[1]
(°)
ΓLoad[1]
Mag
ΓLoad[1]
(°)
OIP3
(dBm)
500 MHz
900 MHz
1.9 GHz
2.4 GHz
0.31
0.15
0.38
0.49
-102
-90
156
177
0.25
0.05
0.05
0.17
-13
-165
45
141
40
40
39
36
Note:
1. Input and output tuners tuned for maximum OIP3 while keeping VSWR better than 2:1
5
Operating at Other Voltages
Operating this RFIC at voltages
less than 5V will affect NF, Gain,
P1dB and IP3. Figure 3 below
demonstrates the affects of
changing supply voltage at
1900 MHz.
MGA-53543 Applications Information
The MGA-53543 operates from a
+5 volt power supply and draws a
nominal current of 53.8 mA. The
RFIC is contained in a miniature
SOT-343 (SC-70 4-lead) package
to minimize printed circuit board
space. This package also offers
good thermal dissipation and RF
characteristics.
Application Guidelines
For most applications, all that is
required to operate the MGA is to
apply a DC bias of +5 volts and
match the RF input and output.
RF Input
The first step to achieve maximum linearity is to match the
input of MGA-53543 to one of the
linearity values listed on the data
sheet. For example, at 1900 MHz
the MGA-53543 needs to see a
complex impedance of 0.38
∠156° looking towards the
source and an output impedance
of 0.05 ∠45° looking towards the
load. This may be accomplished
by a conjugate match from the
system input impedance (typically 50Ω) to ΓS*. Figure 1 shows
the location of these input and
output Gammas (ΓS and ΓL)
required for a high linearity.
6
ΓS
ΓL
20
Figure 1. Matching for linearity at 1900 MHz.
RF Output
Few matching elements are
required on the output of the
MGA-53543 to achieve good
linearity because the output
Gamma (ΓL) is close to 50Ω.
DC Bias
To bias the MGA-53543, a +5 volt
supply is connected to the output
pin through an inductor, RFC,
which isolates the inband signal
from the DC supply as shown in
Figure 2. Capacitor C3 serves as
an RF bypass for inband signals
while C4 helps eliminate out of
band low frequency signals. An
optional resistor R1 may be
added to de-Q any resonance
created between C3 and C4.
Typically values range from 2.2Ω
to 10Ω. A DC blocking capacitor,
C2, is used at the output of the
MMIC to isolate the supply
voltage from succeeding circuits.
NF, GAIN, and P1dB (dB)
Description
The MGA-53543 is a highly linear
enhancement mode PHEMT
(Pseudomorphic High Electron
Mobility Transistor) amplifier
with a frequency range extending
from 450 MHz to 6 GHz. This
range makes the MGA-53543
ideal for both Cellular and PCS
basestation applications. With
high IP3 and low noise figure, the
MGA-53543 may be utilized as a
driver amplifier in a transmit
chain or as a first or second stage
LNA in a receive chain or any
other application requiring high
linearity.
15
10
NF
Gain
P1dB
5
0
1
2
3
4
5
SUPPLY VOLTAGE (V)
Figure 3. Gain, NF and P1dB vs. supply voltage
at 1900 MHz.
The affects of supply voltage on
OIP3 and current at 1900 MHz
are shown in Table 1. The
MGA-53543 is internally biased
for optimal performance at a
quiescent current of 53.8 mA.
Voltage
(V)
OIP3
(dBm)
Id
(mA)
1V
0
4
2V
17
16
3V
28
24
4V
35
41
5V
39
51
Table 1. OIP3 vs. supply power.
C2
1
RFout
2
RFC
53
RFin
C1
3
4
R1
C3
L1
C4
+5V
Figure 2. Schematic diagram with bias
connections.
Matching
The most important criterion
when designing with the
MGA-53543 is choosing the input
and output-matching network.
The MGA-53543 is designed to
give excellent IP3 performance,
however to achieve this requires
both the input and output
matching network to present
specific impedances (ΓS and ΓL)
to the device. It is also possible
to match this part for best NF or
best gain. However, this will
impact the IP3 performance. To
achieve best noise figure, the
input match will need to be
modified to present gamma opt
to the device. To achieve the best
gain will require both the input
and output to be conjugately
matched (which will also result
in the best return loss). Where
needed, the match presented to
the input and the output of the
device can be modified to compromise between IP3, NF and
gain performance.
The MGA-53543 has isolation
large enough to allows input and
output reflection coefficients to
be replaced by S11 and S22.
In general matching for minimum
noise figure does not necessarily
guarantee good IP3 performance
nor does it guarantee good gain.
This is due to the fact that the
impedance parameters shown
below in Table 2 are not guaranteed to lie near each other on a
Smith Chart. So, ideally if all
input matching parameters lied
near each other or at the same
point, and all output parameters
also lied near each other or at the
same point, the amplifier would
have minimum Noise Figure,
maximum IP3 and maximum
Gain all with a single match.
Typically this is not the case and
some parameter must be sacrificed to improve another. Table 2
briefly lists the input and output
parameters required for each
type of match while Figure 4
depicts how each is defined.
7
Match
for
Input
Tuning
Output
Tuning
IP3
Γs
ΓL
NF
Γopt
none
RLin
S11*
none
RLout
none
S22*
Gain
S11*
S22*
Table 2. Required matching for NF, IP3, input &
output Return Loss and Gain.
Input
Match
Output
Match
53
50Ω
50Ω
NF
Γopt
Γopt*
IP3
ΓS
Γ S*
Γ L*
ΓL
Gain
S11*
S11
S22
S22*
This layout provides ample
allowance for package placement
by automated assembly equipment without adding parasitics
that could impair the high
frequency RF performance of the
MGA-53543. The layout is shown
with a footprint of a SOT-343
package superimposed on the
PCB pads for reference.
A microstrip layout with sufficient
ground vias as shown in Figure 6
is recommended for the
MGA-53543 in transitioning from a
package pad layout as in Figure 5.
RF
OUTPUT
53
RF
INPUT
Figure 4. Definition of matching parameters.
Figure 6. Microstripline Layout.
PCB Layout
A recommended PCB pad layout
for the miniature SOT-343
(SC-70) package used by the
MGA-53543 is shown in Figure 5.
RF Grounding
Adequate grounding of Pins 1 and
4 of the RFIC are important to
maintain device stability and RF
performance. Each of the ground
pins should be connected to the
ground plane on the backside of
the PCB by means of plated
through holes (vias). The ground
vias should be placed as close to
the package terminals as practical
to reduce inductance in ground
path. It is good practice to use
multiple vias to further minimize
ground path inductance.
1.30
0.051
1.00
0.039
2.00
0.079
0.60
0.024
.090
0.035
1.15
0.045
Dimensions in inches
mm
Figure 5. Recommended PCB Pad Layout for
Agilent’s SC70 4L/SOT-343 Products.
PCB Materials
FR-4 or G-10 type material is a
good choice for most low cost
wireless applications using single
or multi-layer printed circuit
boards. Typical single-layer
board thickness is 0.020 to 0.031
inches. Circuit boards thicker
than 0.031 inches are not recommended due to excessive inductance in the ground vias.
For noise figure critical or higher
frequency applications, the
additional cost of PTFE/glass
dielectric materials may be
warranted to minimize transmission line loss at the amplifier’s
input.
Application Example
The demonstration circuit board
for the MGA-53543 is shown in
Figure 7. This simple two-layer
board contains microstripline on
the topside and a solid metal
ground plane on the backside
with all RF traces having characteristic impedance of 50Ω.
Multiple 0.02" vias are used to
bring the ground to the topside
of the board and help reduce
ground inductance.
The PCB is fabricated on 0.031"
thick Getek® GR200D dielectric
material with dielectric constant
of 4.2.
MGA - 5X
IN
OUT
SE
12/01
Vd
Figure 7. MGA-53453 PCB Layout.
1900 MHz HLA Design
The following describes a typical
application for the MGA-53543 as
used in a PCS 1900 MHz band
radio receiver optimized for
maximum linearity. Steps include
matching the input and output as
well as providing a DC bias while
maintaining acceptable stability,
gain and noise figure.
As described earlier, a pure
linearity match entails matching
only to Γs and ΓL, thus sacrificing
some NF and Gain. This tradeoff
is explained below and quantified in Figures 8 and 9.
Using the device S-parameters at
1900 MHz, the minimum noise
figure possible, whilst matching
the input to ΓS, is shown to be
1.7 dB.
ΓS – Optimum linearity match
NF = 1.7 dB
Γopt – Optimum NF match
NF = 1.6 dB
NF = 1.5 dB
Figure 8. Noise figure performance.
Because gain depends both on
the input and output match, the
maximum gain is taken from two
sets of circles. One is centered
around S11 and the other is
centered on S22. Thus the
maximum attainable gain is the
lesser of two circles which
completely enclose Γs or ΓL. For
example, in Figure 9 the 16.1 dB
input gain circle completely
encloses Γs, but the smallest
circle that encloses ΓL is 15.9 dB.
Thus the maximum gain is the
weakest link or 15.9 dB.
Ga = 15.9 dB
Ga = 16.1 dB
No matching is required for the
output, but a good rule of thumb
to use when biasing is to limit
series reactance to less than 5Ω
and keep shunt reactance above
500Ω. Therefore choosing an RFC
of 47 nH, which has a reactance
of 561Ω at 1.9 GHz, helps isolate
the DC supply from inband
signals. If any high frequency
signal is created or enters the DC
supply, a 150 pF capacitor is
ready to short it to ground. An
8.2 pF capacitor serves primarily
as a DC block, but also helps the
output match.
The completed 1900 MHz
amplifier schematic is shown in
Figure 10.
8.2 pF
1
RFout
2
47 nH
53
RFin
2.2 pF
3
150 pF
4
2.2Ω
3.3 nH
+5V
0.1 µF
Figure 10. Schematic for a 1900 MHz stable
circuit.
Ga = 16.2 dB
ΓL
ΓS
S11
S22
Ga = 16.2 dB
Ga = 16.1 dB
Figure 9. Input and output gain circles.
8
To accomplish the above performance, a high pass configuration
consisting of a 3.3 nH inductor
and a 2.2 pF capacitor is used for
the input match. Unlike a low
pass configuration, a high pass
configuration provides not only
the impedance transfer required,
but also provides excellent
stability for the demo board by
diminishing low frequency gain.
Included with the schematic is a
complete RF layout (Figure 15)
which includes placement of all
components and SMA connectors. A list of part numbers and
manufacturer used is given
below in Table 3.
3.3 nH
TOKO LL1608-FS3N3S
47 nH
TOKO LL1005-FH47N
2.2Ω
RHOM MCR01J2R2
2.2 pF
Phycomp 0402CG229C9B200
8.2 pF
Phycomp 0402CG829D9B200
150 pF
Phycomp 0402CG151J9B200
0.1 µF
Phycomp 06032F104M8B20
More significant is the linearity
delivered by MGA-53543 at
1900 MHz. Figure 13 plots OIP3
over a frequency range from
1850 MHz to1950 MHz.
This device produces IIP3 of
24 dBm, OIP3 of 38 dBm and
P1dB of 17.8 dBm at 1900 MHz.
Table 3. Component parts list for the
MGA-53543 HLA at 1900 MHz.
20
GAIN and NF (dB)
Gain
5
NF
1.8
2
2.2
2.4
OIP3 (dBm)
40
4.7 pF
35
1
TX
25
1840
5.6 pF
RX
3
2.2Ω
1880
1920
1960
+5V
2000
2.2Ω
FREQUENCY (MHz)
Figure 13. OIP3 vs. Frequency.
Figure 14. Schematic diagram for 900 MHz HLA.
Due to component parasitics and
part variations, actual performance may not be identical to
this example.
22 nH
TOKO LL1608-FS22N
15 nH
TOKO LL1005-FS15N
2.2Ω
RHOM MCR01J2R2
4.7 pF
Phycomp 0402CG479C9B200
5.6 pF
Phycomp 0402CG569D9B200
1000 pF
Phycomp 04022R102K9B200
Table 4. Component parts list for the
MGA-53543 HLA at 900 MHz.
2.6
MGA - 5X
0
C2
R1
IN
RETURN LOSS (dB)
-5
C1
53
L2
S11
C3
J1
-15
L1
S22
R2
OUT
-20
SE
1.8
2
2.2
2.4
FREQUENCY (GHz)
Figure 12. Input and Output return loss vs
Frequency.
9
1000 pF
22 nH
Figure 11. Gain and Noise Figure vs
Frequency.
-25
1.6
15 nH
4
FREQUENCY (GHz)
-10
RFout
2
53
RFin
30
900 MHz HLA Design
Optimizing the MGA-53543 for
maximum linearity at the Cellular band follows very similar to
that of 1900 MHz, except that the
input and output tuning conditions will change according to the
10
0
1.6
An optional 2.2Ω resistor at the
input helps resistively load the
amplifier and improve stability
but slightly degrade noise figure.
45
Performance of MGA-53543 at
1900 MHz
With a device voltage of +5V,
demonstration board MGA-5X
delivers a measured noise figure
of 1.78 dB and an average gain of
14.5 dB as shown in Figure 11.
Gain here is slightly lower than
data sheet due to the losses
acquired in creating a stable
broadband match. Input and
output VSWR are both better
than 2:1 at 1900 MHz, with input
return loss being 10 dB and
output return loss at 13 dB.
15
linearity table on the data sheet.
Figure 14 below shows the
schematic diagram for a complete 900 MHz circuit using Γs of
0.15 ∠-90° and ΓL of
0.05 ∠-165° . Table 4 shows the
component parts list used.
02/01
Vd
2.6
Figure 15. RF Layout for 1900 MHz HLA .
J2
Performance of MGA-53543 at
900 MHz
At 900 MHz MGA-53543 delivers
OIP3 of 40 dBm along with a
noise figure of 1.43 dB. Gain is
measured to be 17.1 dB and input
return loss is 13.7 dB and output
return loss is 13.3 dB as shown
in Figures 16 and 17. P1dB is
18.8 dBm.
20
Gain
GAIN and NF (dB)
15
10
5
900 MHz LNA Design
To demonstrate the versatility of
the MGA-53543, the following
example describes a cellular
band Low Noise Amplifier (LNA)
design. The methodology for a
900 MHz LNA design differs from
the previous examples in that
only the input match affects
noise figure. Thus, optimizing for
minimum noise figure entails
matching only the input to Γopt
instead of ΓS, and the output can
either be matched to S22 for
better gain or ΓL for better
linearity. Figure 18 shows the
complete schematic for a
900 MHz low noise amplifier
design and Table 5 describes the
required components.
Performance of MGA-53543 at
900 MHz
Biased with a +5 Volt supply
MGA-53543 delivers a Noise
Figure of 1.33 dB at 900 MHz.
This number is higher than NFmin
only because of loss from lumped
element components with
parasitic losses. A microstip or
distributed element match may
improve noise figure by .2 dB.
Gain is measured to be 17.4 dB as
shown in Figure 19. Input and
output VSWR are both better
than 2:1, with input return loss
of 25 dB and output return loss
at 17.5 dB shown in Figure 20.
20
Gain
NF
15
4.7 pF
600
800
1000
1200
1400
RFout
FREQUENCY (MHz)
1
Figure 16. Gain and Noise Figure vs
Frequency.
2
15 nH
53
RFin
4.7 pF
3
1000 pF
GAIN and NF (dB)
0
400
5
4
0
NF
2.2Ω
12 nH
0
400
+5V
RETURN LOSS (dB)
10
600
-5
800
1000
1200
1400
FREQUENCY (MHz)
Figure 18. Schematic for 900 MHz LNA design.
-10
Figure 19. Gain, Noise Figure and Output
Power at 900 MHz.
12 nH
TOKO LL1608-FS12NJ
0
15 nH
TOKO LL1005-FS15N
-5
4.7 pF
Phycomp 0402CG479C9B200
2.2Ω
RHOM MCR01J2R2
1000 pF
Phycomp 04022R102K9B200
S11
S22
-20
400
600
800
1000
1200
1400
FREQUENCY (MHz)
Figure 17. Input and Output return loss vs
Frequency.
Table 5. Component Parts List for the
MGA-53543 HLA at 900 MHz.
RETURN LOSS (dB)
-15
-10
-15
-20
S11
S22
-25
-30
400
600
800
1000
1200
1400
FREQUENCY (MHz)
Figure 20. Input and Output return loss at
900 MHz.
Input IIP3 is measured to be
18.6 dBm and P1dB is 19.0 dB at
900 MHz.
10
8.2 pF
1
RFout
2
47 nH
53
RFin
2.2 pF
0
3.9 nH
TOKO LL1608-FS3N9S
47 nH
TOKO LL1005-FH47N
2.2Ω
RHOM MCR01J2R2
2.2 pF
Phycomp 0402CG229C9B200
8.2 pF
Phycomp 0402CG829D9B200
150 pF
Phycomp 0402CG151J9B200
-5
RETURN LOSS (dB)
1900 MHz LNA Design
The final example presented in
this application note is a PCS
band low noise amplifier circuit.
As in the 900 MHz LNA example,
the input is matched to Γopt
which at 1900 MHz is given as
.229 ∠-172° and the output is
matched for maximum linearity
i.e. ΓL. Biasing the DC supply is
done very similar to the
1900 MHz HLA. In fact, the only
major difference between the
PCS HLA presented earlier and
this PCS LNA schematic is a
3.9nH inductor on the input. The
complete schematic is shown
below.
S22
-10
-20
Table 6. Component parts list for the
MGA-53453 LNA amplifier at 1900 MHz.
-25
1.6
Performance of MGA-53543 at
1900 MHz
The typical noise figure for the
1900 MHz LNA is measured to be
1.62 dB with OIP3 at a nominal
37 dBm. Figure 22 shows a
measured gain of 14.8 dB and
Figure 23 shows the input and
output return loss to be 16.4 dB
and 11.3 dB respectively. P1dB is
18 dBm.
150 pF
1.8
2.0
2.2
2.4
2.6
FREQUENCY (GHz)
Figure 23. Input and Output Return Loss for
1900 MHz LNA.
Summary
In summary, the MGA-53543
offers very high IP3 as designed,
but is versatile enough to give
good NF performance wherever
needed. Below is a summary of
the preceding four examples.
20
3
4
2.2Ω
3.9 nH
Figure 21. Schematic for 1900 MHz LNA
design.
15
GAIN and NF (dB)
+5V
1900 MHz
900 MHz
HLA
NF = 1.78 dB
OIP3 = 38 dBm
Ga = 14.5 dB
P1dB = 17.8 dBm
NF = 1.42 dB
OIP3 = 40 dBm
Ga = 17.1 dB
P1dB = 18.8 dBm
LNA
NF = 1.62 dB
OIP3 = 37 dBm
Ga = 14.8 dB
P1dB = 18.0 dBm
NF = 1.33 dB
OIP3 = 36 dBm
Ga = 17.4 dB
P1dB = 19.0 dBm
Gain
10
5
Table 6 shows the complete parts
list used for the 1900 MHz low
noise amplifier.
NF
0
1.6
1.8
2.0
2.2
2.4
2.6
FREQUENCY (GHz)
Figure 22. Gain, Noise Figure vs. Frequency
for 1900 MHz LNA.
11
S11
-15
Table 7. 1900 MHz and 900 MHz HLA and
1900 MHz and 900 MHz LNA summary.
Device Model
Refer to Agilent’s web site
www.agilent.com/view/rf
Part Number Ordering Information
Part Number
MGA-53543-TR1
No. of
Devices
3000
Container
7" Reel
MGA-53543-TR2
MGA-53543-BLK
10000
100
13" Reel
antistatic bag
MGA-53543-TR1G
MGA-53543-TR2G
3000
10000
7" Reel
13" Reel
MGA-53543-BLKG
100
antistatic bag
Note: For lead-free option, the part number will have the
character “G” at the end.
Package Dimensions
Outline 43 (SOT-343/SC70 4 lead)
1.30 (.051)
BSC
HE
E
1.15 (.045) BSC
b1
D
A2
A
A1
b
L
C
DIMENSIONS (mm)
SYMBOL
E
D
HE
A
A2
A1
b
b1
c
L
12
MIN.
1.15
1.85
1.80
0.80
0.80
0.00
0.25
0.55
0.10
0.10
MAX.
1.35
2.25
2.40
1.10
1.00
0.10
0.40
0.70
0.20
0.46
NOTES:
1. All dimensions are in mm.
2. Dimensions are inclusive of plating.
3. Dimensions are exclusive of mold flash & metal burr.
4. All specifications comply to EIAJ SC70.
5. Die is facing up for mold and facing down for trim/form,
ie: reverse trim/form.
6. Package surface to be mirror finish.
Device Orientation
REEL
TOP VIEW
END VIEW
4 mm
CARRIER
TAPE
8 mm
53
USER
FEED
DIRECTION
COVER TAPE
53
53
53
(Package marking example orientation shown.)
Tape Dimensions
For Outline 4T
P
P2
D
P0
E
F
W
C
D1
t1 (CARRIER TAPE THICKNESS)
Tt (COVER TAPE THICKNESS)
K0
10° MAX.
A0
DESCRIPTION
13
10° MAX.
B0
SYMBOL
SIZE (mm)
SIZE (INCHES)
CAVITY
LENGTH
WIDTH
DEPTH
PITCH
BOTTOM HOLE DIAMETER
A0
B0
K0
P
D1
2.40 ± 0.10
2.40 ± 0.10
1.20 ± 0.10
4.00 ± 0.10
1.00 + 0.25
0.094 ± 0.004
0.094 ± 0.004
0.047 ± 0.004
0.157 ± 0.004
0.039 + 0.010
PERFORATION
DIAMETER
PITCH
POSITION
D
P0
E
1.55 ± 0.10
4.00 ± 0.10
1.75 ± 0.10
0.061 + 0.002
0.157 ± 0.004
0.069 ± 0.004
CARRIER TAPE
WIDTH
THICKNESS
W
t1
8.00 + 0.30 - 0.10
0.254 ± 0.02
0.315 + 0.012
0.0100 ± 0.0008
COVER TAPE
WIDTH
TAPE THICKNESS
C
Tt
5.40 ± 0.10
0.062 ± 0.001
0.205 + 0.004
0.0025 ± 0.0004
DISTANCE
CAVITY TO PERFORATION
(WIDTH DIRECTION)
F
3.50 ± 0.05
0.138 ± 0.002
CAVITY TO PERFORATION
(LENGTH DIRECTION)
P2
2.00 ± 0.05
0.079 ± 0.002
www.agilent.com/semiconductors
For product information and a complete list of
distributors, please go to our web site.
For technical assistance call:
Americas/Canada: +1 (800) 235-0312 or
(916) 788-6763
Europe: +49 (0) 6441 92460
China: 10800 650 0017
Hong Kong: (65) 6756 2394
India, Australia, New Zealand: (65) 6755 1939
Japan: (+81 3) 3335-8152(Domestic/International), or
0120-61-1280(Domestic Only)
Korea: (65) 6755 1989
Singapore, Malaysia, Vietnam, Thailand, Philippines,
Indonesia: (65) 6755 2044
Taiwan: (65) 6755 1843
Data subject to change.
Copyright © 2004 Agilent Technologies, Inc.
Obsoletes 5988-9628EN
November 22, 2004
5989-1804EN