a Dual Single-Supply Audio Operational Amplifier SSM2135 FEATURES Excellent Sonic Characteristics High Output Drive Capability 5.2 nV/√Hz Equivalent Input Noise @ 1 kHz 0.001% THD+N (VO = 2.5 V p-p @ 1 kHz) 3.5 MHz Gain Bandwidth Unity-Gain Stable Low Cost APPLICATIONS Multimedia Audio Systems Microphone Preamplifier Headphone Driver Differential Line Receiver Balanced Line Driver Audio ADC Input Buffer Audio DAC l-V Converter and Filter Pseudo-Ground Generator PIN CONNECTIONS 8-Lead Epoxy DIP (P-Suffix) 8-Lead Narrow-Body SOIC (S Suffix) OUT A –IN A V+ SSM2135 OUT B +IN A –IN B V–/GND +IN B OUT A 1 8 V+ –IN A 2 7 OUT B +IN A 3 6 –IN B V–/GND 4 5 +IN B SSM2135 under moderate load conditions. Under severe loading, the SSM2135 still maintains a wide output swing with ultralow distortion. GENERAL DESCRIPTION The SSM2135 Dual Audio Operational Amplifier permits excellent performance in portable or low power audio systems, with an operating supply range of +4 V to +36 V or ± 2 V to ± 18 V. The unity gain stable device has very low voltage noise of 4.7 nV/√Hz, and total harmonic distortion plus noise below 0.01% over normal signal levels and loads. Such characteristics are enhanced by wide output swing and load drive capability. A unique output stage* permits output swing approaching the rail Particularly well suited for computer audio systems and portable digital audio units, the SSM2135 can perform preamplification, headphone and speaker driving, and balanced line driving and receiving. Additionally, the device is ideal for input signal conditioning in single-supply sigma-delta analogto-digital converter subsystems such as the AD1878/AD1879. The SSM2135 is available in 8-lead plastic DIP and SOIC packages, and is guaranteed for operation over the extended industrial temperature range of –40°C to +85°C. *Protected by U. S. Patent No. 5,146,181. FUNCTIONAL BLOCK DIAGRAM V+ OUT +IN 9V 9V –IN V–/GND REV. D Information furnished by Analog Devices is believed to be accurate and reliable. However, no responsibility is assumed by Analog Devices for its use, nor for any infringements of patents or other rights of third parties which may result from its use. No license is granted by implication or otherwise under any patent or patent rights of Analog Devices. One Technology Way, P.O. Box 9106, Norwood, MA 02062-9106, U.S.A. Tel: 617/329-4700 Fax: 617/326-8703 SSM2135–SPECIFICATIONS (VS = +5 V, –408C < TA < +858C unless otherwise noted. Typical specifications apply at TA = +258C.) Parameter Symbol Conditions AUDIO PERFORMANCE Voltage Noise Density Current Noise Density Signal-To-Noise Ratio Headroom Total Harmonic Distortion en in SNR HR THD+N f = 1 kHz f = 1 kHz 20 Hz to 20 kHz, 0 dBu = 0.775 V rms Clip Point = 1% THD+N, f = 1 kHz, RL = 10 kΩ AV = +1, VO = 1 V p-p, f = 1 kHz, 80 kHz LPF RL = 10 kΩ RL = 32 Ω DYNAMIC PERFORMANCE Slew Rate Gain Bandwidth Product Settling Time SR GBW tS INPUT CHARACTERISTICS Input Voltage Range Input Offset Voltage Input Bias Current Input Offset Current Differential Input Impedance Common-Mode Rejection Large Signal Voltage Gain VCM VOS IB IOS ZIN CMR AVO OUTPUT CHARACTERISTICS Output Voltage Swing High VOH Output Voltage Swing Low VOL Short Circuit Current Limit ISC POWER SUPPLY Supply Voltage Range Power Supply Rejection Ratio Supply Current VS PSRR ISY Min RL = 2 kΩ, TA = +25°C 0.6 to 0.1%, 2 V Step Typ nV/√Hz pA/√Hz dBu dBu 0.003 0.005 % % 0.9 3.5 5.8 V/µs MHz µs 0.2 300 0 V ≤ VCM ≤ 4 V, f = dc 0.01 V ≤ VOUT ≤ 3.9 V, RL = 600 Ω 87 2 RL = 100 kΩ RL = 600 Ω RL = 100 kΩ RL = 600 Ω 4.1 3.9 Single Supply Dual Supply VS = +4 V to +6 V, f = dc VOUT = 2.0 V, No Load VS = +5 V VS = ± 18 V, VOUT = 0 V, No Load +4 ±2 90 Units 5.2 0.5 121 5.3 0 VOUT = 2 V VCM = 0 V, VOUT = 2 V VCM = 0 V, VOUT = 2 V Max +4.0 2.0 750 50 4 112 ± 30 3.5 3.0 V V mV mV mA +36 ± 18 V V dB 6.0 7.6 mA mA 120 2.8 3.7 V mV nA nA MΩ dB V/µV ABSOLUTE MAXIMUM RATINGS THERMAL CHARACTERISTICS Supply Voltage Single Supply . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . +36 V Dual Supply . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . ± 18 V Input Voltage . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . ± VS Differential Input Voltage . . . . . . . . . . . . . . . . . . . . . . . . 10 V Output Short Circuit Duration . . . . . . . . . . . . . . . . Indefinite Storage Temperature Range . . . . . . . . . . . . –65°C to +150°C Operating Temperature Range . . . . . . . . . . . –40°C to +85°C Junction Temperature Range (TJ) . . . . . . . . –65°C to +150°C Lead Temperature (Soldering, 60 sec) . . . . . . . . . . . . +300°C Thermal Resistance1 ESD RATINGS Model Temperature Range Package Description SSM2135P SSM2135S –40°C to +85°C –40°C to +85°C 8-Lead Plastic DIP N-8 8-Lead SOIC SO-8 883 (Human Body) Model . . . . . . . . . . . . . . . . . . . . . . . 1 kV EIAJ Model . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 175 V 8-Lead Plastic DIP 8-Lead SOIC θJA θJC θJA θJC 103°C/W 43°C/W 158°C/W 43°C/W θJA is specified for worst case conditions, i.e., θJA is specified for device in socket for P-DIP and device soldered in circuit board for SOIC package. 1 ORDERING GUIDE –2– Package Option REV. D SSM2135 10 +5V VS = +5V 500µF + AV = +1, ƒ = 1kHz VIN = 1Vp-p 1 RL = 10kΩ WITH 80kHz FILTER THD – % RL +2.5Vdc 0.1 Figure 1. Test Circuit for Figures 2–4 0.01 0.001 10 100 1k LOAD RESISTANCE – Ω 10k Figure 4. THD+N vs. Load (See Test Circuit) 1 VS = +5V RL = 100kΩ VOUT = 2.5Vp-p ƒ = 1kHz WITH 80kHz FILTER THD+N – % 0.1 Figure 2. THD+N vs. Amplitude (See Test Circuit; AV = +1, VS = +5 V, f = 1 kHz, with 80 kHz Low-Pass Filter) NONINVERTING INVERTING 0.01 0.001 0 10 20 30 GAIN – dB 40 50 60 Figure 5. THD+N vs. Gain 1 VS = +5V AV = +1, ƒ = 1kHz VIN = 1Vp-p RL = 10kΩ WITH 80kHz FILTER THD+N – % 0.1 0.01 Figure 3. THD+N vs. Frequency (See Test Circuit; AV = +1, VIN = 1 V p-p, with 80 kHz Low-Pass Filter) 0.001 5 10 15 20 25 SUPPLY VOLTAGE – V Figure 6. THD+N vs. Supply Voltage REV. D –3– 30 SSM2135 5 VS = +5V TA = +25°C in – pA/ √Hz 4 3 2 1 0 Figure 7. SMPTE Intermodulation Distortion (AV = +1, VS = +5 V, f = 1 kHz, RL = 10 kΩ) 1 10 100 FREQUENCY – Hz 1k Figure 10. Current Noise Density vs. Frequency 1s 100 90 10 0% Figure 8. Input Voltage Noise (20 nV/div) Figure 11. Frequency Response (AV = +1, VS = +5 V, VIN = 1 V p-p, RL = 10 kΩ) 30 VS = +5V TA = +25°C 25 100 90 en – nV/ √Hz 20 15 10 10 0% 5 0 500m V 1 10 100 FREQUENCY – Hz 1µS 1k Figure 9. Voltage Noise Density vs. Frequency Figure 12. Square Wave Response (VS = +5 V, AV = +1, RL = ∞) –4– REV. D SSM2135 60 50 TA = +25 °C 40 20 AV = +100 CLOSED-LOOP GAIN – dB CHANNEL SEPARATION – dB VS = +5V VS = +5V TA = +25°C 40 0 –20 –40 –60 –80 –100 105 30 20 AV = +10 10 0 AV = +1 –10 –120 –20 10 100 1k 10k 100k FREQUENCY – Hz 1M 10M 1k 1M 10M Figure 16. Closed-Loop Gain vs. Frequency 140 100 VS = +5V VS = +5V TA = +25 °C TA = +25° C 0 80 OPEN-LOOP GAIN – dB 100 80 60 40 60 45 GAIN 90 40 PHASE θm = 57° 20 180 0 20 225 10M –20 1k 10k 100k 1M 135 PHASE – Degrees 120 0 100 1k 10k FREQUENCY – Hz 100k 1M FREQUENCY – Hz Figure 14. Common-Mode Rejection vs. Frequency Figure 17. Open-Loop Gain and Phase vs. Frequency 50 140 80 60 –PSRR RL = 2kΩ VIN = 100mVp–p 40 OVERSHOOT – % 100 VS = +5V 45 VS = +5V AV = +1 TA = +25°C 120 PSRR – dB 100k FREQUENCY – Hz Figure 13. Crosstalk vs. Frequency (RL = 10 kΩ) COMMON-MODE REJECTION – dB 10k +PSRR 40 TA = +25 °C AV = +1 35 30 NEGATIVE EDGE 25 20 POSITIVE EDGE 15 20 10 0 5 0 –20 10 100 1k 10k FREQUENCY – Hz 100k 0 1M 200 300 400 500 LOAD CAPACITANCE – pF Figure 15. Power Supply Rejection vs. Frequency REV. D 100 Figure 18. Small Signal Overshoot vs. Load Capacitance –5– SSM2135 40 50 VS = +5V TA = +25°C 45 VS = +5V AV = +1 RL = 10k ƒ = 1kHz THD+N = 1% TA = +25°C 35 OUTPUT VOLTAGE – Volts 40 IMPEDANCE – Ω 35 AVCL = +100 30 25 AVCL = +10 20 15 30 25 20 15 10 10 5 5 AVCL = +1 0 0 100 1k 10k FREQUENCY – Hz 100k 0 1M 15 20 25 30 SUPPLY VOLTAGE – Volts 35 5.0 5 POSITIVE OUTPUT SWING – Volts 3 2 1 2.0 4.5 1.5 +SWING RL = 2kΩ 4.0 1.0 –SWING RL = 2kΩ +SWING RL = 600Ω 3.5 0.5 –SWING RL = 600Ω 3.0 0 1 10 40 VS = +5.0V VS = +5V TA = +25°C AV = +1 ƒ = 1kHz THD+N = 1% 4 100 1k LOAD RESISTANCE – Ω 10k –50 –75 100k –25 0 25 50 75 100 0 125 TEMPERATURE – °C Figure 20. Maximum Output Voltage vs. Load Resistance Figure 23. Output Swing vs. Temperature and Load 6 2.0 VS = +5V VS = +5V +0.5V ≤ V OUT ≤ +4.0V RL = 2kΩ 5 TA = +25 °C AV = +1 1.5 4 SLEW RATE – V/µs MAXIMUM OUTPUT SWING – Volts 10 Figure 22. Output Swing vs. Supply Voltage Figure 19. Output Impedance vs. Frequency MAXIMUM OUTPUT – Volts 5 NEGATIVE OUTPUT SWING – Volts 10 3 2 +SLEW RATE 1.0 –SLEW RATE 0.5 1 0 1k 10k 100k 1M 0 10M –75 FREQUENCY – Hz –50 –25 0 25 50 75 100 125 TEMPERATURE – °C Figure 21. Maximum Output Swing vs. Frequency Figure 24. Slew Rate vs. Temperature –6– REV. D SSM2135 5 20 VS = +5.0V VO = 3.9V 18 4 SUPPLY CURRENT – mA OPEN-LOOP GAIN – V/µV 16 RL = 2kΩ 14 12 RL = 600Ω 10 8 6 VS = ±18V VS = ±15V 3 VS = +5.0V 2 1 4 2 0 0 –75 –50 –25 0 25 50 75 100 125 –75 –50 –25 TEMPERATURE – °C 0 25 50 75 100 125 TEMPERATURE – °C Figure 25. Open-Loop Gain vs. Temperature 70 Figure 27. Supply Current vs. Temperature 5 500 4 GBW 60 3 θm 55 2 50 –75 –50 –25 0 25 50 75 100 INPUT BIAS CURRENT – nA 65 GAIN-BANDWIDTH PRODUCT – MHz PHASE MARGIN – Degrees VS = +5V VS = +5.0V 300 VS = ±15V 200 100 1 125 0 –75 TEMPERATURE – °C –50 –25 0 25 50 75 100 125 TEMPERATURE – °C Figure 26. Gain Bandwidth Product and Phase Margin vs. Temperature Figure 28. Input Bias Current vs. Temperature The SSM2135 is fully protected from phase reversal for inputs going to the negative supply rail. However, an internal ESD protection diodes will turn “on” when either input is forced more than 0.5 V below the negative rail. Under this condition, input current in excess of 2 mA may cause erratic output behavior, in which case a current limiting resistor should be included in the offending input if phase integrity is required with excessive input voltages. A 500 Ω or higher series input resistor will prevent phase inversion even with the input pulled 1 volt below the negative supply. APPLICATION INFORMATION The SSM2135 is a low voltage audio amplifier that has exceptionally low noise and excellent sonic quality even when driving loads as small as 25 Ω. Designed for single supply use, the SSM2135’s inputs common-mode and output swing to zero volts. Thus with a supply voltage at +5 V, both the input and output will swing from 0 V to +4 V. Because of this, signal dynamic range can be optimized if the amplifier is biased to a +2 V reference rather than at half the supply voltage. The SSM2135 is unity-gain stable, even when driving into a fair amount of capacitive load. Driving up to 500 pF does not cause any instability in the amplifier. However, overshoot in the frequency response increases slightly. “Hot” plugging the input to a signal generally does not present a problem for the SSM2135, assuming the signal does not have any voltage exceeding the device’s supply voltage. If so, it is advisable to add a series input resistor to limit the current, as well as a Zener diode to clamp the input to a voltage no higher than the supply. The SSM2135 makes an excellent output amplifier for +5 V only audio systems such as a multimedia workstation, a CD output amplifier, or an audio mixing system. The amplifier has large output swing even at this supply voltage because it is designed to swing to the negative rail. In addition, it easily drives load impedances as low as 25 Ω with low distortion. REV. D 400 –7– SSM2135 APPLICATION CIRCUITS A Low Noise Microphone Preamplifier A Low Noise Stereo Headphone Driver Amplifier Figure 29 shows the SSM2135 used in a stereo headphone driver for multimedia applications with the AD1848, a 16-bit stereo codec. The SSM2135 is equally well suited for the serialbused AD1849 stereo codec. The headphone’s impedance can be as low as 25 Ω, which covers most commercially available high fidelity headphones. Although the amplifier can operate at up to ± 18 V supply, it is just as efficient powered by a single +5 V. At this voltage, the amplifier has sufficient output drive to deliver distortion-free sound to a low impedance headphone. The SSM2135’s 4.7 nV/√Hz input noise in conjunction with low distortion makes it an ideal device for amplifying low level signals such as those produced by microphones. Figure 31 illustrates a stereo microphone input circuit feeding a multimedia sound codec. As shown, the gain is set at 100 (40 dB), although it can be set to other gains depending on the microphone output levels. Figure 32 shows the preamplifier’s harmonic distortion performance with 1 V rms output while operating from a single +5 V supply. LOUT VCC GND VREF 10kΩ 40 35/36 34/37 8.66kΩ 2 +5V 3 1/2 SSM2135 10µF 32 0.1µF 10µF 5 AD1848 ROUT 470µF 1 0.1µF 6 41 10kΩ 8 L CH The SSM2135 is biased to 2.25 V by the VREF pin of the AD1848 codec. The same voltage is buffered by the 2N4124 transistor to provide “phantom power” to the microphone. A typical electret condenser microphone with an impedance range of 100 Ω to 1 kΩ works well with the circuit. This power booster circuit may be omitted for dynamic microphone elements. 10kΩ R CH 0.1µF 7 +5V AGND 100Ω L CHANNEL MIC IN 1/2 470µF 4 SSM2135 2 2kΩ 29 1 10µF 3 8.66kΩ 10µF 8 10kΩ 1/2 4 SSM2135 +5V 0.1µF +5V 2N4124 Figure 29. A Stereo Headphone Driver for Multimedia Sound Codec Figure 30 shows the total harmonic distortion characteristics versus frequency driving into a 32 Ω load, which is a very typical impedance for a high quality stereo headphone. The SSM2135 has excellent power supply rejection, and as a result, is tolerant of poorly regulated supplies. However, for best sonic quality, the power supply should be well regulated and heavily bypassed to minimize supply modulation under heavy loads. A minimum of 10 µF bypass is recommended. Figure 30. Headphone Driver THD+N vs. Frequency into a 32 Ω Load (VS = +5 V, with 80 kHz Low-Pass Filter) R CHANNEL MIC IN 34/37 32 10µF 2kΩ 35/36 0.1µF LMIC VCC GND VREF AD1848 10kΩ 5 7 10µF 6 100Ω 1/2 SSM2135 28 RMIC 10kΩ Figure 31. Low Noise Microphone Preamp for Multimedia Sound Codec Figure 32. MIC Preamp THD+N Performance (VS = +5 V, AV = 40 dB, VOUT = 1 V rms, with 80 kHz Low-Pass Filter) –8– REV. D SSM2135 An 18-Bit Stereo CD-DAC Output Amplifier A Single Supply Differential Line Receiver The SSM2135 makes an ideal single supply stereo output amplifier for audio D/A converters because of its low noise and distortion. Figure 33 shows the implementation of an 18-bit stereo DAC channel. The output amplifier also provides low-pass filtering for smoothing the oversampled audio signal. The filter’s cutoff frequency is set at 22.5 kHz and it has a maximally flat response from dc to 20 kHz. Receiving a differential signal with minimum distortion is achieved using the circuit in Figure 35. Unlike a difference amplifier (a subtractor), the circuit has a true balanced input impedance regardless of input drive levels. That is, each input always presents a 20 kΩ impedance to the source. For best common-mode rejection performance, all resistors around the differential amplifier must be very well matched. Best results can be achieved using a 10 kΩ precision resistor network. As mentioned above, the amplifier’s outputs can drive directly into a stereo headphone that has impedance as low as 25 Ω with no additional buffering required. 10kΩ +5V 10µF+0.1µF +5V SUPPLY 1 2 3 4 5 6 VL 18-BIT DAC VBL LL DL 7.68kΩ VOL CK VREF DR LR AD1868 18-BIT SERIAL REG. VREF 8 2 4 220µF 1 LEFT CHANNEL OUTPUT DIFFERENTIAL AUDIO IN 1/2 4 SSM2135 20kΩ 7.68kΩ 12 2.0V 1µF 100pF 9.76kΩ 220µF 6 9 7 330pF 5 10Ω 7 5 100Ω RIGHT CHANNEL OUTPUT 10µF 1 +5V 8 3 2 4 0.1µF 47kΩ 1/2 SSM2135 AUDIO OUT 1/2 SSM2135 7.68kΩ 7.68kΩ VS 20kΩ 6 100pF 10 18-BIT DAC 10kΩ 47kΩ 11 DGND VBR 8 330pF VOR 7 8 1 3 9.76kΩ 14 13 AGND 2 3 15 18-BIT SERIAL REG. 20kΩ 1/2 SSM2135 16 7.5kΩ +5V 5kΩ 1/2 SSM2135 2.5kΩ Figure 33. +5 V Stereo 18-Bit DAC Figure 35. Single Supply Balanced Differential Line Receiver A Single Supply Differential Line Driver Signal distribution and routing is often required in audio systems, particularly portable digital audio equipment for professional applications. Figure 34 shows a single supply line driver circuit that has differential output. The bottom amplifier provides a 2 V dc bias for the differential amplifier in order to maximize the output swing range. The amplifier can output a maximum of 0.8 V rms signal with a +5 V supply. It is capable of driving into 600 Ω line termination at a reduced output amplitude. A Pseudo-Reference Voltage Generator For single supply circuits, a reference voltage source is often required for biasing purposes or signal offsetting purposes. The circuit in Figure 36 provides a supply splitter function with low output impedance. The 1 µF output capacitor serves as a charge reservoir to handle a sudden surge in demand by the load as well as providing a low ac impedance to it. The 0.1 µF feedback capacitor compensates the amplifier in the presence of a heavy capacitive load, maintaining stability. 1kΩ The output can source or sink up to 12 mA of current with +5 V supply, limited only by the 100 Ω output resistor. Reducing the resistance will increase the output current capability. Alternatively, increasing the supply voltage to 12 V also improves the output drive to more than 25 mA. +5V 10µF+0.1µF 2 8 1 100µF 3 AUDIO IN 4 1kΩ 1/2 SSM2135 DIFFERENTIAL AUDIO OUT 1kΩ VS+ = +5V → +12V R3 2.5kΩ 6 7 10kΩ 5 2.0V C1 0.1µF 1/2 SSM2135 2.5kΩ +5V 0.1µF 100Ω 1µF 8 2 7.5kΩ 3 4 3 4 R4 100Ω + VS 1 C2 1µF 2 OUTPUT R2 5kΩ 5kΩ Figure 36. Pseudo-Reference Generator Figure 34. Single Supply Differential Line Driver REV. D 8 1/2 SSM2135 2 1 1/2 SSM2135 R1 5kΩ +5V –9– SSM2135 A Digital Volume Control Circuit A Logarithmic Volume Control Circuit Working in conjunction with the AD7528/PM7528 dual 8-bit D/A converter, the SSM2135 makes for an efficient audio attenuator, as shown in Figure 37. The circuit works off a single +5 V supply. The DAC’s are biased to a 2 V reference level which is sufficient to keep the DAC’s internal R-2R ladder switches operating properly. This voltage is also the optimal midpoint of the SSM2135’s common-mode and output swing range. With the circuit as shown, the maximum input and output swing is 1.25 V rms. Total harmonic distortion measures a respectable 0.01% at 1 kHz and 0.1% at 20 kHz. The frequency response at any attenuation level is flat to 20 kHz. Figure 38 shows a logarithmic version of the volume control function. Similar biasing is used. With an 8-bit bus, the AD7111 provides an 88.5 dB attenuation range. Each bit resolves a 0.375 dB attenuation. Refer to AD7111 data sheet for attenuation levels for each input code. +5V 0.1µF 3 47µF L AUDIO IN Each DAC can be controlled independently via the 8-bit parallel data bus. The attenuation level is linearly controlled by the binary weighting of the digital data input. Total attenuation ranges from 0 dB to 48 dB. 10 +5V 10µF+0.1µF L AUDIO IN 4 REF A 47µF FB OUTA 2 2 8 3 AD7111 16 1 FB OUTA AGND 8 R AUDIO IN 3 14 16 47µF 1 15 DGND VDD FB OUTA VIN AD7111 AGND 2 10 10 6 1/2 SSM2135 7 1µF 47µF R AUDIO OUT 5 2kΩ +5V 0.1µF 2.0V 4 SSM2135 L AUDIO OUT 1/2 4 SSM2135 100Ω L AUDIO OUT 47µF 1 2 DATA IN & CONTROL 1/2 2 3 47µF 1 DAC A VDD +5V 0.1µF 3 AD/PM-7528 14 15 DGND VIN +5V 10µF+0.1µF +5V 1 8 2 7.5kΩ 3 4 1/2 SSM2135 5kΩ DATA IN 6 CONTROL SIGNAL R AUDIO IN 15 16 DACA/ DACB CS 19 Figure 38. Single Supply Logarithmic Volume Control WR 18 REF B 47µF FB OUTB DAC B VDD 17 20 6 1 5 1/2 SSM2135 7 R AUDIO OUT 2kΩ DGND 0.1µF +5V 0.1µF 5 100Ω +5V 47µF 2.0V 1µF +5V 1 8 2 7.5kΩ 3 2.0V 4 1/2 SSM2135 5kΩ Figure 37. Digital Volume Control –10– REV. D SSM2135 SPICE MACROMODEL *SSM2135 SPICE Macro-Model 9/92, Rev. A * JCB/ADI *Copyright 1993 by Analog Devices, Inc. * *Node Assignments * * Noninverting Input * Inverting Input * Positive Supply * Negative Supply * Output .SUBCKT SSM2135 3 2 7 4 6 * * INPUT STAGE R3 4 19 1.5E3 R4 4 20 1.5E3 C1 19 20 5.311E–12 I1 7 18 106E–6 IOS 2 3 25E–09 EOS 12 5 POLY(1) 51 4 25E–06 1 Q1 19 3 18 PNP1 Q2 20 12 18 PNP1 CIN 3 2 3E–12 D1 3 1 DY D2 2 1 DY EN 5 2 22 0 1 GN1 0 2 25 0 1E–5 GN2 0 3 28 0 1E–5 * * VOLTAGE NOISE SOURCE WITH FLICKER NOISE DN1 21 22 DEN DN2 22 23 DEN VN1 21 0 DC 2 VN2 0 23 DC 2 * * CURRENT NOISE SOURCE WITH FLICKER NOISE DN3 24 25 DIN DN4 25 26 DIN VN3 24 0 DC 2 VN4 0 26 DC 2 * * SECOND CURRENT NOISE SOURCE DN5 27 28 DIN DN6 28 29 DIN VN5 27 0 DC 2 VN6 0 29 DC 2 * * GAIN STAGE & DOMINANT POLE AT .2000E+01 HZ G2 34 36 19 20 2.65E–04 R7 34 36 39E+06 V3 35 4 DC 6 D4 36 35 DX VB2 34 4 1.6 * * SUPPLY/2 GENERATOR ISY 7 4 0.2E–3 R10 7 60 40E+3 R11 60 4 40E+3 C3 60 0 1E–9 * REV. D * CMRR STAGE & POLE AT 6 kHZ ECM 50 4 POLY(2) 3 60 2 60 0 1.6 1.6 CCM 50 51 26.5E–12 RCM1 50 51 1E6 RCM2 51 4 1 * * OUTPUT STAGE R12 37 36 1E3 R13 38 36 500 C4 37 6 20E–12 C5 38 39 20E–12 M1 39 36 4 4 MN L=9E–6 W=1000E–6 AD=15E–9 AS=15E–9 M2 45 36 4 4 MN L=9E–6 W=1000E–6 AD=15E–9 AS=15E–9 5 39 47 DX D6 47 45 DX Q3 39 40 41 QPA 8 VB 7 40 DC 0.861 R14 7 41 375 Q4 41 7 43 QNA 1 R17 7 43 15 Q5 43 39 6 QNA 20 Q6 46 45 6 QPA 20 R18 46 4 15 Q7 36 46 4 QNA 1 M3 6 36 4 4 MN L=9E–6 W=2000E–6 AD=30E–9 AS=30E–9 * * NONLINEAR MODELS USED * .MODEL DX D (IS=1E–15) .MODEL DY D (IS=1E–15 BV=7) .MODEL PNP1 PNP (BF=220) .MODEL DEN D(IS=1E–12 RS=1016 KF=3.278E–15 AF=1) .MODEL DIN D(IS=1E–12 RS=100019 KF=4.173E–15 AF=1) .MODEL QNA NPN(IS=1.19E–16 BF=253 VAF=193 VAR=15 RB=2.0E3 + IRB=7.73E–6 RBM=132.8 RE=4 RC=209 CJE=2.1E–13 VJE=0.573 + MJE =0.364 CJC=1.64E–13 VJC=0.534 MJC=0.5 CJS=1.37E–12 + VJS=0.59 MJS=0.5 TF=0.43E–9 PTF=30) .MODEL QPA PNP(IS=5.21E–17 BF=131 VAF=62 VAR=15 RB=1.52E3 + IRB=1.67E 5–RBM=368.5 RE=6.31 RC=354.4 CJE=1.1E–13 + VJE=0.745 MJE=0.33 CJC=2.37E–13 VJC=0.762 MJC=0.4 + CJS=7.11E–13 VJS=0.45 MJS=0.412 TF=1.0E–9 PTF=30) .MODEL MN NMOS(LEVEL=3 VTO=1.3 RS=0.3 RD=0.3 TOX=8.5E–8 + LD=1.48E–6WD=1E–6 NSUB=1.53E16UO=650 DELTA= 10VMAX=2E5 + XJ=1.75E–6 KAPPA=0.8 ETA=0.066 THETA=0.01TPG=1 CJ=2.9E–4 + PB=0.837 MJ=0.407 CJSW=0.5E–9 MJSW=0.33) * .ENDS SSM-2135 –11– SSM2135 OUTLINE DIMENSIONS Dimensions shown in inches and (mm). 8 C1772a–10–10/97 8-Lead Plastic DIP (N-8) 5 0.280 (7.11) 0.240 (6.10) 1 4 0.070 (1.77) 0.045 (1.15) 0.430 (10.92) 0.348 (8.84) 0.325 (8.25) 0.300 (7.62) 0.015 (0.381) TYP 0.210 (5.33) MAX 0.195 (4.95) 0.115 (2.93) 0.130 (3.30) MIN 0.160 (4.06) 0.115 (2.93) 0.100 (2.54) BSC 0.022 (0.558) 0.014 (0.356) SEATING PLANE 0.015 (0.381) 0.008 (0.204) 0°- 15° 8-Lead Narrow-Body (SO-8) 8 5 0.2440 (6.20) 0.2284 (5.80) 0.1574 (4.00) 0.1497 (3.80) 4 1 0.1968 (5.00) 0.1890 (4.80) 0.0098 (0.25) 0.0040 (0.10) 0.0688 (1.75) 0.0532 (1.35) 0.0196 (0.50) × 45° 0.0099 (0.25) 0°- 8° 0.0500 (1.27) 0.0160 (0.41) PRINTED IN U.S.A. 0.0500 (1.27) BSC 0.0192 (0.49) SEATING 0.0138 (0.35) PLANE 0.0098 (0.25) 0.0075 (0.19) –12– REV. D