SM73304,SM73305 SM73304 SM73305 Dual and Single Precision, 17 MHz, Low Noise, CMOS Input Amplifiers with Enable Literature Number: SNOSB98 Dual and Single Precision, 17 MHz, Low Noise, CMOS Input Amplifiers with Enable General Description Features The SM73304/SM73305 are dual and single low noise, low offset, CMOS input, rail-to-rail output precision amplifiers with a high gain bandwidth product and an enable pin. The SM73304/SM73305 are ideal for a variety of instrumentation applications. Utilizing a CMOS input stage, the SM73304/SM73305 achieve an input bias current of 100 fA, an input referred voltage noise of 5.8 nV/√Hz, and an input offset voltage of less than ±150 μV. These features make the SM73304/SM73305 superior choices for precision applications. Consuming only 1.15 mA of supply current, the SM73305 offers a high gain bandwidth product of 17 MHz, enabling accurate amplification at high closed loop gains. The SM73304/SM73305 have a supply voltage range of 1.8V to 5.5V, which makes these ideal choices for portable low power applications with low supply voltage requirements. In order to reduce the already low power consumption the SM73304/SM73305 have an enable function. Once in shutdown, the SM73304/SM73305 draw only 140 nA of supply current. The SM73304/SM73305 are built with National’s advanced VIP50 process technology. The SM73305 is offered in a 6-pin TSOT23 package and the SM73304 is offered in a 10-pin MSOP. Unless otherwise noted, typical values at VS = 5V. ■ Renewable Energy Grade ±150 μV (max) ■ Input offset voltage 100 fA ■ Input bias current 5.8 nV/√Hz ■ Input voltage noise 17 MHz ■ Gain bandwidth product 1.15 mA ■ Supply current (SM73305) 1.30 mA ■ Supply current (SM73304) 1.8V to 5.5V ■ Supply voltage range 0.001% ■ THD+N @ f = 1 kHz −40°C to 125°C ■ Operating temperature range ■ Rail-to-rail output swing ■ Space saving TSOT23 package (SM73305) ■ 10-pin MSOP package (SM73304) Applications ■ ■ ■ ■ Photovoltaic Electronics Active filters and buffers Sensor interface applications Transimpedance amplifiers Typical Performance Offset Voltage Distribution Input Referred Voltage Noise 30159422 © 2011 Texas Instruments Incorporated 301594 30159439 www.ti.com SM73304/SM73305 Precision, 17 MHz, Low Noise, CMOS Input Amplifiers with Enable October 5, 2011 SM73304 SM73305 SM73304/SM73305 Soldering Information Infrared or Convection (20 sec) Wave Soldering Lead Temp. (10 sec) Absolute Maximum Ratings (Note 1) If Military/Aerospace specified devices are required, please contact the Texas Instruments Sales Office/ Distributors for availability and specifications. ESD Tolerance (Note 2) Human Body Model Machine Model Charge-Device Model VIN Differential Supply Voltage (VS = V+ – V−) Voltage on Input/Output Pins Storage Temperature Range Junction Temperature (Note 3) Operating Ratings (Note 1) Temperature Range (Note 3) Supply Voltage (VS = V+ – V−) 2000V 200V 1000V ±0.3V 6.0V V+ +0.3V, V− −0.3V −65°C to 150°C +150°C 235°C 260°C −40°C to 125°C 0°C ≤ TA ≤ 125°C 1.8V to 5.5V −40°C ≤ TA ≤ 125°C 2.0V to 5.5V Package Thermal Resistance (θJA(Note 3)) 6-Pin TSOT23 10-Pin MSOP 170°C/W 236°C/W 2.5V Electrical Characteristics Unless otherwise specified, all limits are guaranteed for TA = 25°C, V+ = 2.5V, V− = 0V ,VO = VCM = V+/2, VEN = V+. Boldface limits apply at the temperature extremes. Symbol Parameter Conditions Min (Note 5) Typ (Note 4) Max (Note 5) Units ±180 ±480 μV ±4 μV/°C VOS Input Offset Voltage ±20 TC VOS Input Offset Voltage Temperature Drift SM73305 (Note 6, Note 8) SM73304 –1 IB Input Bias Current –1.75 VCM = 1.0V (Note 7, Note 8) −40°C ≤ TA ≤ 85°C 0.05 1 25 −40°C ≤ TA ≤ 125°C 0.05 1 100 0.006 0.5 50 IOS Input Offset Current VCM = 1.0V (Note 8) CMRR Common Mode Rejection Ratio 0V ≤ VCM ≤ 1.4V 83 80 100 PSRR Power Supply Rejection Ratio 2.0V ≤ V+ ≤ 5.5V V− = 0V, VCM = 0 85 80 100 1.8V ≤ V+ ≤ 5.5V V− = 0V, VCM = 0 85 98 CMVR Common Mode Voltage Range CMRR ≥ 80 dB −0.3 –0.3 CMRR ≥ 78 dB AVOL Open Loop Voltage Gain SM73305, VO = 0.15 to 2.2V RL = 2 kΩ to V+/2 SM73304, VO = 0.15 to 2.2V RL = 2 kΩ to V+/2 SM73305, VO = 0.15 to 2.2V RL = 10 kΩ to V+/2 SM73304, VO = 0.15 to 2.2V RL = 10 kΩ to VOUT Output Voltage Swing High Output Voltage Swing Low www.ti.com V+/2 98 84 80 92 92 88 110 90 86 95 dB V dB RL = 2 kΩ to V+/2 25 70 77 RL = 10 kΩ to V+/2 20 60 66 RL = 2 kΩ to V+/2 30 70 73 RL = 10 kΩ to V+/2 15 60 62 2 pA dB 1.5 1.5 88 82 pA mV from either rail IOUT IS Min (Note 5) Typ (Note 4) Sourcing to V− VIN = 200 mV (Note 9) 36 30 52 Sinking to V+ VIN = −200 mV (Note 9) 7.5 5.0 15 Parameter Output Current Supply Current Conditions SM73305 1.30 1.65 1.10 1.50 1.85 0.03 1 4 Enable Mode VEN ≥ 2.1 Shutdown Mode (per channel) VEN ≤ 0.4 SR Slew Rate GBW Gain Bandwidth en Input Referred Voltage Noise Density AV = +1, Rising (10% to 90%) 8.3 AV = +1, Falling (90% to 10%) 10.3 f = 400 Hz 6.8 f = 1 kHz 5.8 f = 1 kHz 0.01 Units mA 0.95 Enable Mode VEN ≥ 2.1 SM73304 (per channel) Max (Note 5) mA μA V/μs 14 MHz nV/ in Input Referred Current Noise Density ton Turn-on Time 140 ns toff Turn-off Time 1000 ns VEN Enable Pin Voltage Range Enable Mode 2.1 Shutdown Mode IEN THD+N Enable Pin Input Current Total Harmonic Distortion + Noise pA/ 2 - 2.5 0 - 0.5 0.4 1.5 3.0 VEN = 0V (Note 7) 0.003 0.1 f = 1 kHz, AV = 1, RL = 100 kΩ VO = 0.9 VPP 0.003 f = 1 kHz, AV = 1, RL = 600Ω VO = 0.9 VPP 0.004 VEN = 2.5V (Note 7) V μA % 5V Electrical Characteristics Unless otherwise specified, all limits are guaranteed for TA = 25°C, V+ = 5V, V− = 0V, VCM = V+/2, VEN = V+. Boldface limits apply at the temperature extremes. Symbol Parameter Conditions Min (Note 5) Typ (Note 4) Max (Note 5) Units ±150 ±450 μV ±4 μV/°C VOS Input Offset Voltage ±10 TC VOS Input Offset Voltage Temperataure Drift SM73305 (Note 6, Note 8) SM73304 –1 IB Input Bias Current –1.75 VCM = 2.0V (Note 7, Note 8) −40°C ≤ TA ≤ 85°C 0.1 1 25 −40°C ≤ TA ≤ 125°C 0.1 1 100 0.01 0.5 50 IOS Input Offset Current VCM = 2.0V (Note 8) CMRR Common Mode Rejection Ratio 0V ≤ VCM ≤ 3.7V 85 82 100 PSRR Power Supply Rejection Ratio 2.0V ≤ V+ ≤ 5.5V V− = 0V, VCM = 0 85 80 100 1.8V ≤ V+ ≤ 5.5V V− = 0V, VCM = 0 85 98 3 pA pA dB dB www.ti.com SM73304/SM73305 Symbol SM73304/SM73305 Symbol CMVR Parameter Common Mode Voltage Range Conditions CMRR ≥ 80 dB Open Loop Voltage Gain SM73305, VO = 0.3 to 4.7V RL = 2 kΩ to V+/2 SM73304, VO = 0.3 to 4.7V RL = 2 kΩ to V+/2 SM73305, VO = 0.3 to 4.7V RL = 10 kΩ to V+/2 SM73304, VO = 0.3 to 4.7V RL = 10 kΩ to V+/2 VOUT Output Voltage Swing High Output Voltage Swing Low IOUT IS Output Current Supply Current Typ (Note 4) −0.3 –0.3 CMRR ≥ 78 dB AVOL Min (Note 5) 88 82 107 84 80 90 92 88 110 90 86 95 Gain Bandwidth Input Referred Voltage Noise Density dB RL = 10 kΩ to V+/2 22 60 66 RL = 2 kΩ to V+/2 (SM73305) 42 70 73 RL = 2 kΩ to V+/2 (SM73304) 50 75 78 RL = 10 kΩ to V+/2 20 60 62 Sourcing to V− VIN = 200 mV (Note 9) 46 38 66 Sinking to V+ VIN = −200 mV (Note 9) 10.5 6.5 23 SM73305 Shutdown Mode VEN ≤ 0.4 (per channel) en V 70 77 1.40 1.75 1.30 1.70 2.05 0.14 1 4 AV = +1, Rising (10% to 90%) 6.0 9.5 AV = +1, Falling (90% to 10%) 7.5 11.5 7.0 f = 1 kHz 5.8 f = 1 kHz 0.01 mA μA V/μs 17 f = 400 Hz mV from either rail mA 1.15 Enable Mode VEN ≥ 4.6 GBW 4 4 32 Enable Mode VEN ≥ 4.6 Slew Rate Units RL = 2 kΩ to V+/2 SM73304 (per channel) SR Max (Note 5) MHz nV/ in Input Referred Current Noise Density ton Turn-on Time 110 ns toff Turn-off Time 800 ns VEN Enable Pin Voltage Range Enable Mode 4.6 Shutdown Mode IEN THD+N www.ti.com Enable Pin Input Current Total Harmonic Distortion + Noise pA/ 4.5 – 5 0 – 0.5 0.4 VEN = 5V (Note 7) 5.6 10 VEN = 0V (Note 7) 0.005 0.2 f = 1 kHz, AV = 1, RL = 100 kΩ VO = 4 VPP 0.001 f = 1 kHz, AV = 1, RL = 600Ω VO = 4 VPP 0.004 4 V μA % Note 2: Human Body Model, applicable std. MIL-STD-883, Method 3015.7. Machine Model, applicable std. JESD22-A115-A (ESD MM std. of JEDEC) Field-Induced Charge-Device Model, applicable std. JESD22-C101-C (ESD FICDM std. of JEDEC). Note 3: The maximum power dissipation is a function of TJ(MAX), θJA. The maximum allowable power dissipation at any ambient temperature is PD = (TJ(MAX) - TA)/θJA. All numbers apply for packages soldered directly onto a PC Board. Note 4: Typical values represent the most likely parametric norm as determined at the time of characterization. Actual typical values may vary over time and will also depend on the application and configuration. The typical values are not tested and are not guaranteed on shipped production material. Note 5: Limits are 100% production tested at 25°C. Limits over the operating temperature range are guaranteed through correlations using the Statistical Quality Control (SQC) method. Note 6: Offset voltage average drift is determined by dividing the change in VOS at the temperature extremes by the total temperature change. Note 7: Positive current corresponds to current flowing into the device. Note 8: This parameter is guaranteed by design and/or characterization and is not tested in production. Note 9: The short circuit test is a momentary open loop test. Connection Diagrams 6-Pin TSOT23 10-Pin MSOP 30159401 Top View 30159402 Top View Ordering Information Package Part Number Package Marking SM73305MK 6-Pin TSOT23 SM73305MKE SC8B 250 Units Tape and Reel SM73305MKX SM73304MME NSC Drawing MK06A 3k Units Tape and Reel SM73304MM 10-Pin MSOP Transport Media 1k Units Tape and Reel 1k Units Tape and Reel SC8B 250 Units Tape and Reel SM73304MMX MUB10A 3.5k Units Tape and Reel 5 www.ti.com SM73304/SM73305 Note 1: Absolute Maximum Ratings indicate limits beyond which damage to the device may occur. Operating Ratings indicate conditions for which the device is intended to be functional, but specific performance is not guaranteed. For guaranteed specifications and the test conditions, see the Electrical Characteristics Tables. SM73304/SM73305 Typical Performance Characteristics Unless otherwise noted: TA = 25°C, VS = 5V, VCM = VS/2, VEN = V+. Offset Voltage Distribution TCVOS Distribution (SM73305) 30159403 30159481 Offset Voltage Distribution TCVOS Distribution (SM73304) 30159422 30159480 Offset Voltage vs. VCM Offset Voltage vs. VCM 30159410 www.ti.com 30159411 6 SM73304/SM73305 Offset Voltage vs. VCM Offset Voltage vs. Supply Voltage 30159421 30159412 Offset Voltage vs. Temperature CMRR vs. Frequency 30159456 30159409 Input Bias Current Over Temperature Input Bias Current Over Temperature 30159423 30159424 7 www.ti.com SM73304/SM73305 Supply Current vs. Supply Voltage (SM73305) Supply Current vs. Supply Voltage (SM73304) 30159405 30159477 Supply Current vs. Supply Voltage (Shutdown) Crosstalk Rejection Ratio (SM73304) 30159476 30159406 Supply Current vs. Enable Pin Voltage (SM73305) Supply Current vs. Enable Pin Voltage (SM73305) 30159408 www.ti.com 30159407 8 Supply Current vs. Enable Pin Voltage (SM73304) 30159478 30159479 Sourcing Current vs. Supply Voltage Sinking Current vs. Supply Voltage 30159420 30159419 Sourcing Current vs. Output Voltage Sinking Current vs. Output Voltage 30159450 30159454 9 www.ti.com SM73304/SM73305 Supply Current vs. Enable Pin Voltage (SM73304) SM73304/SM73305 Output Swing High vs. Supply Voltage Output Swing Low vs. Supply Voltage 30159417 30159415 Output Swing High vs. Supply Voltage Output Swing Low vs. Supply Voltage 30159416 30159414 Output Swing High vs. Supply Voltage Output Swing Low vs. Supply Voltage 30159418 www.ti.com 30159413 10 SM73304/SM73305 Open Loop Frequency Response Open Loop Frequency Response 30159473 30159441 Phase Margin vs. Capacitive Load Phase Margin vs. Capacitive Load 30159445 30159446 Overshoot and Undershoot vs. Capacitive Load Slew Rate vs. Supply Voltage 30159430 30159429 11 www.ti.com SM73304/SM73305 Small Signal Step Response Large Signal Step Response 30159438 30159437 Small Signal Step Response Large Signal Step Response 30159434 30159433 THD+N vs. Output Voltage THD+N vs. Output Voltage 30159426 www.ti.com 30159404 12 SM73304/SM73305 THD+N vs. Frequency THD+N vs. Frequency 30159457 30159455 PSRR vs. Frequency Time Domain Voltage Noise 30159482 30159428 Input Referred Voltage Noise vs. Frequency Closed Loop Frequency Response 30159439 30159436 13 www.ti.com SM73304/SM73305 Closed Loop Output Impedance vs. Frequency 30159432 CAPACITIVE LOAD The unity gain follower is the most sensitive configuration to capacitive loading. The combination of a capacitive load placed directly on the output of an amplifier along with the output impedance of the amplifier creates a phase lag which in turn reduces the phase margin of the amplifier. If phase margin is significantly reduced, the response will be either underdamped or the amplifier will oscillate. The SM73304/SM73305 can directly drive capacitive loads of up to 120 pF without oscillating. To drive heavier capacitive loads, an isolation resistor, RISO in Figure 1, should be used. This resistor and CL form a pole and hence delay the phase lag or increase the phase margin of the overall system. The larger the value of RISO, the more stable the output voltage will be. However, larger values of RISO result in reduced output swing and reduced output current drive. Application Notes SM73304/SM73305 The SM73304/SM73305 are dual and single, low noise, low offset, rail-to-rail output precision amplifiers with a wide gain bandwidth product of 17 MHz and low supply current. The wide bandwidth makes the SM73304/SM73305 ideal choices for wide-band amplification in portable applications. The low supply current along with the enable feature that is built-in on the SM73304/SM73305 allows for even more power efficient designs by turning the device off when not in use. The SM73304/SM73305 are superior for sensor applications. The very low input referred voltage noise of only 5.8 nV/ at 1 kHz and very low input referred current noise of only 10 mean more signal fidelity and higher signal-to-noise fA/ ratio. The SM73304/SM73305 have a supply voltage range of 1.8V to 5.5V over a wide temperature range of 0°C to 125°C. This is optimal for low voltage commercial applications. For applications where the ambient temperature might be less than 0° C, the SM73304/SM73305 are fully operational at supply voltages of 2.0V to 5.5V over the temperature range of −40°C to 125°C. The outputs of the SM73304/SM73305 swing within 25 mV of either rail providing maximum dynamic range in applications requiring low supply voltage. The input common mode range of the SM73304/SM73305 extends to 300 mV below ground. This feature enables users to utilize this device in single supply applications. The use of a very innovative feedback topology has enhanced the current drive capability of the SM73304/SM73305, resulting in sourcing currents as much as 47 mA with a supply voltage of only 1.8V. The SM73305 is offered in the space saving TSOT23 package and the SM73304 is offered in a 10-pin MSOP. These small packages are ideal solutions for applications requiring minimum PC board footprint. National Semiconductor is heavily committed to precision amplifiers and the market segments they serves. Technical support and extensive characterization data is available for sensitive applications or applications with a constrained error budget. www.ti.com 30159461 FIGURE 1. Isolating Capacitive Load INPUT CAPACITANCE CMOS input stages inherently have low input bias current and higher input referred voltage noise. The SM73304/SM73305 enhance this performance by having the low input bias current of only 50 fA, as well as, a very low input referred voltage noise of 5.8 nV/ . In order to achieve this a larger input stage has been used. This larger input stage increases the input capacitance of the SM73304/SM73305. Figure 2 shows typical input common mode input capacitance of the SM73304/SM73305. 14 30159475 FIGURE 2. Input Common Mode Capacitance This input capacitance will interact with other impedances such as gain and feedback resistors, which are seen on the inputs of the amplifier to form a pole. This pole will have little or no effect on the output of the amplifier at low frequencies and under DC conditions, but will play a bigger role as the frequency increases. At higher frequencies, the presence of this pole will decrease phase margin and also causes gain peaking. In order to compensate for the input capacitance, care must be taken in choosing feedback resistors. In addition to being selective in picking values for the feedback resistor, a capacitor can be added to the feedback path to increase stability. The DC gain of the circuit shown in Figure 3 is simply −R2/ R1. 30159459 FIGURE 4. Closed Loop Frequency Response As mentioned before, adding a capacitor to the feedback path will decrease the peaking. This is because CF will form yet another pole in the system and will prevent pairs of poles, or complex conjugates from forming. It is the presence of pairs of poles that cause the peaking of gain. Figure 5 shows the frequency response of the schematic presented in Figure 3 with different values of CF. As can be seen, using a small value capacitor significantly reduces or eliminates the peaking. 30159464 FIGURE 3. Compensating for Input Capacitance For the time being, ignore CF. The AC gain of the circuit in Figure 3 can be calculated as follows: 30159460 FIGURE 5. Closed Loop Frequency Response TRANSIMPEDANCE AMPLIFIER In many applications, the signal of interest is a very small amount of current that needs to be detected. Current that is transmitted through a photodiode is a good example. Barcode scanners, light meters, fiber optic receivers, and industrial sensors are some typical applications utilizing photodiodes (1) This equation is rearranged to find the location of the two poles: 15 www.ti.com SM73304/SM73305 (2) As shown in Equation 2, as the values of R1 and R2 are increased, the magnitude of the poles are reduced, which in turn decreases the bandwidth of the amplifier. Figure 4 shows the frequency response with different value resistors for R1 and R2. Whenever possible, it is best to chose smaller feedback resistors. SM73304/SM73305 for current detection. This current needs to be amplified before it can be further processed. This amplification is performed using a current-to-voltage converter configuration or transimpedance amplifier. The signal of interest is fed to the inverting input of an op amp with a feedback resistor in the current path. The voltage at the output of this amplifier will be equal to the negative of the input current times the value of the feedback resistor. Figure 6 shows a transimpedance amplifier configuration. CD represents the photodiode parasitic capacitance and CCM denotes the common-mode capacitance of the amplifier. The presence of all of these capacitances at higher frequencies might lead to less stable topologies at higher frequencies. Care must be taken when designing a transimpedance amplifier to prevent the circuit from oscillating. With a wide gain bandwidth product, low input bias current and low input voltage and current noise, the SM73304/ SM73305 are ideal for wideband transimpedance applications. 30159431 FIGURE 7. Modified Transimpedance Amplifier SENSOR INTERFACE The SM73304/SM73305 have low input bias current and low input referred noise, which make them ideal choices for sensor interfaces such as thermopiles, Infra Red (IR) thermometry, thermocouple amplifiers, and pH electrode buffers. Thermopiles generate voltage in response to receiving radiation. These voltages are often only a few microvolts. As a result, the operational amplifier used for this application needs to have low offset voltage, low input voltage noise, and low input bias current. Figure 8 shows a thermopile application where the sensor detects radiation from a distance and generates a voltage that is proportional to the intensity of the radiation. The two resistors, RA and RB, are selected to provide high gain to amplify this signal, while CF removes the high frequency noise. 30159469 FIGURE 6. Transimpedance Amplifier A feedback capacitance CF is usually added in parallel with RF to maintain circuit stability and to control the frequency response. To achieve a maximally flat, 2nd order response, RF and CF should be chosen by using Equation 3 30159427 (3) FIGURE 8. Thermopile Sensor Interface Calculating CF from Equation 3 can sometimes result in capacitor values which are less than 2 pF. This is especially the case for high speed applications. In these instances, its often more practical to use the circuit shown in Figure 7 in order to allow more sensible choices for CF. The new feedback capacitor, C′F, is (1+ RB/RA) CF. This relationship holds as long as RA << RF. www.ti.com PRECISION RECTIFIER Rectifiers are electrical circuits used for converting AC signals to DC signals. Figure 9 shows a full-wave precision rectifier. Each operational amplifier used in this circuit has a diode on its output. This means for the diodes to conduct, the output of the amplifier needs to be positive with respect to ground. If VIN is in its positive half cycle then only the output of the bottom amplifier will be positive. As a result, the diode on the output of the bottom amplifier will conduct and the signal will show at the output of the circuit. If VIN is in its negative half cycle then the output of the top amplifier will be positive, resulting in the diode on the output of the top amplifier conducting and, delivering the signal on the amplifier's output to the circuits output. For R2/ R1 ≥ 2, the resistor values can be found by using the equation shown in Figure 9. If R2/ R1 = 1, then R3 should be 16 SM73304/SM73305 left open, no resistor needed, and R4 should simply be shorted. 30159474 FIGURE 9. Precision Rectifier 17 www.ti.com SM73304/SM73305 Physical Dimensions inches (millimeters) unless otherwise noted 6-Pin TSOT23 NS Package Number MK06A 10-Pin MSOP NS Package Number MUB10A www.ti.com 18 SM73304/SM73305 Notes 19 www.ti.com SM73304/SM73305 Precision, 17 MHz, Low Noise, CMOS Input Amplifiers with Enable Notes TI/NATIONAL INTERIM IMPORTANT NOTICE Texas Instruments has purchased National Semiconductor. As of Monday, September 26th, and until further notice, products sold or advertised under the National Semiconductor name or logo, and information, support and interactions concerning such products, remain subject to the preexisting National Semiconductor standard terms and conditions of sale, terms of use of website, and Notices (and/or terms previously agreed in writing with National Semiconductor, where applicable) and are not subject to any differing terms and notices applicable to other TI components, sales or websites. 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