FREESCALE MC33215

Freescale Semiconductor, Inc.Order this document by MC33215/D
Freescale Semiconductor, Inc...
52 1
FB SUFFIX
PLASTIC PACKAGE
CASE 848B
(TQFP–52)
The MC33215 is developed for use in fully electronic telephone sets with
speakerphone functions. The circuit performs the ac and dc line termination,
2–4 wire conversion, line length AGC and DTMF transmission. The
speakerphone part includes a half duplex controller with signal and noise
monitoring, base microphone and loudspeaker amplifiers and an efficient
supply. The circuit is designed to operate at low line currents down to 4.0 mA
enabling parallel operation with a classical telephone set.
•
•
•
•
•
•
•
•
Highly Integrated Cost Effective Solution
Straightforward AC and DC Parameter Adjustments
42
Efficient Supply for Loudspeaker Amplifier and Peripherals
Stabilized Supply Point for Handset Microphone
1
Stabilized Supply Point for Base Microphone
B SUFFIX
PLASTIC PACKAGE
CASE 858
(SDIP–42)
Loudspeaker Amplifier can be Powered and Used Separately
Smooth Switch–Over from Handset to Speakerphone Operation
Adjustable Switching Depth for Handsfree Operation
ORDERING INFORMATION
Device
Operating
Temperature Range
TQFP–52
MC33215FB
MC33215B
Package
TA = –20° to +70°C
SDIP–42
Simplified Application
AC
Impedance
DC Offset
Line Current
Telephone
Line
DTMF
MF
Handset
Microphone
HM
Base
Microphone
BM
VCC Supply
Attenuator
Line
Driver
DC Slope
Duplex
Controller
VCC or
External Supply
Base Loudspeaker
Current
Splitter
1:10
LS
Attenuator
Receive Signal
Rx
Handset Earpiece
Auxiliary Input
This device contains 2782 active transistors.
This document contains information on a new product. Specifications and information herein
are subject to change without notice.
 Motorola, Inc. 1997
MOTOROLA ANALOG IC DEVICEFor
DATA
More Information On This Product,
Go to: www.freescale.com
Rev 0
1
Freescale Semiconductor,
Inc.
MC33215
FEATURES
• Separate Input for DTMF and Auxiliary Signals
• Parallel Operation Down to 4.0 mA of Line Current
Speakerphone Operation
• Handsfree Operation via Loudspeaker and Base
Microphone
• Integrated Microphone and Loudspeaker Amplifiers
• Differential Microphone Inputs
• Loudspeaker Amplifier can be Powered and Used
Separately from the Rest of the Circuit
• Integrated Switches for Smooth Switch–Over from
Handset to Speakerphone Operation
• Signal and Background Noise Monitoring in Both
Channels
• Adjustable Switching Depth for Handsfree Operation
• Switch–Over • Dial Tone Detector in the Receive Channel
Handset Operation
• Transmit and Receive Amplifiers
• Differential Microphone Inputs
• Sidetone Cancellation Network
• Line Length AGC
• Microphone and Earpiece Mute
43
42
41
40
LSB
N/C
N/C
44
VLS
45
LSO
46
PGD
47
N/C
48
VCC
49
VLN
N/C
50
VHF
51
VMC
52
N/C
Figure 1. Pin Connections
1
VCC
PGD 42
2
VLN
LSO 41
3
VHF
VLS 40
4
VMC
LSB 39
1
SLB
LSF 39
5
SLB
LSF 38
2
REG
BVO 38
6
REG
BVO 37
3
SLP
PPL 37
7
SLP
PPL 36
4
MFI
LSI 36
8
MFI
LSI 35
5
HM1
VOL 35
9
HM1
VOL 34
6
HM2
SWD 34
10 HM2
SWD 33
7
BM2
8
BM1
AGC 32
9
VDD
Gnd 31
10 TSA
RLS 30
11 TSE
RSA 29
12 TBN
RSE 28
13 MUT
RBN 27
REF 33
N/C
SPS
PRS
SWT
LSM
N/C
RXS
RXO
GRX
RXI
N/C
N/C
TQFP–52
N/C
Freescale Semiconductor, Inc...
Line Driver and Supply
• AC and DC Termination of Telephone Line
• Adjustable Set Impedance for Real and Complex
Termination
• Efficient Supply Point for Loudspeaker Amplifier and
Peripherals
• Two Stabilized Supply Points for Handset and Base
Microphones
• Separate Supply Arrangement for Handset and
Speakerphone Operation
14
15
16
17
18
19
20
21
22
23
24
25
26
(Top View)
11 BM2
SDIP–42
REF 32
12 BM1
AGC 31
13 VDD
Gnd 30
14 TSA
RLS 29
15 TSE
RSA 28
16 TBN
RSE 27
17 MUT
RBN 26
18 SPS
RXI 25
19 PRS
GRX 24
20 SWT
RXO 23
21 LSM
RXS 22
(Top View)
2
MOTOROLA ANALOG IC DEVICE DATA
For More Information On This Product,
Go to: www.freescale.com
Freescale Semiconductor,
Inc.
MC33215
MAXIMUM RATINGS
Rating
Min
Max
Unit
–0.5
12
V
–
160
mA
Voltage at VLS (if Powered Separately)
–0.5
12
V
Voltage at VHF (if Externally Applied)
–0.5
5.5
V
Voltage at SPS, MUT, PRS, LSM
–0.5
7.5
V
–
150
°C
–65
150
°C
Peak Voltage at VLN
Maximum Loop Current
Maximum Junction Temperature
Storage Temperature Range
NOTE:
ESD data available upon request.
RECOMMENDED OPERATING CONDITIONS
Freescale Semiconductor, Inc...
Characteristic
Min
Max
Unit
Biasing Voltage at VLN
2.4
10
V
Loop Current
4.0
130
mA
Voltage at VLS
2.4
8.0
V
Voltage at VHF (if Externally Applied)
2.4
5.0
V
0
5.0
V
–20
70
°C
Voltage at SPS, MUT, PRS, LSM
Operating Ambient Temperature Range
ELECTRICAL CHARACTERISTICS (All parameters are specified at T = 25°C, Iline = 18 mA, VLS = 2.9 V, f = 1000 Hz,
PRS = high, MUT = high, SPS = low, LSM = high, test figure in Figure 17 with S1 in position 1, unless otherwise stated.)
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Characteristic
Min
Typ
Max
Unit
–
3.9
4.8
2.4
4.2
5.2
–
4.5
5.6
–
1.2
1.5
mA
DC Voltage at VMC (= VMC0)
1.6
1.75
1.9
V
Current Available from VMC
VMC = VMC0 – 200 mV
1.0
–
–
mA
2.6
2.8
3.0
V
–
1.4
2.0
mA
2.0
–
–
mA
Current Available from VCC
VCC = 2.4 V, Iline = 20 mA
13
15
–
mA
DC Voltage Drop Between VLN and VCC
Iline = 20 mA
–
1.0
1.5
V
–
1.0
1.5
mA
DC LINE VOLTAGE
Line Voltage Vline
Parallel Operation, Iline = 4.0 mA
Iline = 20 mA
Iline = 70 mA
V
SUPPLY POINT VDD
Internal Current Consumption from VDD
VDD = 2.5 V
SUPPLY POINT VMC
SUPPLY POINT VHF
DC Voltage at VHF (= VHF0)
Internal Current Consumption from VHF
VHF = VHF0 + 100 mV
Current Available from VHF
VHF = VHF0 – 300 mV
SUPPLY POINT VCC
SUPPLY INPUT VLS
Internal Current Consumption from VLS
MOTOROLA ANALOG IC DEVICEFor
DATA
More Information On This Product,
Go to: www.freescale.com
3
Freescale Semiconductor,
Inc.
MC33215
ELECTRICAL CHARACTERISTICS (continued) (All parameters are specified at T = 25°C, Iline = 18 mA, VLS = 2.9 V, f = 1000 Hz,
PRS = high, MUT = high, SPS = low, LSM = high, test figure in Figure 17 with S1 in position 1, unless otherwise stated.)
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Characteristic
Min
Typ
Max
Unit
Logic Low Level Pins PRS, MUT, SPS, LSM
–
–
0.4
V
Logic High Level Pins PRS, MUT, SPS, LSM
2.0
–
5.0
V
Internal Pull Up Pins PRS, MUT, LSM
–
100
–
kΩ
Internal Pull Down Pin SPS
–
100
–
kΩ
Voltage Gain from VHM to Vline
VHM = 1.5 mVrms
46
47
48
dB
Gain Reduction in Mute Condition
MUT = Low or PRS = Low or SPS = High
60
–
–
dB
Input Impedance at HM1 and HM2
14
18
22
kΩ
Common Mode Rejection Ratio
–
50
–
dB
Total Harmonic Distortion at VLN
VHM = 4.5 mVrms
–
–
2.0
%
Psophometrically Weighted Noise Level at Vline
HM1 and HM2 Shorted with 200 Ω
–
–72
–
dBmp
Voltage Gain from VBM to Vline
VBM = 0.5 mVrms
53
55.5
58
dB
Input Impedance at BM1 and BM2
14
18
22
kΩ
Common Mode Rejection Ratio
–
50
–
dB
Total Harmonic Distortion at VLN
VBM = 1.5 mV
–
–
2.0
%
Psophometrically Weighted Noise Level at Vline
BM1 and BM2 Shorted with 200 Ω
–
–62
–
dBmp
Gain Reduction in Mute Condition
MUT = Low or PRS = Low or SPS = Low
60
–
–
dB
Voltage Gain from VMF to Vline
VMF = 7.5 mVrms
34
35
36
dB
Input Impedance at MFI
14
18
22
kΩ
Gain Reduction in Mute Condition
MUT = High or PRS = Low
60
–
–
dB
Voltage Gain from VRXI to VEAR (Note 1)
Vline = 20 mVrms
23
24
25
dB
Gain Reduction in Mute Condition
MUT = Low or SPS = Low
60
–
–
dB
Input Impedance at RXI
24
30
36
kΩ
Psophometrically Weighted Noise Level at VEAR
RXI Shorted to Gnd via 10 µF
–
130
–
µVrms
Confidence Level During DTMF Dialing
VMF = 7.5 mVrms, MUT = Low
10
15
20
mVrms
Output Swing Capability into 150 Ω
THD ≤2%
680
–
–
mVpp
Output Swing Capability into 450 Ω
THD ≤2%, RRXO = 360 kΩ
1800
–
–
mVpp
LOGIC INPUTS
Freescale Semiconductor, Inc...
Tx CHANNEL, HANDSET MICROPHONE AMPLIFIER
Tx CHANNEL, BASE MICROPHONE AMPLIFIER (SPS = HIGH, Tx MODE FORCED)
Tx CHANNEL, DTMF AMPLIFIER (MUT = LOW OR PRS = LOW)
Rx CHANNEL, EARPIECE AMPLIFIER
NOTE:
4
1. Corresponding to –0.6 dB gain from the line to output RXO in the typical application.
MOTOROLA ANALOG IC DEVICE DATA
For More Information On This Product,
Go to: www.freescale.com
Freescale Semiconductor,
Inc.
MC33215
ELECTRICAL CHARACTERISTICS (continued) (All parameters are specified at T = 25°C, Iline = 18 mA, VLS = 2.9 V, f = 1000 Hz,
PRS = high, MUT = high, SPS = low, LSM = high, test figure in Figure 17 with S1 in position 1, unless otherwise stated.)
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ÁÁÁÁ
Characteristic
Min
Typ
Max
Unit
Voltage Gain from VRXI to VRLS (Note 2)
Vline = 20 mVrms
21
24
27
dB
Gain Reduction in Mute Condition
SPS = Low or MUT = Low
60
–
–
dB
Voltage Gain from VLSI to VLSP
VLSI = 10 mVrms
25
26
27
dB
Attenuation at Delta RVOL = 47 kΩ
–
32
–
dB
Psophometrically Weighted Noise Level at VLSP
RXI Shorted to Gnd via 10 µF
–
1.2
–
mVrms
Confidence Level During DTMF Dialing
VMF = 7.5 mVrms MUT = Low
150
200
250
mVrms
Available Peak Current from LSO
110
–
–
mApeak
Output Capability into 25 Ω
THD ≤2%, VLSI = 55 mVrms
1.8
–
–
Vpp
Output Capability into 25 Ω
THD ≤2%, VLS = 5.0 V, VLSI = 90 mVrms
2.7
–
–
Vpp
Gain Reduction in Mute Condition
LSM = Low
60
–
–
dB
Peak–to–Peak Limiter Attack Time
VLSI Jumps from 40 mVrms to 120 mVrms
–
–
5.0
ms
Peak–to–Peak Limiter Release Time
VLSI Jumps from 120 mVrms to 40 mVrms
–
300
–
ms
THD at 10 dB Overdrive
VLSI = 120 mVrms
–
–
7.0
%
Peak–to–Peak Limiter Disable Threshold at PPL
–
–
0.1
V
4.5
6.0
7.5
dB
Gain Variation in Transmit and Receive Channel with Respect to Iline =18 mA with
AGC Disabled (AGC to VDD)
–
–
1.5
dB
Highest Line Current for Maximum Gain
–
20
–
mA
Lowest Line Current for Minimum Gain
–
50
–
mA
20
–
–
dB
–
–
28
dB
Voltage Gain from RXI to RSA
VRXI = 15 mVrms
18
20
22
dB
Voltage Gain from BMI to TSA
VBM = 0.5 mVrms
17.5
18.5
19.5
dB
Dynamic Range of Logarithmic Compression from TSA to TSE and RSA to RSE
ITSA and IRSA from 2.5 µA to 250 µA
40
–
–
dB
Envelope Tracking Between TSE and RSE and Between TBN and RBN
–
±3.0
–
dB
0.3
0.4
0.5
µA
Rx CHANNEL, LOUDSPEAKER PRE–AMPLIFIER (SPS = HIGH, Rx MODE FORCED)
Freescale Semiconductor, Inc...
Rx CHANNEL, LOUDSPEAKER AMPLIFIER
Rx CHANNEL PEAK–TO–PEAK LIMITER
AUTOMATIC GAIN CONTROL
Gain Reduction in Transmit and Receive Channel with Respect to Iline = 18 mA
Iline = 70 mA
BALANCE RETURN LOSS
Balance Return Loss with Respect to 600 Ω
SIDETONE
Voltage Gain from VHM to VEAR
S1 in Position 2
LOGARITHMIC AMPLIFIERS AND ENVELOPE DETECTORS
Maximum Source Current from TSE or RSE
NOTE:
2. Corresponding to –0.6 dB gain from the line to output RLS in the typical application.
MOTOROLA ANALOG IC DEVICEFor
DATA
More Information On This Product,
Go to: www.freescale.com
5
Freescale Semiconductor,
Inc.
MC33215
ELECTRICAL CHARACTERISTICS (continued) (All parameters are specified at T = 25°C, Iline = 18 mA, VLS = 2.9 V, f = 1000 Hz,
PRS = high, MUT = high, SPS = low, LSM = high, test figure in Figure 17 with S1 in position 1, unless otherwise stated.)
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ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁ
ÁÁÁÁ
ÁÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁ
ÁÁÁÁ
ÁÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁ
ÁÁÁÁ
ÁÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁ
ÁÁÁÁ
ÁÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁ
ÁÁÁÁ
ÁÁÁÁ
Characteristic
Min
Typ
Max
Unit
Maximum Sink Current into TSE or RSE
100
–
–
µA
Maximum Sink Current into TBN and RBN
0.7
1.0
1.3
µA
Maximum Source Current from TBN or RBN
100
–
–
µA
Dial Tone Detector Threshold at Vline
–
20
–
mVrms
Speech Noise Threshold Both Channels
–
4.5
–
dB
Switching Depth
46
50
54
dB
Adjustable Range for Switching Depth
24
–
60
dB
LOGARITHMIC AMPLIFIERS AND ENVELOPE DETECTORS
ATTENUATOR CONTROL
Freescale Semiconductor, Inc...
Gain Variation in Idle Mode for Both Channels
–
25
–
dB
Current Sourced from SWT
Tx Mode
7.0
10
13
µA
Current Sunk into SWT
Rx Mode
7.0
10
13
µA
PIN FUNCTION DESCRIPTION
Pin
ÁÁÁÁ
ÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁ
ÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁ
ÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁ
ÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁ
ÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁ
ÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁ
ÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁ
ÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁ
ÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁ
ÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁ
ÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁ
ÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁ
ÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁ
ÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁ
ÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁ
ÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁ
ÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁ
ÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁ
ÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁ
ÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁ
ÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁ
ÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁ
ÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁ
ÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁ
ÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
N
Name
D
Description
i i
SDIP–42
TQFP–52
1
47
VCC
Supply Output for Loudspeaker Amplifier and Peripherals
2
48
VLN
Line Connection Input
3
49
VHF
Supply Output for Speakerphone Section and Base Microphone
4
50
VMC
Supply Output for Handset Microphone
–
51
N/C
Not Connected
–
52
N/C
Not Connected
5
1
SLB
SLP Buffered Output
6
2
REG
Regulation of Line Voltage Adjustment
7
3
SLP
DC Slope Adjustment
8
4
MFI
DTMF Input
9
5
HM1
Handset Microphone Input 1
10
6
HM2
Handset Microphone Input 2
11
7
BM2
Base Microphone Input 2
12
8
BM1
Base Microphone Input 1
13
9
VDD
Supply Input for Speech Part
14
10
TSA
Transmit Sensitivity Adjustment
15
11
TSE
Transmit Signal Envelope Timing Adjustment
16
12
TBN
Transmit Background Noise Envelope Timing Adjustment
17
13
MUT
Transmit and Receive Mute Input
–
14
N/C
Not Connected
–
15
N/C
Not Connected
18
16
SPS
Speakerphone Select Input
19
17
PRS
Privacy Switch Input
20
18
SWT
Switch–Over Timing Adjustment
21
19
LSM
Loudspeaker Mute Input
6
MOTOROLA ANALOG IC DEVICE DATA
For More Information On This Product,
Go to: www.freescale.com
Freescale Semiconductor,
Inc.
MC33215
PIN FUNCTION DESCRIPTION (continued)
Freescale Semiconductor, Inc...
Pin
ÁÁÁÁ
ÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁ
ÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁ
ÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁ
ÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁ
ÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁ
ÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁ
ÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁ
ÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁ
ÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁ
ÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁ
ÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁ
ÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁ
ÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁ
ÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁ
ÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁ
ÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁ
ÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁ
ÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁ
ÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁ
ÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁ
ÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁ
ÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁ
ÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁ
ÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁ
ÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁ
ÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁ
ÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁ
ÁÁÁÁ
ÁÁÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
Name
Description
SDIP–42
TQFP–52
–
20
N/C
Not Connected
22
21
RXS
Receive Amplifier Stability
23
22
RXO
Receive Amplifier Output
24
23
GRX
Earpiece Amplifier Feedback Input
25
24
RXI
Receive Amplifier Input
–
25
N/C
Not Connected
–
26
N/C
Not Connected
26
27
RBN
Receive Background Noise Envelope Timing Adjustment
27
28
RSE
Receive Signal Envelope Timing Adjustment
28
29
RSA
Receive Sensitivity Adjustment
29
30
RLS
Receive Output for Loudspeaker Amplifier
30
31
Gnd
Small Signal Ground
31
32
AGC
Line Length AGC Adjustment
32
33
REF
Reference Current Set
33
34
SWD
Switching Depth Adjustment for Handsfree
34
35
VOL
Volume Control Adjustment
35
36
LSI
Loudspeaker Amplifier Input
36
37
PPL
Peak–to–Peak Limiter Timing Adjustment
37
38
BVO
Bias Voltage for Loudspeaker Amplifier Output
38
39
LSF
Loudspeaker Amplifier Feedback Input
–
40
N/C
Not Connected
–
41
N/C
Not Connected
39
42
LSB
Loudspeaker Amplifier Bootstrap Output
40
43
VLS
Supply Input for Loudspeaker Amplifier
41
44
LSO
Loudspeaker Amplifier Output
42
45
PGD
Power Ground
–
46
N/C
Not Connected
MOTOROLA ANALOG IC DEVICEFor
DATA
More Information On This Product,
Go to: www.freescale.com
7
Freescale Semiconductor,
Inc.
MC33215
DESCRIPTION OF THE CIRCUIT
Based on the typical application circuit as given in
Figure 18, the MC33215 will be described in three parts: line
driver and supplies, handset operation, and handsfree
operation. The data used refer to typical data of the
characteristics.
LINE DRIVER AND SUPPLIES
The line driver and supply part performs the ac and dc
telephone line termination and provides the necessary
supply points.
AC Set Impedance
The ac set impedance of the telephone as created by the
line driver and its external components can be approximated
with the equivalent circuit shown in Figure 2.
CVLN
10 n
CVDD
100 µ
RSLB
2.2 k
Inductor
Slope
RREG1
360 k
RREG
∞
CREG
220 n
V zener
R
x
Slope
ǒ Ǔ
1
R
SLP
+
slope
11
VLN
) RRREG1
REG2
Figure 3. Balance Return Loss
40
10 µA x R
REG2
1
Ǔ
REG1
) RRREG1
REG2
ǒǒ
+ 3.8 V ) Iline – 1.0 mA
^ 3.8 V ) Iline x 20
ǒ
Ǔ
Ǔ Ǔ
x 20
Figure 4. Influence of RREG1 and RREG2
on the DC Mask
30
.
12
25
20
RREG1 = 470 k
RREG2 = 220 k
10
15
RREG1 = 365 k
RREG2 = 220 k
8.0
VLN (V)
10
5.0
1000
10000
f, FREQUENCY (Hz)
The influence of the frequency dependent parasitic
components is seen for the lower frequencies (Inductor) and
the higher frequencies (CVLN) by a decreasing BRL value.
DC Set Impedance
The line current flowing towards the MC33215 application
is partly consumed by the circuitry connected to VDD while
the rest flows into Pin VLN. At Pin VLN, the current is split up
8
x
Ǔ
slope
In the typical application this leads to a line voltage of 4.2 V
at 20 mA of line current with a slope of 20 Ω. Adding a 1.5 V
voltage drop for the diode bridge and the interruptor, the dc
voltage at tip–ring will equal 5.7 V.
If the dc mask is to be adapted to a country specific
requirement, this can be done by adjusting the resistors
RREG1 and RREG2, as a result, the zener voltage and the
slope are varied. It is not advised to change the resistor RSLP
since this changes many parameters. The influence of RREG1
and RREG2 is shown in Figure 4.
35
0
100
ILN x R
+ 0.2 x 1 ) RRREG1 )
+ Iline – IVDD
+ RREG1 x CREG x RSLP
11
+ RSLP
11
ǒ
If RREG2 is not mounted, the term between the brackets
becomes equal to 1.
With the values shown in the typical application and under
the assumption that IVDD = 1.0 mA, the above formulas can
be simplified to:
With the component values of the typical application, the
inductor calculates as 1.6 H. Therefore, in the audio range of
300 Hz to 3400 Hz, the set impedance is mainly determined
by ZVDD. As a demonstration, the impedance matching or
Balance Return Loss BRL is shown in Figure 3.
BRL (dB)
Freescale Semiconductor, Inc...
Inductor
Zbal
With:
+ Vzener )
ǒ Ǔǒ
ǒ Ǔ
VLN
ILN
Figure 2. Equivalent of the AC impedance
ZVDD
620
into a small part for biasing the internal line drive transistor
and into a large part for supplying the speakerphone. The
ratio between these two currents is fixed to 1:10. The dc set
impedance or dc setting of the telephone as created by the
line driver and its external components can be approximated
with the equivalent of a zener voltage plus a series resistor
according to:
6.0
RREG1 = 365 k
RREG2 = Infinite
4.0
RREG1 = 470 k
RREG2 = Infinite
2.0
0
0
20
40
60
80
100
Iline (mA)
As can be seen in Figure 4, for low line currents below
10 mA, the given dc mask relations are no longer valid. This
is the result of an automatic decrease of the current drawn
MOTOROLA ANALOG IC DEVICE DATA
For More Information On This Product,
Go to: www.freescale.com
Freescale Semiconductor,
Inc.
MC33215
from Pin REG by the internal circuit (the 10 µA term in the
formulas). This built–in feature drops the line voltage and
therefore enables parallel operation.
The voltage over the line driver has to be limited to 12 V to
protect the device. A zener of 11 V at VLN is therefore the
maximum advised.
VDD Supply
The internal circuitry for the line driver and handset
interface is powered via VDD. This pin may also be used to
power peripherals like a dialer or microcontroller. The voltage
at VDD is not internally regulated and is a direct result of the
line voltage setting and the current consumption at VDD
internally (IVDD) and externally (IPER). It follows that:
Ǔ
)
VLN – I
I
x R set
DD
VDD
PER
For correct operation, it must be ensured that VDD is
biased at 1.8 V higher than SLP. This translates to a
maximum allowable voltage drop across Z VDD of
Vzener – 1.8 V. In the typical application, this results in a
maximum allowable current consumption by the peripherals
of 2.0 mA.
VMC Supply
At VMC, a stabilized voltage of 1.75 V is available for
powering the handset microphone. Due to this stabilized
supply, microphones with a low supply rejection can be used
which reduces system costs. In order to support the parallel
operation of the telephone set, the voltage at VMC will be
maintained even at very low line currents down to 4.0 mA.
Under normal supply conditions of line currents of 20 mA
and above, the supply VMC is able to deliver a guaranteed
minimum of 1.0 mA. However, for lower line currents, the
supply capability of VMC will decrease.
Figure 5. VMC Under Different Microphone Loads
1.8
1.7
Iline = 20 mA
Iline = 4.0 mA
2.7 k VMC–VHF
1.6
1.5
VMC (V)
Freescale Semiconductor, Inc...
ǒ
+
V
Iline = 4.0 mA
1.3
1.2
1.1
1.0
0.2
0.4
0.6
VHF Supply
VHF is a stabilized supply which powers the internal
duplex controller part of the MC33215, and which is also
meant to power the base microphone or other peripherals.
The base microphone however, can also be connected to
VMC, which is preferred in case of microphones with a poor
supply rejection. Another possibility is to create an additional
filter at VHF, like is shown in the typical application. The
supply capability of VHF is guaranteed as 2.0 mA for line
currents of 20 mA and greater.
Since in parallel operation not enough line current is
available to power a loudspeaker and thus having a
speakerphone working, the current internally supplied to VHF
is cut around 10 mA of line current to save current for the
handset operated part. A small hysteresis is built in to avoid
system oscillations.
When the current to VHF is cut, the voltage at VHF will
drop rapidly due to the internal consumption of 1.4 mA and
the consumption of the peripherals. When VHF drops below
2.0 V, the device internally switches to the handset mode,
neglecting the state of the speakerphone select Pin SPS.
In case an application contains a battery pack or if it is
mains supplied, speakerphone operation becomes possible
under all line current conditions. In order to avoid switch–over
to handset operation below the 10 mA, VHF has to be
supplied by this additional power source and preferably kept
above 2.4 V.
VCC Supply
At VCC the major part of the line current is available for
powering the loudspeaker amplifier and peripheral circuitry.
This supply pin should be looked at as a current source since
the voltage on VCC is not stabilized and depends on the
instantaneous line voltage and the current to and consumed
from VCC.
The maximum portion of the line current which is available
at VCC is given by the following relation:
10 x I
I
– I
– I
– I
line
VDD
VHF
VCC
VMC
11
+
1.4
0
If, during parallel operation, a high current is required from
VMC, a 2.7 k resistor between VMC and VHF can be applied.
In Figure 5, the VMC voltage under different microphone
currents, is shown.
0.8
IVMC (mA)
1.0
1.2
1.4
1.6
ǒ ǒ
ǓǓ
This formula is valid when the voltage drop from VLN to
VCC is sufficient for the current splitter to conduct all this
current to VCC. When the drop is not sufficient, the current
source saturates and the surplus of current is conducted to
the power ground PGD to avoid distortion in the line driver. In
fact, when no current is drawn from VCC, the voltage at VCC
will increase until the current splitter is in balance. In Figure 6
this behavior is depicted.
MOTOROLA ANALOG IC DEVICEFor
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9
Freescale Semiconductor,
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Figure 6. Available Current at VCC
100
3.5
90
3.0
IVCC at 98% of
IVCC(max)
80
2.5
IVCC/lline (%)
60
VLN–V CC (V)
mA AND %
70
50
40
30
Freescale Semiconductor, Inc...
0
20
40
60
80
100
VCC Open
0
20
0
40
60
80
Iline (mA)
Iline (mA)
A. Maximum Available Current at VCC
B. Voltage Drop to VCC
For instance, at a line current of 20 mA a maximum of
15 mA of current is available at VCC. If all this current is
taken, VCC will be 1.7 V below VLN. When not all this current
is drawn from VCC, but for instance only 1.0 mA for biasing of
the loudspeaker amplifier, the voltage at VCC will be 1.2 V
below VLN. Although the measurements for Figure 6 are
done with RREG1 = 365 k, the results are also globally valid
for other dc settings.
As can be seen from Figure 6, the voltage at VCC is limited
by the voltage at VLN minus 1.0 V. This means that the
voltage at VCC is limited by the external zener at VLN. If it is
necessary to limit the voltage at VCC in order to protect
peripheral circuits, a zener from VCC to Gnd can be added. If
the supply of the loudspeaker VLS is also connected to VCC,
it is advisable that VCC does not exceed 8.0 V.
The high efficiency of the VCC power supply contributes
to a high loudspeaker output power at moderate line
currents. More details on this can be found in the handsfree
operation paragraph.
HANDSET OPERATION
During handset operation, the MC33215 performs the
basic telephone functions for the handset microphone and
earpiece. It also enables DTMF transmission.
Handset Microphone Amplifier
The handset microphone is to be capacitively connected
to the circuit via the differential input HM1 and HM2. The
microphone signal is amplified by the HMIC amplifier and
modulates the line current by the injection of the signal into
the line driver. This transfer from the microphone inputs to the
line current is given as 15/(RSLP/11), which makes a total
transmit voltage gain AHM from the handset microphone
inputs to the line of:
V
Z
x Z set
line
15
A
x line
HM
V
Z
Z set
R
11
HM
line
SLP
With the typical application and Zline = 600 Ω the transmit
gain calculates as 47 dB.
In case an electret microphone is used, it can be supplied
from the stabilized microphone supply point VMC of 1.75 V
properly biased with resistors RHM1 and RHM2. This allows
the setmaker to use an electret microphone with poor supply
rejection to reduce total system costs. Since the transmit gain
AHM is fixed by the advised RSLP = 220 Ω and the constraints
of set impedance and line impedance, the transmit gain is set
+
10
VCC to VLS
1.5
0.5
10
0
2.0
1.0
IVCC(max) (mA)
20
IVCC at 50% of
IVCC(max)
+
ń
)
100
by adjusting the sensitivity of the handset microphone by
adjusting the resistors RHM1 and RHM2. It is not advised to
adjust the gain by including series resistors towards the Pins
HM1 and HM2.
A high pass filter is introduced by the coupling capacitors
CHM1 and CHM2 in combination with the input impedance. A
low pass filter can be created by putting capacitors in parallel
with the resistors RHM1 and RHM2.
The transmit noise is measured as –72 dBmp with the
handset microphone inputs loaded with a capacitively
coupled 200 Ω. In a real life application, the inputs will be
loaded with a microphone powered by VMC. Although VMC
is a stablized supply voltage, it will contain some noise which
can be coupled to the handset microphone inputs, especially
when a microphone with a poor supply rejection is used. An
additional RC filter on VMC can improve the noise figure, see
also the base microphone section.
Handset Earpiece Amplifier
The handset earpiece is to be capacitively connected to
the RXO output. Here, the receive signal is available which is
amplified from the line via the sidetone network and the Rx
and EAR amplifiers. The sidetone network attenuates the
receive signal from the line via the resistor divider composed
of RSLB and Zbal, see also the sidetone section. The
attenuation in the typical application by this network equals
24.6 dB. Then the signal from the sidetone network is
pre–amplified by the amplifier Rx with a typical gain of 6.0 dB.
This amplifier also performs the AGC and MUTE functions,
see the related paragraphs. Finally, the signal is amplified by
the noninverting voltage amplifier EAR. The overall receive
gain ARX from the line to the earpiece output then follows as:
R
V
RXO
RXO
A
x A
x 1
A
RXI
RX
ST
R
V
line
GRX
+
+
ǒ Ǔ
)
With: AST = Attenuation of the Sidetone Network
ARXI = Gain of the Pre–Amplifier Rx
For the typical application an overall gain from the line to
the earpiece is close to 0 dB.
The receive gain can be adjusted by adjusting the resistor
ratio RRXO over RGRX. However, RRXO also sets the
confidence tone level during dialing which leaves RGRX to be
chosen freely. A high pass filter is introduced by the coupling
capacitor CRXI together with the input impedance of the input
MOTOROLA ANALOG IC DEVICE DATA
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MC33215
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Sidetone Cancellation
The line driver and the receiver amplifier of the MC33215
are tied up in a bridge configuration as depicted in Figure 7.
This bridge configuration performs the so–called hybrid
function which, in the ideal case, prevents transmitted signals
from entering the receive channel.
Figure 7. Sidetone Bridge
Automatic Gain Control
To obtain more or less constant signal levels for transmit
and receive regardless of the telephone line length, both the
transmit and receive gain can be varied as a function of line
current when the AGC feature is used. The gain reduction as
a function of line current, and thus line length, is depicted in
Figure 8.
Figure 8. Automatic Gain Control
0
–1.0
RAGC = 20 k
–2.0
AGC (dB)
RXI. A second high pass filtering is introduced by the
combination of CGRX and RGRX. A low pass filter is created
by CRXO and RRXO. The coupling capacitor at the output
RXO is not used for setting a high pass filter but merely for dc
decoupling.
In combination with dynamic ear capsules, the EAR
amplifier can become unstable due to the highly inductive
characteristic of some of the capsules. To regain stability, a
100 nF capacitor can be connected from RXS to Gnd in
those cases. An additional 10 nF at the RXI input, as shown
in the typical application, improves the noise figure of the
receiver stage.
RAGC = 30 k
–3.0
–4.0
–5.0
–6.0
0
10
20
30
VLN
Zline//Zset
V
Zbal
x 15
ń
HM
R
11
SLP
Transmit
Gnd
RXI
Receive
RSLP/11
RSLB
Gnd
SLP
As can be seen from Figure 7 by inspection, the receiver
will not pick up any transmit signal when the bridge is in
balance, that is to say when:
Z
Z
Z set
bal
line
R
R
11
SLB
SLP
The sidetone suppression is normally measured in an
acoustic way. The signal at the earpiece when applying a
signal on the microphone is compared with the signal at the
earpiece when applying a signal on the line. The suppression
takes into account the transmit and receive gains set. In fact
the sidetone suppression can be given as a purely electrical
parameter given by the properties of the sidetone bridge
itself. For the MC33215, this so–called electrical sidetone
suppression ASTE can be given as:
R
11
Z
SLP
A
1 – bal x
STE
R
Z
Z set
SLB
line
Values of –12 dB or better, thus ASTE < 0.25, can easily be
reached in this way.
+
ńń
ń
ń
ńń
+
40
50
60
70
Iline (mA)
For small line currents, and thus long lines, no gain
reduction is applied and thus the transmit and receive gains
are at their maximum. For line currents higher than Istart, the
gain is gradually reduced until a line current Istop is reached.
This should be the equivalent of a very short line, and the
gain reduction equals 6.0 dB. For higher line currents the
gain is not reduced further. For the start and stop currents the
following relations are valid:
1
I stop
R
11
SLP
+
+ R 1 ń11
SLP
ń
20 µ x R
ń
AGC
11
SLP
For the typical application, where RAGC = 30 kΩ, the gain
will start to be reduced at Istart = 20 mA while reaching 6.0 dB
of gain reduction at Istop = 50 mA. When AGC is connected to
VDD, the AGC function is disabled leading to no gain
reduction for any line current. This is also sometimes called
PABX mode.
The automatic gain control takes effect in the HMIC and Rx
amplifiers as well as in the BMIC amplifier. In this way the
AGC is also active in speakerphone mode, see the handsfree
operation paragraph.
I start
–
R
Privacy and DTMF Mode
During handset operation a privacy and a DTMF mode can
be entered according the logic Table 1.
Table 1. Logic Table for Handset Mode
ÁÁÁÁ
ÁÁÁ
ÁÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁ
ÁÁÁ
ÁÁÁÁ
ÁÁÁ
ÁÁÁÁ
ÁÁÁ
ÁÁÁÁ
ÁÁÁ
ÁÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁ
ÁÁÁ
ÁÁÁÁ
ÁÁÁ
ÁÁÁÁ
ÁÁÁ
ÁÁÁÁ
ÁÁÁ
ÁÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁ
ÁÁÁ
ÁÁÁÁ
ÁÁÁ
ÁÁÁÁ
ÁÁÁ
ÁÁÁÁ
ÁÁÁ
ÁÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁ
ÁÁÁ
ÁÁÁÁ
ÁÁÁ
ÁÁÁÁ
ÁÁÁ
Logic Inputs
Amplifiers
SPS
MUT
PRS
HMIC
BMIC
DTMF
Rx
RXatt
EAR
0
1
1
Handset Normal
On
Off
Off
On
Off
On
0
1
0
0
0
Handset Privacy
Off
Off
On
On
Off
On
X
Handset DTMF
Off
Off
On
Off
Off
On
M d
Mode
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11
Freescale Semiconductor,
Inc.
MC33215
Table 2. Logic Table for Handsfree Mode
Logic Inputs
Amplifiers
ÁÁÁÁ
ÁÁÁ
ÁÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁ
ÁÁÁ
ÁÁÁÁ
ÁÁÁ
ÁÁÁÁ
ÁÁÁ
ÁÁÁÁ
ÁÁÁ
ÁÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁ
ÁÁÁ
ÁÁÁÁ
ÁÁÁ
ÁÁÁÁ
ÁÁÁ
ÁÁÁÁ
ÁÁÁ
ÁÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁ
ÁÁÁ
ÁÁÁÁ
ÁÁÁ
ÁÁÁÁ
ÁÁÁ
ÁÁÁÁ
ÁÁÁ
ÁÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁ
ÁÁÁ
ÁÁÁÁ
ÁÁÁ
ÁÁÁÁ
ÁÁÁ
SPS
MUT
PRS
1
1
1
1
1
1
0
BMIC
DTMF
Rx
RXatt
EAR
Handsfree Normal
Off
On
Off
On
On
Off
0
Handsfree Privacy
Off
Off
On
On
On
Off
X
Handsfree DTMF
Off
Off
On
Off
On
Off
By applying a logic 0 to Pin MUT, the DTMF mode is
entered where the DTMF amplifier is enabled and where the
Rx amplifier is muted. A DTMF signal can be sent to the line
via the MFI input for which the gain ADTMF is given as:
V
Z
x Z set
line
3.75
A
x line
DTMF
V
Z
Z set
R
11
MFI
line
SLP
In the typical application, the gain equals 35 dB. The
DTMF gain can be controlled by a resistor divider at the input
MFI as shown in the typical application. The signal has to be
capacitively coupled to the input via CMFI which creates a
high pass filter with the input impedance. The line length
AGC has no effect on the DTMF gains.
The signal applied to the MFI input is made audible at the
earpiece output for confidence tone. The signal is internally
applied to the GRX pin where it is amplified via the EAR
amplifier which is used as a current to voltage amplifier. The
gain is therefore proportional to the feedback resistor RRXO.
For RRXO = 180 kΩ the gain equals 6.0 dB. The confidence
tone is also audible at the loudspeaker output when the
loudspeaker amplifier is activated, see speakerphone
operation.
By applying a logic 0 to Pin PRS, the MC33215 enters
privacy mode. In this mode, both handset and handsfree
microphone amplifiers are muted while the DTMF amplifier is
enabled. Through the MFI input, a signal, for example music
on hold, can be sent to the line. In the same way, the MFI
input can also be used to couple in signals from, for instance,
an answering machine.
+
Freescale Semiconductor, Inc...
HMIC
M d
Mode
+
ń
)
HANDSFREE OPERATION
Handsfree operation, including DTMF and Privacy modes,
can be performed by making Pin SPS high according Table 2.
The handset amplifiers will be switched off while the base
amplifiers will be activated. The MC33215 performs all the
necessary functions, such as signal monitoring and
switch–over, under supervision of the duplex controller.
With the MC33215 also a group listening–in application
can be built. For more information on this subject please refer
to application note AN1574.
Base Microphone Amplifier
The base microphone can be capacitively connected to
the circuit via the differential input BM1 and BM2. The setup
is identical to the one for the handset microphone amplifier.
The total transmit voltage gain ABM from the base
microphone inputs to the line is:
V
Z
x Z set
line
37.5
A
x line
BM
V
Z
Z set
R
11
BM
line
SLP
+
12
+
ń
With the typical application and Zline = 600 Ω the transmit
gain calculates as 55 dB.
The electret base microphone can be supplied directly
from VHF but it is advised to use an additional RC filter to
obtain a stable supply point, as shown in the typical
application. The microphone can also be supplied by VMC.
The transmit gain is set by adjusting the sensitivity of the
base microphone by adjusting the resistors RBM1 and RBM2.
It is not advised to adjust the gain by including series
resistors towards the Pins BM1 and BM2.
A high pass filter is introduced by the coupling capacitors
CBM1 and CBM2 in combination with the input impedance. A
low pass filter can be created by putting capacitors in parallel
with the resistors RBM1 and RBM2.
Loudspeaker Amplifier
The loudspeaker amplifier of the MC33215 has three major
benefits over most of the existing speakerphone loudspeaker
amplifiers: it can be supplied and used in a telephone line
powered application but also stand alone, it has an all NPN
bootstrap output stage which provides maximum output
swing under any supply condition, and it includes a
peak–to–peak limiter to limit the distortion at the output.
The loudspeaker amplifier is powered at Pin VLS. In
telephone line powered applications, this pin should be
connected to VCC where most of the line current is available,
see the VCC supply paragraph. In an application where an
external power supply is used, VLS and thus the loudspeaker
amplifier can be powered separately from the rest of the
circuit. The amplifier is grounded to PGD, which is the circuits
power ground shared by both the loudspeaker amplifier and
the current splitter of the VCC supply. Half the supply voltage
of VLS is at BVO, filtered with a capacitor to VLS. This
voltage is used as the reference for the output amplifier.
The receive signal present at RLS can be capacitively
coupled to LSI via the resistor RLSI. The overall gain from
RLS to LSO follows as:
V
R
LSO
A
– LSF x 4.0
LS
V
R
RLS
LSI
In the typical application this leads to a loudspeaker gain
ALS of 26 dB. The above formula follows from the fact that the
overall amplifier architecture from RLS to LSO can be looked
at as an inverting voltage amplifier with an internal current
gain from LSI to LSF of 4. The input LSI is a signal current
summing node which allows other signals to be applied here.
+
+
)
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MC33215
Figure 9. Loudspeaker Output Stage
0.5 VLS
1.5 VLS
0
VLS
VLS
–0.5 VLS
0.5 VLS
Loudspeaker
LSB
VLS
CLSO
T2
LSO
0.5 VLS
PGD
0
Figure 10. Loudspeaker Amplifier Output Power with External Supply
140
300
120
P LSP (mW)
200
80
60
150
RLSP = 50 Ω
100
40
RLSP = 50 Ω
50
20
0
2.0
RLSP = 25 Ω
250
RLSP = 25 Ω
100
P LSP (mW)
Freescale Semiconductor, Inc...
T1
VLS
3.0
4.0
5.0
6.0
7.0
8.0
0
2.0
3.0
4.0
5.0
6.0
7.0
8.0
VLS (V)
VLS (V)
A. Peak–to–Peak Limiter Active
The total gain from the telephone line to the loudspeaker
output includes, besides the loudspeaker amplifier gain, also
the attenuation of the sidetone network and the internal gain
from RXI to RLS. When in receive mode, see under duplex
controller, the gain from RXI to RLS is maximum and equals
24 dB at maximum volume setting. The attenuation of the
sidetone network in the typical application equals 24.6 dB
which makes an overall gain from line to loudspeaker of
25.4 dB. Due to the influence of the line length AGC on the Rx
amplifier, the gain will be reduced for higher line currents.
The output stage of the MC33215 is a modified all NPN
bootstrap stage which ensures maximum output swing under
all supply conditions. The major advantage of this type of
output stage over a standard rail–to–rail output is the higher
stability. The principle of the bootstrap output stage is
explained with the aid of Figure 9.
The output LSO is biased at half the supply VLS while the
filtering of the loudspeaker with the big capacitor CLSO
requires that LSB is biased at VLS. In fact, because of the
filtering, LSB is kept at VLS/2 above the LSO output even if
LSO contains an ac signal. This allows the output transistor
B. Peak–to–Peak Limiter Disabled
T2 to be supplied for output signals with positive excursions
up to VLS without distorting the output signal. The resulting
ac signal over the loudspeaker will equal the signal at LSO.
As an indication of the high performance of this type of
amplifier, in Figure 10, the output power of the loudspeaker
amplifier as a function of supply voltage is depicted for 25 Ω
and 50 Ω loads with both the peak–to–peak limiter active and
disabled. As can be seen, in case the peak–to–peak limiter is
disabled, the output power is roughly increased with 6.0 dB,
this at the cost of increased distortion levels up to 30%.
In a telephone line powered application, the loudspeaker
amplifier output power is limited not only by the supply
voltage but also by the telephone line current. This means
that in telephones the use of 25 Ω or 50 Ω speakers is
preferred over the use of the cheaper 8.0 Ω types. Figure 11
gives the output power into the loudspeaker for a line
powered application and two different dc settings with the
peak–to–peak limiter active. In case the peak–to–peak limiter
is disabled the output power will be increased for the higher
line currents up to 6.0 dB.
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Freescale Semiconductor,
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MC33215
Figure 11. Loudspeaker Amplifier Output
Power when Line Powered
100
RREG1 = 365 k
RREG2 = 220 k
RLSP = 25 Ω
90
80
70
RREG1 = 365 k
RREG2 = Infinite
50
RLSP = 25 Ω
R
40
REG1 = 365 k
RREG2 = Infinite
30 R = 50 Ω
LSP
20
PLSP (mW)
60
loudspeaker amplifier is muted which is needed for correct
handset operation.
The volume of the loudspeaker signal can be varied via a
potentiometer at VOL. A fixed current of 10 µA is running
through the potentiometer and the resulting voltage at VOL
is a measure for the gain reduction. The relation between
the voltage at VOL and the obtained gain reduction is given
in Figure 13.
RREG1 = 365 k
RREG2 = 220 k
RLSP = 50 Ω
Figure 13. Volume Reduction
0
–5.0
10
–10
0
20
40
60
80
100
The quality of the audio output of the loudspeaker amplifier
is mainly determined by the distortion level. To keep high
quality under difficult supply conditions, the MC33215
incorporates a peak–to–peak limiter. The peak–to–peak
limiter will detect when the output stage gets close to its
maximum output swing and will then reduce the gain from LSI
to LSF. The attack and release of the limiter is regulated by
the CPPL capacitor. Figure 12 depicts the limiter’s attack
behavior with CPPL = 100 nF. The release time is given as
3 x CPPL x RPPL. In the typical application this leads to a
release time of 300 ms.
Figure 12. Peak–to–Peak Limiter Dynamic Behavior
VLSO
0.5 V/DIV
Freescale Semiconductor, Inc...
Iline (mA)
VPPL
Vin
0
1.0
2.0
3.0
4.0
5.0
6.0
t, TIME (ms)
Figure 12 clearly shows that due to the action of the
peak–to–peak limiter, the output swing and thus the output
power is reduced with respect to the maximum possible as
already indicated in Figure 10. The peak–to–peak limiter can
be disabled by connecting the PPL pin to ground.
On top of the peak–to–peak limiter, the MC33215
incorporates a supply limiter, which reduces the gain rapidly
when the supply voltage VLS drops too much. This will
avoid malfunctioning of the amplifier and unwanted
oscillations. The voltage drop is detected via the BVO input
and for that reason the CBVO has to be connected to VLS
and not to Gnd.
The amplifier can be activated by making Pin LSM high. In
the typical application this pin is connected to SPS, which
activates the loudspeaker amplifier automatically when the
speakerphone mode is entered. When LSM is made low, the
14
dA LSP (dB)
0
–15
–20
–25
–30
–35
–40
0
100
200
300
400
500
VVOL (mV), dALSP (dB)
It can be seen from Figure 13 that a linear variation of
RVOL will give a logarithmic gain reduction which adapts
better to the human ear than a linear gain reduction.
During DTMF dialing, see Table 2, a confidence tone is
audible at the loudspeaker of which the level is proportional
to the feedback resistor RLSF only. At RLSF = 180 kΩ the gain
from MFI to LSO equals 28.5 dB.
Half Duplex Controller
To avoid howling during speakerphone operation, a half
duplex controller is incorporated. By monitoring the signals in
both the transmit and receive channel the duplex controller
will reduce the gain in the channel containing the smallest
signal. A typical gain reduction will be between 40 dB and
52 dB depending on the setting, see below. In case of equal
signal levels or by detection of noise only, the circuit goes into
idle mode. In this mode the gain reduction in both channels is
halfway, leading to 20 dB to 26 dB of reduction.
In a speakerphone built around the MC33215, following
the signal path from base microphone to the line and via
sidetone, loudspeaker and acoustic coupling back to the
microphone, the loop gain can be expressed as a sum of the
gains of the different stages. However, since the transmit and
receive gains are dependent on AGC and the sidetone
suppression is dependent on matching with the different lines
we are mostly interested by the maximum possible loop gain
ALOOP(max). It follows:
ALOOP(max) = ABMRX(max) + ARXBM(max) – ASWD (dB)
With: ABMRX(max) = Maximum gain from BM1 and BM2 to
RXI as a function of line length AGC and line
impedance matching
ARXBM(max) = Maximum gain from RXI to BM1 and
BM2 as a function of line length AGC and acoustic
coupling
MOTOROLA ANALOG IC DEVICE DATA
For More Information On This Product,
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Freescale Semiconductor,
Inc.
MC33215
A SWD = Switching depth as performed in the
attenuators
To avoid howling, the maximum possible loop gain should
be below 0 dB and preferably below –10 dB for comfort. In a
practical telephone design, both the ABMRX(max) and the
ARXBM(max) will be less than 20 dB thus a switching depth of
50 dB will give a loop gain of less than –10 dB. An optimized
sidetone network is of high importance for handsfree
operation. The better the network matches with the
telephone line the less local feedback and the smaller the
switching range can be.
The amount of gain reduction ASWD obtained by the
duplex controller is set via resistor RSWD according:
2
3.6 x R
SWD
A
20 log
(dB)
SWD
R
REF
+
ǒ
Ǔ
Freescale Semiconductor, Inc...
In the typical application the gain reduction will be 50 dB.
To compare the transmit and receive signals with each
other, they have to be monitored. This is done by making a
signal envelope and a background noise envelope via the
CTSE, CTBN capacitors for the transmit channel and via the
CRSE, CRBN capacitors for the receive channel. In Figure 14,
a schematic behavior of the envelopes is depicted which is
equal for both transmit and receive.
The voltage signal at the input is first transferred to a
current via the sensitivity adjust network. Then this current is
led through a diode which gives a logarithmic compression in
voltage. It is this voltage from which the signal envelope is
created by means of asymmetric charge and discharge of the
signal envelope capacitor. The noise envelope voltage then
follows in a similar way. Based on the envelope levels, the
MC33215 will switch to transmit, receive or idle mode
following Table 3. The fact that in receive mode the signal on
the base microphone is greater than it is in case of transmit
mode, due to the coupling of the high loudspeaker signal, is
automatically taken into account.
In the table, two particulars can be found. At first, the set
will go to idle mode if the signals are not at least 4.5 dB
greater then the noise floor, which calculates as a 13 mV
voltage difference in envelopes. This avoids continuous
switching over between the modes under slight variations of
the background noise due to, for instance, typing on a
keyboard. Second, a dial tone detector threshold is
implemented to avoid that the set goes to idle mode in
presence of a continuous strong receive signal like a dial
tone. The dial tone detector threshold is proportional to the
RRSA resistor. In the typical application with RRSA = 3.3 kΩ,
the threshold is at 1.26 mVrms at the input RXI or 20 mVrms
at the line. Line length AGC is of influence on the dial tone
detector threshold, increasing the level depending on the line
current with a maximum of 6.0 dB.
In order to perform a correct comparison between the
signal strengths, the sensitivity of the envelope detectors can
be adjusted via the resistors connected to TSA and RSA.
Based on the above, and on the fact that there is an effective
gain of 20 dB in the transmit monitor, it can be derived that for
stable operation the following two relations are valid:
ǒ Ǔt ǒ Ǔ
ǒ Ǔu ǒ Ǔ
20 log R
20 log R
TSA
20 log R
TSA
RSA
20 log R
– A
)
– A
RSA
BMRX(max)
– A
) 20 (dB)
RXBM(max)
20 (dB)
SW
By measuring the gains and choosing the RRSA, the limits
for RTSA follow. The choice for the sensitivity resistors is not
completely free. The logarithmic compressors and the
amplifier stages have a certain range of operation and, on the
receive side, the choice for RRSA is given by the desired dial
tone detector threshold. Figure 15 indicates the available
dynamic range for the selected value of the sensitivity
resistors.
Figure 14. Signal and Noise Envelopes
1.8 V
Internal
VHF
CTSE
TSE
VHF
CTBN
TBN
Microphone
Input Signal
TSA
RTSA
CTSA
MOTOROLA ANALOG IC DEVICEFor
DATA
More Information On This Product,
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15
Freescale Semiconductor,
Inc.
MC33215
Table 3. Logic Table for Switch–Over
TSE > RSE
TSE > TBN + 13 mV
RSE > VDDT
RSE > RBN + 13 mV
1
1
X
X
Transmit
1
0
X
X
Idle
0
X
1
X
Receive
0
X
0
1
Receive
0
X
0
0
Idle
Mode
The electrical characteristics and the behavior of the
MC33215 are not the only factor in designing a handsfree
speakerphone. During the design the acoustics have to be
taken into account from the beginning. The choice of the
transducers and the design of the cabinet are of great
influence on the speakerphone performance. Also, to
achieve a proper handsfree operation, the fine tuning of the
components around the duplex controller have to be done
with the final choice of the cabinet and the transducers.
The resistors for the sensitivity setting have to be coupled
capacitively to the pins for dc decoupling, and also to create
a high pass filter to suppress low frequent background noises
like footsteps and 50 Hz.
The switch–over timing is performed by charging and
discharging the CSWT capacitor. The switch–over from
transmit to receive or vice versa is fast, on the order of
milliseconds, and is proportional to the value of CSWT. The
switch–over to idle mode is slow, in the order of a few
seconds, and is proportional to the product of the values of
RSWT and CSWT. Figure 16 depicts a typical switch–over
behavior when applying transmit and receive stimuli.
Figure 15. Compression Range of the Signal Monitors
100.0E–3
100.0E–3
Upper Limit of
Compression
Dial Tone
Threshold
1.0E–3
Upper Limit of
Compression
10.0E–3
Lower Limit of
Compression
VBM1 (Vrms)
10.0E–3
VRXI (Vrms)
Freescale Semiconductor, Inc...
ÁÁÁÁÁÁÁÁ
ÁÁÁÁÁÁÁ
ÁÁÁÁÁÁÁÁ
ÁÁÁÁÁÁÁÁ
ÁÁÁÁÁÁÁ
ÁÁÁÁÁÁÁÁ
ÁÁÁÁÁÁÁ
ÁÁÁÁÁÁÁÁ
ÁÁÁÁÁÁÁÁ
ÁÁÁÁÁÁÁ
ÁÁÁÁÁÁÁÁ
ÁÁÁÁÁÁÁ
ÁÁÁÁÁÁÁÁ
ÁÁÁÁÁÁÁÁ
ÁÁÁÁÁÁÁ
ÁÁÁÁÁÁÁÁ
ÁÁÁÁÁÁÁ
ÁÁÁÁÁÁÁÁ
ÁÁÁÁÁÁÁÁ
ÁÁÁÁÁÁÁ
ÁÁÁÁÁÁÁÁ
ÁÁÁÁÁÁÁ
ÁÁÁÁÁÁÁÁ
ÁÁÁÁÁÁÁÁ
ÁÁÁÁÁÁÁ
ÁÁÁÁÁÁÁÁ
ÁÁÁÁÁÁÁ
ÁÁÁÁÁÁÁÁ
ÁÁÁÁÁÁÁÁ
ÁÁÁÁÁÁÁ
Lower Limit of
Compression
1.0E–3
100.0E–6
10.0E–6
100
1000
10000
100000
100.0E–6
100
1000
10000
RRSA (Ω)
RTSA (Ω)
A. Receive Monitor
B. Transmit Monitor
100000
Figure 16. Switch–Over Behavior
Receive
Transmit
VMC + 0.5
SWT
VMC – 0.5
16
MOTOROLA ANALOG IC DEVICE DATA
For More Information On This Product,
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Freescale Semiconductor,
Inc.
MC33215
Figure 17. Test Circuit
ZVDD
620
CVDD
100 µ
VDD
Gnd
RREG
360 k
VDD
Zbal
33 k
CREG
220 n
VMC
Supply
MC33215
CHM1
33 n HM1
Freescale Semiconductor, Inc...
VHM
Driver
1x
HMIC
0.2 V
CHM2
33 n
CBM1
33 n BM1
MBM
CTSE
330 n TBN
VOL
SLB
VMF
MUT
VMUT
MBM
MDF
MRX
PRS
Logic
Control
Block
VPRS
LSM
MRA
Attenuator
Control
VLSM
MEAR
SWT
CRBN
RBN 4.7 µ
AGC
Rx Log–Amp
and Envelope
Detectors
Analog
Control
Block
VSWT
CRSE
RSE 330 n
VHF
CRSA
470 n
RSA
RRSA
3.3 k
MRX
Rx Attenuator
Rx
CRXI
47 n
AGC
MRA
VLS
2
RXI
BVO
CBVO
220 n
CMF1
47 n
VSPS
RVOL
47 k
V VRLS
RSLP
220
SPS
Tx Log–Amp
and
Envelope
Detectors
RLS
Iline
CVCC
470 µ
DTMF
AGC
CTBN
4.7 µ
RAGC
30 k AGC
RREF
20 k REF
RSWD
100 k SWD
CVHF
47 µ
MFI
MHM
VHF
VCC
MDF
Tx Attenuator
BMIC
RTSA
2.2 k TSA
TSE
CVMC
10 µ
SLP
AGC
CBM2
33 n BM2
CTSA
470 n
VHF
MHM
HM2
VBM
Supply
1:10
600
Vac
RSLB
2.2 k
VLN
REG
Vline V
S1
1
VRXI
MEAR
VLS
V VLSP
25
LSB
CLSO
47 µ
LSO
RLSO
PGD
LSP
RXO
EAR
Peak
Limiter
GRX
CEAR
10 µ
RRXO
180 k
V VEAR
180 k
LSF
PPL
RPPL
1.0 M
CPPL
100 n
LSI
RXS
RLSI
36 k
CLSI
47 n
CRXS
100 n
RGRX
24 k
CGRX
47 n
VLSI
MOTOROLA ANALOG IC DEVICEFor
DATA
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17
Freescale Semiconductor,
Inc.
MC33215
Figure 18. Typical Application
T1
ZVDD
620
CVDD
100 µ
VDD
Gnd
RREG2
RREG1
365 k
REG
VDD
VHF
Supply
1:10
MC33215
VMC
VCC
CHM1
33 n HM1
RHM1
1.0 k
Driver
Freescale Semiconductor, Inc...
0.2 V
10 µF
RBM2
1.0 k
MFI
Ring
Dialer or
Microcontroller
SPS
AGC
MUT
MHM
VHF
TSE
CTSE
330 n
MBM
Tx Log–Amp
and Envelope
Detectors
MDF
MRX
TBN
Logic Control
Block
MEAR
AGC
RREF
20 k
REF
RSWD
100 k
SWD
Attenuator
Control
AGC
Analog
Control
Block
PRS
Rx Log–Amp
and Envelope
Detectors
VOL
VMC
RBN
CRBN
4.7 µ
RSWT
2.2 M
RSE
CRSE
330 n
Rx Attenuator
Rx
6
7
8
9
*
0
#
VHF
CRSA
470 n
RXI
CRXI
33 n
BVO
CBVO
220 n
3
5
RRSA
3.3 k
MRX
RLS
2
4
Speakerphone
Button
CSWT
SWT 100 n
RSA
RVOL
50 k
VCC
Privacy
Button
1
LSM
MRA
CTBN
4.7 µ
RAGC
30 k
CMF1
47 n
DTMF
RTSA
470 TSA
CTSA
1.0 µF
RSLP
220
MDF
Tx Attenuator
BMIC
VDD
CVHF
47 µ
Tip
MBM
CBM2
33 n BM2
T2
CVMC
10 µ
SLB
SLP
AGC
CBM1
33 n BM1
RBM1
1.0 k
1.0 k
1x
HMIC
RHM2
1.0 k
VHF
Hook
Switch
CVCC
470 µ
MHM
CHM2
33 n HM2
0.01
RSLB
2.2 k
VLN
VMC
Supply
Z1
10 V
Zbal
33 k
CREG
220 n
10 n
AGC
MRA
VLS
MEAR
CEAR
10 µ
LSB
25 Ω
RXO
CLSO
47 µ
LSO
RLSO
180 k
PGD
LSP
EAR
RRXO
180 k
Peak Limiter
LSF
PPL
RPPL
1.0 M
CRLS
33 n
18
150 Ω
GRX
LSI
CPPL
100 n
RXS
CRXS
100 n
RGRX
24 k
CGRX
47 n
RLSI
36 k
MOTOROLA ANALOG IC DEVICE DATA
For More Information On This Product,
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Freescale Semiconductor,
Inc.
MC33215
OUTLINE DIMENSIONS
FB SUFFIX
PLASTIC PACKAGE
CASE 848B–04
(TQFP–52)
ISSUE C
B
L
B
39
27
S
D
–A–, –B–, –D–
DETAIL A
S
S
C A–B
V
M
F
0.20 (0.008)
B
0.20 (0.008)
M
L
0.05 (0.002) A–B
–B–
–A–
Freescale Semiconductor, Inc...
H A–B
S
DETAIL A
D
26
40
J
N
14
52
1
13
BASE METAL
D
–D–
B
0.20 (0.008) M H A–B
0.02 (0.008)
S
D
S
V
M
C A–B
S
D
S
DETAIL C
M_
C
E
–H–
DATUM
PLANE
0.10 (0.004)
H
–C–
M_
G
C A–B
S
D
S
SECTION B–B
0.05 (0.002) A–B
0.20 (0.008)
M
SEATING
PLANE
NOTES:
1. DIMENSIONING AND TOLERANCING PER ANSI
Y14.5M, 1982.
2. CONTROLLING DIMENSION: MILLIMETER.
3. DATUM PLANE –H– IS LOCATED AT BOTTOM OF
LEAD AND IS COINCIDENT WITH THE LEAD WHERE
THE LEAD EXITS THE PLASTIC BODY AT THE
BOTTOM OF THE PARTING LINE.
4. DATUMS –A–, –B– AND –D– TO BE DETERMINED AT
DATUM PLANE –H–.
5. DIMENSIONS S AND V TO BE DETERMINED AT
SEATING PLANE –C–.
6. DIMENSIONS A AND B DO NOT INCLUDE MOLD
PROTRUSION. ALLOWABLE PROTRUSION IS 0.25
(0.010) PER SIDE. DIMENSIONS A AND B DO
INCLUDE MOLD MISMATCH AND ARE DETERMINED
AT DATUM PLANE –H–.
7. DIMENSION D DOES NOT INCLUDE DAMBAR
PROTRUSION. ALLOWABLE DAMBAR PROTRUSION
SHALL BE 0.08 (0.003) TOTAL IN EXCESS OF THE D
DIMENSION AT MAXIMUM MATERIAL CONDITION.
DAMBAR CANNOT BE LOCATED ON THE LOWER
RADIUS OR THE FOOT.
U_
R
Q_
K
T
W
X
DETAIL C
MOTOROLA ANALOG IC DEVICEFor
DATA
More Information On This Product,
Go to: www.freescale.com
DIM
A
B
C
D
E
F
G
H
J
K
L
M
N
Q
R
S
T
U
V
W
X
MILLIMETERS
MIN
MAX
9.90
10.10
9.90
10.10
2.10
2.45
0.22
0.38
2.00
2.10
0.22
0.33
0.65 BSC
–––
0.25
0.13
0.23
0.65
0.95
7.80 REF
5_
10_
0.13
0.17
0_
7_
0.13
0.30
12.95
13.45
0.13
–––
0_
–––
12.95
13.45
0.35
0.45
1.6 REF
INCHES
MIN
MAX
0.390
0.398
0.390
0.398
0.083
0.096
0.009
0.015
0.079
0.083
0.009
0.013
0.026 BSC
–––
0.010
0.005
0.009
0.026
0.037
0.307 REF
5_
10_
0.005
0.007
0_
7_
0.005
0.012
0.510
0.530
0.005
–––
0_
–––
0.510
0.530
0.014
0.018
0.063 REF
19
Freescale Semiconductor,
Inc.
MC33215
OUTLINE DIMENSIONS
B SUFFIX
PLASTIC PACKAGE
CASE 858–01
(SDIP–42)
ISSUE O
NOTES:
1. DIMENSIONING AND TOLERANCING PER ANSI
Y14.5M, 1982.
2. CONTROLLING DIMENSION: INCH.
3. DIMENSION L TO CENTER OF LEAD WHEN
FORMED PARALLEL.
4. DIMENSIONS A AND B DO NOT INCLUDE MOLD
FLASH. MAXIMUM MOLD FLASH 0.25 (0.010).
–A–
42
22
–B–
1
21
L
H
C
Freescale Semiconductor, Inc...
DIM
A
B
C
D
F
G
H
J
K
L
M
N
–T–
SEATING
PLANE
0.25 (0.010)
N
G
F
D 42 PL
K
M
T A
M
J 42 PL
S
0.25 (0.010)
M
T B
INCHES
MIN
MAX
1.435
1.465
0.540
0.560
0.155
0.200
0.014
0.022
0.032
0.046
0.070 BSC
0.300 BSC
0.008
0.015
0.115
0.135
0.600 BSC
0_
15 _
0.020
0.040
MILLIMETERS
MIN
MAX
36.45
37.21
13.72
14.22
3.94
5.08
0.36
0.56
0.81
1.17
1.778 BSC
7.62 BSC
0.20
0.38
2.92
3.43
15.24 BSC
0_
15_
0.51
1.02
S
Motorola reserves the right to make changes without further notice to any products herein. Motorola makes no warranty, representation or guarantee regarding
the suitability of its products for any particular purpose, nor does Motorola assume any liability arising out of the application or use of any product or circuit, and
specifically disclaims any and all liability, including without limitation consequential or incidental damages. “Typical” parameters which may be provided in Motorola
data sheets and/or specifications can and do vary in different applications and actual performance may vary over time. All operating parameters, including “Typicals”
must be validated for each customer application by customer’s technical experts. Motorola does not convey any license under its patent rights nor the rights of
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arising out of, directly or indirectly, any claim of personal injury or death associated with such unintended or unauthorized use, even if such claim alleges that
Motorola was negligent regarding the design or manufacture of the part. Motorola and
are registered trademarks of Motorola, Inc. Motorola, Inc. is an Equal
Opportunity/Affirmative Action Employer.
Mfax is a trademark of Motorola, Inc.
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INTERNET: http://www.mot.com/SPS/
20
MC33215/D
◊For More Information On This Product,
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DATA
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