TI TPS51125RGER

TPS51125
www.ti.com
SLUS786A – OCTOBER 2007 – REVISED NOVEMBER 2007
Dual-Synchronous, Step-Down Controller with Out-of-Audio™ Operation and 100-mA
LDOs for Notebook System Power
FEATURES
1
•
•
•
•
•
2
•
•
•
•
•
•
•
•
DESCRIPTION
Wide Input Voltage Range: 5.5 V to 28 V
Output Voltage Range: 2 V to 5.5 V
Built-in 100-mA 5-V/3.3-V LDO with Switches
Built-in 1% 2-V Reference Output
With/Without Out-of-Audio™ Mode Selectable
Light Load and PWM only Operation
Internal 1.6-ms Voltage Servo Softstart
Adaptive On-Time Control Architecture with
Four Selectable Frequency Setting
4500 ppm/°C RDS(on) Current Sensing
Built-In Output Discharge
Power Good Output
Built-in OVP/UVP/OCP
Thermal Shutdown (Non-latch)
QFN24 (RGE)
The TPS51125 is a cost effective, dual-synchronous
buck controller targeted for notebook system power
supply solutions. It provides 5-V and 3.3-V LDOs and
requires few external components. The 270-kHz
VCLK output can be used to drive an external charge
pump, generating gate drive voltage for the load
switches without reducing the main converter’s
efficiency. The TPS51125 supports high efficiency,
fast transient response and provides a combined
power-good signal. Out-of-Audio™ mode light-load
operation enables low acoustic noise at much higher
efficiency than conventional forced PWM operation.
Adaptive on-time D-CAP™ control provides
convenient and efficient operation. The part operates
with supply input voltages ranging from 5.5 V to 28 V
and supports output voltages from 2 V to 5.5 V. The
TPS51125 is available in a 24-pin QFN package and
is specified from -40°C to 85°C ambient temperature
range.
APPLICATIONS
•
•
•
Notebook Computers
I/O Supplies
System Power Supplies
Typical Application Diagram
SGND
C0
0.22mF
R3
13kW
3.3V/100mA
R6
110kW
-
R4
20kW
R1
30kW
R2
20kW
R5
110kW
SGND
SGND
7 VO2
C20
10mF
Q3
IRF7821
L2
3.3mH
VF
B
EN
T
1
VR
EF
VIN
1
RIP
1
2
VO1
C4
0.1mF
24
8 VREG3
PGOOD
23
9 VBST2
VBST1
22
DRVH1
21
LL1
20
+
VIN
5.5 ~ 28V
+
VO1
5V/6A
-
VO1_GND
-
5V/100mA
-
15V/10mA
C6
10mF
C5
10mF
PG
R7
100kW VREG5
PGND
R8
5.1W
C3
0.1mF
R9
5.1W
TPS51125RGE
(QFN24)
10 DRVH2
Q1
IRF7821
L1
3.3mH
+
11 LL2
PowerPAD
Q4
IRF7821
SK
IP
GN
D
VIN
VR
EG
5
VC
L
DRVL1
EN
0
-
SE
L
12 DRVL2
Q2
IRF7821
13
14
15
16
17
18
CO1
POSCAP
330mF
19
K
CO2
POSCAP
330mF
VO2_GND
3
PGND
PGND
VO2
3.3V/6A
4
TO
C8
10mF
2
RIP
2
EN
T
C7
10mF
5
VF
B
6
NS
EL
VIN
SGND
PGND
EN0
PGND
PGND
PGND
VREG5
C11
100n
F
C21
10mF
R10
620kW
VO1
VREF
D0
PGND
PGND
C10
100n
F
D1
C13
100n
F
D2
C12
100n
F
D4
C14
1uF
SGND
PGND
PGND
PGND
1
2
Please be aware that an important notice concerning availability, standard warranty, and use in critical applications of
Texas Instruments semiconductor products and disclaimers thereto appears at the end of this data sheet.
Out-of-Audio, D-CAP are trademarks of Texas Instruments.
PRODUCTION DATA information is current as of publication date.
Products conform to specifications per the terms of the Texas
Instruments standard warranty. Production processing does not
necessarily include testing of all parameters.
Copyright © 2007, Texas Instruments Incorporated
TPS51125
www.ti.com
SLUS786A – OCTOBER 2007 – REVISED NOVEMBER 2007
ORDERING INFORMATION
TA
PACKAGE
PART NUMBER
-40°C to 85°C
Plastic Quad Flat Pack
(QFN)
PINS
TPS51125RGET
24
TPS51125RGER
OUTPUT
SUPPLY
MIN
QUANTITY
Tape
-and-Reel
250
Tape
-and-Reel
3000
ECO PLAN
Green
(RoHS and
no Sb/Br)
ABSOLUTE MAXIMUM RATINGS (1)
over operating free-air temperature range (unless otherwise noted)
PARAMETER
Input voltage range
(1)
VBST1, VBST2
-0.3 to 36
VIN
-0.3 to 30
LL1, LL2
Output voltage range
(2)
-0.3 to 6
EN0, ENTRIP1, ENTRIP2, VFB1, VFB2, VO1, VO2, TONSEL, SKIPSEL
-0.3 to 6
DRVH1, DRVH2
-1.0 to 36
DRVH1, DRVH2
(2)
-0.3 to 6
TJ
Junction temperature range
-40 to 125
Tstg
Storage temperature
-55 to 150
(2)
V
-0.3 to 6
PGOOD, VCLK, VREG3, VREG5, VREF, DRVL1, DRVL2
(1)
UNIT
-2.0 to 30
VBST1, VBST2
(1)
VALUE
°C
Stresses beyond those listed under "absolute maximum ratings" may cause permanent damage to the device. These are stress ratings
only and functional operation of the device at these or any other conditions beyond those indicated under "recommended operating
conditions" is not implied. Exposure to absolute-maximum-rated conditions for extended periods may affect device reliability.
Voltage values are with respect to the corresponding LLx terminal.
DISSIPATION RATINGS
2-oz. trace and copper pad with solder.
(1)
PACKAGE
TA < 25°C POWER RATING
DERATING FACTOR ABOVE TA
= 25°C
TA = 85°C POWER RATING
24 pin RGE (1)
1.85 W
18.5 mW/°C
0.74 W
Enhanced thermal conductance by 3x3 thermal vias beneath thermal pad.
RECOMMENDED OPERATING CONDITIONS
over operating free-air temperature range (unless otherwise noted)
PARAMETER
MIN
MAX
VIN
Input voltage range
VBST1, VBST2
-0.1
34
VBST1, VBST2 (wrt LLx)
-0.1
5.5
EN0, ENTRIP1, ENTRIP2, VFB1, VFB2, VO1, VO2,
TONSEL, SKIPSEL
-0.1
5.5
DRVH1, DRVH2
-0.8
34
DRVH1, DRVH2 (wrt LLx)
-0.1
5.5
LL1, LL2
-1.8
28
VREF, VREG3, VREG5
-0.1
5.5
PGOOD, VCLK, DRVL1, DRVL2
-0.1
5.5
Operating free-air temperature
-40
85
Output voltage range
TA
2
5.5
TYP
Supply voltage
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UNIT
28
V
°C
Copyright © 2007, Texas Instruments Incorporated
Product Folder Link(s): TPS51125
TPS51125
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SLUS786A – OCTOBER 2007 – REVISED NOVEMBER 2007
ELECTRICAL CHARACTERISTICS
over operating free-air temperature range, VIN = 12 V (unless otherwise noted)
PARAMETER
CONDITIONS
MIN
TYP
MAX
UNIT
Supply Current
IVIN1
VIN supply current1
VIN current, TA = 25°C, no load, VO1 = 0 V, VO2 =
0 V, EN0=open, ENTRIPx = 5 V,
VFB1 = VFB2 = 2.05 V
0.55
1
mA
IVIN2
VIN supply current2
VIN current, TA = 25°C, no load, VO1 = 5 V, VO2 =
3.3 V, EN0=open, ENTRIPx = 5 V,
VFB1 = VFB2 = 2.05 V
4
6.5
µA
IVO1
VO1 current
VO1 current, TA = 25°C, no load, VO1 = 5 V, VO2
= 3.3 V, EN0=open, ENTRIPx = 5 V,
VFB1 = VFB2 = 2.05 V
0.8
1.5
mA
IVO2
VO2 current
VO2 current, TA = 25°C, no load, VO1 = 5 V, VO2
= 3.3 V, EN0=open, ENTRIPx = 5 V,
VFB1 = VFB2 = 2.05 V
12
100
IVINSTBY
VIN standby current
VIN current, TA = 25°C, no load,
EN0 = 1.2 V, ENTRIPx = 0 V
95
250
IVINSDN
VIN shutdown current
VIN current, TA = 25°C, no load,
EN0 = ENTRIPx = 0 V
10
25
µA
VREF Output
VVREF
VREF output voltage
IVREF = 0 A
1.98
2.00
2.02
-5 µA < IVREF < 100 µA
1.97
2.00
2.03
V
VREG5 Output
VO1 = 0 V, IVREG5 < 100 mA, TA = 25°C
VVREG5
VREG5 output voltage
IVREG5
VREG5 output current
VTH5VSW
Switch over threshold
R5VSW
5 V SW RON
4.8
5
5.2
VO1 = 0 V, IVREG5 < 100 mA, 6.5 V < VIN < 28 V
4.75
5
5.25
VO1 = 0 V, IVREG5 < 50 mA, 5.5 V < VIN < 28 V
5.25
4. 75
5
VO1 = 0 V, VREG5 = 4.5 V
100
175
250
Turns on
4.55
4.7
4.85
Hysteresis
0.15
0.25
0.3
1
3
3.2
3.33
3.46
VO2 = 0 V, IVREG3 < 100 mA, 6.5 V < VIN < 28 V
3.13
3.33
3.5
VO2 = 0 V, IVREG3 < 50 mA, 5.5 V < VIN < 28 V
3.13
3.33
3.5
VO2 = 0 V, VREG3 = 3 V
100
175
250
Turns on
3.05
3.15
3.25
0.1
0.2
0.25
1.5
4
VO1 = 5 V, IVREG5 = 100 mA
V
mA
V
Ω
VREG3 Output
VO2 = 0 V, IVREG3 < 100 mA, TA= 25°C
VVREG3
VREG3 output voltage
IVREG3
VREG3 output current
VTH3VSW
Switch over threshold
R3VSW
3 V SW RON
Hysteresis
VO2 = 3.3 V, IVREG3 = 100 mA
V
mA
V
Ω
Internal Reference Voltage
VIREF
VVFB
Internal reference voltage
VFB regulation voltage
IVREF = 0 A, beginning of ON state
1.95
1.98
2.01
FB voltage, IVREF = 0 A, skip mode
1.98
2.01
2.04
2.00
2.035
2.07
FB voltage, IVREF = 0 A, OOA mode
(1)
FB voltage, IVREF = 0 A, continuous conduction
IVFB
(1)
VFB input current
VFBx = 2.0 V, TA= 25°C
(1)
V
2.00
-20
20
nA
Ensured by design. Not production tested.
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SLUS786A – OCTOBER 2007 – REVISED NOVEMBER 2007
ELECTRICAL CHARACTERISTICS (continued)
over operating free-air temperature range, VIN = 12 V (unless otherwise noted)
PARAMETER
CONDITIONS
MIN
TYP
MAX
UNIT
VOUT Discharge
IDischg
VOUT discharge current
ENTRIPx = 0 V, VOx = 0.5 V
10
60
mA
Output Drivers
RDRVH
DRVH resistance
RDRVL
DRVL resistance
TD
Dead time
Source, VBSTx - DRVHx = 100 mV
4
8
1.5
4
4
8
Sink, VDRVLx = 100 mV
1.5
4
DRVHx-off to DRVLx-on
10
DRVLx-off to DRVHx-on
30
Sink, VDRVHx - LLx = 100 mV
Source, VVREG5 - DRVLx = 100 mV
Ω
ns
Clock Output
VCLKH
High level voltage
IVCLK = -10 mA, VO1 = 5 V, TA = 25 °C
VCLKL
Low level voltage
IVCLK = 10 mA, VO1 = 5 V, TA = 25 °C
fCLK
Clock frequency
TA = 25 °C
4.84
4.92
0.06
0.12
175
270
325
0.7
V
kHz
Internal BST Diode
VFBST
Forward voltage
VVREG5-VBSTx, IF = 10 mA, TA = 25 °C
0.8
0.9
V
IVBSTLK
VBST leakage current
VBSTx = 34 V, LLx = 28 V, TA = 25 °C
0.1
1
µA
Duty and Frequency Control
TON11
CH1 on time 1
VIN = 12 V, VO1 = 5 V, 200 kHz setting
2080
TON12
CH1 on time 2
VIN = 12 V, VO1 = 5 V, 245 kHz setting
1700
TON13
CH1 on time 3
VIN = 12 V, VO1 = 5 V, 300 kHz setting
1390
TON14
CH1 on time 4
VIN = 12 V, VO1 = 5 V, 365 kHz setting
1140
TON21
CH2 on time 1
VIN = 12 V, VO2 = 3.3 V, 250 kHz setting
1100
TON22
CH2 on time 2
VIN = 12 V, VO2 = 3.3 V, 305 kHz setting
900
TON23
CH2 on time 3
VIN = 12 V, VO2 = 3.3 V, 375 kHz setting
730
TON24
CH2 on time 4
VIN = 12 V, VO2 = 3.3 V, 460 kHz setting
600
TON(min)
Minimum on time
TA = 25 °C
80
TOFF(min)
Minimum off time
TA = 25 °C
300
Internal SS time
Internal soft start
1.1
1.6
2.1
PG in from lower
92.50%
95%
97.50%
PG in from higher
102.50
%
105%
107.50
%
PG hysteresis
2.50%
5%
7.50%
5
12
350
510
ns
Softstart
TSS
ms
Powergood
VTHPG
PG threshold
IPGMAX
PG sink current
PGOOD = 0.5 V
TPGDEL
PG delay
Delay for PG in
4
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mA
670
µs
Copyright © 2007, Texas Instruments Incorporated
Product Folder Link(s): TPS51125
TPS51125
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SLUS786A – OCTOBER 2007 – REVISED NOVEMBER 2007
ELECTRICAL CHARACTERISTICS (continued)
over operating free-air temperature range, VIN = 12 V (unless otherwise noted)
PARAMETER
CONDITIONS
MIN
TYP
MAX
UNIT
Logic Threshold and Setting Conditions
Shutdown
VEN0
EN0 setting voltage
IEN0
EN0 current
VEN
ENTRIP1, ENTRIP2
threshold
0.4
Enable, VCLK = off
0.8
Enable, VCLK = on
2.4
1.6
VEN0 = 0.2 V
2
3.5
5
VEN0 = 1.5 V
1
1.75
2.5
Shutdown
350
400
450
Hysteresis
10
30
60
200 kHz/250 kHz
VTONSEL
TONSEL setting voltage
SKIPSEL setting voltage
µA
mV
1.5
245 kHz/305 kHz
1.9
2.1
300 kHz/375 kHz
2.7
3.6
365 kHz/460 kHz
4.7
V
PWM only
VSKIPSEL
V
1.5
Auto skip
1.9
OOA auto skip
2.7
VENTRIPx = 920 mV, TA= 25°C
9.4
2.1
Protection: Current Sense
IENTRIP
ENTRIPx source current
TCIENTRIP
ENTRIPx current temperature
On the basis of 25°C
coefficient
VOCLoff
OCP comparator offset
((VENTRIPx-GND/9)-24 mV -VGND-LLx) voltage,
VENTRIPx-GND = 920 mV
VOCL(max)
Maximum OCL setting
VENTRIPx = 5 V
VZC
Zero cross detection
comparator offset
VGND-LLx voltage
VENTRIP
Current limit threshold
VENTRIPx-GND voltage,
10
10.6
4500
(2)
ppm/°C
-8
0
8
185
205
225
-5
0
5
0.515
µA
2
mV
V
Protection: UVP & OVP
VOVP
OVP trip threshold
TOVPDEL
OVP prop delay
OVP detect
110%
115%
120%
µs
2
UVP detect
55%
60%
65%
VUVP
Output UVP trip threshold
TUVPDEL
Output UVP prop delay
20
32
40
µs
TUVPEN
Output UVP enable delay
1.4
2
2.6
ms
Hysteresis
10%
UVLO
VUVVREG5
VREG5 UVLO threshold
VUVVREG3
VREG3 UVLO threshold
Wake up
Hysteresis
Shutdown
(2)
4.1
4.2
4.3
0.38
0.43
0.48
V
VO2-1
Thermal Shutdown
TSDN
(2)
Thermal shutdown threshold
Shutdown temperature
Hysteresis
(2)
(2)
150
10
°C
Ensured by design. Not production tested.
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TPS51125
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SLUS786A – OCTOBER 2007 – REVISED NOVEMBER 2007
DEVICE INFORMATION
Table 1. TERMINAL FUNCTIONS TABLE
TERMINAL
NAME
NO.
I/O
DESCRIPTION
VIN
16
I
High voltage power supply input for 5-V/3.3-V LDO.
GND
15
-
Ground.
VREG3
8
O
3.3-V power supply output.
VREG5
17
O
5-V power supply output.
VREF
3
O
2-V reference voltage output.
Master enable input.
Open : LDOs on, and ready to turn on VCLK and switcher channels.
EN0
13
I/O
620 kΩ to GND : enable both LDOs, VCLK off and ready to turn on switcher channels. Power
consumption is almost the same as the case of VCLK = ON. 330 pF to 1 nF should be connected to
GND near the device
GND : disable all circuit
Channel 1 and Channel 2 enable and OCL trip setting pins.
ENTRIP1,
ENTRIP2
1, 6
I/O
VO1, VO2
24, 7
I/O
VFB1,
VFB2
2, 5
I
23
O
PGOOD
Connect resistor from this pin to GND to set threshold for synchronous RDS(on) sense. Short to ground
to shutdown a switcher channel.
Output connection to SMPS. These terminals work as fixed voltage inputs and output discharge
inputs. VO1 and VO2 also work as 5 V and 3.3 V switch over return power input respectively.
SMPS feedback inputs. Connect with feedback resistor divider.
Power Good window comparator output for channel 1 and 2. (Logical AND)
Selection pin for operation mode:
SKIPSEL
14
I
OOA auto skip : Connect to VREG3 or VREG5
Auto skip : Connect to VREF
PWM only : Connect to GND
On-time adjustment pin.
365 kHz/460 kHz setting : connect to VREG5
TONSEL
4
I
300 kHz/375 kHz setting : connect to VREG3
245 kHz/305 kHz setting : connect to VREF
200 kHz/250 kHz setting : connect to GND
DRVL1,
DRVL2
19, 12
O
VBST1,
VBST2
22, 9
I
DRVH1,
DRVH2
21, 10
O
LL1, LL2
20, 11
I
Switch node connections for high-side drivers, current limit and control circuitry.
18
O
270-kHz clock output for 15-V charge pump.
VCLK
6
Low-side N-channel MOSFET driver outputs. GND referenced drivers.
Supply input for high-side N-channel MOSFET driver (boost terminal).
High-side N-channel MOSFET driver outputs. LL referenced drivers.
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SLUS786A – OCTOBER 2007 – REVISED NOVEMBER 2007
VO1
PGOOD
VBST1
DRVH1
LL1
DRVL1
24
23
22
21
20
19
QFN Package (top view)
TONSEL
4
15
GND
VFB2
5
14
SKIPSEL
ENTRIP2
6
13
EN0
12
VIN
DRVL2
16
11
3
LL2
VREF
10
VREG5
DRVH2
17
9
2
VBST2
VFB1
8
VCLK
VREG3
18
7
1
VO2
ENTRIP1
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SLUS786A – OCTOBER 2007 – REVISED NOVEMBER 2007
Functional Block Diagram
8
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SLUS786A – OCTOBER 2007 – REVISED NOVEMBER 2007
Switcher Controller Block
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SLUS786A – OCTOBER 2007 – REVISED NOVEMBER 2007
TYPICAL CHARACTERISTICS
VIN SUPPLY CURRENT1
vs
JUNCTION TEMPERATURE
VIN SUPPLY CURRENT1
vs
INPUT VOLTAGE
800
800
IVIN1 - VIN Supply Current1 - mA
IVIN1 - VIN Supply Current1 - mA
700
700
600
500
400
300
200
100
600
500
400
300
200
100
0
-50
0
50
100
0
150
5
TJ - Junction Temperature - °C
10
15
20
25
V IN - Input Voltage - V
Figure 1.
Figure 2.
VIN SUPPLY CURRENT2
vs
INPUT VOLTAGE
9
9
8
8
IVIN2 - VIN Supply Current2 - mA
IVIN2 - VIN Supply Current2 - mA
VIN SUPPLY CURRENT2
vs
JUNCTION TEMPERATURE
7
6
5
4
3
2
7
6
5
4
3
2
1
1
0
0
-50
0
50
100
150
5
Figure 3.
10
10
15
20
25
V IN - Input Voltage - V
T J - Junction Temperature - °C
Figure 4.
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SLUS786A – OCTOBER 2007 – REVISED NOVEMBER 2007
TYPICAL CHARACTERISTICS (continued)
VIN STANDBY CURRENT
vs
INPUT VOLTAGE
VIN STANDBY CURRENT
vs
JUNCTION TEMPERATURE
250
IVINSTBY - VIN Standby Current - h A
IVINSTBY - VIN Standby Current - mA
250
200
150
100
50
200
150
100
50
0
0
-50
0
50
100
5
150
10
T J - Junction Temperature - °C
15
Figure 5.
25
Figure 6.
VIN SHUTDOWN CURRENT
vs
JUNCTION TEMPERATURE
VIN SHUTDOWN CURRENT
vs
INPUT VOLTAGE
25
IVINSDN - VIN Shutdown Current - mA
25
IVINSDN - VIN Shutdown Current - mA
20
V IN - Input Voltage - V
20
15
10
5
20
15
10
5
0
0
-50
0
50
100
150
5
10
15
20
25
V IN - Input Voltage - V
T J - Junction Temperature - °C
Figure 7.
Figure 8.
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SLUS786A – OCTOBER 2007 – REVISED NOVEMBER 2007
TYPICAL CHARACTERISTICS (continued)
CURRENT SENSE CURRENT
vs
JUNCTION TEMPERATURE
VCLK FREQUENCY
vs
JUNCTION TEMPERATURE
325
13
300
f CLK - VCLK Frequency - kHz
IENTRIP - Current Sense Current - mA
14
12
11
10
9
8
275
250
225
200
7
175
-50
6
-50
0
50
100
150
0
50
100
T J - Junction Temperature - °C
T J - Junction Temperature - °C
Figure 9.
Figure 10.
SWITCHING FREQUENCY
vs
INPUT VOLTAGE
SWITCHING FREQUENCY
vs
INPUT VOLTAGE
500
500
TONSEL = 2V
f SW - Swithching Frequency - kHz
fSW - Swithching Frequency - kHz
TONSEL = GND
400
300
CH2
200
CH1
100
0
400
CH2
300
CH1
200
100
0
6
8
10
12
14
16
18
20
22
24
26
6
8
V IN - Input Voltage - V
10
12
14
16
18
20
22
24
26
V IN - Input Voltage - V
Figure 11.
12
150
Figure 12.
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TYPICAL CHARACTERISTICS (continued)
SWITCHING FREQUENCY
vs
INPUT VOLTAGE
SWITCHING FREQUENCY
vs
INPUT VOLTAGE
500
500
CH2
400
f SW - Swithching Frequency - kHz
f SW - Swithching Frequency - kHz
TONSEL = 3.3V
300
CH1
200
100
0
CH1
300
200
100
0
6
8
10
12
14
16
18
20
22
24
26
6
8
10
V IN - Input Voltage - V
12
14
16
18
20
22
24
26
V IN - Input Voltage - V
Figure 13.
Figure 14.
SWITCHING FREQUENCY
vs
OUTPUT CURRENT
SWITCHING FREQUENCY
vs
OUTPUT CURRENT
500
500
TONSEL = GND
TONSEL = 2V
f SW - Swithching Frequency - kHz
f SW - Swithching Frequency - kHz
CH2
TONSEL = 5V
400
400
300
CH2 PWM Only
200
CH1 PWM Only
100
CH2 Auto-skip
CH2 OOA
CH1 OOA
400
CH2 PWM Only
300
200
CH1 PWM Only
CH2 Auto-skip
100
CH2 OOA
CH1 OOA
CH1 Auto-skip
0
0.001
0.01
0.1
1
CH1 Auto-skip
10
0
0.001
IOUT - Output Current - A
0.01
0.1
1
10
IOUT - Output Current - A
Figure 15.
Figure 16.
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TYPICAL CHARACTERISTICS (continued)
SWITCHING FREQUENCY
vs
OUTPUT CURRENT
SWITCHING FREQUENCY
vs
OUTPUT CURRENT
500
500
400
TONSEL = 5V
f SW - Swithching Frequency - kHz
f SW - Swithching Frequency - kHz
TONSEL = 3.3V
CH2 PWM Only
300
CH1 PWM Only
200
CH2 Auto-skip
100
CH2 OOA
CH2 PWM Only
400
CH1 PWM Only
300
200
CH2 Auto-skip
CH2 OOA
100
CH1 OOA
CH1 OOA
CH1 Auto-skip
CH1 Auto-skip
0
0.001
0.01
0.1
1
0
0.001
10
IOUT - Output Current - A
0.01
0.1
Figure 17.
10
Figure 18.
OVP/UVP THRESHOLD VOLTAGE
vs
JUNCTION TEMPERATURE
VREG5 OUTPUT VOLTAGE
vs
OUTPUT CURRENT
150
5.05
140
130
V VREG5 - VREG5 Output Voltage - V
V OVP/VUVP - OVP/UVP Threshold - %
1
IOUT - Output Current - A
120
110
100
90
80
70
60
50
40
-50
0
TJ
50
100
- Junction Temperature - °C
5.00
4.95
150
4.90
0
20
40
60
80
100
IVREG5 - VREG5 Output Current - m A
Figure 19.
14
Figure 20.
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TYPICAL CHARACTERISTICS (continued)
VREG3 OUTPUT VOLTAGE
vs
OUTPUT CURRENT
VREF OUTPUT VOLTAGE
vs
OUTPUT CURRENT
3.35
2.015
V VREF - VREF Output Voltage - V
V VREG3 - VREG3 Output Voltage - V
2.020
3.3
3.25
2.010
2.005
2.000
1.995
1.990
1.985
3.2
1.980
0
20
40
60
80
100
0
IVREG3 - VREG3 Output Current - m A
20
Figure 21.
100
3.360
OOA
OOA
5.050
V OUT2 - 3.3-V Output Voltage - V
V OUT1 - 5-V Output Voltage - V
80
3.3-V OUTPUT VOLTAGE
vs
OUTPUT CURRENT
5.075
5.000
60
Figure 22.
5-V OUTPUT VOLTAGE
vs
OUTPUT CURRENT
5.025
40
IVREF - VREF Output Current - mA
Auto-skip
PWM Only
4.975
4.950
0.001
0.01
0.1
1
10
3.330
Auto-skip
3.300
PWM Only
3.270
3.240
0.001
IOUT1 - 5-V Output Current - A
0.01
0.1
1
10
IOUT2 - 3.3-V Output Current - A
Figure 23.
Figure 24.
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TYPICAL CHARACTERISTICS (continued)
5-V OUTPUT VOLTAGE
vs
INPUT VOLTAGE
3.3-V OUTPUT VOLTAGE
vs
INPUT VOLTAGE
3.360
5.050
V OUT2 - 3.3-V Output Voltage - V
V OUT1 - 5-V Output Voltage - V
5.075
IO = 0A
5.025
5.000
IO = 6A
4.975
4.950
3.330
IO = 0A
3.300
IO = 6A
3.270
3.240
6
8
10
12
14
16
18
20
22
24
26
6
8
10
V IN - Input Voltage - V
12
14
16
Figure 25.
100
Auto-skip
VIN=8V
h - Efficiency - %
h - Efficiency - %
24
26
Auto-skip
80
60
VIN=12V
VIN=20V
40
OOA
VIN=8V
60
VIN=12V
40
20
VIN=20V
OOA
PWM Only
PWM Only
0
0.001
0.01
0.1
1
10
0
0.001
0.01
0.1
5-V Switcher ON
1
10
IOUT2 - 3.3-V Output Current - A
IOUT1 - 5-V Output Current - A
Figure 27.
16
22
3.3-V EFFICIENCY
vs
OUTPUT CURRENT
80
20
20
Figure 26.
5-V EFFICIENCY
vs
OUTPUT CURRENT
100
18
V IN - Input Voltage - V
Figure 28.
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TYPICAL CHARACTERISTICS (continued)
5-V Load Transient Response
VOUT1 (100mV/div)
3.3-V Load Transient Response
VOUT2 (100mV/div)
IIND (5A/div)
IIND (5A/div)
IOUT2 (5A/div)
IOUT1 (5A/div)
Figure 29.
Figure 30.
5-V Startup Waveforms
3.3-V Startup Waveforms
ENTRIP2 (2V/div)
ENTRIP1 (2V/div)
VOUT1 (2V/div)
VOUT2 (2V/div)
PGOOD (2V/div)
PGOOD (2V/div)
Figure 31.
Figure 32.
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TYPICAL CHARACTERISTICS (continued)
5-V Switchover Waveforms
3.3-V Switchover Waveforms
VREG5 (200mV/div)
VREG3 (200mV/div)
VOUT2 (200mV/div)
VOUT1 (200mV/div)
Figure 33.
Figure 34.
5-V Soft-stop Waveforms
3.3-V Soft-stop Waveforms
ENTRIP1 (5V/div)
ENTRIP2 (5V/div)
VOUT1 (2V/div)
VOUT2 (2V/div)
PGOOD (5V/div)
PGOOD (5V/div)
DRVL2 (5V/div)
DRVL1 (5V/div)
Figure 35.
18
Figure 36.
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APPLICATION INFORMATION
PWM Operations
The main control loop of the switch mode power supply (SMPS) is designed as an adaptive on-time pulse width
modulation (PWM) controller. It supports a proprietary D-CAP™ mode. D-CAP™ mode does not require external
compensation circuit and is suitable for low external component count configuration when used with appropriate
amount of ESR at the output capacitor(s).
At the beginning of each cycle, the synchronous top MOSFET is turned on, or becomes ‘ON’ state. This
MOSFET is turned off, or becomes ‘OFF’ state, after internal one shot timer expires. This one shot is determined
by VIN and VOUT to keep frequency fairly constant over input voltage range, hence it is called adaptive on-time
control. The MOSFET is turned on again when the feedback point voltage, VFB, decreased to match with internal
2-V reference. The inductor current information is also monitored and should be below the over current threshold
to initiate this new cycle. Repeating operation in this manner, the controller regulates the output voltage. The
synchronous bottom or the “rectifying” MOSFET is turned on at the beginning of each ‘OFF’ state to keep the
conduction loss minimum.The rectifying MOSFET is turned off before the top MOSFET turns on at next switching
cycle or when inductor current information detects zero level. In the auto-skip mode or the OOA skip mode, this
enables seamless transition to the reduced frequency operation at light load condition so that high efficiency is
kept over broad range of load current.
Adaptive On-Time Control and PWM Frequency
TPS51125 does not have a dedicated oscillator on board. However, the part runs with pseudo-constant
frequency by feed-forwarding the input and output voltage into the on-time, one-shot timer. The on-time is
controlled inverse proportional to the input voltage and proportional to the output voltage so that the duty ratio will
be kept as VOUT/VIN technically with the same cycle time. The frequencies are set by TONSEL terminal
connection as Table 2.
Table 2. TONSEL Connection and Switching Frequency
TONSEL CONNECTION
SWITCHING FREQUENCY
CH1
CH2
GND
200 kHz
250 kHz
VREF
245 kHz
305 kHz
VREG3
300 kHz
375 kHz
VREG5
365 kHz
460 kHz
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Loop Compensation
From small-signal loop analysis, a buck converter using D-CAPTM mode can be simplified as below.
VIN
R1
DRVH
PWM
VFB
+
R2
+
Control
logic
&
Driver
Lx
Ic
IL
DRVL
Io
2V
ESR
Vc
Voltage Divider
RL
Switching Modulator
Co
Output Capacitor
Figure 37. Simplifying the Modulator
The output voltage is compared with internal reference voltage after divider resistors, R1 and R2. The PWM
comparator determines the timing to turn on high-side MOSFET. The gain and speed of the comparator is high
enough to keep the voltage at the beginning of each on cycle substantially constant. For the loop stability, the
0dB frequency, f0, defined below need to be lower than 1/4 of the switching frequency.
f0 =
f
1
£ sw
2p ´ ESR ´ Co
4
(1)
TM
As f0 is determined solely by the output capacitor's characteristics, loop stability of D-CAP mode is determined
by the capacitor's chemistry. For example, specialty polymer capacitors (SP-CAP) have Co in the order of
several 100 µF and ESR in range of 10 mΩ. These will make f0 in the order of 100 kHz or less and the loop will
be stable. However, ceramic capacitors have f0 at more than 700 kHz, which is not suitable for this operational
mode.
Ramp Signal
The TPS51125 adds a ramp signal to the 2-V reference in order to improve its jitter performance. As described in
the previous section, the feedback voltage is compared with the reference information to keep the output voltage
in regulation. By adding a small ramp signal to the reference, the S/N ratio at the onset of a new switching cycle
is improved. Therefore the operation becomes less jitter and stable. The ramp signal is controlled to start with
-20mV at the beginning of ON-cycle and to become 0 mV at the end of OFF-cycle in steady state. By using this
scheme, the TPS51125 improve jitter performance without sacrificing the reference accuracy.
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Light Load Condition in Auto-Skip Operation
The TPS51125 automatically reduces switching frequency at light load conditions to maintain high efficiency.
This reduction of frequency is achieved smoothly and without increase of VOUT ripple. Detail operation is
described as follows. As the output current decreases from heavy load condition, the inductor current is also
reduced and eventually comes to the point that its ‘valley’ touches zero current, which is the boundary between
continuous conduction and discontinuous conduction modes. The rectifying MOSFET is turned off when this zero
inductor current is detected. As the load current further decreased, the converter runs in discontinuous
conduction mode and it takes longer and longer to discharge the output capacitor to the level that requires next
‘ON’ cycle. The ON time is kept the same as that in the heavy load condition. In reverse, when the output current
increase from light load to heavy load, switching frequency increases to the preset value as the inductor current
reaches to the continuous conduction. The transition load point to the light load operation IOUT(LL) (i.e. the
threshold between continuous and discontinuous conduction mode) can be calculated as follows;
I
=
OUT ( LL )
(
)´
1
´ V IN V OUT V OUT
2´ L´ f
V IN
(2)
where f is the PWM switching frequency.
Switching frequency versus output current in the light load condition is a function of L, VIN and VOUT, but it
decreases almost proportional to the output current from the IOUT(LL) given above. For example, it will be 60 kHz
at IOUT(LL)/5 if the frequency setting is 300 kHz.
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Out-of-Audio™ Light-Load Operation
Out-of-Audio™ (OOA) light-load mode is a unique control feature that keeps the switching frequency above
acoustic audible frequencies toward virtually no load condition while maintaining best of the art high conversion
efficiency. When the Out-of-Audio™ operation is selected, OOA control circuit monitors the states of both
MOSFET and force to change into the ‘ON’ state if both of MOSFETs are off for more than 32 µs. This means
that the top MOSFET is turned on even if the output voltage is higher than the target value so that the output
capacitor is tends to be overcharged.
The OOA control circuit detects the over-voltage condition and begins to modulate the on time to keep the output
voltage regulated. As a result, the output voltage becomes 0.5% higher than normal light-load operation.
Enable and Soft Start
EN0 is the control pin of VREG5, VREG3 and VREF regulators. Bring this node down to GND disables those
three regulators and minimize the shutdown supply current to 10 µA. Pulling this node up to 3.3 V or 5 V will turn
the three regulators on to standby mode. The two switch mode power supplies (channel-1, channel-2) become
ready to enable at this standby mode. The TPS51125 has an internal, 1.6 ms, voltage servo softstart for each
channel. When the ENTRIPx pin becomes higher than the enable threshold voltage, which is typically 430 mV,
an internal DAC begins ramping up the reference voltage to the PWM comparator. Smooth control of the output
voltage is maintained during start up. As TPS51125 shares one DAC with both channels, if ENTRIPx pin
becomes higher than the enable threshold voltage while another channel is starting up, soft start is postponed
until another channel soft start has completed. If both of ENTRIP1 and ENTRIP2 become higher than the enable
threshold voltage at a same time (within 60 µs), both channels start up at same time.
Table 3. Enabling State
EN0
ENTRIP1
ENTRIP2
VREF
VREG5
VREG3
CH1
CH2
VCLK
GND
Don’t Care
Don’t Care
Off
Off
Off
Off
Off
Off
R to GND
Off
Off
On
On
On
Off
Off
Off
R to GND
On
Off
On
On
On
On
Off
Off
R to GND
Off
On
On
On
On
Off
On
Off
R to GND
On
On
On
On
On
On
On
Off
Open
Off
Off
On
On
On
Off
Off
Off
Open
On
Off
On
On
On
On
Off
On
Open
Off
On
On
On
On
Off
On
Off
Open
On
On
On
On
On
On
On
On
VREG5/VREG3 Linear Regulators
There are two sets of 100-mA standby linear regulators which outputs 5 V and 3.3 V, respectively. The VREG5
serves as the main power supply for the analog circuitry of the device and provides the current for gate drivers.
The VREG3 is intended mainly for auxiliary 3.3-V supply for the notebook system during standby mode.
Add a ceramic capacitor with a value between 10 µF and 22 µF placed close to the VREG5 and VREG3 pins to
stabilize LDOs.
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VREG5 Switch Over
When the VO1 voltage becomes higher than 4.7 V AND channel-1 internal powergood flag is generated, internal
5-V LDO regulator is shut off and the VREG5 output is connected to VO1 by internal switch over MOSFET. The
510-µs powergood delay helps a switch over without glitch.
VREG3 Switch Over
When the VO2 voltage becomes higher than 3.15 V AND channel-2 internal powergood flag is generated,
internal 3.3-V LDO regulator is shut off and the VREG3 output is connected to VO2 by internal switch over
MOSFET. The 510-µs powergood delay helps a switch over without glitch.
Powergood
The TPS51125 has one powergood output that indicates 'high' when both switcher outputs are within the targets
(AND gated). The powergood function is activated with 2-ms internal delay after ENTRIPx goes high. If the
output voltage becomes within +/-5% of the target value, internal comparators detect power good state and the
powergood signal becomes high after 510-µs internal delay. Therefore PGOOD goes high around 2.5 ms after
ENTRIPx goes high. If the output voltage goes outside of +/-10% of the target value, the powergood signal
becomes low after 2-µs internal delay. The powergood output is an open drain output and is needed to be pulled
up outside.
Output Discharge Control
When ENTRIPx is low, the TPS51125 discharges outputs using internal MOSFET which is connected to VOx
and GND. The current capability of these MOSFETs is limited to discharge slowly.
Low-Side Driver
The low-side driver is designed to drive high current low RDS(on) N-channel MOSFET(s). The drive capability is
represented by its internal resistance, which are 4 Ω for VREG5 to DRVLx and 1.5 Ω for DRVLx to GND. A dead
time to prevent shoot through is internally generated between top MOSFET off to bottom MOSFET on, and
bottom MOSFET off to top MOSFET on. 5-V bias voltage is delivered from VREG5 supply. The instantaneous
drive current is supplied by an input capacitor connected between VREG5 and GND. The average drive current
is equal to the gate charge at Vgs = 5 V times switching frequency. This gate drive current as well as the
high-side gate drive current times 5 V makes the driving power which need to be dissipated from TPS51125
package.
High-Side Driver
The high-side driver is designed to drive high current, low RDS(on) N-channel MOSFET(s). When configured as a
floating driver, 5-V bias voltage is delivered from VREG5 supply. The average drive current is also calculated by
the gate charge at Vgs = 5 V times switching frequency. The instantaneous drive current is supplied by the flying
capacitor between VBSTx and LLx pins. The drive capability is represented by its internal resistance, which are 4
Ω for VBSTx to DRVHx and 1.5Ω for DRVHx to LLx.
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VCLK for Charge Pump
270-kHz clock signal can be used for charge pump circuit to generate approximately 15-V dc voltage. The clock
signal becomes available when EN0 becomes higher than 2.4 V or open state. Note that the clock driver uses
VO1 as its power supply. Regardless of enable or disable of VCLK, power consumption of the TPS51125 is
almost the same. Therefore even if VCLK is not used, one can let EN0 pin open or supply logic ‘high’, as shown
in Figure 38, and let VCLK pin open. This approach further reduces the external part count.
3.3V
TPS51125
TPS51125
EN0
EN0
Control
Input
13
13
GND
GND
Control
Input
15
15
(b) Control by Logic
(a) Control by MOSFET switch
Figure 38. Control Example of EN0 Master Enable
VCLK 18
100nF
100nF
VO1 (5V)
D0
D1
100nF
PGND
D2
100nF
PGND
15V/10mA
D4
1uF
PGND
Figure 39. 15-V / 10-mA Charge Pump Configuration
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Current Protection
TPS51125 has cycle-by-cycle over current limiting control. The inductor current is monitored during the ‘OFF’
state and the controller keeps the ‘OFF’ state during the inductor current is larger than the over current trip level.
In order to provide both good accuracy and cost effective solution, TPS51125 supports temperature
compensated MOSFET RDS(on) sensing. ENTRIPx pin should be connected to GND through the trip voltage
setting resistor, RTRIP. ENTRIPx terminal sources ITRIP current, which is 10 µA typically at room temperature, and
the trip level is set to the OCL trip voltage VTRIP as below. Note that the VTRIP is limited up to about 205 mV
internally.
Vtrip ( mV ) =
Rtrip ( k W ) ´ I trip ( m A )
9
- 24( mV )
(3)
The inductor current is monitored by the voltage between GND pin and LLx pin so that LLx pin should be
connected to the drain terminal of the bottom MOSFET properly. Itrip has 4500 ppm/°C temperature slope to
compensate the temperature dependency of the RDS(on). GND is used as the positive current sensing node so
that GND should be connected to the proper current sensing device, i.e. the source terminal of the bottom
MOSFET.
As the comparison is done during the ‘OFF’ state, VTRIP sets valley level of the inductor current. Thus, the load
current at over current threshold, IOCP, can be calculated as follows;
I ocp = Vtrip Rdson + I ripple 2
=
Vtrip
Rdson
+
(4)
(V - VOUT ) ´ VOUT
1
´ IN
2´ L´ f
VIN
(5)
In an over current condition, the current to the load exceeds the current to the output capacitor thus the output
voltage tends to fall down. Eventually, it ends up with crossing the under voltage protection threshold and
shutdown both channels.
Over/Under Voltage Protection
TPS51125 monitors a resistor divided feedback voltage to detect over and under voltage. When the feedback
voltage becomes higher than 115% of the target voltage, the OVP comparator output goes high and the circuit
latches as the top MOSFET driver OFF and the bottom MOSFET driver ON.
Also, TPS51125 monitors VOx voltage directly and if it becomes greater than 5.75 V the TPS51125 turns off the
top MOSFET driver.
When the feedback voltage becomes lower than 60% of the target voltage, the UVP comparator output goes
high and an internal UVP delay counter begins counting. After 32 µs, TPS51125 latches OFF both top and
bottom MOSFETs drivers, and shut off both drivers of another channel. This function is enabled after 2 ms
following ENTRIPx has become high.
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UVLO Protection
TPS51125 has VREG5 under voltage lock out protection (UVLO). When the VREG5 voltage is lower than UVLO
threshold voltage both switch mode power supplies are shut off. This is non-latch protection. When the VREG3
voltage is lower than (VO2 - 1 V), both switch mode power supplies are also shut off
Thermal Shutdown
TPS51125 monitors the temperature of itself. If the temperature exceeds the threshold value (typically 150°C),
TPS51125 is shut off including LDOs. This is non-latch protection.
External Parts Selection
The external components selection is much simple in D-CAP™ Mode.
1. Determine the Value of R1 and R2
Recommended R2 value is from 10 kΩ to 20 kΩ. Determine R1 using equation as below.
R1 =
(V out - 2.0)
2 .0
´ R2
(6)
2. Choose the Inductor
The inductance value should be determined to give the ripple current of approximately 1/4 to 1/2 of maximum
output current. Larger ripple current increases output ripple voltage and improves S/N ratio and helps stable
operation.
L=
1
I
IND( ripple )
´f
´
(V
IN (max)
)
-V OUT ´V OUT
V
IN (max)
=
3
I
OUT (max)
´f
´
(V
IN (max)
)
-V OUT ´V OUT
V
IN (max)
(7)
The inductor also needs to have low DCR to achieve good efficiency, as well as enough room above peak
inductor current before saturation. The peak inductor current can be estimated as follows.
I
IND( peak )
=
Vtrip
RDS ( on )
+
(VIN (max) - VOUT ) ´ VOUT
1
´
L´ f
VIN (max)
(8)
3. Choose the Output Capacitor(s)
Organic semiconductor capacitor(s) or specialty polymer capacitor(s) are recommended. Determine ESR to meet
required ripple voltage above. A quick approximation is as shown in Equation 9. This equation is based on that
required output ripple slope is approximately 20 mV per TSW (switching period) in terms of VFB terminal voltage.
D stands for duty factor.
ESR = V OUT
26
´ 20[ mV ] ´ ( 1 - D )
2[V ] ´ I ripple
=
20[ mV ] ´ L ´ f
2[V ]
(9)
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Copyright © 2007, Texas Instruments Incorporated
Product Folder Link(s): TPS51125
TPS51125
www.ti.com
SLUS786A – OCTOBER 2007 – REVISED NOVEMBER 2007
Layout Considerations
Certain points must be considered before starting a layout work using the TPS51125.
• TPS51125 has only one GND pin and special care of GND trace design makes operation stable, especially
when both channels operate. Group GND terminals of output voltage divider of both channels and the VREF
capacitor as close as possible, connect them to an inner GND plane with PowerPad, overcurrent setting
resistor, EN0 pull-down resistor and EN0 bypass capacitor as shown in the thin GND line of Figure 40. This
trace is named Signal Ground (SGND). Group ground terminals of VIN capacitor(s), VOUT capacitor(s) and
source of low-side MOSFETs as close as possible, and connect them to another inner GND plane with GND
pin of the device, GND terminal of VREG3 and VREG5 capacitors as shown in the bold GND line of
Figure 40. This trace is named Power Ground (PGND). SGND and 15-V charge-pump circuit should be
connected to PGND at the middle point between ground terminal of VOUT capacitors.
• Inductor, VOUT capacitor(s), VIN capacitor(s) and MOSFETs are the power components and should be
placed on one side of the PCB (solder side). Power components of each channel should be at the same
distance from the TPS51125. Other small signal parts should be placed on another side (component side).
Inner GND planes above should shield and isolate the small signal traces from noisy power lines.
• PCB trace defined as LLx node, which connects to source of high-side MOSFET, drain of low-side MOSFET
and high-voltage side of the inductor, should be as short and wide as possible.
• VREG5 and VREG3 require at least 10-µF, VREF requires a 220-nF ceramic bypass capacitor which should
be placed close to the device and traces should be no longer than 10 mm.
• Connect the overcurrent setting resistors from ENTRIPx to SGND and close to the device, right next to the
device if possible.
• The discharge path (VOx) should have a dedicated trace to the output capacitor; separate from the output
voltage sensing trace. When LDO5 is switched over Vo1 trace should be 1.5 mm with no loops. When LDO3
is switched over and loaded Vo2 trace should also be 1.5 mm with no loops. There is no restriction for just
monitoring Vox. Make the feedback current setting resistor (the resistor between VFBx to SGND close to the
device. Place on the component side and avoid vias between this resistor and the device.
• Connections from the drivers to the respective gate of the high-side or the low-side MOSFET should be as
short as possible to reduce stray inductance. Use 0.65-mm (25 mils) or wider trace and via(s) of at least 0.5
mm (20 mils) diameter along this trace.
• All sensitive analog traces and components such as VOx, VFBx, VREF, GND, EN0, ENTRIPx, PGOOD,
TONSEL and SKIPSEL should be placed away from high-voltage switching nodes such as LLx, DRVLx,
DRVHx and VCLK nodes to avoid coupling. Connect 330-pF to 1-nF ceramic bypass capacitor to EN0 in
parallel with 620-kΩ resistor when VCLK is disabled.
• Traces for VFB1 and VFB2 should be short and laid apart each other to avoid channel to channel
interference.
• In order to effectively remove heat from the package, prepare thermal land and solder to the package’s
thermal pad. Three by three or more vias with a 0.33-mm (13 mils) diameter connected from the thermal land
to the internal ground plane should be used to help dissipation. This thermal land underneath the package
should be connected to SGND, and should NOT be connected to PGND.
SGND
VIN
220n
F
VIN
TPS51125
5
3
2
VFB2
VREF
VFB1
Vout1
Vout2
DRVL2
DRVL1
12
19
PGND
PGND
PowerPAD
VREG5
17
GND
15
10u
F
VREG3
15V Out
8
10u
F
VCLK
Chargepump
SGND
Figure 40. GND system of DC/DC converter using the TPS51125
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Product Folder Link(s): TPS51125
27
PACKAGE MATERIALS INFORMATION
www.ti.com
21-Nov-2007
TAPE AND REEL BOX INFORMATION
Device
Package Pins
Site
Reel
Diameter
(mm)
Reel
Width
(mm)
A0 (mm)
B0 (mm)
K0 (mm)
P1
(mm)
W
Pin1
(mm) Quadrant
TPS51125RGER
RGE
24
SITE 41
330
12
4.3
4.3
1.5
8
12
Q2
TPS51125RGET
RGE
24
SITE 41
180
12
4.3
4.3
1.5
8
12
Q2
Pack Materials-Page 1
PACKAGE MATERIALS INFORMATION
www.ti.com
21-Nov-2007
Device
Package
Pins
Site
Length (mm)
Width (mm)
TPS51125RGER
RGE
24
SITE 41
346.0
346.0
29.0
TPS51125RGET
RGE
24
SITE 41
190.0
212.7
31.75
Pack Materials-Page 2
Height (mm)
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