TEMIC U210B1

U210B1
Phase Control Circuit–Load Current Feedback Applications
Description
The interated circuit, U210B1, is designed as a phasecontrol circuit for load-current feedback application in
bipolar technology. To realize motor control systems, it
has integrated load current detection, voltage monitoring
and soft-start functions. The voltage obtained due to load
current proportionality, can be used according to the
application i.e., load-current compensation or loadcurrent regulation.
Features
D
D
D
D
D
Externally controlled integrated amplifier
Variable soft start
Automatic retriggering
D Internal supply voltage monitoring
D Temperature constant reference source
D Current requirement ≤ 3 mA
Voltage and current synchronization
Package: DIP14
Triggering pulse typ. 125 mA
14
Voltage
detector
1
Current
detector
Automatic
retriggering
Output
pulse
4
5
8
+
7
6
Control
amplifier
Phase
control unit
ö = f (V12)
–
3
Supply
voltage
limitation
Reference
voltage
2
–VS
GND
13
Voltage
monitoring
Load
current
detection
12
11
Soft start
9
10
95 10686
Figure 1. Block diagram
TELEFUNKEN Semiconductors
Rev. A1, 28-May-96
1 (12)
2 (12)
R6
4.7 k W
R9
10 kW
2.2 m F/
16 V
C9
R7
100 k W
Set speed
voltage
12
C3
220 nF
7
8
–
+
Load
current
detector
1
11
9
R5
2 kW
R4
470 k W
Current
detector
Control
amplifier
Voltage
detector
14
R3
220 kW
C4
10 m F/
16 V
10
Soft start
Phase
control unit
ö = f (V12 )
Automatic
retriggering
Voltage
monitoring
Reference
voltage
Supply
voltage
limitation
Output
pulse
C2
10 nF
13
GND
C5
C1
100 W
R 12
R 2 220 k W
2 –VS
3
6
5
4
95 10693
18 k W
1.5 W
1N4007
1 mF/
16 V
M
22 mF/
25 V
50 m W
R1
D1
R8
BTA
12–800
X
N
VM =
230 V
L
U210B1
Figure 2. Block diagram with external circuitry Open loop control with load current compensation
TELEFUNKEN Semiconductors
Rev. A1, 28-May-96
U210B1
Description
Mains Supply
The U210B1 is fitted with voltage limiting and can therefore be supplied directly from the mains. The supply
voltage between Pin 2 (+pol/ ) and Pin 3 builds up
across D1 and R1 and is smoothed by C1. The vaIue of the
series resistance can be approximated using:
ă
R1=
VM–VS
2 IS
Further information regarding the design of the mains
supply can be found in the data sheets in the appendix.
The reference voltage source on Pin 13 of typ. –8.9 V is
derived from the supply voltage. It represents the reference level of the control unit.
Operation using an externally stabiIised dc voltage is not
recommended.
If the supply cannot be taken directly from the mains because the power dissipation in R1 would be too large, then
the circuit shown in the following figure 3 should be
employed.
~
24 V~
1
R1
2
3
4
5
The current sensor on Pin 1 ensures that, for operation
with inductive loads, no pulse will be generated in a new
half cycle as long as current from the previous half cycle
is still flowing in the opposite direction to the supply voltage at that instant. This makes sure that “Gaps” in the load
current are prevented.
The control signal on Pin 9 can be in the range 0 V to –7 V
(reference point Pin 2).
If V9 = –7 V then the phase angle is at maximum = max
i .e. the current flow angle is a minimum. The minimum
phase angle min is when V9 = V2.
Voltage Monitoring
As the voltage is built up, uncontrolled output pulses are
avoided by internal voltage surveillance. At the same
time, all of the latches in the circuit (phase control, soft
start) are reset and the soft-start capacitor is short circuited. Used with a switching hysteresis of 300 mV, this
system guarantees defined start-up behaviour each time
the supply voltage is switched on or after short interruptions of the mains supply.
Soft-Start
C1
95 10362
Figure 3. Supply voltage for high current requirements
Phase Control
The function of the phase control is largely identical to
that of the well known component TEA1007. The phase
angle of the trigger pulse is derived by comparing the
ramp voltage, which is mains synchronized by the voltage
detector, with the set value on the control input Pin 9. The
slope of the ramp is determined by C2 and its charging
current. The charging current can be varied using R2 on
Pin 5. The maximum phase angle max can also be
adjusted using R2.
TELEFUNKEN Semiconductors
Rev. A1, 28-May-96
When the potential on Pin 6 reaches the nominal value
predetermined at Pin 9, then a trigger pulse is generated
whose width tp is determined by the value of C2 (the value
of C2 and hence the pulse width can be evaluated by
assuming 8 s/nF). At the same time, a latch is set, so that
as long as the automatic retriggering has not been
activated, then no more pulses can be generated in that
half cycle.
As soon as the supply voltage builds up (t1), the integrated
soft-start is initiated. The figure below shows the
behavior of the voltage across the soft-start capacitor and
is identical with the voltage on the phase control input on
Pin 9. This behaviour allows a gentle start-up for the
motor.
C4 is first charged with typ. 30 A. The charging current
then increases as the voltage across C4 increases giving a
progressively rising charging function with more and
more strongly accelerates the motor with increasing rotational speed. The charging function determines the
acceleration up to the set point. The charging current can
have a maximum value of 85 A.
3 (12)
U210B1
96 11565
V10
Pulse Output Stage
The pulse output stage is short circuit protected and can
typically deliver currents of 125 mA. For the design of
smaller triggering currents, the function IGT = f (RGT) has
been given in the data sheets in the appendix. In contrast
to the TEA1007, the pulse output stage of the U210B1 has
no gate bypass resistor.
V9
Automatic Retriggering
t
t1
t2
ttot
The automatic retriggering prevents half cycles without
current flow, even if the triac is turned off earlier e.g., due
to not exactly centred collector (brush lifter) or in the
event of unsuccessful triggering. After a time lapse of
tpp = 4.5 tp is generated another triggering pulse which is
repeated until either the triac fires or the half cycle
finishes.
General Hints and Explanation of Terms
Figure 4. Soft–start
t1
t2
ttot
= build-up of supply voltage
= run-up time
= total start-up time to required speed
Control Amplifier
The integrated control amplifier with differential input
has a bipolar current output, with typically ±110 mA at
Pin 9 and a transmittance of typ. 1000 mA/V. The amplification and frequency response are determined by external
circuit. For operation as a power control, it should be connected with Pin 7. Phase angle of the firing pulse can be
adjusted by using the voltage at Pin 8. An internal limiting
circuit prevents the voltage on Pin 9 becoming more
negative than V13 + 1 V.
Load Current Detection, Figure 2
Voltage drop across R8, dependent of load current, generates an input-current at Pin 11 limited by R5. Proportional
output current of 0.44 x I11 (CTR) is available at Pin 12.
It is proportional with respect to phase and amplitude of
load current.
Capacitor C3 integrates the current whereas resistor R7
evaluates it. The voltage obtained due to load current
proportionality, can be used according to the application
i.e., load current compensation or load current regulation.
4 (12)
To ensure safe and trouble-free operation, the following
points should be taken into consideration when circuits
are being constructed or in the design of printed boards.
D The connecting lines from C2 to Pin 6 and Pin 2 should
be as short as possible, and the connection to Pin 2
should not carry any additional high current such as
the load current. When selecting C2, a low temperature coefficient is desirable.
95 10716
V
Mains
Supply
p/2
p
3/2p
2p
VGT
Trigger
Pulse
tp
tpp = 4.5 tp
VL
Load
Voltage
ö
IL
Load
Current
F
Figure 5. Explanation of terms in phase relationship
TELEFUNKEN Semiconductors
Rev. A1, 28-May-96
U210B1
Absolute Maximum Ratings
Reference point Pin 2, unless otherwise specified
Parameters
t ≤ 10 ms
t ≤ 10 ms
Value
30
100
5
5
35
35
Unit
mA
Pin 1
Pin 14
Pin 1
Pin 14
Symbol
–IS
–is
–Isync.I
–Isync.V
–iI
iv
t ≤ 10 ms
Pin 11
Pin 11
–II
–II
2
5
mA
Pin 9
Pin 9
Pin 5
"I
–VI
0 to 7
500
1
mA
Pin 10
–VI
V13j to 0
V
Pin 4
Vo
VS to 5
V
Pin 8
Pin 7
VI
–VI
0 to VS
V13j to 0
V
Pin 13
Io
Tstg
Tj
Tamb
7.5
–40 to +125
125
–10 to +100
mA
°C
°C
°C
Symbol
RthJA
Value
120
Unit
K/W
Current requirement
q
Pin 3
t ≤ 10 ms
Synchronisation current
Load current monitoring
Input current
Phase control
Input voltage
Input current
Soft–start
Input voltage
Pulse output
Reverse voltage
Amplifier
Input voltage
Reference voltage source
Output current
Storage temperature range
Junction temperature
Ambient temperature range
"
I
–II
mA
V
mA
j
j
Thermal Resistance
Parameters
Junction ambient
DIP14
Electrical Characteristics
–Vs = 13 V, Tamb = 25°C, reference point Pin 2, unless otherwise specified
Parameters
Supply voltage for mains
operations
Supply voltage limitation
DC supply current
Reference voltage source
Test Conditions / Pins
Pin 3
–IS = 3 mA
–IS = 30 mA
–VS =13 V
–IL = 10 mA
–IL = 5 mA
Temperature coefficient
Voltage monitoring
Turn-on threshold
Turn-off threshold
TELEFUNKEN Semiconductors
Rev. A1, 28-May-96
Symbol
–VS
Min.
13.0
Pin 3
–VS
Pin 3
Pin 13
–IS
–VRef
14.6
14.7
1.2
8.6
8.3
Pin 13
–TCVRef
Pin 3
Pin 3
–VSON
–VSOFF
Typ.
2.5
8.9
Max.
VLimit
Unit
V
16.6
16.8
3.0
9.2
9.1
V
0.5
9.9
11.2
10.9
mA
V
mV/K
13.0
V
V
5 (12)
U210B1
Parameters
Phase control currents
Current synchronization
Voltage synchronization
Voltage limitation
Reference ramp, figure 6
Load current
R–reference voltage
Temperature coefficient
Pulse output, figure 11
Output pulse current
Reverse current
Output pulse width
Automatic retriggering
Repetition rate
Amplifier
Common mode voltage
range
Input bias current
Input offset voltage
Output current
Test Conditions / Pins
Symbol
Min.
Isync.I
Isync.V
VI
VI
0.35
0.35
8.0
8.0
I6 = f(RF)
Figure 6
Rf = 1 K ... 820 K Pin 6
≥ 180 °
Pin5,3
Pin 5
I6
VRef
TCVRef
1
1.06
RGT= 0, VGT=1.2 V Pin 4
Pin 4
C = 10 nF
Pin4,2
Io
Ior
tp
100
125
0.01
80
150
3.0
mA
A
s
Pin 4
tpp
3
4.5
6
tp
Pin7,8
V7,8
V13
–1
V
Pin 8
Pin7,8
Pin 9
IIB
VIO
–IO
+IO
Yf
1
A
±IS= 5 mA
Figure 9
Pin 1
Pin 14
Pin 1
Pin 14
Short circuit forward trans- I12 = f(V10-11)
Pin 9
mittance
Soft-start, figures 7, 8
Pin 10
Starting current
V10 = V13
Final current
V10 = –0.5 V
Discharge current, restart
pulse
Load current detection, figure 10
Pin 11
Input current voltage
VI = 300 mV, R1 = 1 K
Input offset voltage
Output open current
Output current
Current transfer ratio
I 12
CTR
I 11
+
Temperature coefficient of
current transfer ratio
6 (12)
VI = 0 V, R1= 1 K Pin 12
VI = 300 mV, R1 = 1 K
V12 = V13
Pin 12
I12 = 150 A
Pin 12/11
Pin 12/11
I12 = 300 A
Pin 12/11
"
"
75
88
IO
IO
–IO
20
50
0.5
II
II
VIO
IO
0
300
–8
1.9
IO
CTR
120
TC
Typ.
Max.
Unit
mA
8.9
8.9
3.5
3.5
9.5
9.5
1.13
0.5
0.01
13
110
120
1000
30
85
3
127
0.44 ± 5%
0.42 ± 6%
0.2
20
1.18
145
165
50
130
10
V
A
V
mV/K
mV
A
A/V
A
A
mA
A
A
500
308
0
5.5
mV
A
134
A
0/ /K
00
TELEFUNKEN Semiconductors
Rev. A1, 28-May-96
U210B1
240
Phase Control
Reference Point Pin 2
200
Control Amplifier
4.7nF
50
2.2nF
I 9 ( A )
Phase Angle
(° )
10nF
100
160
0
120
–50
C /t=1.5nF
80
–100
Reference Point Pin 13
0
0
0.2
95 10302
0.4
0.6
R ( M )
0.8
–300
1.0
–200
100
200
300
Figure 9.
100
500
Soft Start
80
R5=100
400
Reference Point for:
I12 Pin 13, VR8 Pin 2
220
500
60
I12 ( A )
I 10 ( A )
0
V7–8 ( V )
96 11615
Figure 6.
40
300
1k
2k
200
20
100
f/V-Converter non–active
Reference Point Pin 13
0
0
2
4
6
8
V10 ( V )
96 11616
–100
0
10
0
0.15
0.3
0.45
0.6
0.75
V(R8) ( V )
95 10336
Figure 7.
Figure 10.
10
100
8
80
Pulse Output
I GT ( mA )
V10 ( V )
Soft Start
6
4
2
60
40
1.4V
VGT = 0.8V
20
f/V-Converter non–active
Reference Point Pin 13
0
0
0
96 11617
t=f(C4)
Figure 8.
TELEFUNKEN Semiconductors
Rev. A1, 28-May-96
95 10313
200
400
600
RGT ( )
800
1000
Figure 11.
7 (12)
U210B1
50
Design Calculations for Mains Supply
40
The following equations can be used for the evaluation of
the series resistor R1 for worst case conditions:
R 1( kW )
Mains Supply
30
R 1max
Mmin
Smax
R 1min
tot
20
P (R1max)
10
Mmax
Smin
+ V 2 –I V
M
Smin
Smax
2
1
0
0
4
8
16
12
Itot ( mA )
95 10315
Figure 12.
6
5
Mains Supply
P(R1) ( W )
+ 0.85 V 2 –I V
+ (V 2 –RV )
4
3
X
where:
VM = Mains voltage, 230 V
VS
= Supply voltage on Pin 3
= Total DC current requirement of the circuit
Itot
= ISmax + Ip + Ix
ISmax = Current requirement of the IC in mA
= Average current requirement of the triggering
Ip
pulses
= Current requirement of other peripheral
Ix
components
R1 can be easily evaluated from the diagrams figures 12
to 14.
2
1
0
0
10
20
R1 ( kW )
95 10316
40
30
Figure 13.
6
5
P(R1) ( W )
Mains Supply
4
3
2
1
0
0
95 10317
3
6
9
12
15
Itot ( mA )
Figure 14.
8 (12)
TELEFUNKEN Semiconductors
Rev. A1, 28-May-96
U210B1
Applications
In contrast to simple speed controller, the circuits shown
in figures 15 and 16, react to the load dependent speed
drop in which the magnitude of the load current acts on
the speed compensation.
The integrated load current proportional signal at C3
effects in the same direction on the control input as the set
point i.e., by the increase of load current follows an automatic increase of manipulated set point, so that a
compensation of speed falls.
For this purpose, the load current is measured by shunt
resistor R8. The voltage drop generates a current at Pin 11
dependent of R5, which reflects in the specified current at
the output of Pin 12.
Compensation arrangement is influenced with resistance
values i.e. R5 (= 100 to 5 k) and R7 (= 10 k to 150 k)
whereas the higher effect is achieved by increasing the
value of R7 and decreasing R5. Influence of compensation
can be increased up to the value where the drive system
(motor) starts to oscillate.
Rated impedance of the output current at Pin 12 is represented through the coupling resistance R7 and the total
impedance of the set point.
Dimensioning in the applications are with the drill
machine of 700 W power.
R6
4.7 k
L
220 nF
R3
220 k
230 V~
M
D1
1N4004
15 F
10 V
14
R1
18 k
1.5 W
13
R7
22 k
C3
C4
N
T1
R15
10 k
BC308B
min
max
R10
100 k
12
R5
2 k
11
10
9
8
5
6
7
95 10786
U210B
1
2
3
4
R4
470 k
BTA
12–800
R8
50 m
R2
R12
22 F
25 V
C1
100 220 k
C2
10 nF
Figure 15. Speed control with load current compensation
TELEFUNKEN Semiconductors
Rev. A1, 28-May-96
9 (12)
U210B1
R6
6.8 kW
L
C3
R3
220 kW
230 V~
N
M
20 kW
C4
R11
100 kW
15 mF
10 V
14
13
12
R5
2 kW
11
10
9
8
5
6
7
min
220 kW
max
R10
10 kW
U210B
95 10787
R1
18 kW
1.5 W
R7
220 nF
D1
1N4004
R15
1
2
3
4
R4
470 kW
BTA
12–800
R8
50 mW
R2
R12
C1
22 mF
25 V
100 W
220 kW
C2
10 nF
Figure 16. Speed control with load current compensation
10 (12)
TELEFUNKEN Semiconductors
Rev. A1, 28-May-96
U210B1
L
R3
220 kW
230 V~
N
C3
14
13
4.7 mF
10 V
15 mF
10 V
C4
470 nF
D1
1N4004
Load
R7
2.2 kW
R6
330 kW
12
11
C5
min
0.1 mF
9
10
C6
P1
100 kW
max
8
R9
47 kW
R1
18 kW
1.5 W
R5
2 kW
95 10788
U210B
1
2
3
5
4
6
7
R4
470 kW
BTA
12–800
R8
50 mW
R2
R12
C1
22 mF
25 V
100 kW
220 kW
C
10 nF
Figure 17. Load current regulation with soft start
Current regulation is achieved by the integrated operational amplifier as P1-controller (R7, C5, C6). Inverted
input (Pin 7) of the operational amplifier is directly connected at C3 with load current proportional test signal
(actual value).
Desired value is obtained with the help of potentiometer
at Pin 8.
Dimensions in mm
Package: DIP14
94 9445
TELEFUNKEN Semiconductors
Rev. A1, 28-May-96
11 (12)
U210B1
Ozone Depleting Substances Policy Statement
It is the policy of TEMIC TELEFUNKEN microelectronic GmbH to
1. Meet all present and future national and international statutory requirements.
2. Regularly and continuously improve the performance of our products, processes, distribution and operating systems
with respect to their impact on the health and safety of our employees and the public, as well as their impact on
the environment.
It is particular concern to control or eliminate releases of those substances into the atmosphere which are known as
ozone depleting substances ( ODSs).
The Montreal Protocol ( 1987) and its London Amendments ( 1990) intend to severely restrict the use of ODSs and
forbid their use within the next ten years. Various national and international initiatives are pressing for an earlier ban
on these substances.
TEMIC TELEFUNKEN microelectronic GmbH semiconductor division has been able to use its policy of
continuous improvements to eliminate the use of ODSs listed in the following documents.
1. Annex A, B and list of transitional substances of the Montreal Protocol and the London Amendments respectively
2 . Class I and II ozone depleting substances in the Clean Air Act Amendments of 1990 by the Environmental
Protection Agency ( EPA) in the USA
3. Council Decision 88/540/EEC and 91/690/EEC Annex A, B and C ( transitional substances ) respectively.
TEMIC can certify that our semiconductors are not manufactured with ozone depleting substances and do not contain
such substances.
We reserve the right to make changes to improve technical design and may do so without further notice.
Parameters can vary in different applications. All operating parameters must be validated for each customer
application by the customer. Should the buyer use TEMIC products for any unintended or unauthorized
application, the buyer shall indemnify TEMIC against all claims, costs, damages, and expenses, arising out of,
directly or indirectly, any claim of personal damage, injury or death associated with such unintended or
unauthorized use.
TEMIC TELEFUNKEN microelectronic GmbH, P.O.B. 3535, D-74025 Heilbronn, Germany
Telephone: 49 ( 0 ) 7131 67 2831, Fax number: 49 ( 0 ) 7131 67 2423
12 (12)
TELEFUNKEN Semiconductors
Rev. A1, 28-May-96