TEMIC U211B

U211B2/ B3
Phase Control Circuit - General Purpose Feedback
Description
The integrated circuit U211B2/ B3 is designed as a phase
control circuit in bipolar technology with an internal frequency-voltage converter. Furthermore, it has an internal
control amplifier which means it can be used for speedregulated motor applications.
It has an integrated load limitation, tacho monitoring and
soft-start functions, etc. to realize sophisticated motor
control systems.
Features
D
D
D
D
D
D
D
D
D
D
D
Internal frequency-to-voltage converter
Externally-controlled integrated amplifier
Overload limitation with a “fold back” characteristic
Optimized soft-start function
Tacho monitoring for shorted and open loop
Triggering pulse typ. 155 mA
Voltage and current synchronization
Internal supply-voltage monitoring
Temperature reference source
Current requirement ≤ 3 mA
Package:
Automatic retriggering switchable
17(16)
1(1)
DIP18 - U211B2,
SO16 - U211B3
5*)
Automatic
retriggering
Voltage / Current
detector
Output
pulse
Control
amplifier
11(10)
+
4(4)
6(5)
7(6)
10(9)
–
Phase
control unit
ö = f (V12)
3(3)
Supply
voltage
limitation
Reference
voltage
14(13)
15(14)
Load limitation
speed / time
controlled
2(2)
–V
S
GND
16(15)
Voltage
monitoring
controlled
current sink
Soft start
Pulse-blocking
tacho
monitoring
Frequencyto-voltage
converter
18*)
–VRef
12(11)
13(12)
9(8)
8(7)
95 10360
Figure 1. Block diagram (Pins in brackets refer to SO16)
*) Pins 5 and 18 connected internally
TELEFUNKEN Semiconductors
Rev. A1, 29-May-96
1 (20)
2 (20)
R19
100 k W
R14
56 k W
Actual speed
voltage
4.7m F /16V
C9
1 MW R
9
R 10
1 kW
2.2 m F /16V
C 10
Set speed
voltage
R 31
100 kW
47 k W
R13
C6
100 nF
15
14
10
11
Control
amplifier
22 k W
R7
C8
C3
220 nF
2.2 m F
16 V
C5
1 nF
8
R5
1 kW
C4
R6
100 kW
10 m F /16V
C7
9
C2
16
Speed sensor
95 10361
GND C
11
C1
1 MW
3.3 nF
R2
R 12
180 W
2 –V S
3
7
6
4
Pulse blocking
tacho
18
monitoring
2 MW
13
Frequency
to voltage
converter
Voltage
monitoring
Reference
voltage
Supply
voltage
limitation
Output
pulse
220 nF
12
–V Ref
Soft start
Phase
control unit
ö = f (V12 )
Automatic
retriggering
5
R11
controlled
current sink
Load limitation
speed / time
controlled
–
+
1
R4
470 k W
Voltage / Current
detector
17
R3
220 k W
18 kW
2W
1N4007
M
2.2 m F
22 m F
25 V
R8
33 m W
1W
TIC
226
R1
D1
N
VM =
230 V ~
L
U211B2/ B3
Figure 2. Speed control, automatic retriggering, load limiting, soft start
TELEFUNKEN Semiconductors
Rev. A1, 29-May-96
U211B2/ B3
Description
Mains Supply
The U211B2 is fitted with voltage limiting and can
therefore be supplied directly from the mains. The supply
voltage between Pin 2 (+ pol/ ) and Pin 3 builds up
across D1 and R1 and is smoothed by C1. The value of the
series resistance can be approximated using (see
figure 2):
ă
R1
+ V 2 –I V
M
When the potential on Pin 7 reaches the nominal value
predetermined at Pin 12, then a trigger pulse is generated
whose width tp is determined by the value of C2 (the value
of C2 and hence the pulse width can be evaluated by
assuming 8 ms/nF). At the same time, a latch is set, so that
as long as the automatic retriggering has not been
activated, then no more pulses can be generated in that
half cycle.
S
S
Further information regarding the design of the mains
supply can be found in the data sheets in the appendix.
The reference voltage source on Pin 16 of typ. –8.9 V is
derived from the supply voltage and is used for
regulation.
Operation using an externally stabilised DC voltage is not
recommended.
If the supply cannot be taken directly from the mains
because the power dissipation in R1 would be too large,
then the circuit shown in the following figure 3 should be
used.
The current sensor on Pin 1 ensures that, for operations
with inductive loads, no pulse will be generated in a new
half-cycle as long as a current from the previous half
cycle is still flowing in the opposite direction to the
supply voltage at that instant. This makes sure that “gaps”
in the load current are prevented.
The control signal on Pin 12 can be in the range 0 V to
–7 V (reference point Pin 2).
If V12 = –7 V then the phase angle is at maximum = amax
i.e., the current flow angle is a minimum. The phase angle
amin is minimum when V12 = V2.
~
Voltage Monitoring
24 V~
1
R1
2
3
4
5
C1
95 10362
As the voltage is built up, uncontrolled output pulses are
avoided by internal voltage surveillance. At the same
time, all of the latches in the circuit (phase control, load
limit regulation, soft start) are reset and the soft-start
capacitor is short circuited. Used with a switching
hysteresis of 300 mV, this system guarantees defined
start-up behavior each time the supply voltage is switched
on or after short interruptions of the mains supply.
Figure 3. Supply voltage for high current requirements
Phase Control
There is a general explanation in the data sheet,
TEA1007, on the common phase control function. The
phase angle of the trigger pulse is derived by comparing
the ramp voltage (which is mains synchronized by the
voltage detector) with the set value on the control input
Pin 12. The slope of the ramp is determined by C2 and its
charging current. The charging current can be varied
using R2 on Pin 6. The maximum phase angle amax can
also be adjusted using R2.
TELEFUNKEN Semiconductors
Rev. A1, 29-May-96
Soft-Start
As soon as the supply voltage builds up (t1), the integrated
soft-start is initiated. The figure below shows the
behaviour of the voltage across the soft-start capacitor
and is identical with the voltage on the phase control input
on Pin 12. This behaviour guarantees a gentle start-up for
the motor and automatically ensures the optimum run-up
time.
3 (20)
U211B2/ B3
95 10272
VC3
V12
The converter is based on the charge pumping principle.
With each negative half wave of the input signal, a
quantity of charge determined by C5 is internally
amplified and then integrated by C6 at the converter
output on Pin 10. The conversion constant is determined
by C5, its charge transfer voltage of Vch, R6 (Pin 10) and
the internally adjusted charge transfer gain.
Gi
V0
ƪ ƫ+
I 10
I9
k = Gi
t
t1
t3
t2
ttot
Figure 4. Soft-start
t1
t2
t1 + t2
t3
ttot
= build-up of supply voltage
= charging of C3 to starting voltage
= dead time
= run-up time
= total start-up time to required speed
C3 is first charged up to the starting voltage V0 with
typical 45 mA current (t2). By then reducing the charging
current to approx. 4 mA, the slope of the charging function
is substantially reduced so that the rotational speed of the
motor only slowly increases. The charging current then
increases as the voltage across C3 increases giving a
progressively rising charging function which accelerates
the motor more and more strongly with increasing
rotational speed. The charging function determines the
acceleration up to the set-point. The charging current can
have a maximum value of 55 mA.
Frequency to Voltage Converter
The internal frequency to voltage converter (f/Vconverter) generates a DC signal on Pin 10 which is
proportional to the rotational speed using an AC signal
from a tacho-generator or a light beam whose frequency
is in turn dependent on the rotational speed. The high
impedance input Pin 8, compares the tacho-voltage to a
switch-on threshold of typ. –100 mV. The switch-off
threshold is given with –50 mV. The hysteresis
guarantees very reliable operation even when relatively
simple tacho-generators are used. The tacho-frequency is
given by:
f
where:
4 (20)
+ 60n
p (Hz)
n = revolutions per minute
p = number of pulses per revolution
8.3
C5
R6
Vch
The analog output voltage is given by
VO = k
@f
The values of C5 and C6 must be such that for the highest
possible input frequency, the maximum output voltage
VO does not exceed 6 V. While C5 is charging up, the Ri
on Pin 9 is .approx. 6.7 kW. To obtain good linearity of the
f/V converter the time constant resulting from Ri and C5
should be considerably less (1/5) than the time span of the
negative half-cycle for the highest possible input
frequency. The amount of remaining ripple on the output
voltage on Pin 10 is dependent on C5, C6 and the internal
charge amplification.
∆VO =
Gi
Vch
C5
C6
The ripple ∆Vo can be reduced by using larger values of
C6. However, the increasing speed will then also be
reduced.
The value of this capacitor should be chosen to fit the
particular control loop where it is going to be used.
Pulse Blocking
The output of pulses can be blocked using Pin 18 (standby
operation) and the system reset via the voltage monitor if
V18 ≥ –1.25 V. After cycling through the switching point
hysteresis, the output is released when V18 ≤ –1.5 V
followed by a soft-start such as that after turn on.
Monitoring of the rotation can be carried out by
connecting an RC network to Pin 18. In the event of a
short or open circuit, the triac triggering pulses are cut off
by the time delay which is determined by R and C. The
capacitor C is discharged via an internal resistance
Ri = 2 kW with each charge transfer process of the f/V
converter. If there are no more charge transfer processes
C is charged up via R until the switch-off threshold is
exceeded and the triac triggering pulses are cut off. For
operation without trigger pulse blocking or monitoring of
the rotation, Pins 18 and 16 must be connected together.
TELEFUNKEN Semiconductors
Rev. A1, 29-May-96
U211B2/ B3
(reference voltage Pin 16) then a latch is set and the load
limiting is turned on. A current source (sink) controlled
by the control voltage on Pin 15 now draws current from
Pin 12 and lowers the control voltage on Pin 12 so that the
phase angle is increased to max.
C = 1 F
10 V
18
17
16
15
R = 1 M
1
2
3
4
95 10363
Figure 5. Operation delay
Control Amplifier (Figure 2)
The integrated control amplifier with differential input
compares the set value (Pin 11) with the instantaneous
value on Pin 10 and generates a regulating voltage on the
output Pin 12 (together with the external circuitry on
Pin 12) which always tries to hold the actual voltage at the
value of the set voltages. The amplifier has a
transmittance of typically 1000 A/V and a bipolar
current source output on Pin 12 which operates with
typically ±110 A. The amplification and frequency
response are determined by R7, C7, C8 and R11 (can be left
out). For open loop operation, C4, C5, R6, R7, C7, C8 and
R11 can be omitted. Pin 10 should be connected with
Pin 12 and Pin 8 with Pin 2. The phase angle of the
triggering pulse can be adjusted using the voltage on
Pin 11. An internal limitation circuit prevents the voltage
on Pin 12 from becoming more negative than V16 + 1 V.
Load Limitation
The load limitation, with standard circuitry, provides
absolute protection against overloading of the motor. the
function of the load limiting takes account of the fact that
motors operating at higher speeds can safely withstand
large power dissipations than at lower speeds due to the
increased action of the cooling fan. Similary, considerations have been made for short term overloads for the
motor which are, in practice, often required. These
finctions are not damaging and can be tolerated.
In each positive half-cycle, the circuit measures via R10
the load current on Pin 14 as a potential drop across R8
and produces a current proportional to the voltage on
Pin 14. This current is available on Pin 15 and is
integrated by C9. If, following high current amplitudes or
a large phase angle for current flow, the voltage on C9
exceeds an internally set threshold of approx. 7.3 V
TELEFUNKEN Semiconductors
Rev. A1, 29-May-96
The simultaneous reduction of the phase angle during
which current flows causes firstly: a reduction of the
rotational speed of the motor which can even drop to zero
if the angular momentum of the motor is excessively
large, and secondly: a reduction of the potential on C9
which in turn reduces the influence of the current sink on
Pin 12. The control voltage can then increase again and
bring down the phase angle. This cycle of action sets up
a “balanced condition” between the “current integral” on
Pin 15 and the control voltage on Pin 12.
Apart from the amplitude of the load current and the time
during which current flows, the potential on Pin 12 and
hence the rotational speed also affects the function of the
load limiting. A current proportional to the potential on
Pin 10 gives rise to a voltage drop across R10, via Pin 14,
so that the current measured on Pin 14 is smaller than the
actual current through R8.
This means that higher rotational speeds and higher
current amplitudes lead to the same current integral.
Therefore, at higher speeds, the power dissipation must
be greater than that at lower speeds before the internal
threshold voltage on Pin 15 is exceeded. The effect of
speed on the maximum power is determined by the
resistor R10 and can therefore be adjusted to suit each
individual application.
If, after the load limiting has been turned on, the
momentum of the load sinks below the “o-momentum”
set using R10, then V15 will be reduced. V12 can then increase again so that the phase angle is reduced. A smaller
phase angel corresponds to a larger momentum of the motor and hence the motor runs up - as long as this is allowed
by the load momentum. For an already rotating machine,
the effect of rotation on the measured “current integral”
ensures that the power dissipation is able to increase with
the rotational speed. the result is: a current controlled
accelleration run-up., which ends in a small peak of accelleraton when the set point is reached. The latch of the load
limiting is simultaneously reset. The speed of the motor
is then again under control and it is capable of carrying its
full load. The above mentioned peak of accelleration
depends upon the ripple of actual speed voltage. A large
amount of ripple also leads to a large peak of
accelleration.
The measuring resistor R8 should have a value which
ensures that the amplitude of the voltage across it does not
exceed 600 mV.
5 (20)
U211B2/ B3
Design Hints
Practical trials are normally needed for the exact
determination of the values of the relevant components in
the load limiting. To make this evaluation easier, the
Parameters
Pmax
Pmin
Pmax / min
td
tr
Pmax
Pmin
td
tr
n.e
following table shows the effect of the circuitry on the
important parameters of the load limiting and summarises
the general tendencies.
Component affected
R10
increases
increases
increases
n.e.
n.e.
– maximum continuous power dissipation
– power dissipation with no rotation
– operation delay time
– recovery time
– no effect
R9
decreases
decreases
n.e.
decreases
increases
C9
n.e.
n.e.
n.e.
increases
increases
0
P1 = f(n) n 0
P1 = f(n) n = 0
Pulse Output Stage
General Hints and Explanation of Terms
The pulse output stage is short circuit protected and can
typically deliver currents of 125 mA. For the design of
smaller triggering currents, the function IGT = f(RGT) has
been given in the data sheets in the appendix.
To ensure safe and trouble-free operation, the following
points should be taken into consideration when circuits
are being constructed or in the design of printed circuit
boards.
– The connecting lines from C2 to Pin 7 and Pin 2
should be as short as possible: The connection to Pin 2
should not carry any additional high current such as
the load current. When selecting C2, a low
temperature coefficient is desirable.
– The common (earth) connections of the set-point
generator, the tacho-generator and the final
interference suppression capacitor C4 of the f/V
converter should not carry load current.
– The tacho-generator should be mounted without
influence by strong stray fields from the motor.
– The connections from R10 and C5 should be as short
as possible.
To achieve a high noise immunity, a maximum ramp
voltage of 6 V should be used.
The typical resistance Rö can be calculated from Iö as
follows:
T(ms)
1.13(V)
10 3
R ö (kW)
C nF)
6(V)
Automatic Retriggering
The variable automatic retriggering prevents half cycles
without current flow, even if the triac is turned off earlier
e.g. due to a collector which is not exactly centered (brush
lifter) or in the event of unsuccessful triggering. If it is
necessary, another triggering pulse is generated after a
time lapse which is determined by the repetition rate set
by resistance between Pin 5 and Pin 3 (R5-3). With the
maximum repetition rate (Pin 5 directly connected to
Pin 3), the next attempt to trigger comes after a pause of
4.5 tp and this is repeated until either the triac fires or the
half-cycle finishes. If Pin 5 is connected, then only one
trigger pulse per half-cycle is generated. Because the
value of R5-3 determines the charging current of C2, any
repetition rate set using R5-3 is only valid for a fixed value
of C2.
+
ń
T = Period duration for mains frequency
(10 ms at 50 Hz)
Cö = Ramp capacitor, max. ramp voltage 6 V
and constant voltage drop at Rö = 1.13 V.
A 10% lower value of Rö (under worst case conditions)
is recommended.
6 (20)
TELEFUNKEN Semiconductors
Rev. A1, 29-May-96
U211B2/ B3
95 10716
V
Mains
Supply
p/2
p
3/2p
2p
VGT
Trigger
Pulse
tp
tpp = 4.5 tp
VL
Load
Voltage
ö
IL
Load
Current
F
Figure 6. Explanation of terms in phase relationship
Design Calculations for Mains Supply
The following equations can be used for the evaluation of the series resistor R1 for worst case conditions:
R 1max
+ 0.85 V
P (R1max)
+ (V
– V Smax
2 I tot
Mmin
R 1min
+ V 2 –I V
M
Smin
Smax
– V Smin) 2
2 R1
Mmax
where:
= Mains voltage
= Supply voltage on Pin 3
= Total DC current requirement of the circuit
Itot
= IS + Ip + Ix
ISmax = Current requirement of the IC in mA
Ip
= Average current requirement of the triggering pulse
= Current requirement of other peripheral components
Ix
R1 can be easily evaluated from the figures 20 to 22.
VM
VS
TELEFUNKEN Semiconductors
Rev. A1, 29-May-96
7 (20)
U211B2/ B3
Absolute Maximum Ratings
Reference point Pin 2, unless otherwise specified
Parameters
Current requirement
Pin 3
t ≤ 10 ms
Synchronization current
t
t
f/V converter
Input current
t
Load limiting
Limiting current, neg. half wave
t
Input voltage
Phase control
Input voltage
Input current
Soft-start
Input voltage
Pulse output
Reverse voltage
Pulse blocking
Input voltage
Amplifier
Input voltage
Pin 9 open
Reference voltage source
Output current
Storage temperature range
Junction temperature
Ambient temperature range
t 10 ms
t 10 ms
t 10 ms
t 10 ms
Pin 1
Pin 17
Pin 1
Pin 17
Pin 8
Symbol
–IS
Value
30
Unit
mA
–is
100
IsyncI
IsyncV
±iI
±iI
5
5
35
35
mA
II
3
mA
±iI
13
II
5
Pin 14
mA
35
Pin 14
Pin 15
±Vi
–VI
1
V16 to 0
Pin 12
Pin 12
Pin 6
–VI
±II
–II
0 to 7
500
1
mA
Pin 13
–VI
V16 to 0
V
Pin 4
VR
VS to 5
V
Pin 18
–VI
V16 to 0
V
Pin 11
Pin 10
VI
–VI
0 to VS
V16 to 0
V
Pin 16
Io
Tstg
Tj
Tamb
7.5
–40 to +125
125
–10 to +100
mA
°C
°C
°C
Symbol
RthJA
Maximum
120
180
100
Unit
K/W
V
V
mA
Thermal Resistance
Parameters
Junction ambient
8 (20)
DIP18
SO16 on p.c.
SO16 on ceramic
TELEFUNKEN Semiconductors
Rev. A1, 29-May-96
U211B2/ B3
Electrical Characteristics
–VS = 13.0 V, Tamb = 25°C, reference point Pin 2, unless otherwise specified
Parameters
Test Conditions / Pins
Supply voltage for mains opPin 3
eration
Supply voltage limitation
–IS = 4 mA
Pin 3
–IS = 30 mA
DC current requirement
–VS = 13.0 V
Pin 3
Reference voltage source
–IL = 10 mA
Pin 16
–IL = 5 mA
Temperature coefficient
Pin 16
Voltage monitoring
Turn-on threshold
Pin 3
Turn-off threshold
Pin 3
Phase control currents
Synchronization current
Pin 1
Voltage limitation
Reference ramp, figure 7
Charge current
Rö-reference voltage
Temperature coefficient
Pulse output, figure 18
Output pulse current
Reverse current
Output pulse width
Amplifier
Common mode signal range
Input bias current
Input offset voltage
Output current
Pin 17
IL = 5 mA Pins 1 and 17
"
I7 = f (R6);
Pin 7
R6 = 50 k to 1 MW
a ≥ 180°C
Pins 6 and 3
Pin 6
Pin 4
RGT = 0, VGT = 1.2 V
Cϕ = 10 nF
Pins 10 and 11
Pin 11
Pins 10 and 11
Pin 12
Short circuit forward,
Figure 14
Pin 12
transmittance
I12 = f(V10 -11)
Pulse blocking, tacho-monitoring
Pin 18
Logic-on
Logic-off
Input current
V18 = VTOFF = 1.25 V
V18 = V16
Output resistance
TELEFUNKEN Semiconductors
Rev. A1, 29-May-96
Symbol
–VS
Min.
13.0
–VS
–VS
IS
–VRef
14.6
14.7
1.2
8.6
8.3
–TCVRef
–VSON
–VSOFF
"I
"I
"V
11.2
9.9
Typ.
2.5
8.9
Max.
VLimit
Unit
V
16.6
16.8
3.0
9.2
9.1
V
mA
V
0.5
mV/K
13.0
10.9
V
V
syncI
0.35
2.0
syncV
0.35
2.0
I
1.4
1.6
1.8
V
I7
VöRef
TCVöRef
1
1.06
20
1.13
0.5
1.18
A
V
mV/K
Io
Ior
tp
100
155
0.01
80
V10, 11
IIO
V10
–IO
+IO
V16
75
88
Yf
–VTON
–VTOFF
II
RO
0.01
10
110
120
m
190
3.0
mA
mA
ms
–1
1
V
mA
mV
mA
145
165
1000
3.7
14.5
1.5
mA
m
A/V
1.5
1.25
0.3
V
1.0
1
m
6
10
kW
A
9 (20)
U211B2/ B3
Parameters
Test Conditions / Pins
Frequency to voltage converter
Pin 8
Input bias current
Input voltage limitation
Figure 13
II = –1 mA
II = +1 mA
Turn-on threshold
Turn-off threshold
Charge amplifier
Discharge current
Figure 2
C5 = 1 nF,
Pin 9
Charge transfer voltage
Pins 9 to 16
Charge transfer gain
I10/I9
Pins 9 and 10
Conversion factor
Figure 2
C5 = 1 nF, R6 = 100 kW
Output operating range
Pins 10 to 16
Linearity
Soft-start, figures 8, 9, 10, 11, 12 f/v-converter non-active
Starting current
V13 = V16, V8 = V2 Pin 13
Final current
V13 = 0.5
Pin 13
f/v-converter active
Starting current
V13 = V16
Pin 13
Final current
V13 = 0.5
Discharge current
Restart pulse
Pin 13
Automatic retriggering, figure 19
Pin 5
Repetition
rate
R5-3 = 0
p
R5-3 = 15 kW
Load limiting, figures 15, 16, 17
Pin 14
Operating voltage range
Pin 14
Offset current
V10 = V16
Pin 14
V14 = V2 via 1 kW
Pin 15–16
Input current
V10 = 4.5 V
Pin 14
Output current
V14 = 300 mV Pin 15–16
Overload ON
Pin 15–16
10 (20)
Symbol
Min.
IIB
–VI
+VI
–VTON
–VTOFF
Max.
Unit
0.6
2
mA
750
8.05
150
mV
V
mV
mV
660
7.25
20
Idis
Vch
Gi
Typ.
100
50
0.5
6.50
7.5
K
VO
6.70
8.3
mA
6.90
9.0
5.5
0-6
1
V
mV/Hz
V
%
mA
IO
20
50
45
85
55
130
IO
IO
2
30
0.5
4
55
3
7
80
10
mA
tpp
3
4.5
20
6
tp
VI
IO
–1.0
5
1.0
12
V
II
IO
VTON
60
110
7.05
0.1
90
7.4
1.0
120
140
7.7
mA
mA
mA
V
TELEFUNKEN Semiconductors
Rev. A1, 29-May-96
U211B2/ B3
240
10
Phase Control
Reference Point Pin 2
200
4.7nF
Soft Start
2.2nF
V13 ( V )
Phase Angle
(° )
8
10nF
160
120
6
4
C /t=1.5nF
80
2
f/V-Converter Non Active
Reference Point Pin 16
0
0
0
0.2
95 10302
0.4
0.6
R ( M )
0.8
1.0
t=f(C3)
95 10305
Figure 7.
Figure 10.
100
10
Soft Start
Soft Start
8
V13 ( V )
I 13 ( A )
80
60
40
f/V-Converter Active
Reference Point Pin 16
6
4
20
2
f/V-Converter Non Active
Reference Point Pin 16
0
0
0
2
4
6
8
10
V13 ( V )
95 10303
t=f(C3)
95 10306
Figure 8.
Figure 11.
Soft Start
Soft Start
8
80
Reference Point Pin 16
V13 ( V )
f/V-Converter Active
Reference Point Pin 16
I 13 ( A )
95 10307
10
100
60
6
4
40
2
20
0
0
0
95 10304
2
4
6
8
10
t=f(C3)
Motor Standstill ( Dead Time )
Motor in Action
V13 ( V )
Figure 9.
TELEFUNKEN Semiconductors
Rev. A1, 29-May-96
Figure 12.
11 (20)
U211B2/ B3
200
500
f/V–Converter
Load Limit Control
250
150
I 14–2 ( m A)
I 8 (mA )
Reference Point Pin 2
0
100
–250
50
–500
–10
0
–8
–6
–4
–2
0
2
4
V8 ( V )
95 10308
0
2
4
8
6
V10–16 (V)
95 10311
Figure 13.
Figure 16.
250
Load current detection
100
Control Amplifier
200
I 15–16 ( m A )
I 12 ( mA )
50
0
150
100
–50
I15=f ( VShunt )
V10=V16
50
Reference Point
for I12 = –4V
–100
–300
–200
–100
0
0
100
200
300
V10–11 ( V )
95 10309
0
100
200
300
400
Figure 14.
600
700
Figure 17.
200
100
Load Limit Control
Pulse Output
80
I GT ( mA )
m A)
150
100
–I
12–16 (
500
V14–2 ( mV )
95 10312
60
40
1.4V
VGT=0.8V
50
20
0
0
0
95 10310
2
4
V15–16 ( V )
Figure 15.
12 (20)
6
8
0
95 10313
200
400
600
RGT ( W )
800
1000
Figure 18.
TELEFUNKEN Semiconductors
Rev. A1, 29-May-96
U211B2/ B3
20
6
Automatic Retriggering
5
Mains Supply
P(R1) ( W )
R 5–3
( kW )
15
10
4
3
2
5
1
0
0
0
6
12
18
24
30
tpp/tp
95 10314
0
10
40
30
Figure 21.
50
6
5
40
Mains Supply
P(R1) ( W )
Mains Supply
R 1( kW )
R1 ( kW )
95 10316
Figure 19.
30
20
4
3
2
10
1
0
0
0
95 10315
20
4
8
Itot ( mA )
Figure 20.
TELEFUNKEN Semiconductors
Rev. A1, 29-May-96
12
16
0
95 10317
3
6
9
12
15
Itot ( mA )
Figure 22.
13 (20)
Speed sensor
R5
1 kW
9
C4
220 nF
C5
R7
15 k W
10
680 pF
2.2 mF / 10 V
R13
47 k W
Set speed
voltage
C7
7
12
5
4
GND
R8= 3 x 11 m W
1W
C1
22 mF
25 V
180 W
470 k W
M
N
230 V~
L
R1
1N4004
18 kW
1.5 W
R4
1
R12
2
17
R3
R10
2.2 k W
47 k W
R16
R15
T1
D1
47 k W
T2
220 k W
18
10 kW
R14
3
16
–VS
C9
R9
470 kW
2.2 m F
C11
95 10364
BZX55
R2
1 MW
6
U211B2
15
14
2.2 mF
10 V
13
R
ö
C3
220 nF
4.7m F
10 V
C8
ö
C2
2.2 nF C /t
8
11
1 MW
R11
100 k W
C6
R6
C10
100 nF
R31
250 k W
2.2 m F
10 V
U211B2/ B3
Figure 23. Speed control, automatic retriggering, load switch-off, soft start
The switch-off level at maximum load shows in principle
the same speed dependency as the original version (see
figure 2), but when reaching the maximum load, the
motor is switched off completely.
14 (20)
This function is effected by the thyristor (formed by T1
and T2) which ignites when the voltage at Pin 15 reaches
typ. 7.4 V (Reference point Pin 16). The circuit is thereby
switched into the “stand-by” over the release Pin 18.
TELEFUNKEN Semiconductors
Rev. A1, 29-May-96
Speed sensor
/t
ö
ö
R
R2
1 MW
22 m F
25 V
180W
N
230 V~
M
R8 = 3 x 11 mW
1W
C1
470 k W
R12
2
1
18 kW
1.5 W
R4
R1
D1
1N4004
L
R10
2.2 k W
47 k W
GND –VS
4
3
16
17
18
R3
220 k W
T2
R16
C2
2.2 nF C
7
6
5
U211B2
13
15
14
2.2 m F
10 V
R14
10 kW
T1
95 10366
BZX55
C4
220 nF
R5
1 kW
9
8
11
12
C3
C8
4.7m F
10 V
C9
2.2 m F
C 11
R9
470 kW
33 kW
R15
C5
R7
15 k W
10
680 pF
2.2 m F 10
/ V
R13
47 k W
Set speed
voltage
C7
1 MW
C6
R 11
100 kW
220 nF
R6
C10
100 nF
R31
250 k W
2.2 m F
10 V
U211B2/ B3
Figure 24. Speed control, automatic retriggering, load switch-off, soft-start
The maximum load regulation shows the principle in the
same speed dependency as the original version (see
figure 2). When reaching the maximum load, the control
unit is turned to amax, adjustable with R2. Then only IO
flows. This function is effected by the thyristor, formed
by T1 and T2 which ignites as soon as the voltage at Pin 15
reaches ca. 6.8 V (Reference point Pin 16). The potential
TELEFUNKEN Semiconductors
Rev. A1, 29-May-96
at Pin 15 is lifted and kept by R14 over the internally
operating threshold whereby the maximum load
regulation starts and adjusts the control unit constantly to
amax (IO), inspite of a reduced load current. The motor
shows that the circuit is still in operation by a quiet
buzzing noise.
15 (20)
16 (20)
N
230 V~
L
95 10365
M
R8 = 3 x 11 m W
1W
R10
1 kW
C1
R1
1N4004
D1
R4
22 m F
25 V
470 k W
18 k W
1.5 W
R3
220 k W
1 MW
220 W
R12
1
18
2
17
GND
1m F /10 V
22 nF
C 11
3
16
–VS
4
15
C9
4.7m F
5
R2
1 MW
U211B2
14
2.2 m F
10 V
6
13
7
12
C2
2.2 nF C
ö
R
C3
C8
R9
1 M W 220 nF
/t
ö
R5
1 kW
C7
100 nF
C 10
220 nF
C4
C5
1 nF
2.2 m F /10 V
10
9
R6
C6
Speed sensor
8
11
1.5 MW
R11
68 k W
R7
22 k W
R 13
47 k W
Set speed
voltage
250 k W
R31
2.2 m F
10 V
U211B2/ B3
Figure 25. Speed control, automatic retriggering, load limiting, soft-start, tacho control
TELEFUNKEN Semiconductors
Rev. A1, 29-May-96
TELEFUNKEN Semiconductors
Rev. A1, 29-May-96
95 10687
C12
230 V~
150 nF
250 V~
ca 220 Pulses / Revolution
47 m F
25 V
1
18
2
GND
17
D2
1N4004
IGT = 50 mA
470 k W
18 k W
1.5 W
R14
C1
R1
1N4004
R5
L2
D1
R4
220 k W
100 W
M
L1
all diodes BYW83
–VS
100 W
3
16
15
4
C11
14
13
R3
4.7 k W
R2
1 MW
R15
3.5 k W / 8 W
R6
5
6
C2
Rö
R7
C3
U211B2
22 nF
2.2 m F
10 V
7
Cö/t
C10
R10
8
C6
C5
Z3
BZX55
C9V1
100 W
R11
16 k W
R17 R16
470 W
R13
Set speed
max
R18
Set speed
min
CNY 70
R31
100 k W
C13
10 V
470 nF
C7
C8
10 m F
4.7 m F
10 V
470 nF
220 k W
100 m F
10 V
1.5 k W
R9
9
C4
220 nF
10
680 pF
11
3.3 nF
12
470 k W
R8
47 k W
U211B2/ B3
Figure 26. Speed control with reflective opto coupler CNY70 as emitter
17 (20)
18 (20)
230 V~
95 10688
C12
100 W
M
R8= 3 x 0.1 W
150 nF
250 V~
R10
1.1 k W
C1
R1
D1
–VS
15
14
13
R4
22 mF
25 V
1
IGT = 50 mA
220 k W
10 k W
1.1 W
1N4004
2
GND
100 W
3
4
R12
R2
1 MW
5
6
U211B2
C2
Rö
12
3.3 nF
Cö/t
R5
2.2 k W
7
8
11
820 k W
C4
10
C5
470 nF
C6
10 mF
47 mF
10 V
1 nF
R16
10 kW
680 pF
9
C13
1mF
470 nF
C8
16
R11
C3
R6
82 k W
R3
17
2.2 mF
10 V
4.7 mF
10 V
C7
22 nF
C9
110 k W
18
220 k W
C11
R9
R31
R17
33 k W
R7
16 k W
R18
470 W
9V
R13
Set speed
max
R14
Set speed
min
CNY 70
220 k W
C10
U211B2/ B3
Figure 27. Speed control, max. load control with reflective opto coupler CNY70 as emitter
TELEFUNKEN Semiconductors
Rev. A1, 29-May-96
U211B2/ B3
The circuit is designed as a speed control on the
reflection-coupled principle with 4 periods per revolution
and a max. speed of 30.000 rpm. The separation of the
coupler from the rotating aperture should be 1 mm
approximately. In this experimental circuit, the power
supply for the coupler was provided externally because of
the relatively high current consumption.
Instructions for adjusting:
D In the initial adjustment of the phase-control circuit,
R2 should be adjusted so that when R14 = 0 and R31 are
in min. position, the motor just turns.
D The speed can now be adjusted as desired by means of
R31 between the limits determined by R13 and R14.
D The switch-off power of the limit load control can be
set by R9. The lower R9, the higher the switch-off
power.
Dimensions in mm
Package: DIP18 – U211B2
94 8877
Package: SO16 – U211B3
94 8875
TELEFUNKEN Semiconductors
Rev. A1, 29-May-96
19 (20)
U211B2/ B3
Ozone Depleting Substances Policy Statement
It is the policy of TEMIC TELEFUNKEN microelectronic GmbH to
1. Meet all present and future national and international statutory requirements.
2. Regularly and continuously improve the performance of our products, processes, distribution and operating systems
with respect to their impact on the health and safety of our employees and the public, as well as their impact on
the environment.
It is particular concern to control or eliminate releases of those substances into the atmosphere which are known as
ozone depleting substances ( ODSs).
The Montreal Protocol ( 1987) and its London Amendments ( 1990) intend to severely restrict the use of ODSs and
forbid their use within the next ten years. Various national and international initiatives are pressing for an earlier ban
on these substances.
TEMIC TELEFUNKEN microelectronic GmbH semiconductor division has been able to use its policy of
continuous improvements to eliminate the use of ODSs listed in the following documents.
1. Annex A, B and list of transitional substances of the Montreal Protocol and the London Amendments respectively
2 . Class I and II ozone depleting substances in the Clean Air Act Amendments of 1990 by the Environmental
Protection Agency ( EPA) in the USA
3. Council Decision 88/540/EEC and 91/690/EEC Annex A, B and C ( transitional substances ) respectively.
TEMIC can certify that our semiconductors are not manufactured with ozone depleting substances and do not contain
such substances.
We reserve the right to make changes to improve technical design and may do so without further notice.
Parameters can vary in different applications. All operating parameters must be validated for each customer
application by the customer. Should the buyer use TEMIC products for any unintended or unauthorized
application, the buyer shall indemnify TEMIC against all claims, costs, damages, and expenses, arising out of,
directly or indirectly, any claim of personal damage, injury or death associated with such unintended or
unauthorized use.
TEMIC TELEFUNKEN microelectronic GmbH, P.O.B. 3535, D-74025 Heilbronn, Germany
Telephone: 49 ( 0 ) 7131 67 2831, Fax number: 49 ( 0 ) 7131 67 2423
20 (20)
TELEFUNKEN Semiconductors
Rev. A1, 29-May-96