U2010B Phase Control Circuit for Current Feedback Description The U2010B is designed as a phase-control circuit in bipolar technology. It enables load-current detection and has a soft-start function as well as reference voltage output. Motor control with load-current feedback and overload protection are preferred applications. Features D Full wave current sensing D Internal supply voltage monitoring D Current requirement 3 mA D Temperature compensated reference voltage v D Mains supply variation compensated D Programmable load-current limitation with over- and high-load output D Variable soft-start Applications D Voltage and current synchronization D Advanced motor control D Grinder D Drilling machine D Automatic retriggering switchable D Triggering pulse typical 125 mA Package: DIP16, SO16 Block Diagram 15 96 11646 14 13 11 12 Overload Limiting detector Voltage detector Mains voltage compensation Automatic retriggering 100% Output Current detector Phase control unit ö = f (V4) – 1 2 10 Supply voltage High load 70% GND A amax B Programmable Auto– start overload protection C Imax + Full wave rectifier 9 16 Pulse output 1 Voltage monitoring Load current detector 2 Level shift 3 Soft start 4 5 6 7 Reference voltage 8 Figure 1. Block diagram TELEFUNKEN Semiconductors Rev. A1, 28-May-96 1 (12) The U2010B contains voltage limiting and can be connected with the mains supply via D1 and R1. Supply voltage between Pin 10 and Pin 11 is smoothed by C1. * 2 (12) R6 230 V ~ Mains Supply * R3 General Description In the case of V6 (70% of overload threshold voltage), Pins 11 and 12 are connected internally whereby VT70, the supply current Vsat 1.2 V. When V6 flows across D3. v v 1 16 Limiting detector 2 Load current detector Current detector Automatic retriggering $250 mV 3.3 kW R5 ^ V(R6)= 3.3 kW R4 180W TIC 226 Load 15 C3 10 nF 3 Level shift ö a max R10 – C4 2 P1 50 kW mF + 13 R7 8.2 kW Set point Full wave rectifier 1 R11 1 MW Overload BYT51K Output C5 0.1 m F 0.15 5 100 kW Load current compensation 4 D1 Mains voltage compensation R8 470 k W 14 Phase control unit = f (V4 ) Voltage detector R2 330 k W R1 18 k W /2 W 7 Soft start C2 4.7 m F Voltage monitoring Overload threshold 6 70% C Imax B Auto– start A a max Supply voltage 11 8 10 96 11647 9 GND C7 1 mF Reference voltage Programmable overload protection 100% High load 12 VS LED D3 S1 A B C Mode C1 22 m F U2010B Figure 2. Block diagram with external circuit w TELEFUNKEN Semiconductors Rev. A1, 28-May-96 U2010B Pin Description Isense 1 16 Output Isense 2 15 VSync. Cö 3 14 VRö Control 4 13 Overload Comp. 5 12 High load ILoad 6 11 VS Csoft 7 10 GND VRef 8 9 Mode Pin 1 2 3 4 5 6 7 8 9 10 11 12 13 14 15 16 Symbol Isense Isense Cö Control Comp. ILoad Csoft VRef Mode GND VS High load Overload VRö VSync. Output Function Load current sensing Load current sensing Ramp voltage Control input Compensation output Load current limitation Soft start Reference voltage Mode selection Ground Supply voltage High load indication Overload indication Ramp current adjust Voltage synchronization Trigger output 95 11406 Series resistance R1 can be calculated as follows: R 1max Vmains VSmax Itot ISmax Ix +V mains 2 – V Smax whereas I tot + Mains supply voltage + Maximum supply voltage + Total current consumption = I )I + Maximum current consumption of the IC + Current consumption of the Smax x external components Voltage Monitoring As the voltage is built up, uncontrolled output pulses are avoided by internal voltage monitoring. Apart from that all the latches in the circuit (phase control, load limit regulation) are reset and the soft-start capacitor is short circuited. This guarantees a specified start-up behavior each time the supply voltage is switched on or after short interruptions of the mains supply. Soft-start is initiated after the supply voltage has been built up. This behavior guarantees a gentle start-up for the motor and automatically ensures the optimum run-up time. Phase Control The function of the phase control is largely identical to the well known IC family U211B. The phase angle of the trigger pulse is derived by comparing the ramp voltage V3 which is mains synchronized by the voltage detector with the set value on the control input, Pin 4. The slope of the TELEFUNKEN Semiconductors Rev. A1, 28-May-96 ramp is determined by Cö and its charging current Iö. The charging current can be varied using Rö at Pin 14. The maximum phase angle, αmax, can also be adjusted by using Rö (minimum current flow angle ömin) see figure 4. When the potential on Pin 3 reaches the set point level of Pin 4, a trigger pulse width, tp, is determined from the value of Cö (tp = 9 ms/nF). At the same time, a latch is set with the output pulse, as long as the automatic retriggering has not been activated, then no more pulses can be generated in that half cycle. Control input at Pin 4 (with respect to Pin 10) has an active range from V8 to –1 V. When V4 = V8, then the phase angle is at its maximum, αmax, i.e., the current flow angle is minimum. The minimum phase angle, αmin, is set with V4 –1 V. w Automatic Retriggering The current-detector circuit monitors the state of the triac after triggering by measuring the voltage drop at the triac gate. A current flow through the triac is recognized, when the voltage drop exceeds a thres hold level of typ. 40 mV. If the triac is quenched within the relevant half-wave after triggering; for example owing to low load currents before or after the zero crossing of current wave or; for commutator motors, owing to brush lifters. Then the automatic retriggering circuit ensures immediate retriggering, if necessary with a high repetition rate, tpp/tp, until the triac remains reliably triggered. 3 (12) U2010B Current Synchronization Current synchronization fulfils two functions: * Monitoring the current flow after triggering. In case the triac extinguishes again or it does not switch on, automatic triggering is activated until the triggering is successful. * Avoiding a triggering due to inductive load. In the case of inductive load operation the current synchronization ensures that in the new half wave no pulse is enabled as long as there is a current available which from the previous half-wave, which flows from the opposite polarity to the actual supply voltage. A special feature of the integrated circuit is the realization of this current synchronization. The device evaluates the voltage at the pulse output between gate and reference electrode of the triac. This results in saving separate current synchronization input with specified series resistance. Voltage Synchronization with Mains Voltage Compensation The voltage detector synchronizes the reference ramp with the mains-supply voltage. At the same time, the mains dependent input current at Pin 15 is shaped and rectified internally. This current activates the automatic retriggering and at the same time is available at Pin 5. By suitable dimensioning, it is possible to attain the specified compensation effect. Automatic retriggering and mains voltage compensation are not activated until |V15 – 10| increases to 8 V. Resistance, Rsync. defines the width of the zero voltage cross over pulse, synchronization current, and hence the mains supply voltage compensation current. Mains 96 11648 v Load Current Compensation The circuit continuously measures the load current as a voltage drop at resistance R6. The evaluation and use of both half waves results in a quick reaction to load current change. Due to voltage at resistance R6, there is a difference between both input currents at Pins 1 and 2. This difference controls the internal current source, whose positive current values are available at Pins 5 and 6. The output current generated at Pin 5 contains the difference from the load-current detection and from the mains-voltage compensation (see figure 1). The effective control voltage at Pin 4 is the final current at Pin 5 together with the desired value network. An increase of mains voltage causes the increase of control angle α, an increase of load current results in a decrease in the control angle. This avoiding a decrease in revolution by increasing the load as well as the increase of revolution by the increment of mains supply voltage. Load Current Limitation The total output load current is available at Pin 6. It results in a voltage drop across R11. When the potential of the load current reaches about 70% of the threshold value (VT70) i.e., ca. 4.35 V at Pin 6, it switches the high load comparator and opens the switch between Pins 11 and 12. By using an LED between these pins, (11 and 12) a high load indication can be realized. If the potential at Pin 6 increases to ca. 6.2 V (= VT100), it switches the overload comparator. The result is programmable at Pin 9 (operation mode). Mode selection: R2 15 U2010B 2x BZX55 C6V2 10 Figure 3. 4 (12) If the mains voltage compensation and the automatic retriggering are not required, both functions can be suppressed by limiting |V15 – 10| 7 V (figure 3). a) αmax (V9 = 0) In this mode of operation, after V6 has reached the threshold VT100, Pin 13 switches to –VS (Pin 11) and Pin 6 to GND (Pin 10). A soft-start capacitor is then shorted and the control angle is switched to αmax. This position is maintained until the supply voltage is switched off. The motor can be started again with soft-start function when the power is switched on again. As the overload condition switches Pin 13 to Pin 11, it is possible to set in a smaller control angle, αmax, by connecting a further resistance between Pins 13 and 14. TELEFUNKEN Semiconductors Rev. A1, 28-May-96 U2010B * b) Auto start (Pin 9 open) The circuit behaves as written under αmax (V9 = 0), with the exception that Pin 6 is not connected to GND. If the value of V6 decreases to 25% of the threshold value (VT25), the circuit becomes active again with soft-start. c) Imax (V9 = V8) When V6 has attained the overload threshold maximum value i.e. V6 = VT100; Pin 13 is switched to Pin 8 (VRef) through the resistance R (= 2 kW) without soft-start capacitor discharging at Pin 7. With this mode of operation, direct load current control (Imax) is possible. A recommended circuit is shown in figure 18. Absolute Maximum Ratings Reference point Pin 10, unless otherwise specified Parameters Sink current t v t v Sync. currents " " Value 30 100 5 20 Unit mA Pin 15 Symbol –IS –is IsyncV isyncV Pins 4 and 8 Pin 4 Pin 14 –VI II – Iϕ max " 0 – V8 500 0.5 V mA mA Pins 7 and 8 –VI 0 – V8 V Pin 16 +VI –VI 2 V11 V Pin 8 I0 10 30 mA Pin 11 s 10 m s 10 m Phase control Control voltage Input current Charging current Soft-start Input voltage Pulse output Input voltage Reference voltage source Output current t 10 ms Load current sensing Input currents Input voltages Overload output High-load output t 10 ms Storage temperature range Junction temperature range Ambient temperature range v v Pins 1 and 2 Pins 5 and 6 Pin 13 Pin 12 " Ii – Vi IL IL Tstg Tj Tamb 1 0 – V8 1 30 100 40 to 125 125 10 to 100 * * ) ) mA mA V mA mA C C C Thermal Resistance Parameters Junction ambient TELEFUNKEN Semiconductors Rev. A1, 28-May-96 DIP16 SO16 on p.c. SO16 on ceramic Symbol RthJA Value 120 180 100 Unit K/W 5 (12) U2010B Electrical Characteristics VS + –13 V, T amb = 25°C, reference point Pin 10, unless otherwise specified Parameters Supply Supply voltage limitation Current requirement Reference voltage source Reference voltage Temperature coefficient Test Conditions / Pins Pin 11 –IS = 3.5 mA –IS = 30 mA –VS = 13.0 V (Pins 1, 2, 8 and 15 open) Pin 8 IL = 10 A IL = 2.5 mA IS = 2.5 mA IS = 10 A Pin 11 Symbol Min. –VS 14.5 14.6 –IS –VRef " " " w 8.6 8.4 TCVRef Voltage monitoring Turn-on threshold –VSon Phase control – synchronization Pin 15 Input current Voltage sync. IsyncV Voltage limitation IL = 2 mA VsyncV Input current Current sync. Pin 16 IsyncI Reference ramp, figure 4 Charging current Pin 14 –Iϕ Start voltage Pin 3 –Vmax Temperature coefficient of Pin 3 TCR start voltage Final voltage Pin 3 –Vmin Rϕ − reference voltage Iϕ = Α Pins 14 and 11 VRϕ Temperature coefficient Iϕ = Α Pin 14 TCVRϕ Iϕ = Α Pulse output current V16 = – 1.2 V, figure 5, Pin 16 I0 Output pulse width VS = Vlimit, tp C3 = 3.3 nF, figure 6, Pin 16 Automatic retriggering Repetition rate I15 150 A tpp Threshold voltage Pin 16 VI Soft start, figure 7 and 8 Pin 7 Starting current V7 = V8 –I0 Final current V7–10 = –1V –I0 Discharge current +I0 Output current Pin 4 +I0 Supply voltage compensation, figure 9 Pin 15 Transfer gain I15/ I5 Pin 15/5 Gi (Pins 1 and 2 open) Output offset current V(R6) = V15 = V5 = 0 I0 Load current detection, R1 = R2 = 3 k, V15 = 0, V5 = V6 = V8, figure 10 Transfer gain I5/150 mV, I6/150 mV GI Output offset currents Pin 5, Pin 6 - 8 –I0 Reference voltage I1, I2 = 100 A Pins 1 and 2 –VRef Shunt voltage amplitude see figure 2 V(R6) " Typ. " 0.15 8.0 3 1 1.85 6 (12) Unit 16.5 16.8 3.2 V 9.2 9.1 11.3 12.3 V 8.5 2 9.0 30 mA V A 100 2.05 A V 1.95 0.96 "200 mV) V %/K –0.003 (V8 mA 8.9 8.8 –0.004 +0.006 %/K 1.02 0.03 0.06 125 30 1.10 V %/K 150 mA s 3 20 5 7.5 60 tp mV 5 15 0.5 0.2 10 25 15 40 A A mA mA 14 17 100 2 " " Max. 0.28 0 300 0.32 3 20 2 A 0.37 6 400 250 A/mV A mV mV TELEFUNKEN Semiconductors Rev. A1, 28-May-96 U2010B Parameters Load current limitation, High load switching Test Conditions / Pins Pin 6-8, figs. 11 to 14 Threshold VT70 Symbol Min. Typ. Max. Unit VT70 4 4.35 4.7 V Overload switching Threshold VT100 VT100 5.8 6.2 6.6 V Restart switching Threshold VT25 VT25 1.25 1.55 1.85 V Ii R0 2 4 1 8 mA kW –V9 –I9 I9 3.8 5 5 4.3 10 10 4.7 20 20 mA Vsat Vlim 0.5 7.0 0.75 7.4 1.0 7.8 Input current Enquiry mode Output impedance Switching mode Programming input, figure 2, Pin 9 Input voltage - auto-start Pin 9 open Input current V9 = 0 (amax) V9 = V8 (Imax) High load output, VT70, figure 12, I12 = –3 mA, Pin 11-12 Saturation voltages V6-8 VT70 V6-8 VT70 Overload output, VT100, V9 = open or V9 = V10, fig. 13 Leakage current V6-8 VT25 V13 = (V11+1)V Pin 13 Saturation voltages V6-8 VT100, Pins 11-13 I13 = 10 mA Output current, max. load V9 = V8, fig. 13 Pin 13 Leakage current V6 VT100 Pin 13 Output impedance Open collector Pin 13 V6 VT100 Saturation voltage V6-8 VT100, Pin 13 I13 = 10 mA v w v w v w w 0.5 Vsat I13 Ilkg 0.1 1 4 R0 4 V mA V mA mA kW 8 100 mV 120 Pulse Output VGT=–1.2V 100 3.3 nF 2.2 nF 80 IGT ( mA ) 6.8 nF 200 33 nF 4.7 nF 10 nF 150 100 Cö/ t = 1.5 nF 60 40 20 50 0 0 0 96 11797 2 V13–8 250 Phase angle a (° ) Ilkg V 200 400 600 Rö ( kW ) Figure 4. TELEFUNKEN Semiconductors Rev. A1, 28-May-96 800 0 1000 95 10338 200 400 600 800 1000 RGT ( W ) Figure 5. 7 (12) U2010B 400 0 Output Pulse Width Dtp/DCö=9ms/nF 40 I 5 (mA ) t p ( ms ) 300 200 80 120 Mains Supply 160 Compensation Pins 1 and 2 open Vs=–13V 200 –2 –1 100 0 0 10 30 20 Cö = ( nF ) 95 10339 I15 ( mA ) 200 Soft Start VS=–13V V6=V8 30 Reference Point Pin 8 Reference Point Pin 8 Load Current Detection V6=VRef=V8 VS=–13V V15=V10=0V 160 I5 ( m A ) I 7 (mA ) 40 120 20 80 10 40 0 0 0 2.5 5.0 10 7.5 V7 ( V ) 95 10340 –400 –200 0 400 200 V(R6) ( mV ) 95 10343 Figure 7. Figure 10. 12 20 Load Current limitation: Auto Start Operation VS=–13V Pin 9 open Reference Points: V13=Pin 10, V6=Pin 8 Reference Point Pin 8 1 mF 8 2.2mF 16 –V13–10 ( V ) 10 V7 ( V ) 2 1 Figure 9. 50 4.7mF 6 Cö=10mF 4 Soft Start VS=–13V V6=V8 2 0 0 2 4 6 t(s) Figure 8. 8 (12) 0 95 10342 Figure 6. 95 10341 Reference Point Pin 10 8 12 8 4 VT25 0 10 0 95 10344 2 VT100 4 6 8 10 V6–8 ( V ) Figure 11. TELEFUNKEN Semiconductors Rev. A1, 28-May-96 U2010B 10 10 High Load Output ( 70% ) I12=–3mA Power Dissipation at Series Resistance R1 8 PV ( W ) V11–12 ( V ) 8 6 6 4 4 Reference Point Pin 8 2 2 VT70 0 0 0 1 2 3 4 5 6 7 V6 ( V ) 95 10345 0 10 VS=–13V V9=V8 Reference Points: V13=Pin 10 V6=Pin 8 8 6 PV ( W ) –V13–10 ( V ) Power Dissipation at Series Resistance 8 6 4 2 2 VT100 0 0 2 4 6 0 8 10 t(s) 95 10346 0 3 20 9 12 15 IS ( mA ) Figure 16. 100 Load Current limitation: amax Operation VS=–13V V9=V10 Reference Points: V13=Pin 10, V6=Pin 8 X Max. Series Resistance VM=230V 80 R 1max (k W ) 16 6 95 10350 Figure 13. V13–10 ( V ) 50 10 4 12 8 4 60 40 20 VT100 0 0 95 10347 40 Figure 15. Load Current limitation: Current Control Operation 10 30 R1 ( kW ) 95 10348 Figure 12. 12 20 2 4 0 6 V6–8 ( V ) Figure 14. TELEFUNKEN Semiconductors Rev. A1, 28-May-96 8 10 0 95 10349 2 4 6 8 10 IS ( mA ) Figure 17. 9 (12) 10 (12) N R6 R4 180 W R3 1 16 "250 mV 3.3 kW R5 ^ V (R6) = 3.3 k W TIC 226 Load 2 Load current detector Current detector Automatic retriggering Limiting detector C3 10 nF 3 Level shift ö Phase control unit = f(V4 ) Voltage detector 15 L 330 kW R1 R2 18 k W /2 W 230 V ~ 4 R 10 – C4 P1 50 k W mF C5 0.1 mF 0.15 5 2 + 13 Set point 1 MW R 11 R7 8.2 k W Full wave rectifier 1 Output Overload BYT51K amax amax Mains voltage compensation R9 100 kW Load current compensation 14 1 MW 470 k W R8 D1 Overload threshold 6 C2 4.7 mF 7 Soft start Voltage monitoring I max C B Auto– start A amax Supply voltage 11 C7 1 mF 8 Reference voltage 70% Programmable overload protection 100% High load 12 VS LED D3 D2 S1 R 13 100 k W 1N4148 9 GND 10 R 12 T1 C6 1m F BC308 220 kW A B C 22 mF C1 96 11649 U2010B Application Circuit Figure 18. TELEFUNKEN Semiconductors Rev. A1, 28-May-96 U2010B Dimensions in mm Package: DIP16 94 9128 Package: SO16 94 8875 TELEFUNKEN Semiconductors Rev. A1, 28-May-96 11 (12) U2010B Ozone Depleting Substances Policy Statement It is the policy of TEMIC TELEFUNKEN microelectronic GmbH to 1. Meet all present and future national and international statutory requirements. 2. Regularly and continuously improve the performance of our products, processes, distribution and operating systems with respect to their impact on the health and safety of our employees and the public, as well as their impact on the environment. It is particular concern to control or eliminate releases of those substances into the atmosphere which are known as ozone depleting substances ( ODSs). The Montreal Protocol ( 1987) and its London Amendments ( 1990) intend to severely restrict the use of ODSs and forbid their use within the next ten years. Various national and international initiatives are pressing for an earlier ban on these substances. TEMIC TELEFUNKEN microelectronic GmbH semiconductor division has been able to use its policy of continuous improvements to eliminate the use of ODSs listed in the following documents. 1. Annex A, B and list of transitional substances of the Montreal Protocol and the London Amendments respectively 2 . Class I and II ozone depleting substances in the Clean Air Act Amendments of 1990 by the Environmental Protection Agency ( EPA) in the USA 3. Council Decision 88/540/EEC and 91/690/EEC Annex A, B and C ( transitional substances ) respectively. TEMIC can certify that our semiconductors are not manufactured with ozone depleting substances and do not contain such substances. We reserve the right to make changes to improve technical design and may do so without further notice. Parameters can vary in different applications. All operating parameters must be validated for each customer application by the customer. Should the buyer use TEMIC products for any unintended or unauthorized application, the buyer shall indemnify TEMIC against all claims, costs, damages, and expenses, arising out of, directly or indirectly, any claim of personal damage, injury or death associated with such unintended or unauthorized use. TEMIC TELEFUNKEN microelectronic GmbH, P.O.B. 3535, D-74025 Heilbronn, Germany Telephone: 49 ( 0 ) 7131 67 2831, Fax number: 49 ( 0 ) 7131 67 2423 12 (12) TELEFUNKEN Semiconductors Rev. A1, 28-May-96