TI TPS82675

TPS82671, TPS82672, TPS82675
TPS82676, TPS82677
SLVSAI0C – OCTOBER 2010 – REVISED NOVEMBER 2011
www.ti.com
600-mA, HIGH-EFFICIENCY MicroSiP™ STEP-DOWN CONVERTER (PROFILE <1.0mm)
Check for Samples: TPS82671, TPS82672, TPS82675, TPS82676, TPS82677
FEATURES
1
•
•
•
90% Efficiency at 5.5MHz Operation
17μA Quiescent Current
Wide VIN Range From 2.3V to 4.8V
5.5MHz Regulated Frequency Operation
Spread Spectrum, PWM Frequency Dithering
Best in Class Load and Line Transient
±2% Total DC Voltage Accuracy
Automatic PFM/PWM Mode Switching
Low Ripple Light-Load PFM Mode
≥35dB VIN PSRR (1kHz to 10kHz)
Internal Soft Start, 120-µs Start-Up Time
Integrated Active Power-Down Sequencing
(Optional)
Current Overload and Thermal Shutdown
Protection
Sub 1-mm Profile Solution
Total Solution Size <6.7 mm2
APPLICATIONS
•
•
•
Cell Phones, Smart-Phones
Digital TV, WLAN, GPS and Bluetooth™
Applications
POL Applications
DESCRIPTION
The TPS8267x device is a complete 600mA, DC/DC
step-down power supply intended for low-power
applications. Included in the package are the
switching regulator, inductor and input/output
capacitors. No additional components are required to
finish the design.
The TPS8267x is based on a high-frequency
synchronous step-down dc-dc converter optimized for
battery-powered
portable
applications.
The
MicroSiPTM DC/DC converter operates at a regulated
5.5-MHz switching frequency and enters the
power-save mode operation at light load currents to
maintain high efficiency over the entire load current
range.
The PFM mode extends the battery life by reducing
the quiescent current to 17μA (typ) during light load
operation. For noise-sensitive applications, the device
has PWM spread spectrum capability providing a
lower noise regulated output, as well as low noise at
the input. These features, combined with high PSRR
and AC load regulation performance, make this
device suitable to replace a linear regulator to obtain
better power conversion efficiency.
The TPS8267x is packaged in a compact (2.3mm x
2.9mm) and low profile (1.0mm) BGA package
suitable for automated assembly by standard surface
mount equipment.
250
100
90
VI = 3.6 V,
VO = 1.8 V
225
80
Efficiency
PFM/PWM Operation
DC/DC Converter
VIN
2.3 V .. 4.8 V
VIN
SW
GND
FB
VOUT
1.8 V @ 600mA
CO
CI
ENABLE
L
EN
MODE
MODE
SELECTION
Efficiency - %
TPS82671SIP
175
60
150
50
125
40
100
75
30
Power Loss
PFM/PWM Operation
20
GND
Figure 1. Typical Application
200
70
50
25
10
0
0.1
Power Loss - mW
•
•
•
•
•
•
•
•
•
•
•
•
23
1
10
100
IO - Load Current - mA
0
1000
Figure 2. Efficiency vs. Load Current
1
2
3
Please be aware that an important notice concerning availability, standard warranty, and use in critical applications of Texas
Instruments semiconductor products and disclaimers thereto appears at the end of this data sheet.
MicroSiP is a trademark of Texas Instruments.
Bluetooth is a trademark of Bluetooth SIG, Inc.
UNLESS OTHERWISE NOTED this document contains
PRODUCTION DATA information current as of publication date.
Products conform to specifications per the terms of Texas
Instruments standard warranty. Production processing does not
necessarily include testing of all parameters.
Copyright © 2010–2011, Texas Instruments Incorporated
TPS82671, TPS82672, TPS82675
TPS82676, TPS82677
SLVSAI0C – OCTOBER 2010 – REVISED NOVEMBER 2011
www.ti.com
This integrated circuit can be damaged by ESD. Texas Instruments recommends that all integrated circuits be handled with
appropriate precautions. Failure to observe proper handling and installation procedures can cause damage.
ESD damage can range from subtle performance degradation to complete device failure. Precision integrated circuits may be more
susceptible to damage because very small parametric changes could cause the device not to meet its published specifications.
ORDERING INFORMATION
TA
-40°C to 85°C
PART
NUMBER
OUTPUT
VOLTAGE (2)
DEVICE
SPECIFIC FEATURE
ORDERING (3)
PACKAGE
MARKING
TPS82671
1.8V
PWM Spread Spectrum Modulation
Low PFM Output Ripple Voltage
TPS82671SIP
RA
TPS82672
1.5V
PWM Spread Spectrum Modulation
Low PFM Output Ripple Voltage
TPS82672SIP
WD
TPS82674 (4)
1.2V
PWM Spread Spectrum Modulation
Low PFM Output Ripple Voltage
Output Capacitor Discharge
TPS82675
1.2V
PWM Spread Spectrum Modulation
Low PFM Output Ripple Voltage
TPS82675SIP
RB
TPS82676
1.1V
PWM Spread Spectrum Modulation
Low PFM Output Ripple Voltage
Output Capacitor Discharge
TPS82676SIP
TU
TPS82677
1.2V
Output Capacitor Discharge
TPS82677SIP
SK
1.35V
PWM Spread Spectrum Modulation
Output Capacitor Discharge
TPS82678SIP
TT
TPS82678
(1)
(2)
(3)
(4)
(1)
(4)
For the most current package and ordering information, see the Package Option Addendum at the end of this document, or see the TI
website at www.ti.com.
Internal tap points are available to facilitate output voltages in 25mV increments.
The SIP package is available in tape and reel. Add a R suffix (e.g. TPS82671SIPR) to order quantities of 3000 parts. Add a T suffix (e.g.
TPS82671SIPT) to order quantities of 250 parts.
Product Preview
ABSOLUTE MAXIMUM RATINGS
over operating free-air temperature range (unless otherwise noted) (1)
VALUE
MIN
VI
–0.3
6
V
Voltage at VOUT (3)
–0.3
3.6
V
–0.3
VIN + 0.3
V
(3)
Power dissipation
TA
Operating temperature range (4)
TINT (max)
Maximum internal operating temperature
Tstg
Storage temperature range
(5)
(2)
(3)
(4)
(5)
2
Internally limited
85
°C
125
°C
125
°C
Human body model
2
kV
Charge device model
1
kV
200
V
Machine model
(1)
UNIT
Voltage at VIN (2) (3)
Voltage at EN, MODE
ESD rating
MAX
–40
–55
Stresses beyond those listed under absolute maximum ratings may cause permanent damage to the device. These are stress ratings
only and functional operation of the device at these or any other conditions beyond those indicated under recommended operating
conditions is not implied. Exposure to absolute-maximum-rated conditions for extended periods may affect device reliability.
Operation above 4.8V input voltage for extended periods may affect device reliability.
All voltage values are with respect to network ground terminal.
In applications where high power dissipation and/or poor package thermal resistance is present, the maximum ambient temperature may
have to be derated. Maximum ambient temperature (TA(max)) is dependent on the maximum operating temperature (TINT(max)), the
maximum power dissipation of the device in the application (PD(max)), and the junction-to-ambient thermal resistance of the part/package
in the application (θJA), as given by the following equation: TA(max)= TJ(max)–(θJA X PD(max)). To achieve optimum performance, it is
recommended to operate the device with a maximum internal temperature of 105°C.
The human body model is a 100-pF capacitor discharged through a 1.5-kΩ resistor into each pin. The machine model is a 200-pF
capacitor discharged directly into each pin.
Copyright © 2010–2011, Texas Instruments Incorporated
TPS82671, TPS82672, TPS82675
TPS82676, TPS82677
SLVSAI0C – OCTOBER 2010 – REVISED NOVEMBER 2011
www.ti.com
THERMAL INFORMATION
TPS8267xSIP
THERMAL METRIC (1) (2)
SIP
UNITS
8 PINS
θJA
Junction-to-ambient (top) thermal resistance
125
Junction-to-ambient (bottom) thermal resistance
70
θJCtop
Junction-to-case (top) thermal resistance
θJB
Junction-to-board thermal resistance
ψJT
Junction-to-top characterization parameter
ψJB
Junction-to-board characterization parameter
θJCbot
Junction-to-case (bottom) thermal resistance
(1)
(2)
°C/W
For more information about traditional and new thermal metrics, see the IC Package Thermal Metrics application report, SPRA953.
Thermal data have been measured using TI's 4-layer evaluation board.
RECOMMENDED OPERATING CONDITIONS
VIN
Input voltage range
IO
Output current range
Additional output capacitance (PFM/PWM operation) (2)
MIN
NOM MAX
2.3
4.8 (1)
UNIT
0
600
mA
V
TPS82671 to TPS82676
0
2.5
µF
TPS82677, TPS82678
0
4
µF
0
7
µF
Additional output capacitance (PWM operation) (2)
TA
Ambient temperature
–40
+85
°C
TJ
Operating junction temperature
–40
+125
°C
(1)
(2)
Operation above 4.8V input voltage for extended periods may affect device reliability.
In certain applications larger capacitor values can be tolerable, see output capacitor selection section for more details.
ELECTRICAL CHARACTERISTICS
Minimum and maximum values are at VIN = 2.3V to 5.5V, VOUT = 1.8V, EN = 1.8V, AUTO mode and TA = –40°C to 85°C;
Circuit of Parameter Measurement Information section (unless otherwise noted). Typical values are at VIN = 3.6V, VOUT =
1.8V, EN = 1.8V, AUTO mode and TA = 25°C (unless otherwise noted).
PARAMETER
TEST CONDITIONS
MIN
TYP
MAX
IO = 0mA. Device not switching
17
40
IO = 0mA. PWM operation
5.8
UNIT
SUPPLY CURRENT
IQ
Operating quiescent current
ISD
Shutdown current
UVLO
Undervoltage lockout threshold
EN = GND
μA
mA
0.5
5
μA
2.05
2.1
V
PROTECTION
Thermal shutdown
Thermal shutdown hysteresis
ILIM
Peak Input Current Limit
ISC
Input current limit under short-circuit
conditions
VO shorted to ground
140
°
C
10
°
C
1100
mA
13.5
mA
ENABLE, MODE
VIH
High-level input voltage
VIL
Low-level input voltage
Ilkg
Input leakage current
1.0
Input connected to GND or VIN
V
0.4
V
0.01
1.5
μA
5.45
6.0
MHz
OSCILLATOR
fSW
Oscillator frequency
IO = 0mA. PWM operation
Copyright © 2010–2011, Texas Instruments Incorporated
4.9
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TPS82676, TPS82677
SLVSAI0C – OCTOBER 2010 – REVISED NOVEMBER 2011
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ELECTRICAL CHARACTERISTICS (continued)
Minimum and maximum values are at VIN = 2.3V to 5.5V, VOUT = 1.8V, EN = 1.8V, AUTO mode and TA = –40°C to 85°C;
Circuit of Parameter Measurement Information section (unless otherwise noted). Typical values are at VIN = 3.6V, VOUT =
1.8V, EN = 1.8V, AUTO mode and TA = 25°C (unless otherwise noted).
PARAMETER
TEST CONDITIONS
MIN
TYP
MAX
UNIT
2.5V ≤ VI ≤ 4.8V, 0mA ≤ IO ≤ 600 mA
PFM/PWM operation
0.98×VNOM
VNOM
1.03×VNOM
V
2.5V ≤ VI ≤ 5.5V, 0mA ≤ IO ≤ 600 mA
PFM/PWM operation
0.98×VNOM
VNOM
1.04×VNOM
V
2.5V ≤ VI ≤ 5.5V, 0mA ≤ IO ≤ 600 mA
PWM operation
0.98×VNOM
VNOM
1.02×VNOM
V
2.5V ≤ VI ≤ 4.8V, 0mA ≤ IO ≤ 600 mA
PFM/PWM operation
0.98×VNOM
VNOM
1.04×VNOM
V
2.5V ≤ VI ≤ 5.5V, 0mA ≤ IO ≤ 600 mA
PWM operation
0.98×VNOM
VNOM
1.02×VNOM
V
OUTPUT
Regulated DC
output voltage
TPS82671
TPS82672
TPS82674
TPS82675
TPS82676
TPS82678
VOUT
TPS82677
TPS82678
Line regulation
VI = VO + 0.5V (min 2.5V) to 5.5V, IO = 200 mA
Load regulation
IO = 0mA to 600 mA. PWM operation
0.23
Feedback input resistance
ΔVO
rDIS
%/V
–0.00085
%/mA
480
kΩ
TPS82671
IO = 1mA, VO = 1.8V
19
mVPP
TPS82675
IO = 1mA, VO = 1.2V
16
mVPP
TPS82676
IO = 1mA, VO = 1.1V
16
mVPP
TPS82677
IO = 1mA, VO = 1.2V
25
mVPP
TPS82678
IO = 1mA, VO = 1.35V
TBD
mVPP
Start-up time
TPS82671
IO = 0mA, Time from active EN to VO
120
μs
Discharge resistor
for power-down
sequence
TPS82674
TPS82676
TPS82677
TPS82678
Device featuring active discharge
Power-save mode
ripple voltage
70
150
Ω
PIN ASSIGNMENTS
SIP-8
(TOP VIEW)
VOUT
A1
A2
MODE
B1
B2
GND
C1
C2
A3
C3
SIP-8
(BOTTOM VIEW)
VIN
VIN
EN
EN
GND
GND
A3
C3
A2
A1
VOUT
B2
B1
MODE
C2
C1
GND
PIN DESCRIPTIONS
PIN
NAME
VOUT
NO.
I/O
DESCRIPTION
A1
O
Power output pin. Apply output load between this pin and GND.
VIN
A2, A3
I
The VIN pins supply current to the TPS8267x internal regulator.
EN
B2
I
This is the enable pin of the device. Connect this pin to ground to force the converter into
shutdown mode. Pull this pin to VI to enable the device. This pin must not be left floating and
must be terminated.
This is the mode selection pin of the device. This pin must not be left floating and must be
terminated.
MODE
B1
I
C1, C2, C3
–
MODE = LOW: The device is operating in regulated frequency pulse width modulation mode
(PWM) at high-load currents and in pulse frequency modulation mode (PFM) at light load
currents.
MODE = HIGH: Low-noise mode is enabled and regulated frequency PWM operation is forced.
GND
4
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Ground pin.
Copyright © 2010–2011, Texas Instruments Incorporated
Product Folder Link(s): TPS82671 TPS82672 TPS82675 TPS82676 TPS82677
TPS82671, TPS82672, TPS82675
TPS82676, TPS82677
SLVSAI0C – OCTOBER 2010 – REVISED NOVEMBER 2011
www.ti.com
FUNCTIONAL BLOCK DIAGRAM
MODE
EN
VIN
CI
2.2µF
DC/DC CONVERTER
VIN
Undervoltage
Lockout
Bias Supply
Bandgap
Soft-Start
Negative Inductor
Current Detect
V REF = 0.8 V
Power Save Mode
Switching
Thermal
Shutdown
Current Limit
Detect
Frequency
Control
R1
-
L
Gate Driver
R2
Anti
Shoot-Through
VREF
VOUT
1µH
CO
4.7µF
+
Feedback Divider
GND
PARAMETER MEASUREMENT INFORMATION
TPS8267XSIP
DC/DC Converter
VIN
VIN
SW
GND
FB
CI
ENABLE
L
VOUT
CO
EN
MODE
MODE
SELECTION
GND
Copyright © 2010–2011, Texas Instruments Incorporated
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TPS82671, TPS82672, TPS82675
TPS82676, TPS82677
SLVSAI0C – OCTOBER 2010 – REVISED NOVEMBER 2011
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TYPICAL CHARACTERISTICS
Table of Graphs
FIGURE
η
vs Load current
Efficiency
VO
3, 4
vs Input voltage
5
Peak-to-peak output ripple voltage
vs Load current
6, 7, 8
DC output voltage
vs Load current
9, 10, 11
Combined line/load transient
response
12, 13
14, 15, 16, 17
18, 19, 20
Load transient response
AC load transient response
21
22, 23, 24, 25
26, 27, 28
Load transient response
AC load transient response
29
PFM/PWM boundaries
vs Input voltage
30, 31
IQ
Quiescent current
vs Input voltage
32
fs
PWM switching frequency
vs Input voltage
33
Start-up
PSRR
34, 35
Power supply rejection ratio
vs. Frequency
36
Spurious output noise (PFM mode)
vs. Frequency
37
Spurious output noise (PWM mode)
vs. Frequency
38
Output spectral noise density
vs. Frequency
39
EFFICIENCY
vs
LOAD CURRENT
EFFICIENCY
vs
LOAD CURRENT
100
100
VO = 1.8 V
VO = 1.2 V
90
80
80
60
50
40
70
VI = 3.6 V
PFM/PWM Operation
VI = 4.2 V
PFM/PWM Operation
VI = 3.6 V
Forced PWM Operation
60
50
30
20
20
10
10
1
10
100
1000
VI = 3.6 V
PFM/PWM Operation
VI = 4.2 V
PFM/PWM Operation
VI = 3.6 V
Forced PWM Operation
40
30
0
0.1
6
VI = 2.7 V
PFM/PWM Operation
Efficiency - %
Efficiency - %
70
VI = 2.7 V
PFM/PWM Operation
90
0
0.1
1
10
IO - Load Current - mA
IO - Load Current - mA
Figure 3.
Figure 4.
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100
1000
Copyright © 2010–2011, Texas Instruments Incorporated
Product Folder Link(s): TPS82671 TPS82672 TPS82675 TPS82676 TPS82677
TPS82671, TPS82672, TPS82675
TPS82676, TPS82677
SLVSAI0C – OCTOBER 2010 – REVISED NOVEMBER 2011
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TYPICAL CHARACTERISTICS (continued)
EFFICIENCY
vs
INPUT VOLTAGE
PEAK-TO-PEAK OUTPUT RIPPLE VOLTAGE
vs
LOAD CURRENT
30
VO = 1.8 V
PFM/PWM Operation
92
IO = 100 mA
IO = 300 mA
90
Efficiency - %
88
86
84
82
IO = 10 mA
80
IO = 1 mA
78
76
VO - Peak-to-Peak Output Ripple Voltage - mV
94
VO = 1.8 V (TPS82671)
26
VI = 3.6 V
24
22
20
18
16
VI = 4.5 V
14
12
VI = 2.7 V
10
8
6
4
PFM/PWM Operation
2
0
74
2.5 2.7 2.9 3.1 3.3 3.5 3.7 3.9 4.1 4.3 4.5 4.7
VI - Input Voltage - V
0
20
40
60
80 100 120 140 160 180 200
IO - Load Current - mA
Figure 5.
Figure 6.
PEAK-TO-PEAK OUTPUT RIPPLE VOLTAGE
vs
LOAD CURRENT
PEAK-TO-PEAK OUTPUT RIPPLE VOLTAGE
vs
LOAD CURRENT
26
45
VO = 1.2 V (TPS82675)
24
22
VI = 2.7 V
20
18
VI = 3.6 V
16
VI = 4.5 V
14
12
10
8
6
4
2
PFM/PWM Operation
0
0
20
40
60
80 100 120 140 160 180 200
IO - Load Current - mA
Figure 7.
Copyright © 2010–2011, Texas Instruments Incorporated
VO - Peak-to-Peak Output Ripple Voltage - mV
VO - Peak-to-Peak Output Ripple Voltage - mV
28
VO = 1.2 V (TPS82677)
40
VI = 4.5 V
35
VI = 3.6 V
30
VI = 2.7 V
25
20
15
10
5
0
0
25 50 75 100 125 150 175 200 225 250 275 300
IO - Load Current - mA
Figure 8.
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TPS82671, TPS82672, TPS82675
TPS82676, TPS82677
SLVSAI0C – OCTOBER 2010 – REVISED NOVEMBER 2011
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TYPICAL CHARACTERISTICS (continued)
DC OUTPUT VOLTAGE
vs
LOAD CURRENT
DC OUTPUT VOLTAGE
vs
LOAD CURRENT
1.836
1.224
VO = 1.8 V (TPS82671)
PFM/PWM Operation
VO = 1.2 V (TPS82675)
PFM/PWM Operation
1.818
VI = 4.5 V
VI = 3.6 V
1.800
VI = 2.7 V
1.782
VO - Output Voltage - V
VO - Output Voltage - V
1.212
VI = 4.5 V
1.2
VI = 3.6 V
VI = 2.7 V
1.188
1.764
0.1
1
10
100
1000
1.176
0.1
1
10
100
1000
IO - Load Current - mA
IO - Load Current - mA
Figure 9.
Figure 10.
DC OUTPUT VOLTAGE
vs
LOAD CURRENT
COMBINED LINE/LOAD TRANSIENT RESPONSE
1.224
VO = 1.2 V (TPS82677)
PFM/PWM Operation
VO = 1.8 V (TPS82671)
30 to 300 mA Load Step
VO - Output Voltage - V
1.212
VI = 4.5 V
3.3V to 3.9V Line Step
1.2
VI = 3.6 V
VI = 2.7 V
1.188
MODE = Low
1.176
0.1
1
10
100
IO - Load Current - mA
Figure 11.
8
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1000
Figure 12.
Copyright © 2010–2011, Texas Instruments Incorporated
Product Folder Link(s): TPS82671 TPS82672 TPS82675 TPS82676 TPS82677
TPS82671, TPS82672, TPS82675
TPS82676, TPS82677
SLVSAI0C – OCTOBER 2010 – REVISED NOVEMBER 2011
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TYPICAL CHARACTERISTICS (continued)
COMBINED LINE/LOAD TRANSIENT RESPONSE
LOAD TRANSIENT RESPONSE IN
PFM/PWM OPERATION
VO = 1.8 V (TPS82671)
VI = 3.6 V,
VO = 1.8 V (TPS82671)
30 to 150 mA Load Step
5 to 150 mA Load Step
2.7V to 3.3V Line Step
MODE = Low
MODE = Low
Figure 13.
Figure 14.
LOAD TRANSIENT RESPONSE IN
PFM/PWM OPERATION
LOAD TRANSIENT RESPONSE IN
PFM/PWM OPERATION
VI = 3.6 V,
VO = 1.8 V (TPS82671)
50 to 350 mA Load Step
VI = 2.7 V,
VO = 1.8 V (TPS82671)
50 to 350 mA Load Step
MODE = Low
Figure 15.
Copyright © 2010–2011, Texas Instruments Incorporated
MODE = Low
Figure 16.
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TPS82671, TPS82672, TPS82675
TPS82676, TPS82677
SLVSAI0C – OCTOBER 2010 – REVISED NOVEMBER 2011
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TYPICAL CHARACTERISTICS (continued)
LOAD TRANSIENT RESPONSE IN
PFM/PWM OPERATION
VI = 4.5 V,
VO = 1.8 V (TPS82671)
50 to 350 mA Load Step
LOAD TRANSIENT RESPONSE IN
PFM/PWM OPERATION
VI = 3.6 V,
VO = 1.8 V (TPS82671)
150 to 500 mA Load Step
MODE = Low
MODE = Low
Figure 17.
Figure 18.
LOAD TRANSIENT RESPONSE IN
PFM/PWM OPERATION
LOAD TRANSIENT RESPONSE
IN PFM/PWM OPERATION
VI = 2.7 V,
VO = 1.8 V (TPS82671)
150 to 500 mA Load Step
VI = 4.5 V,
VO = 1.8 V (TPS82671)
150 to 500 mA Load Step
MODE = Low
Figure 19.
10
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MODE = Low
Figure 20.
Copyright © 2010–2011, Texas Instruments Incorporated
Product Folder Link(s): TPS82671 TPS82672 TPS82675 TPS82676 TPS82677
TPS82671, TPS82672, TPS82675
TPS82676, TPS82677
SLVSAI0C – OCTOBER 2010 – REVISED NOVEMBER 2011
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TYPICAL CHARACTERISTICS (continued)
LOAD TRANSIENT RESPONSE
IN PFM/PWM OPERATION
AC LOAD TRANSIENT RESPONSE
VI = 3.6 V,
VO = 1.8 V (TPS82671)
VI = 3.6 V,
VO = 1.2 V
5 to 300 mA Load Sweep
5 to 150 mA Load Step
MODE = Low
VI = 3.6 V,
VO = 1.2 V
MODE = Low
Figure 21.
Figure 22.
LOAD TRANSIENT RESPONSE
IN PFM/PWM OPERATION
LOAD TRANSIENT RESPONSE
IN PFM/PWM OPERATION
50 to 350 mA Load Step
VI = 2.7 V,
VO = 1.2 V
50 to 350 mA Load Step
MODE = Low
Figure 23.
Copyright © 2010–2011, Texas Instruments Incorporated
MODE = Low
Figure 24.
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TYPICAL CHARACTERISTICS (continued)
LOAD TRANSIENT RESPONSE
IN PFM/PWM OPERATION
50 to 350 mA Load Step
LOAD TRANSIENT RESPONSE
IN PFM/PWM OPERATION
VI = 3.6 V,
VO = 1.2 V
150 to 500 mA Load Step
MODE = Low
VI = 2.7 V,
VO = 1.2 V
MODE = Low
Figure 25.
Figure 26.
LOAD TRANSIENT RESPONSE
IN PFM/PWM OPERATION
LOAD TRANSIENT RESPONSE
IN PFM/PWM OPERATION
150 to 500 mA Load Step
VI = 4.5 V,
VO = 1.2 V
150 to 500 mA Load Step
MODE = Low
Figure 27.
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MODE = Low
Figure 28.
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TPS82671, TPS82672, TPS82675
TPS82676, TPS82677
SLVSAI0C – OCTOBER 2010 – REVISED NOVEMBER 2011
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TYPICAL CHARACTERISTICS (continued)
AC LOAD TRANSIENT RESPONSE
PFM/PWM BOUNDARIES
140
PFM to PWM
Mode Change
Always PWM
VI = 3.6 V,
VO = 1.2 V
5 to 300 mA Load Sweep
120
The switching mode
changes at these
borders
IO - Load Current - mA
100
MODE = Low
80
60
PWM to PFM
Mode Change
Always PFM
40
20
VO = 1.8 V (TPS82671)
0
2.7
Figure 30.
PFM/PWM BOUNDARIES
QUIESCENT CURRENT
vs
INPUT VOLTAGE
26
Always PWM
PFM to PWM
Mode Change
24
4.8
80
PWM to PFM
Mode Change
60
Always PFM
40
TA = 85°C
TA = 25°C
22
The switching mode changes
at these borders
IQ - Quiescent Current - mA
IO - Load Current - mA
4.5
28
100
20
20
18
16
14
12
TA = -40°C
10
8
6
4
VO = 1.2 V (TPS82674)
0
2.7
3.3
3.6
3.9
4.2
VI - Input Voltage - V
Figure 29.
140
120
3
3
3.3
3.6
3.9
4.2
VI - Input Voltage - V
Figure 31.
Copyright © 2010–2011, Texas Instruments Incorporated
2
4.5
4.8
0
2.7
3
3.3
3.6
3.9
4.2
VI - Input Voltage - V
4.5
4.8
Figure 32.
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TYPICAL CHARACTERISTICS (continued)
PWM SWITCHING FREQUENCY
vs
INPUT VOLTAGE
START-UP
6
IO = 150 mA
fS - Switching Frequency - MHz
5.5
5
IO = 300 mA
VI = 3.6 V,
VO = 1.8 V (TPS82671),
IO = 0 mA
IO = 400 mA
4.5
IO = 500 mA
4
3.5
MODE = Low
3
VO = 1.8 V
2.9
3.1 3.3 3.5 3.7 3.9
VI - Input Voltage - V
4.1 4.3 4.5
Figure 33.
Figure 34.
START-UP
POWER SUPPLY REJECTION RATIO
vs
FREQUENCY
VI = 3.6 V,
VO = 1.8 V (TPS82671),
RL = 100 Ω
MODE = Low
Figure 35.
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PSRR - Power Supply Rejection Ratio - dB
2.5
2.5 2.7
85
VI = 3.6 V,
80
IO = 10 mA
VO = 1.8 V (TPS82671)
75
PFM Operation
70
IO = 150 mA
65
60
PWM Operation
55
50
45
40
35 IO = 400 mA
30 PWM Operation
25
20
15
10
5
0
0.01
0.1
1
10
100
1000
f - Frequency - kHz
Figure 36.
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Product Folder Link(s): TPS82671 TPS82672 TPS82675 TPS82676 TPS82677
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TYPICAL CHARACTERISTICS (continued)
SPURIOUS OUTPUT NOISE (PFM MODE)
vs
FREQUENCY
SPURIOUS OUTPUT NOISE (PWM MODE)
vs
FREQUENCY
5m
500 m
Spurious Output Noise (PWM Mode) - V
Spurious Output Noise (PFM Mode) - V
4.5 m
5m
3.5 m
3m
2.5 m
VI = 2.7 V
2m
VI = 4.2 V
1.5 m
VI = 3.6 V
1m
500 m
50 n
0
VO = 1.8 V (TPS82671),
RL = 150 Ω
Span = 1 MHz
f - Frequency - MHz
10
VO = 1.8 V (TPS82671),
450 m R = 12 Ω
L
400 m
350 m
VI = 4.2 V
300 m
250 m
200 m
VI = 2.7 V
150 m
100 m
VI = 3.6 V
50 m
5n
0
Span = 4 MHz
f - Frequency - MHz
Figure 37.
40
Figure 38.
OUTPUT SPECTRAL NOISE DENSITY
vs
FREQUENCY
Output Spectral Noise Density - µV/VHz
10
VIN = 3.6 V
VOUT = 1.8 V (TPS82671)
1
IOUT = 10 mA (PFM Mode)
0.1
IOUT = 150 mA (PWM Mode)
0.01
0.001
0.1
Copyright © 2010–2011, Texas Instruments Incorporated
1
10
100
f - Frequency - kHz
Figure 39.
1000
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DETAILED DESCRIPTION
OPERATION
The TPS8267x is a stand-alone, synchronous, step-down converter. The converter operates at a regulated
5.5-MHz frequency pulse width modulation (PWM) at moderate to heavy load currents (up to 600mA output
current). At light load currents, the TPS8267x converter operates in power-save mode with pulse frequency
modulation (PFM).
The converter uses a unique frequency-locked ring-oscillating modulator to achieve best-in-class load and line
response. One key advantage of the non-linear architecture is that there is no traditional feed-back loop. The
loop response to change in VO is essentially instantaneous, which explains the transient response. Although this
type of operation normally results in a switching frequency that varies with input voltage and load current, an
internal frequency lock loop (FLL) holds the switching frequency constant over a large range of operating
conditions.
Combined with best-in-class load and line-transient response characteristics, the low quiescent current of the
device (approximately 17μA) helps to maintain high efficiency at light load while that current preserves a fast
transient response for applications that require tight output regulation.
The TPS8267x integrates an input current limit to protect the device against heavy load or short circuits and
features an undervoltage lockout circuit to prevent the device from misoperation at low input voltages. Fully
functional operation is permitted down to 2.1V input voltage.
POWER-SAVE MODE
If the load current decreases, the converter enters power-save mode automatically. During power-save mode,
the converter operates in discontinuous current, (DCM) single-pulse PFM mode, which produces a low output
ripple compared with other PFM architectures.
When in power-save mode, the converter resumes its operation when the output voltage falls below the nominal
voltage. The converter ramps up the output voltage with a minimum of one pulse and goes into power-save
mode when the output voltage is within its regulation limits.
The IC exits PFM mode and enters PWM mode when the output current can no longer be supported in PFM
mode. As a consequence, the DC output voltage is typically positioned approximately 0.5% above the nominal
output voltage. The transition between PFM and PWM is seamless.
PFM Mode at Light Load
PFM Ripple
Nominal DC Output Voltage
PWM Mode at Heavy Load
Figure 40. Operation in PFM Mode and Transfer to PWM Mode
MODE SELECTION
The MODE pin selects the operating mode of the device. Connecting the MODE pin to GND enables the
automatic PWM and power-save mode operation. The converter operates in regulated frequency PWM mode at
moderate to heavy loads, and operates in PFM mode during light loads. This type of operation maintains high
efficiency over a wide load current range.
Pulling the MODE pin high forces the converter to operate in PWM mode even at light-load currents. The
advantage is that the converter modulates its switching frequency according to a spread spectrum PWM
modulation technique that allows simple filtering of the switching harmonics in noise-sensitive applications. In this
mode, the efficiency is lower when compared to the power-save mode during light loads.
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For additional flexibility, it is possible to switch from power-save mode to PWM mode during operation. This type
of operation allows efficient power management by adjusting the operation of the converter to the specific system
requirements.
SPREAD SPECTRUM, PWM FREQUENCY DITHERING
The goal of spread spectrum architecture is to spread out the emitted RF energy over a larger frequency range
so that any resulting electromagnetic interference (EMI) is similar to white noise. The end result is a spectrum
that is continuous and lower in peak amplitude. Spread spectrum makes it easier to comply with EMI standards.
It also makes it easier to comply with the power supply ripple requirements in cellular and non-cellular wireless
applications. Radio receivers are typically susceptible to narrowband noise that is focused on specific
frequencies.
Switching regulators can be particularly troublesome in applications where electromagnetic interference (EMI) is
a concern. Switching regulators operate on a cycle-by-cycle basis to transfer power to an output. In most cases,
the frequency of operation is either fixed or regulated, based on the output load. This method of conversion
creates large components of noise at the frequency of operation (fundamental) and multiples of the operating
frequency (harmonics).
The spread spectrum architecture varies the switching frequency by approximately ±10% of the nominal
switching frequency, thereby significantly reduces the peak radiated and conducting noise on both the input and
output supplies. The frequency dithering scheme is modulated with a triangle profile and a modulation frequency
fm.
0 dBV
FENV,PEAK
Dfc
Dfc
Non-modulated harmonic
F1
Side-band harmonics
window after modulation
0 dBVref
B = 2 × fm × (1 + mf ) = 2 × ( Dfc + fm )
B = 2 × fm × (1 + mf ) = 2 × ( Dfc + fm )
Figure 41. Spectrum of a Frequency Modulated
Sin. Wave with Sinusoidal Variation in Time
Bh = 2 × fm × (1 + mf × h )
Figure 42. Spread Bands of Harmonics in
Modulated Square Signals (1)
Figure 41 and Figure 42 show that after modulation the sideband harmonic is attenuated when compared to the
non-modulated harmonic, and when the harmonic energy is spread into a certain frequency band. The higher the
modulation index (mf) the larger the attenuation.
mƒ =
δ ´ ƒc
ƒm
(1)
With:
fc is the carrier frequency (i.e. nominal switching frequency)
fm is the modulating frequency (approx. 0.016*fc)
δ is the modulation ratio (approx 0.1)
d=
(1)
D ƒc
ƒc
(2)
Spectrum illustrations and formulae (Figure 41 and Figure 42) copyright IEEE TRANSACTIONS ON ELECTROMAGNETIC
COMPATIBILITY, VOL. 47, NO.3, AUGUST 2005. See REFERENCES Section for full citation.
Copyright © 2010–2011, Texas Instruments Incorporated
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The maximum switching frequency is limited by the process and by the parameter modulation ratio (δ), together
with fm, which is the bandwidth of the side-band harmonics around the carrier frequency fc. The bandwidth of a
frequency modulated waveform is approximately given by the Carson’s rule and can be summarized as:
B = 2 ´ ¦m ´ 1 + m ¦
(
)=2
´
(D ¦c
+ ¦m )
(3)
fm < RBW: The receiver is not able to distinguish individual side-band harmonics; so, several harmonics are
added in the input filter and the measured value is higher than expected in theoretical calculations.
fm > RBW: The receiver is able to properly measure each individual side-band harmonic separately, so that the
measurements match the theoretical calculations.
SOFT START
The TPS8267x has an internal soft-start circuit that limits the in-rush current during start-up. This circuit limits
input voltage drop when a battery or a high-impedance power source is connected to the input of the MicroSiP™
DC/DC converter.
The soft-start system progressively increases the switching on-time from a minimum pulse-width of 35ns as a
function of the output voltage. This mode of operation continues for approximately 100μs after the enable. If the
output voltage does not reach its target value within the soft-start time, the soft-start transitions to a second mode
of operation.
If the output voltage rises above approximately 0.5V, the converter increases the input current limit and thus
enables the power supply to come up properly. The start-up time mainly depends on the capacitance present at
the output node and the load current.
ENABLE
The TPS8267x device starts operation when EN is set high and starts up with the soft start as previously
described. For proper operation, the EN pin must be terminated and must not be left floating.
Pulling the EN pin low forces the device into shutdown. In this mode, all internal circuits are turned off and the
VIN current reduces to the device leakage current, which is typically a few hundred nanoamps.
The TPS8267x device can actively discharge the output capacitor when it turns off. The integrated discharge
resistor has a typical resistance of 100 Ω. The required time to ramp down the output voltage depends on the
load current and the capacitance present at the output node.
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APPLICATION INFORMATION
INPUT CAPACITOR SELECTION
Because of the pulsating input current nature of the buck converter, a low ESR input capacitor is required to
prevent large voltage transients that can cause misbehavior of the device or interference in other circuits in the
system.
For most applications, the input capacitor that is integrated into the TPS8267x should be sufficient. If the
application exhibits a noisy or erratic switching frequency, experiment with additional input ceramic capacitance
to find a remedy.
The TPS8267x uses a tiny ceramic input capacitor. When a ceramic capacitor is combined with trace or cable
inductance, such as from a wall adapter, a load step at the output can induce ringing at the VIN pin. This ringing
can couple to the output and be mistaken as loop instability or can even damage the part. In this circumstance,
additional "bulk" capacitance, such as electrolytic or tantalum, should be placed between the input of the
converter and the power source lead to reduce ringing that can occur between the inductance of the power
source leads and CI.
OUTPUT CAPACITOR SELECTION
The advanced, fast-response, voltage mode, control scheme of the TPS8267x allows the use of a tiny ceramic
output capacitor (CO). For most applications, the output capacitor integrated in the TPS8267x is sufficient.
At nominal load current, the device operates in PWM mode; the overall output voltage ripple is the sum of the
voltage step that is caused by the output capacitor ESL and the ripple current that flows through the output
capacitor impedance. At light loads, the output capacitor limits the output ripple voltage and provides holdup
during large load transitions.
The TPS8267x is designed as a Point-Of-Load (POL) regulator, to operate stand-alone without requiring any
additional capacitance. Adding a 2.2μF ceramic output capacitor (X7R or X5R dielectric) generally works from a
converter stability point of view, but does not necessarily help to minimize the output ripple voltage.
For best operation (i.e. optimum efficiency over the entire load current range, proper PFM/PWM auto transition),
the TPS8267xSIP requires a minimum output ripple voltage in PFM mode. The typical output voltage ripple is ca.
1% of the nominal output voltage VO. The PFM pulses are time controlled resulting in a PFM output voltage
ripple and PFM frequency that depends (first order) on the capacitance seen at the MicroSiPTM DC/DC
converter's output.
In applications requiring additional output bypass capacitors located close to the load, care should be taken to
ensure proper operation. If the converter exhibits marginal stability or erratic switching frequency, experiment
with additional low value series resistance (e.g. 50 to 100mΩ) in the output path to find a remedy.
Because the damping factor in the output path is directly related to several resistive parameters (e.g. inductor
DCR, power-stage rDS(on), PWB DC resistance, load switches rDS(on) …) that are temperature dependant, the
converter small and large signal behavior must be checked over the input voltage range, load current range and
temperature range.
The easiest sanity test is to evaluate, directly at the converter’s output, the following aspects:
•
•
PFM/PWM efficiency
PFM/PWM and forced PWM load transient response
During the recovery time from a load transient, the output voltage can be monitored for settling time, overshoot or
ringing that helps judge the converter’s stability. Without any ringing, the loop has usually more than 45° of phase
margin.
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LAYOUT CONSIDERATION
In making the pad size for the SiP LGA balls, it is recommended that the layout use non-solder-mask defined
(NSMD) land. With this method, the solder mask opening is made larger than the desired land area, and the
opening size is defined by the copper pad width. Figure 43 shows the appropriate diameters for a MicroSiPTM
layout.
Copper Trace Width
Solder Pad Width
Solder Mask Opening
Copper Trace Thickness
Solder Mask Thickness
M0200-01
Figure 43. Recommended Land Pattern Image and Dimensions
SOLDER PAD
DEFINITIONS (1) (2) (3) (4)
COPPER PAD
Non-solder-mask
defined (NSMD)
0.30mm
(1)
(2)
(3)
(4)
(5)
(6)
SOLDER MASK
OPENING
0.360mm
(5)
COPPER
THICKNESS
STENCIL (6)
OPENING
STENCIL THICKNESS
1oz max (0.032mm)
0.34mm diameter
0.1mm thick
Circuit traces from non-solder-mask defined PWB lands should be 75μm to 100μm wide in the exposed area inside the solder mask
opening. Wider trace widths reduce device stand off and affect reliability.
Best reliability results are achieved when the PWB laminate glass transition temperature is above the operating the range of the
intended application.
Recommend solder paste is Type 3 or Type 4.
For a PWB using a Ni/Au surface finish, the gold thickness should be less than 0.5mm to avoid a reduction in thermal fatigue
performance.
Solder mask thickness should be less than 20 μm on top of the copper circuit pattern.
For best solder stencil performance use laser cut stencils with electro polishing. Chemically etched stencils give inferior solder paste
volume control.
SURFACE MOUNT INFORMATION
The TPS8267x MicroSiP™ DC/DC converter uses an open frame construction that is designed for a fully
automated assembly process and that features a large surface area for pick and place operations. See the "Pick
Area" in the package drawings.
Package height and weight have been kept to a minimum thereby to allow the MicroSiP™ device to be handled
similarly to a 0805 component.
See JEDEC/IPC standard J-STD-20b for reflow recommendations.
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THERMAL INFORMATION
The die temperature of the TPS8267x must be lower than the maximum rating of 125°C, so care should be taken
in the layout of the circuit to ensure good heat sinking of the TPS8267x.
To estimate the junction temperature, approximate the power dissipation within the TPS8267x by applying the
typical efficiency stated in this datasheet to the desired output power; or, by taking a power measurement if you
have an actual TPS8267x device and TPS82671EVM evaluation module. Then calculate the internal temperature
rise of the TPS8267x above the surface of the printed circuit board by multiplying the TPS8267x power
dissipation by the thermal resistance.
The actual thermal resistance of the TPS8267x to the printed circuit board depends on the layout of the circuit
board, but the thermal resistance given in the Thermal Information Table can be used as a guide.
Three basic approaches for enhancing thermal performance are listed below:
• Improve the power dissipation capability of the PCB design.
• Improve the thermal coupling of the component to the PCB.
• Introduce airflow into the system.
PACKAGE SUMMARY
SIP PACKAGE
TOP VIEW
A1
BOTTOM VIEW
YML
D
CC
LSB
C1
C2
B1
B2
A1
A2
C3
A3
E
Code:
•
CC — Customer Code (device/voltage specific)
•
YML — Y: Year, M: Month, L: Lot trace code
•
LSB — L: Lot trace code, S: Site code, B: Board locator
MicroSiPTM DC/DC MODULE PACKAGE DIMENSIONS
The TPS8267x device is available in an 8-bump ball grid array (BGA) package. The package dimensions are:
• D = 2.30 ±0.05 mm
• E = 2.90 ±0.05 mm
REFERENCES
"EMI Reduction in Switched Power Converters Using Frequency Modulation Techniques", in IEEE
TRANSACTIONS ON ELECTROMAGNETIC COMPATIBILITY, VOL. 4, NO. 3, AUGUST 2005, pp 569-576 by
Josep Balcells, Alfonso Santolaria, Antonio Orlandi, David González, Javier Gago.
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REVISION HISTORY
Note: Page numbers of current version may differ form previous versions.
Changes from Original (October 2010) to Revision A
Page
•
Added devices TPS82677 and TPS82678 to Header info ................................................................................................... 1
•
Added TPS82678 to Ordering Info table and removed "Product Preview" attribute from TPS82677 .................................. 2
•
Changed graph for Figure 8 .................................................................................................................................................. 7
•
Changed graph for Figure 11 ................................................................................................................................................ 8
•
Added copyright attribution for spectrum illustrations ......................................................................................................... 17
Changes from Revision A (April 2011) to Revision B
Page
•
Added TPS82676 part number to the data sheet header ..................................................................................................... 1
•
Deleted product preview attribute fromTPS82676 device in the Ordering Information table. .............................................. 2
Changes from Revision B (August 2011) to Revision C
Page
•
Added device TPS82672 to Header info .............................................................................................................................. 1
•
Deleted Product Preview annotation from device TPS82672 in Ordering Info table ............................................................ 2
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PACKAGE OPTION ADDENDUM
www.ti.com
8-Feb-2012
PACKAGING INFORMATION
Orderable Device
Status
(1)
Package Type Package
Drawing
Pins
Package Qty
Eco Plan
(2)
Lead/
Ball Finish
MSL Peak Temp
(3)
Samples
(Requires Login)
TPS82671SIPR
ACTIVE
uSiP
SIP
8
3000
TBD
Call TI
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TPS82671SIPT
ACTIVE
uSiP
SIP
8
250
TBD
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TPS82672SIPR
ACTIVE
uSiP
SIP
8
3000
TBD
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TPS82672SIPT
ACTIVE
uSiP
SIP
8
250
TBD
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TPS82675SIPR
ACTIVE
uSiP
SIP
8
3000
TBD
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TPS82675SIPT
ACTIVE
uSiP
SIP
8
250
TBD
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TPS82676SIPR
ACTIVE
uSiP
SIP
8
3000
TBD
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TPS82676SIPT
ACTIVE
uSiP
SIP
8
250
TBD
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TPS82677SIPR
ACTIVE
uSiP
SIP
8
3000
TBD
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TPS82677SIPT
ACTIVE
uSiP
SIP
8
250
TBD
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(1)
The marketing status values are defined as follows:
ACTIVE: Product device recommended for new designs.
LIFEBUY: TI has announced that the device will be discontinued, and a lifetime-buy period is in effect.
NRND: Not recommended for new designs. Device is in production to support existing customers, but TI does not recommend using this part in a new design.
PREVIEW: Device has been announced but is not in production. Samples may or may not be available.
OBSOLETE: TI has discontinued the production of the device.
(2)
Eco Plan - The planned eco-friendly classification: Pb-Free (RoHS), Pb-Free (RoHS Exempt), or Green (RoHS & no Sb/Br) - please check http://www.ti.com/productcontent for the latest availability
information and additional product content details.
TBD: The Pb-Free/Green conversion plan has not been defined.
Pb-Free (RoHS): TI's terms "Lead-Free" or "Pb-Free" mean semiconductor products that are compatible with the current RoHS requirements for all 6 substances, including the requirement that
lead not exceed 0.1% by weight in homogeneous materials. Where designed to be soldered at high temperatures, TI Pb-Free products are suitable for use in specified lead-free processes.
Pb-Free (RoHS Exempt): This component has a RoHS exemption for either 1) lead-based flip-chip solder bumps used between the die and package, or 2) lead-based die adhesive used between
the die and leadframe. The component is otherwise considered Pb-Free (RoHS compatible) as defined above.
Green (RoHS & no Sb/Br): TI defines "Green" to mean Pb-Free (RoHS compatible), and free of Bromine (Br) and Antimony (Sb) based flame retardants (Br or Sb do not exceed 0.1% by weight
in homogeneous material)
(3)
MSL, Peak Temp. -- The Moisture Sensitivity Level rating according to the JEDEC industry standard classifications, and peak solder temperature.
Important Information and Disclaimer:The information provided on this page represents TI's knowledge and belief as of the date that it is provided. TI bases its knowledge and belief on information
provided by third parties, and makes no representation or warranty as to the accuracy of such information. Efforts are underway to better integrate information from third parties. TI has taken and
continues to take reasonable steps to provide representative and accurate information but may not have conducted destructive testing or chemical analysis on incoming materials and chemicals.
TI and TI suppliers consider certain information to be proprietary, and thus CAS numbers and other limited information may not be available for release.
Addendum-Page 1
PACKAGE OPTION ADDENDUM
www.ti.com
8-Feb-2012
In no event shall TI's liability arising out of such information exceed the total purchase price of the TI part(s) at issue in this document sold by TI to Customer on an annual basis.
Addendum-Page 2
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