ML13150 Narrowband FM Coilless Detector IF Subsystem NARROWBAND FM COILLESS DETECTOR IF SUBSYSTEM FOR CELLULAR AND ANALOG APPLICATIONS SEMICONDUCTOR TECHNICAL DATA Legacy Device: Motorola MC13150 ML13150-A9P PLASTIC PACKAGE (LQFP-24) The ML13150 is a narrowband FM IF subsystem targeted at cellular and other analog applications. The ML13150 has an onboard Colpitts VCO that can be crystal controlled or phased lock for second LO in dual conversion receivers. The mixer is a double balanced configuration with excellent third order intercept. It is useful to beyond 200 MHz. The IF amplifier is split to accommodate two low cost cascaded filters. RSSI output is derived by summing the output of both IF sections., The quadrature detector is a unique design eliminating the conventional tunable quadrature coil. 24 32 Linear Coilless Detector Adjustable Demodulator Bandwidth 2.5 to 6.0 Vdc Operation Low Drain Current <2.0 mA Typical Sensitivity of 2.0 µV for 12 dB SINAD IIP3, Input Third Order Intercept Point of 0 dBm • • • • ML13150-B9P PLASTIC PACKAGE (LQFP-32) 1 CROSS REFERENCE/ORDERING INFORMATION MOTOROLA LANSDALE PACKAGE LQFP-24 LQFP-32 Applications for the ML13150 include cellular, CT-1, 900 MHz cordless telephone, data links and other radio systems utilizing narrowband FM modulation. • • • • • • 1 MC13150FTA MC13150FTB ML13150-A9P ML13150-B9P Note: Lansdale lead free (Pb) product, as it becomes available, will be identified by a part number prefix change from ML to MLE. RSSI Range of Greater Than 100 dB Internal 1.4 kΩ Terminations for 455 kHz Filters Split IF for Improved filtering and Extended RSSI Range Operating Temperature Range - TA = -40° to +85°C PIN CONNECTIONS Mixout 1 VCC1 2 VEE1 LOe LOb Enable RSSI Mix in VEE1 VCC (N/C) LOe LOb VCC (N/C) Enable RSSI 24 23 22 21 20 19 32 31 29 28 27 26 25 18 RSSIb Mixer MixOut 1 30 24 RSSIb Mixer VCC1 2 17 DETout IFd1 4 IFd2 5 IFout 6 IF 23 DETout VCC (N/C) 3 22 VEE (N/C) 16 VEE2 IFin 4 21 VEE2 15 DET Gain IFd1 5 20 DETGain 14 AFTFilt Limiter 13 AFT out IF VCC (N/C) 6 IFd2 7 Detector 3 Detector IFin LQFP-32 Mix in LQFP-24 Limiter Page 1 of 20 www.lansdale.com LIMd1 LIMd2 BWAdj FAdj 11 12 13 14 15 16 FAdj LIM in 10 BWAdj V CC2 9 LIM d2 VCC (N/C) 12 LIM d1 11 VCC (N/C) 10 LIM in 9 V CC2 8 18 AFTFilt 17 AFTout IFout 8 7 19 VEE (N/C) Issue A LANSDALE Semiconductor, Inc. ML13150 MAXIMUM RATINGS Rating Pin Symbol Value Unit Power Supply Voltage 2, 9 VCC(max) 6.5 Vdc Junction Temperature - TJmax +150 C Storage Temperature Range - Tstg -65 to +150 C NOTE: 1. Devices should not be operated at or outside these values. The “Recommended Operating Limits” provide for actual device operation. 2. ESD data available upon request. RECOMMENDED OPERATING CONDITIONS Rating Power Supply Voltage –40 C TA = 25 C TA 85 C Pin Symbol Value Unit 2, 9 21, 31 VCC VEE 2.5 to 6.0 0 Vdc 32 fin 10 to 500 MHz (See Figure 22) Input Frequency Ambient Temperature Range - TA -40 to +85 C Input Signal Level 32 Vin 0 dBm DC ELECTRICAL CHARACTERISTICS (TA = 25 C, VCC1 = VCC2 = 3.0 Vdc, No Input Signal.) Characteristics Total Drain Current (See Figure 2) Condition Pin Symbol Min Typ Max Unit VS = 3.0 Vdc 2+9 ITOTAL - 1.7 3.0 mA - 2+9 - - 40 - nA Supply Current, Power Down (See Figure 3) AC ELECTRICAL CHARACTERISTICS (TA = 25 C, VS = 3.0 Vdc, fRF = 50 MHz, fLO = 50.455 MHz, LO Level = –10 dBm, see Figure 1 Test Circuit*, unless otherwise specified.) Characteristics Condition Pin Symbol Min Typ Max Unit fmod = 1.0 kHz; fdev = ±5.0 kHz 32 - - –100 - dBm RSSI Dynamic Range (See Figure 7) - 25 - - 100 - dB Input 1.0 dB Compression Point Input 3rd Order Intercept Point (See Figure 18) - - 1.0 dB C. Pt. IIP3 - -1 1 -1.0 - dBm Measured with No IF Filters - ∆BW adj - 26 - kHz/µA Pin = -30 dBm; PLO = -10 dBm 32 - - 10 - dB Single-Ended 32 - - 200 - Ω - 1 - - 1.5 - kΩ - 29 - 30 63 100 µA IF and Limiter RSSI Slope Figure 7 25 - - 0.4 - µA/dB IF Gain 12 dB SINAD Sensitivity (See Figure 15) Coilless Detector Bandwidth Adjust (See Figure 11) MIXER Conversion Voltage Gain (See Figure 5) Mixer Input Impedance Mixer Output Impedance LOCAL OSCILLATOR LO Emitter Current (See Figure 26) IF & LIMITING AMPLIFIERS SECTION Figure 8 4, 8 - - 42 - dB IF Input & Output Impedance - 4, 8 - - 1.5 - kΩ Limiter Input Impedance - 10 - - 1.5 - kΩ Limiter Gain - - - - 96 - dB * Figure 1 Test Circuit uses positive (VCC) Ground. Page 2 of 20 www.lansdale.com Issue A LANSDALE Semiconductor, Inc. ML13150 AC ELECTRICAL CHARACTERISTICS (continued) (TA = 25°C, VS = 3.0 Vdc, fRF = 50 MHz, fLO = 50.455 MHz, LO Level = -10 dBm, see Figure 1 T est Circuit*, unless otherwise specified.) Characteristics Condition Pin Symbol Min Typ Max Unit Frequency Adjust Current Figure 9, fIF = 455 kHz 16 - 41 49 56 µA Frequency Adjust Voltage Figure 10, fIF = 455 kHz 16 - 600 650 700 mVdc Bandwidth Adjust Voltage Figure 12, I15 = 1.0 µA 15 - - 570 - mVdc - 23 - - 1.36 - Vdc fdev = ±3.0 kHz 23 - 85 122 175 mVrms DETECTOR Detector DC Output Voltage (See Figure 25) Recovered Audio Voltage * Figure 1 Test Circuit uses positive (VCC) Ground. Figure 1. Test Circuit LO Input VEE1 10 µ 220 n + 100 n 1:4 Z Xformer Mixer In Enable 49.9 RSSI 100 n 31 32 220 n Mixer Out 1 1.5 k 30 29 28 27 25 2 RSSI Buffer 24 Mixer VCC1 Detector Output 23 Local Oscillator 100 p RSSI Buffer 3 IF In 26 VEE1 22 RL 100 k 220 n 49.9 4 VEE2 21 5 20 220 n 220 n (6) IF 220 n 7 IF Amp Out Limiter 220 n 8 1.5 k Limiter In 19 220 n Detector 6 11 220 n 12 13 14 220 n 220 n 220 n 15 I15 10 µ + VEE2 18 17 VCC2 9 10 RS 100 k 100 k V18–V17 = 0; fIF = 455 kHz 16 I16 49.9 This device contains 292 active transistors. Page 3 of 20 www.lansdale.com Issue A LANSDALE Semiconductor, Inc. ML13150 ML13150 CIRCUIT DESCRIPTION GENERAL DESCRIPTION The ML13150 is a very low power single conversion narrowband FM receiver incorporating a split IF. This device can be used as a single conversion or as the backend in analog narrowband FM systems such as 900 MHz cordless phones, and narrowband data links with data rates up to 9.6 k baud. It contains a mixer, oscillator, extended range received signal strength indicator (RSSI), RSSI buffer, IF amplifier, limiting IF, a unique coilless quadrature detector and a device enabler function (see Package Pin Outs/Block Diagram). LOW CURRENT OPERATION The ML13150 is designed for battery and portable applications. Supply current is typically 1.7 mAdc at 3.0 Vdc. Figure 2 shows the supply current versus supply voltage. ENABLE The enable function is provided for battery powered operation. The enabled pin is pulled down to enable the regulators. Figure 3 shows the supply current versus enable voltage, Venable (relative to VCC) needed to enable the device. Note that the device is fully enabled at VCC - 1.3 Vdc. Figure 4 shows the relationship of the enable current, Ienable, to enable voltage, Venable. MIXER The mixer is a double-balanced four quadrant multiplier and is designed to work up to 500 MHz. It has a single ended input. Figure 5 shows the mixer gain and saturated output response as a function of input signal drive and for –10 dBm LO drive level. This is measured in the application circuit shown in Figure 15 in which a single LC matching network is used. Since the single–ended input impedance of the mixer is 200 Ω, and alternate solution uses a 1:4 impedance transformer to match the mixer to 50 Ω input impedance. The linear voltage gain of the mixer alone is approximately 4.0 dB (plus an additional 6.0 dB for the transformer). Figure 6 shows the mixer gain versus the LO input level for various mixer input levels at 50 MHz RF input. Page 4 of 20 The buffered output of the mixer is internally loaded, resulting in an output impedance of 1.5kΩ. LOCAL OSCILLATOR The on–chip transistor operates with crystal and LC resonant elements up to 220 MHz. Series resonant, overtone crystals are used to achieve excellent local oscillator stability. 3rd overtone crystals are used through about 65 to 70 MHz. Operation for 70 MHz up to 200 MHz is feasible using the on–chip transistor with a 5th or 7th overtone crystal. To enhance operation using an overtone crystal, the internal transistor's bias is increased by adding an external resistor from Pin 29 (in 32 pin QFP package) to VEE to keep the oscillator on continuously or it may be taken to the enable pin to shut is off when the receiver is disabled. –10 dBm of local oscillator drive is needed to adequately drive the mixer (Figure 6). The oscillator configurations specified above are described in the application section. RSSI The received signal strength indicator (RSSI) output is a current proportional to the log of the received signal amplitude. The RSSI current output is derived by summing the currents from the IF and limiting amplifier stages. An external resistor at Pin 25 (in 32 pin QFP package) sets the voltage range or swing of the RSSI output voltage. Linearity of the RSSI is optimized by using external ceramic bandpass filters which have an insertions loss of 4.0 dB. The RSSI circuit is designed to provide 100+ dB of dynamic range with temperature compensation (see Figures 7 and 23 which show the RSSI response of the applications circuit). RSSI BUFFER The RSSI buffer has limitations in what loads it can drive. It can pull loads well towards the positive and negative supplies, but has problems pulling the load away from the supplies. The load should be biased at half supply to overcome this situation. www.lansdale.com Issue A LANSDALE Semiconductor, Inc. ML13150 Figure 2. Supply Current versus Supply Voltage 10–2 ISUPPLY, SUPPLY CURRENT (A) ISUPPLY, SUPPLY CURRENT (mA) 2.0 1.6 1.2 0.8 0.4 TA = 25°C 0 1.5 2.5 3.5 4.5 5.5 6.5 10–5 10–6 10–7 10–8 10–9 0.7 0.9 1.1 1.3 1.5 VENABLE, ENABLE VOLTAGE (Vdc) Figure 4. Enable Current versus Enable Voltage Figure 5. Mixer IF Output Level versus RF Input Level 20 VCC = 3.0 Vdc TA = 25°C 60 MIXER IF OUTPUT LEVEL (dBm) IENABLE, ENABLE CURRENT ( µ A) 10–4 VENABLE, SUPPLY VOLTAGE (Vdc) 50 40 30 20 10 0 0 0.4 0.8 1.2 1.6 2.0 0 –10 –20 –40 –40 –30 –20 –10 0 RF INPUT LEVEL (dBm) Figure 6. Mixer IF Output Level versus Local Oscillator Input Level Figure 7. RSSI Output Current versus Input Signal Level 10 20 –20 0 50 VEE = –3.0 Vdc TA = 25°C RSSI OUTPUT CURRENT (µA) RF In = 0 dBm –20 dBm –20 –40 dBm –40 –60 –80 –60 fRF = 50 MHz; fLO = 50.455 MHz LO Input Level = –10 dBm (100 mVrms) (Rin = 50 Ω; Rout = 1.4 kΩ –30 VENABLE, ENABLE VOLTAGE (Vdc) 20 0 VEE = –3.0 Vdc TA = 25°C 10 –50 –50 –10 MIXER IF OUTPUT LEVEL (dBm) VCC = 3.0 Vdc TA = 25°C VENABLE Measured Relative to VCC 10–3 10–10 0.5 7.5 70 fRF = 50 MHz; fLO = 50.455 MHz Rin = 50 Ω; Rout = 1.4 kΩ 40 30 VCC = 3.0 Vdc f = 50 MHz fLO = 50.455 MHz 455 kHz Ceramic Filter See Figure 15 20 10 0 –50 –40 –30 –20 –10 0 LO DRIVE (dBm) Page 5 of 20 Figure 3. Supply Current versus Enable Voltage –120 –100 –80 –60 –40 SIGNAL INPUT LEVEL (dBm) www.lansdale.com Issue A LANSDALE Semiconductor, Inc. ML13150 IF AMPLIFIER The first IF amplifier section is composed of three differential stages. This section has internal dc feedback and external input decoupling for improved symmetry and stability. The total gain of the IF amplifier block is approximately 42 dB at 455 kHz. Figure 8 shows the gain of the IF amplifier as a function of the IF frequency. The fixed internal input impedance is 1.5 kΩ; it is designed for applications where a 455 kHz ceramic filter is used and no external output matching is necessary since the filter requires a 1.5 kΩ source and load impedance. Overall RSSI linearity is dependent on having total midband attenuation of 10 dB (4.0 insertion loss plus 6.0 dB impedance matching loss) for the filter. The output of the IF amplifier is buffered and the impedance if 1.5kΩ. LIMITER The limiter section is similar to the IF amplifier section except that six stages are used. The fixed internal input impedance is 1.5 kΩ. The total gain of the limiting amplifier sections is approximately 96 dB. This IF limiting amplifier section internally drives the quadrature detector section. Figure 9. Fadj Current versus IF Frequency 50 120 45 100 Fadj CURRENT ( µA) IF AMP GAIN (dB) Figure 8. IF Amplifier Gain versus IF Frequency 40 35 Vin = 100 µV Rin = 50 Ω Rout = 1.4 kΩ BW (3.0 dB) = 2.4 MHz TA = 25°C 30 25 20 0.01 80 60 40 20 0 0.1 800 1.0 10 0 200 400 600 f, FREQUENCY (MHz) f, IF FREQUENCY (kHz) Figure 10. Fadj Voltage versus Fadj Current Figure 11. BWadj Current versus IF Frequency 800 1000 480 500 3.5 VCC = 3.0 Vdc TA = 25°C VCC = 3.0 Vdc BW 26 kHz/µA 3.0 750 BWadj CURRENT ( µA) Fadj VOLTAGE (mVdc) VCC = 3.0 Vdc Slope at 455 kHz = 9.26 kHz/µA 700 650 2.5 2.0 1.5 1.0 0.5 600 0 20 40 60 80 100 0 400 Page 6 of 20 420 440 460 f, IF FREQUENCY (kHz) Fadj CURRENT (µA) www.lansdale.com Issue A LANSDALE Semiconductor, Inc. ML13150 COILLESS DETECTOR The quadrature detector is similar to a PLL. There is an internal oscillator running at the IF frequency and two detector outputs. One is used to deliver the audio signal and the other one is filtered and used to tune the oscillator. The oscillator frequency is set by and external resistor at the Fadj pin. Figure 9 shows the control current required for a particular frequency; Figure 10 shows the pin voltage at that current. From this the value of RF is chosen. For example, 455 kHz would require a current of around 50 µA. The pin voltage (Pin 16 in the 32 pin QFP package) is around 655mV giving a resistor of 13.1 kΩ. Choosing 12 kΩ as the nearest standard value gives a current of approximately 55 µA. The 5.0 µA difference can be taken up by the tuning resistor, RT. The best nominal frequency for the AFTout pin (Pin 17) would be half supply. A supply voltage of 3.0 Vdc suggests a resistor value of (1.5 – 0.655) V/5.0 µA = 169 kΩ. Choosing 150 kΩ would give a tuning current of 3/150 kΩ = 20 µA. From Figure 9 this would give a tuning range of roughly 10 kHz/µA or ± 100 kHz which should be adequate. The bandwidth can be adjusted with the help of Figure 11. 10–4 So, for example, 150 kΩ and 1.0 µF give a 3.0 dB point of 4.5 kHz. The recovered audio is set by RL to give roughly 50mV per kHz deviation per 100 k of resistance. The dc level can be shifted by RS from the nominal 0.68 V by the following equation: Detector DC Output = ((RL + RS)/RS) 0.68 Vdc Thus RS = RL sets the output at 2 x 0.68 = 1.36 V; RL = 2RS sets the output at 3 x .068 = 2.0V. Figure 12. BWadj Current versus BWadj Voltage Figure 13. Demodulator Output versus Frequency 10 VCC = 3.0 Vdc TA = 25 C 10–5 10–6 10–7 2.3 RTCT = 0.68/f3dB. DEMODULATOR OUTPUT (dB) BWadj CURRENT (A) 10–3 For example, 1.0 µA would give a band width of ± 13 kHz. The voltage across the bandwidth resistor, RB from Figure 12 is VCC – 2.44 Vdc = 0.56 Vdc for VCC = 3.0 Vdc, so RB = 0.56V/1.0 µA = 560 kΩ. Actually the locking range will be ±13 kHz while the audio bandwidth wil be approximately ±8.4 kHz due to an internal filter capacitor. This is verified in Figure 13. For some applications it may be desireable that the audio bandwidth is increased; this is done by reducing RB. Reducing RB widens the detector bandwidth and improves the distortion at high input levels at the expense of 12 dB SINAD sensitivity. The low frequency 3.0dB point is set by the tuning circuit such that the product 2.5 2.7 0 RB = 560 k –10 –20 –30 –40 –50 0.1 BWadj VOLTAGE (Vdc) Page 7 of 20 VCC = 3.0 Vdc TA = 25 C fRF = 50 MHz fLO = 50.455 MHz LO Level =–10 dBm No IF Bandpass Filters fdev = ±4.0 kHz 1.0 RB = 1.0 M 10 100 f, FREQUENCY (kHz) www.lansdale.com Issue A LANSDALE Semiconductor, Inc. ML13150 Legacy Applications Information EVALUATION PC BOARD The evaluation PCB is very versatile and is intended to be used across the entire useful frequency range of this device. The center section of the board provides an area for attaching all SMT components to the circuit side and radial leaded components to the component ground side (see Figures 29 and 30). Additionally, the peripheral area surrounding the RF core provides pads to add supporting and interface circuitry as a particular application requires. There is an area dedicated for a LNA preamp. This evaluation board will be discussed and referenced in this section. COMPONENT SELECTION The evaluation PC board is designed to accommodate specific components, while also being versatile enough to use components from various manufacturers and coil types. The applications circuit schematic (Figure 15) specifies particular components that were used to achieve the results shown in the typical curves but equivalent components should give similar results. Component placement views are shown in Figures 27 and 28 for the application circuit in Figure 15 and for the 83.616 MHz crystal oscillator circuit in Figure 16. INPUT MATCHING COMPONENTS The input matching circuit shown in the application circuit schematic (Figure 15) is a series L, shunt C single L section which is used to match the mixer input to 50 Ω. An alternative input network may use 1:4 surface mount transformers or BALUNs. The 12 dB SINAD sensitivity using the 1:4 impedance transformer is typically –100 dBm for fmod = 1.0 kHz and fdev = ±5.0 kHz at f in = 50 MHz and fLO = 50.455 MHz (see Figure 14). It is desirable to use a SAW filter before the mixer to provide additional selectivity an adjacent channel rejection and improved sensitivity. SAW filters sourced from Toko (Part #SWS083GBWA) and Murata (Part # SAF83.16MA51X) are excellent choices to easily interface with the MC13150 mixer. They are packaged in a 12 pin low profile surface mount ceramic package. The center frequency is 83.161 MHz and the 3.0 dB bandwidth is 30 kHz. Figure 14. S+N+D, N+D, N, 30% AMR versus Input Signal Level S+N+D, N+D, N, 30% AMR (dB) 20 10 S+N+D 0 –10 –20 –30 –40 –50 VCC = 3.0 Vdc fmod = 1.0 kHz fdev = ±5.0 kHz fin = 50 MHz N+D 30% AMR fLO = 50.455 MHz LO Level = –10 dBm See Figure 15 N –60 –120 –100 –80 –60 –40 INPUT SIGNAL (dBm) Page 8 of 20 www.lansdale.com Issue A LANSDALE Semiconductor, Inc. ML13150 Legacy Applications Information Figure 15. Application Circuit (3) LO Input (1) 180 nH 100 n 51 100 n 32 31 30 29 28 27 26 VEE1 (2) 455 kHz IF Ceramic Filter Mixer VCC1 100 n RSSI Buffer Local Oscillator 1.0 n 22 VEE2 4 21 5 20 6 7 Limiter 1.0 n RL 150 k RS 150 k 19 (6) IF 100 n 18 17 8 Detector Output 23 3 1.0 n 100 n RSSI Buffer 24 1 2 82 k 25 Detector RF/IF Input (4) Enable (5) RSSI 11 p 1.0 µ CT VCC2 9 10 11 12 13 14 15 16 150 k RT 100 n 455 kHz IF Ceramic Filter 100 n 10 µ 560 k RB 12 k RF (6) Coilless Detector Circuit + VCC NOTES: 1. Alternate solution is 1:4 impedance transformer (sources include Mini Circuits, Coilcraft and Toko). 2. 455 kHz ceramic filters (source Murata CFU455 series which are selected for various bandwidths). 3. For external LO source, a 51 Ω pullup resistor is used to bias the base of the on–board transistor as shown in Figure 15. Designer may provide local oscillator with 3rd, 5th, or 7th overtone crystal oscillator circuit. The PC board is laid out to accommodate external components needed for a Butler emitter coupled crystal oscillator (see Figure 16). 4. Enable IC by switching the pin to V EE. 5. The resistor is chosen to set the range of RSSI voltage output swing. 6. Details regarding the external components to setup the coilless detector are provided in the application section. Page 9 of 20 www.lansdale.com Issue A LANSDALE Semiconductor, Inc. ML13150 Legacy Applications Information LOCAL OSCILLATORS HF & VHF APPLICATIONS In the application schematic, an external sourced local oscillator is utilized in which the base is biased via a 51 Ω resistor to VCC. However, the on–chip grounded collector transistor may be used for HF and VHF local oscillators with higher order overtone crystals. Figure 16 shows a 5th overtone oscillator at 83.616 MHz. The circuit uses a Butler overtone oscillator configuration. The amplifier is an emitter follower. The crystal is driven from the emitter and is coupled to the high impedance base through a capacitive tap network. Operation at the desired overtone frequency is ensured by the parallel resonant circuit formed by the variable inductor and the tap capacitors and parasitic capacitances of the on–chip transistor and PC board. The variable inductor specified in the schematic could be replaced with a high tolerance, high Q ceramic or air wound surface mount component if the other components have tight enough tolerance. A variable inductor provides an adjustment for gain and frequency of the resonant tank ensuring lock up and start–up of the crystal oscillator. The overtone crystal is chosen with ESR of typically 80 Ω and 120 Ω maximum; if the resistive loss in the crystal is too high the performance of oscillator may be impacted by lower gain margins. A series LC network to ac ground (which is VCC) is comprised of the inductance of the base lead of on–chip transistor and PC board traces and tap capacitors. Parasitic oscillations often occur in the 200 to 800 MHz range. A small resistor is placed in series with the base (Pin 28) to cancel the negative resistance associated with this undesired mode of oscillation. Since the base input impedance is so large, a small resistor in the range of 27 to 68 Ω has very little effect on the desired Butler mode of oscillation. The crystal parallel capacitance, Co, provides a feedback path that is low enough in reactance at frequencies of 5th overtones or higher to cause trouble. Co has little effect near resonance because of the low impedance of the crystal motional arm (Rm-Lm-Cm). As the tunable inductor, which forms the resonant tank with the tap capacitors, is tuned off the crystal resonant frequency, it may be difficult to tell if the oscillation is under crystal control. Frequency jumps may occur as the inductor is tuned. In order to eliminate this behavior an inductor, Lo, is placed in parallel with the crystal. Lo is chosen to resonant with the crystal parallel capacitance, Co, at the desired operation frequency. This inductor provides a feedback path at frequencies well below resonance; however, the parallel tank network of the tap capacitors and tunable inductor prevent oscillation at these frequencies. Figure 16. ML13150 Overtone Oscillator fRF = 83.16 MHz; f LO = 83.616 MHz 5th Overtone Crystal Oscillator (4) 0.135 µH MC13150 + 1.0 µ 33 Mixer 28 1.0 µH 39 p 39 p 29 (3) 27 k 5th OT XTAL VEE 10 n 31 VCC Page 10 of 20 www.lansdale.com Issue A LANSDALE Semiconductor, Inc. ML13150 RECEIVER DESIGN CONSIDERATIONS The curves of signal levels at various portions of the application receiver with respect to RF input level are shown in Figure 17. This information helps determine the network topology and gain blocks required ahead of the ML13150 to achieve the desired sensitivity and dynamic range of the receiver system. The PCB is laid out to accommodate a low noise preamp followed by the 83.16 MHz SAW filter. In the application circuit (Figure 15), the input 1.0 dB compression point is –10 dBm and the input third order intercept (IP3) performance of the system is approximately 0 dBm (see Figure 18). TYPICAL PERFORMANCE OVER TEMPERATURE Figures 19–26 show the device performance over temperature. Figure 17. Signal Levels versus RF Input Signal Level 10 0 IF Output POWER (dBm) –10 –20 Limiter Input –30 RF Input at Transformer Input Mixer Output Mixer Input –40 IF Input –50 fRF = 50 MHz fLO = 50.455 MHz; LO Level = –10 dBm See Figure 15 –60 –70 –80 –70 –60 –50 –40 –30 –20 –10 0 RF INPUT SIGNAL LEVEL (dBm) Page 11 of 20 www.lansdale.com Issue A LANSDALE Semiconductor, Inc. ML13150 Figure 18. 1.0 dB Compression Point and Input Third Order Intercept Point versus Input Power MIXER IF OUTPUT LEVEL (dBm) 20 1.0 dB Compression Point = –11 dBm VCC = 3.0 Vdc fRF1 = 50 MHz fRF2 = 50.01 MHz fLO = 50.455 MHz PLO = –10 dBm See Figure 15 0 IP3 = –0.5 dBm –20 –40 –60 –80 –60 –40 –20 0 20 RF INPUT POWER (dBm) TYPICAL PERFORMANCE OVER TEMPERATURE Figure 19. Supply Current, IVEE1 versus Signal Input Level Figure 20. Supply Current, IVEE2 versus Ambient Temperature 0.35 4.5 4.0 3.5 VCC = 3.0 Vdc fc = 50 MHz fdev = ±4.0 kHz IVEE2 , SUPPLY CURRENT (mA) IVEE1, SUPPLY CURRENT (mA) 5.0 3.0 2.5 TA = 85°C 2.0 1.5 1.0 0.5 0 –120 TA = 25°C VCC = 3.0 Vdc 0.3 0.25 TA = –40°C 0.2 –105 –90 –75 –60 –45 –30 –15 0 SIGNAL INPUT LEVEL (dBm) Page 12 of 20 –40 –20 0 20 40 60 80 TA, AMBIENT TEMPERATURE (°C) www.lansdale.com Issue A LANSDALE Semiconductor, Inc. ML13150 TYPICAL PERFORMANCE OVER TEMPERATURE Figure 21. Total Supply Current versus Ambient Temperature Figure 22. Minimum Supply Voltage versus Ambient Temperature 3.0 1.75 MINIMUM SUPPLY VOLTAGE (Vdc) TOTAL SUPPLY CURRENT (mA) 1.8 VCC = 3.0 Vdc 1.7 1.65 1.6 1.55 1.5 1.45 1.4 –20 0 20 40 60 1.5 80 –40 –20 0 20 40 60 80 TA, AMBIENT TEMPERATURE (°C) TA, AMBIENT TEMPERATURE (°C) Figure 23. RSSI Current versus Ambient Temperature and Signal Level Figure 24. Recovered Audio versus Ambient Temperature 0.7 60 Vin = 40 0 dBm –20 dBm 30 –40 dBm 20 –60 dBm –80 dBm –100 dBm 10 RECOVERED AUDIO (Vpp ) VCC = 3.0 Vdc fRF = 50 MHz 50 RSSI CURRENT ( µA) 2.0 1.0 –40 –120 dBm 0 –40 –20 0 20 40 60 80 0.65 0.6 0.55 VCC = 3.0 Vdc RF In = –50 dBm fc = 50 MHz fLO = 50.455 MHz fdev = –4.0 kHz 0.5 0.45 0.4 100 –40 –20 0 20 40 60 80 TA, AMBIENT TEMPERATURE (°C) TA, AMBIENT TEMPERATURE (°C) Figure 25. Demod DC Output Voltage versus Ambient Temperature Figure 26. LO Current versus Ambient Temperature 100 100 1.7 VCC = 3.0 Vdc RF In = –50 dBm fc = 50 MHz fLO = 50.455 MHz fdev = ±4.0 kHz 1.6 1.5 1.4 1.3 1.2 1.1 VCC = 3.0 Vdc RF In = –50 dBm fc = 50 MHz fLO = 50.455 MHz fdev = ±4.0 kHz 90 LO CURRENT ( µA) DEMOD DC OUTPUT VOLTAGE (Vdc) 2.5 80 70 60 1.0 0.9 –40 50 –20 0 20 40 60 80 TA, AMBIENT TEMPERATURE (°C) Page 13 of 20 –40 –20 0 20 40 60 80 TA, AMBIENT TEMPERATURE (°C) www.lansdale.com Issue A LANSDALE Semiconductor, Inc. ML13150 Legacy Applications Information Figure 27. Component Placement View – Circuit Side 100 n 10 n 50 Ω Semi±Rigid Coax 39 p 33 39 p 27 k 82 k 1n 11 p 180 n 150 k MC13150FTB 150 k 100 n 100 n 1n 1n 1 µ 1n 150 k 100 n 560 k 1n 12 k + 100 n 10 µ GND Page 14 of 20 VCC www.lansdale.com Issue A LANSDALE Semiconductor, Inc. ML13150 Legacy Applications Information Figure 28. Component Placement View – Ground Side VCC BW_adj F_adj DET_out GND 455 kHz Ceramic Filter 455 kHz Ceramic Filter RSSI AFT_adj 455 kHz Ceramic Filter 455 kHz Ceramic Filter 1 µH 83.616 MHz ENABLE Xtal 135 nH LO Tuning SMA LO IN RF1 IN RF2 IN 3.8" Page 15 of 20 www.lansdale.com Issue A LANSDALE Semiconductor, Inc. ML13150 Legacy Applications Information Figure 29. PCB Circuit Side View GND VCC MC13150 Rev 0 3/95 3.8" Page 16 of 20 www.lansdale.com Issue A LANSDALE Semiconductor, Inc. ML13150 Legacy Applications Information Figure 30. PCB Ground Side View VCC BW_adj F_adj DET_out GND 455 kHz Ceramic Filter RSSI AFT_adj 455 kHz Ceramic Filter ENABLE Xtal LO Tuning LO IN RF1 IN RF2 IN 3.8" Page 17 of 20 www.lansdale.com Issue A LANSDALE Semiconductor, Inc. ML13150 OUTLINE DIMENSIONS ML13150-A9P PLASTIC PACKAGE CASE 977–01 (LQFP–24) ISSUE O 4X 9 NOTES: 1 DIMENSIONING AND TOLERANCING PER ANSI Y14.5M, 1982. 2 CONTROLLING DIMENSION: MILLIMETER. 3 DATUM PLANE –AB– IS LOCATED AT BOTTOM OF LEAD AND IS COINCIDENT WITH THE LEAD WHERE THE LEAD EXITS THE PLASTIC BODY AT THE BOTTOM OF THE PARTING LINE. 4 DATUMS –T–, –U–, AND –Z– TO BE DETERMINED AT DATUM PLANE –AB–. 5 DIMENSIONS S AND V TO BE DETERMINED AT DATUM PLANE –AC–. 6 DIMENSIONS A AND B DO NOT INCLUDE MOLD PROTRUSION. ALLOWABLE PROTRUSION IS 0.250 (0.010) PER SIDE. DIMENSIONS A AND B DO INCLUDE MOLD MISMATCH AND ARE DETERMINED AT DATUM PLANE AB. 7 DIMENSION D DOES NOT INCLUDE DAMBAR PROTRUSION. DAMBAR PROTRUSION SHALL NOT CAUSE THE D DIMENSION TO EXCEED 0.350 (0.014). 8 MINIMUM SOLDER PLATE THICKNESS SHALL BE 0.0076 (0.0003). 9 EXACT SHAPE OF EACH CORNER IS OPTIONAL. 0.200 (0.008) AB T–U Z A A1 24 –T– DETAIL Y 19 1 18 –U– V B V1 13 6 7 B1 12 –Z– S1 S 4X 0.200 (0.008) AB T–U Z DETAIL AD DIM A A1 B B1 C D E F G H J K M N P Q R S S1 V V1 W X MILLIMETERS MIN MAX 4.000 BSC 2.000 BSC 4.000 BSC 2.000 BSC 1.400 1.600 0.170 0.270 1.350 1.450 0.170 0.230 0.500 BSC 0.050 0.150 0.090 0.200 0.500 0.700 12 REF 0.090 0.160 0.250 BSC 1° 5° 0.150 0.250 6.000 BSC 3.000 BSC 6.000 BSC 3.000 BSC 0.200 REF 1.000 REF INCHES MIN MAX 0.157 BSC 0.079 BSC 0.157 BSC 0.079 BSC 0.055 0.063 0.007 0.011 0.053 0.057 0.007 0.009 0.020 BSC 0.002 0.006 0.004 0.008 0.020 0.028 12 REF 0.004 0.006 0.010 BSC 1° 5° 0.006 0.010 0.236 BSC 0.118 BSC 0.236 BSC 0.118 BSC 0.008 REF 0.039 REF –AB– –AC– 0.080 (0.003) AC M TOP & BOTTOM –T–, –U–, –Z– J R C E AE N AE F D 0.080 (0.003) W H K X DETAIL AD Page 18 of 20 Q GAUGE PLANE P 0.250 (0.010) S AC T–U S Z S SECTION AEAE G DETAIL Y www.lansdale.com Issue A LANSDALE Semiconductor, Inc. ML13150 OUTLINE DIMENSIONS ML13150-B9P PLASTIC PACKAGE CASE 873–01 (LQFP–32) ISSUE A L B 24 32 S D S S H A–B DETAIL A V M B -A-,-B-,-DDETAIL A J 9 1 F BASE METAL 0.20 (0.008) L S -B- -A- D 16 0.20 (0.008) M C A–B 0.05 (0.002) A–B 25 P B 17 N 8 D -D- 0.20 (0.008) M C A–B S D S A 0.20 (0.008) M C A–B 0.05 (0.002) A–B D S SECTION B-B S VIEW ROTATED 905 CLOCKWISE S 0.20 (0.008) M H A–B D S S C E -H- -CSEATING PLANE H M G U T R -HDATUM PLANE K X Q DATUM PLANE 0.01 (0.004) NOTES: 1. DIMENSIONING AND TOLERANCING PER ANSI Y14.5M, 1982. 2. CONTROLLING DIMENSION: MILLIMETER. 3. DATUM PLANE -H- IS LOCATED AT BOTTOM OF LEAD AND IS COINCIDENT WITH THE LEAD WHERE THE LEAD EXITS THE PLASTIC BODY AT THE BOTTOM OF THE PARTING LINE. 4. DATUMS -A-, -B- AND -D- TO BE DETERMINED AT DATUM PLANE -H-. 5. DIMENSIONS S AND V TO BE DETERMINED AT SEATING PLANE -C-. 6. DIMENSIONS A AND B DO NOT INCLUDE MOLD PROTRUSION. ALLOWABLE PROTRUSION IS 0.25 (0.010) PER SIDE. DIMENSIONS A AND B DO INCLUDE MOLD MISMATCH AND ARE DETERMINED AT DATUM PLANE -H-. 7. DIMENSION D DOES NOT INCLUDE DAMBAR PROTRUSION. ALLOWABLE DAMBAR PROTRUSION SHALL BE 0.08 (0.003) TOTAL IN EXCESS OF THE D DIMENSION AT MAXIMUM MATERIAL CONDITION. DAMBAR CANNOT BE LOCATED ON THE LOWER RADIUS OR THE FOOT. DETAIL C Page 19 of 20 DETAIL C M www.lansdale.com DIM A B C D E F G H J K L M N P Q R S T U V X MILLIMETERS MIN MAX 7.10 6.95 7.10 6.95 1.60 1.40 0.273 0.373 1.50 1.30 – 0.273 0.80 BSC 0.20 – 0.119 0.197 0.57 0.33 5.6 REF 8° 6° 0.119 0.135 0.40 BSC 5° 10° 0.15 0.25 8.85 9.15 0.15 0.25 5° 11° 8.85 9.15 1.0 REF INCHES MIN MAX 0.274 0.280 0.274 0.280 0.055 0.063 0.010 0.015 0.051 0.059 – 0.010 0.031 BSC 0.008 – 0.005 0.008 0.013 0.022 0.220 REF 8° 6° 0.005 0.005 0.016 BSC 10° 5° 0.006 0.010 0.348 0.360 0.006 0.010 5° 11° 0.348 0.360 0.039 REF Issue A LANSDALE Semiconductor, Inc. ML13150 Lansdale Semiconductor reserves the right to make changes without further notice to any products herein to improve reliability, function or design. Lansdale does not assume any liability arising out of the application or use of any product or circuit described herein; neither does it convey any license under its patent rights nor the rights of others. “Typical” parameters which may be provided in Lansdale data sheets and/or specifications can vary in different applications, and actual performance may vary over time. All operating parameters, including “Typicals” must be validated for each customer application by the customer’s technical experts. Lansdale Semiconductor is a registered trademark of Lansdale Semiconductor, Inc. Page 20 of 20 www.lansdale.com Issue A