LMP7711/LMP7712 Single and Dual Precision, 17 MHz, Low Noise, CMOS Input Amplifiers General Description Features The LMP7711/LMP7712 are single and dual low noise, low offset, CMOS input, rail-to-rail output precision amplifiers with a high gain bandwidth product and an enable pin. The LMP7711/LMP7712 are part of the LMP™ precision amplifier family and are ideal for a variety of instrumentation applications. Unless otherwise noted, typical values at VS = 5V. ± 150 µV (max) n Input offset voltage n Input bias current 100 fA n Input voltage noise 5.8 nV/ n Gain bandwidth product 17 MHz n Supply current (LMP7711) 1.15 mA n Supply current (LMP7712) 1.30 mA n Supply voltage range 1.8V to 5.5V n THD+N @ f = 1 kHz 0.001% n Operating temperature range −40oC to 125˚C n Rail-to-rail output swing n Space saving TSOT23 package (LMP7711) n MSOP-10 package (LMP7712) Utilizing a CMOS input stage, the LMP7711/LMP7712 achieve an input bias current of 100 fA, an input referred , and an input offset voltage of voltage noise of 5.8 nV/ less than ± 150 µV. These features make the LMP7711/ LMP7712 superior choices for precision applications. Consuming only 1.15 mA of supply current, the LMP7711 offers a high gain bandwidth product of 17 MHz, enabling accurate amplification at high closed loop gains. The LMP7711/LMP7712 have a supply voltage range of 1.8V to 5.5V, which makes these ideal choices for portable low power applications with low supply voltage requirements. In order to reduce the already low power consumption the LMP7711/LMP7712 have an enable function. Once in shutdown, the LMP7711/LMP7712 draw only 140 nA of supply current. The LMP7711/LMP7712 are built with National’s advanced VIP50 process technology. The LMP7711 is offered in a 6-pin TSOT23 package and the LMP7712 is offered in a 10-pin MSOP. Applications n Active filters and buffers n Sensor interface applications n Transimpedance amplifiers Typical Performance Offset Voltage Distribution Input Referred Voltage Noise 20150322 20150339 LMP™ is a trademark of National Semiconductor Corporation. © 2005 National Semiconductor Corporation DS201503 www.national.com LMP7711/LMP7712 Precision, 17 MHz, Low Noise, CMOS Input Amplifiers November 2005 LMP7711/LMP7712 Absolute Maximum Ratings (Note 1) Soldering Information If Military/Aerospace specified devices are required, please contact the National Semiconductor Sales Office/ Distributors for availability and specifications. Infrared or Convection (20 sec) 235˚C Wave Soldering Lead Temp. (10 sec) 260˚C ESD Tolerance (Note 2) Human Body Model 2000V Machine Model Operating Ratings (Note 1) 200V Temperature Range (Note 3) ± 0.3V VIN Differential Supply Voltage (VS = V+ – V−) Voltage on Input/Output Pins + Supply Voltage (VS = V – V ) 6.0V V+ +0.3V, V− −0.3V Storage Temperature Range −65˚C to 150˚C Junction Temperature (Note 3) −40˚C to 125˚C − 0˚C ≤ TA ≤ 125˚C 1.8V to 5.5V −40˚C ≤ TA ≤ 125˚C 2.0V to 5.5V Package Thermal Resistance (θJA(Note 3)) +150˚C 6-Pin TSOT23 170˚C/W 10-Pin MSOP 236˚C/W 2.5V Electrical Characteristics Unless otherwise specified, all limits are guaranteed for TA = 25˚C, V+ = 2.5V, V− = 0V ,VO = VCM = V+/2, VEN = V+. Boldface limits apply at the temperature extremes. Symbol Parameter VOS Input Offset Voltage TC VOS Input Offset Voltage Drift (Note 6) Conditions Min (Note 5) Typ (Note 4) Max (Note 5) ± 20 ± 180 ± 480 µV ±4 µV/˚C LMP7711 –1 LMP7712 –1.75 Units IB Input Bias Current VCM = 1V (Notes 7, 8) 0.05 50 100 pA IOS Input Offset Current VCM = 1V (Note 8) 0.006 25 50 pA CMRR Common Mode Rejection Ratio 0V ≤ VCM ≤ 1.4V 83 80 100 PSRR Power Supply Rejection Ratio 2.0V ≤ V+ ≤ 5.5V V− = 0V, VCM = 0 85 80 100 1.8V ≤ V+ ≤ 5.5V V− = 0V, VCM = 0 85 98 CMVR Input Common-Mode Voltage Range CMRR ≥ 80 dB CMRR ≥ 78 dB AVOL Large Signal Voltage Gain LMP7711, VO = 0.15 to 2.2V RL = 2 kΩ to V+/2 88 82 98 LMP7712, VO = 0.15 to 2.2V RL = 2 kΩ to V+/2 84 80 92 LMP7711, VO = 0.15 to 2.2V RL = 10 kΩ to V+/2 92 88 110 LMP7712, VO = 0.15 to 2.2V RL = 10 kΩ to V+/2 90 86 95 RL = 2 kΩ to V+/2 70 77 25 RL = 10 kΩ to V+/2 60 66 20 VO Output Swing High Output Swing Low www.national.com −0.3 –0.3 dB dB 1.5 1.5 dB mV from V+ RL = 2 kΩ to V+/2 30 70 73 RL = 10 kΩ to V+/2 15 60 62 2 V mV (Continued) Unless otherwise specified, all limits are guaranteed for TA = 25˚C, V+ = 2.5V, V− = 0V ,VO = VCM = V+/2, VEN = V+. Boldface limits apply at the temperature extremes. Symbol IO IS SR Parameter Output Short Circuit Current Supply Current Slew Rate GBW Gain Bandwidth Product en Input-Referred Voltage Noise Conditions Min (Note 5) Typ (Note 4) Sourcing to V− VIN = 200 mV (Note 9) 36 30 52 Sinking to V+ VIN = −200 mV (Note 9) 7.5 5.0 15 Max (Note 5) Units mA LMP7711 Enable Mode VEN ≥ 2.1 0.95 1.30 1.65 LMP7712 (per channel) Enable Mode VEN ≥ 2.1 1.10 1.50 1.85 Shutdown Mode (per channel) VEN ≤ 0.4 0.03 1 4 AV = +1, Rising (10% to 90%) 8.3 AV = +1, Falling (90% to 10%) 10.3 f = 400 Hz 6.8 f = 1 kHz 5.8 f = 1 kHz 0.01 mA µA V/µs 14 MHz nV/ in Input-Referred Current Noise ton Turn-on Time 140 ns toff Turn-off Time 1000 ns VEN Enable Pin Voltage Range Enable Mode 2.1 Shutdown Mode IEN THD+N Enable Pin Input Current Total Harmonic Distortion + Noise pA/ 2 - 2.5 0 - 0.5 VEN = 2.5V (Note 7) 0.4 1.5 3.0 VEN = 0V (Note 7) 0.003 0.1 f = 1 kHz, AV = 1, RL = 100 kΩ VO = 0.9 VPP 0.003 f = 1 kHz, AV = 1, RL = 600Ω VO = 0.9 VPP 0.004 V µA % 5V Electrical Characteristics Unless otherwise specified, all limits are guaranteed for TA = 25˚C, V+ = 5V, V− = 0V, VCM = V+/2, VEN = V+. Boldface limits apply at the temperature extremes. Symbol Parameter Conditions Min (Note 5) Typ (Note 4) Max (Note 5) Units ± 10 ± 150 ± 450 µV ±4 µV/˚C VOS Input Offset Voltage TC VOS Input Offset Average Drift (Note 6) LMP7711 –1 LMP7712 –1.75 IB Input Bias Current (Notes 7, 8) 0.1 50 100 pA IOS Input Offset Current (Note 8) 0.01 25 50 pA CMRR Common Mode Rejection Ratio 0V ≤ VCM ≤ 3.7V 85 82 100 PSRR Power Supply Rejection Ratio 2.0V ≤ V+ ≤ 5.5V V− = 0V, VCM = 0 85 80 100 1.8V ≤ V+ ≤ 5.5V V− = 0V, VCM = 0 85 98 CMVR Input Common-Mode Voltage Range CMRR ≥ 80 dB CMRR ≥ 78 dB −0.3 –0.3 3 dB dB 4 4 V www.national.com LMP7711/LMP7712 2.5V Electrical Characteristics LMP7711/LMP7712 5V Electrical Characteristics AVOL VO Large Signal Voltage Gain Output Swing High Output Swing Low IO IS SR Output Short Circuit Current Supply Current Slew Rate GBW Gain Bandwidth Product en Input-Referred Voltage Noise in Input-Referred Current Noise ton Turn-on Time toff Turn-off Time VEN Enable Pin Voltage Range (Continued) LMP7711, VO = 0.3 to 4.7V RL = 2 kΩ to V+/2 88 82 107 LMP7712, VO = 0.3 to 4.7V RL = 2 kΩ to V+/2 84 80 90 LMP7711, VO = 0.3 to 4.7V RL = 10 kΩ to V+/2 92 88 110 LMP7712, VO = 0.3 to 4.7V RL = 10 kΩ to V+/2 90 86 95 RL = 2 kΩ to V+/2 70 77 32 RL = 10 kΩ to V+/2 60 66 22 THD+N Enable Pin Input Current Total Harmonic Distortion + Noise www.national.com mV from V+ RL = 2 kΩ to V+/2 (LMP7711) 42 70 73 RL = 2 kΩ to V+/2 (LMP7712) 50 75 78 RL = 10 kΩ to V+/2 20 60 62 Sourcing to V− VIN = 200 mV (Note 9) 46 38 66 Sinking to V+ VIN = −200 mV (Note 9) 10.5 6.5 23 1.15 1.40 1.75 LMP7712 (per channel) Enable Mode VEN ≥ 4.6 1.30 1.70 2.05 Shutdown Mode VEN ≤ 0.4 (per channel) 0.14 1 4 AV = +1, Rising (10% to 90%) 6.0 9.5 AV = +1, Falling (90% to 10%) 7.5 11.5 7.0 f = 1 kHz 5.8 f = 1 kHz 0.01 Enable Mode 4.6 µA MHz nV/ pA/ 110 ns 800 ns 4.5 – 5 0 – 0.5 0.4 VEN = 5V (Note 7) 5.6 10 VEN = 0V (Note 7) 0.005 0.2 f = 1 kHz, AV = 1, RL = 100 kΩ VO = 4 VPP 0.001 f = 1 kHz, AV = 1, RL = 600Ω VO = 4 VPP 0.004 4 mA V/µs 17 f = 400 Hz mV mA LMP7711 Enable Mode VEN ≥ 4.6 Shutdown Mode IEN dB V µA % Note 2: Human Body Model is 1.5 kΩ in series with 100 pF. Machine Model is 0Ω in series with 200 pF. Note 3: The maximum power dissipation is a function of TJ(MAX), θJA. The maximum allowable power dissipation at any ambient temperature is PD = (TJ(MAX) - TA)/θJA. All numbers apply for packages soldered directly onto a PC Board. Note 4: Typical values represent the most likely parametric norm at the time of characterization. Note 5: Limits are 100% production tested at 25˚C. Limits over the operating temperature range are guaranteed through correlations using the Statistical Quality Control (SQC) method. Note 6: Offset voltage average drift is determined by dividing the change in VOS at the temperature extremes by the total temperature change. Note 7: Positive current corresponds to current flowing into the device. Note 8: Guaranteed by design. Note 9: The short circuit test is a momentary open loop test. Connection Diagrams 6-Pin TSOT23 10-Pin MSOP 20150301 Top View 20150302 Top View Ordering Information Package 6-Pin TSOT23 10-Pin MSOP Part Number LMP7711MK LMP7711MKX LMP7712MM LMP7712MMX Package Marking Transport Media 1k Units Tape and Reel AC3A 3k Units Tape and Reel 1k Units Tape and Reel AD3A 3.5k Units Tape and Reel 5 NSC Drawing MK06A MUB10A www.national.com LMP7711/LMP7712 Note 1: Absolute Maximum Ratings indicate limits beyond which damage to the device may occur. Operating Ratings indicate conditions for which the device is intended to be functional, but specific performance is not guaranteed. For guaranteed specifications and the test conditions, see the Electrical Characteristics Tables. LMP7711/LMP7712 Typical Performance Characteristics Unless otherwise noted: TA = 25˚C, VS = 5V, VCM = VS/2, VEN = V +. TCVOS Distribution (LMP7711) Offset Voltage Distribution 20150303 20150381 Offset Voltage Distribution TCVOS Distribution (LMP7712) 20150322 20150380 Offset Voltage vs. VCM Offset Voltage vs. VCM 20150310 www.national.com 20150311 6 = V+. (Continued) Offset Voltage vs. VCM Offset Voltage vs. Supply Voltage 20150321 20150312 Offset Voltage vs. Temperature CMRR vs. Frequency 20150356 20150309 Input Bias Current Over Temperature Input Bias Current Over Temperature 20150323 20150324 7 www.national.com LMP7711/LMP7712 Typical Performance Characteristics Unless otherwise noted: TA = 25˚C, VS = 5V, VCM = VS/2, VEN LMP7711/LMP7712 Typical Performance Characteristics Unless otherwise noted: TA = 25˚C, VS = 5V, VCM = VS/2, VEN = V+. (Continued) Supply Current vs. Supply Voltage (LMP7711) Supply Current vs. Supply Voltage (LMP7712) 20150305 20150377 Supply Current vs. Supply Voltage (Shutdown) Crosstalk Rejection Ratio (LMP7712) 20150376 20150306 Supply Current vs. Enable Pin Voltage (LMP7711) Supply Current vs. Enable Pin Voltage (LMP7711) 20150308 www.national.com 20150307 8 = V+. (Continued) Supply Current vs. Enable Pin Voltage (LMP7712) Supply Current vs. Enable Pin Voltage (LMP7712) 20150378 20150379 Sourcing Current vs. Supply Voltage Sinking Current vs. Supply Voltage 20150320 20150319 Sourcing Current vs. Output Voltage Sinking Current vs. Output Voltage 20150350 20150354 9 www.national.com LMP7711/LMP7712 Typical Performance Characteristics Unless otherwise noted: TA = 25˚C, VS = 5V, VCM = VS/2, VEN LMP7711/LMP7712 Typical Performance Characteristics Unless otherwise noted: TA = 25˚C, VS = 5V, VCM = VS/2, VEN = V+. (Continued) Output Swing High vs. Supply Voltage Output Swing Low vs. Supply Voltage 20150317 20150315 Output Swing High vs. Supply Voltage Output Swing Low vs. Supply Voltage 20150316 20150314 Output Swing High vs. Supply Voltage Output Swing Low vs. Supply Voltage 20150318 www.national.com 20150313 10 = V+. (Continued) Open Loop Frequency Response Open Loop Frequency Response 20150373 20150341 Phase Margin vs. Capacitive Load Phase Margin vs. Capacitive Load 20150345 20150346 Overshoot and Undershoot vs. Capacitive Load Slew Rate vs. Supply Voltage 20150330 20150329 11 www.national.com LMP7711/LMP7712 Typical Performance Characteristics Unless otherwise noted: TA = 25˚C, VS = 5V, VCM = VS/2, VEN LMP7711/LMP7712 Typical Performance Characteristics Unless otherwise noted: TA = 25˚C, VS = 5V, VCM = VS/2, VEN = V+. (Continued) Small Signal Step Response Large Signal Step Response 20150338 20150337 Small Signal Step Response Large Signal Step Response 20150334 20150333 THD+N vs. Output Voltage THD+N vs. Output Voltage 20150326 www.national.com 20150304 12 = V+. (Continued) THD+N vs. Frequency THD+N vs. Frequency 20150357 20150355 PSRR vs. Frequency Input Referred Voltage Noise vs. Frequency 20150339 20150328 Closed Loop Frequency Response Closed Loop Output Impedance vs. Frequency 20150332 20150336 13 www.national.com LMP7711/LMP7712 Typical Performance Characteristics Unless otherwise noted: TA = 25˚C, VS = 5V, VCM = VS/2, VEN LMP7711/LMP7712 Application Notes LMP7711/LMP7712 The LMP7711/LMP7712 are single and dual, low noise, low offset, rail-to-rail output precision amplifiers with a wide gain bandwidth product of 17 MHz and low supply current. The wide bandwidth makes the LMP7711/LMP7712 ideal choices for wide-band amplification in portable applications. The low supply current along with the enable feature that is built-in on the LMP7711/LMP7712 allows for even more power efficient designs by turning the device off when not in use. 20150361 FIGURE 1. Isolating Capacitive Load The LMP7711/LMP7712 are superior for sensor applications. The very low input referred voltage noise of only 5.8 at 1 kHz and very low input referred current noise nV/ mean more signal fidelity and higher of only 10 fA/ signal-to-noise ratio. INPUT CAPACITANCE CMOS input stages inherently have low input bias current and higher input referred voltage noise. The LMP7711/ LMP7712 enhance this performance by having the low input bias current of only 50 fA, as well as, a very low input referred voltage noise of 5.8 nV/ . In order to achieve this a larger input stage has been used. This larger input stage increases the input capacitance of the LMP7711/ LMP7712. Figure 2 shows typical input common mode input capacitance of the LMP7711/LMP7712. The LMP7711/LMP7712 have a supply voltage range of 1.8V to 5.5V over a wide temperature range of 0˚C to 125˚C. This is optimal for low voltage commercial applications. For applications where the ambient temperature might be less than 0˚C, the LMP7711/LMP7712 are fully operational at supply voltages of 2.0V to 5.5V over the temperature range of −40˚C to 125˚C. The outputs of the LMP7711/LMP7712 swing within 25 mV of either rail providing maximum dynamic range in applications requiring low supply voltage. The input common mode range of the LMP7711/LMP7712 extends to 300 mV below ground. This feature enables users to utilize this device in single supply applications. The use of a very innovative feedback topology has enhanced the current drive capability of the LMP7711/ LMP7712, resulting in sourcing currents as much as 47 mA with a supply voltage of only 1.8V. The LMP7711 is offered in the space saving TSOT23 package and the LMP7712 is offered in a 10-pin MSOP. These small packages are ideal solutions for applications requiring minimum PC board footprint. National Semiconductor is heavily committed to precision amplifiers and the market segments they serves. Technical support and extensive characterization data is available for sensitive applications or applications with a constrained error budget. 20150375 FIGURE 2. Input Common Mode Capacitance CAPACITIVE LOAD The unity gain follower is the most sensitive configuration to capacitive loading. The combination of a capacitive load placed directly on the output of an amplifier along with the output impedance of the amplifier creates a phase lag which in turn reduces the phase margin of the amplifier. If phase margin is significantly reduced, the response will be either underdamped or the amplifier will oscillate. The LMP7711/LMP7712 can directly drive capacitive loads of up to 120 pF without oscillating. To drive heavier capacitive loads, an isolation resistor, RISO in Figure 1, should be used. This resistor and CL form a pole and hence delay the phase lag or increase the phase margin of the overall system. The larger the value of RISO, the more stable the output voltage will be. However, larger values of RISO result in reduced output swing and reduced output current drive. www.national.com This input capacitance will interact with other impedances such as gain and feedback resistors, which are seen on the inputs of the amplifier to form a pole. This pole will have little or no effect on the output of the amplifier at low frequencies and under DC conditions, but will play a bigger role as the frequency increases. At higher frequencies, the presence of this pole will decrease phase margin and also causes gain peaking. In order to compensate for the input capacitance, care must be taken in choosing feedback resistors. In addition to being selective in picking values for the feedback resistor, a capacitor can be added to the feedback path to increase stability. The DC gain of the circuit shown in Figure 3 is simply −R2/R1. 14 As mentioned before, adding a capacitor to the feedback path will decrease the peaking. This is because CF will form yet another pole in the system and will prevent pairs of poles, or complex conjugates from forming. It is the presence of pairs of poles that cause the peaking of gain. Figure 5 shows the frequency response of the schematic presented in Figure 3 with different values of CF. As can be seen, using a small value capacitor significantly reduces or eliminates the peaking. (Continued) 20150364 FIGURE 3. Compensating for Input Capacitance For the time being, ignore CF. The AC gain of the circuit in Figure 3 can be calculated as follows: 20150360 FIGURE 5. Closed Loop Frequency Response (1) This equation is rearranged to find the location of the two poles: TRANSIMPEDANCE AMPLIFIER In many applications, the signal of interest is a very small amount of current that needs to be detected. Current that is transmitted through a photodiode is a good example. Barcode scanners, light meters, fiber optic receivers, and industrial sensors are some typical applications utilizing photodiodes for current detection. This current needs to be amplified before it can be further processed. This amplification is performed using a current-to-voltage converter configuration or transimpedance amplifier. The signal of interest is fed to the inverting input of an op amp with a feedback resistor in the current path. The voltage at the output of this amplifier will be equal to the negative of the input current times the value of the feedback resistor. Figure 6 shows a transimpedance amplifier configuration. CD represents the photodiode parasitic capacitance and CCM denotes the common-mode capacitance of the amplifier. The presence of all of these capacitances at higher frequencies might lead to less stable topologies at higher frequencies. Care must be taken when designing a transimpedance amplifier to prevent the circuit from oscillating. With a wide gain bandwidth product, low input bias current and low input voltage and current noise, the LMP7711/ LMP7712 are ideal for wideband transimpedance applications. (2) As shown in Equation (2), as the values of R1 and R2 are increased, the magnitude of the poles are reduced, which in turn decreases the bandwidth of the amplifier. Figure 4 shows the frequency response with different value resistors for R1 and R2. Whenever possible, it is best to chose smaller feedback resistors. 20150359 FIGURE 4. Closed Loop Frequency Response 15 www.national.com LMP7711/LMP7712 Application Notes LMP7711/LMP7712 Application Notes Thermopiles generate voltage in response to receiving radiation. These voltages are often only a few microvolts. As a result, the operational amplifier used for this application needs to have low offset voltage, low input voltage noise, and low input bias current. Figure 8 shows a thermopile application where the sensor detects radiation from a distance and generates a voltage that is proportional to the intensity of the radiation. The two resistors, RA and RB, are selected to provide high gain to amplify this signal, while CF removes the high frequency noise. (Continued) 20150369 FIGURE 6. Transimpedance Amplifier 20150327 A feedback capacitance CF is usually added in parallel with RF to maintain circuit stability and to control the frequency response. To achieve a maximally flat, 2nd order response, RF and CF should be chosen by using Equation (3) FIGURE 8. Thermopile Sensor Interface PRECISION RECTIFIER Rectifiers are electrical circuits used for converting AC signals to DC signals. Figure 9 shows a full-wave precision rectifier. Each operational amplifier used in this circuit has a diode on its output. This means for the diodes to conduct, the output of the amplifier needs to be positive with respect to ground. If VIN is in its positive half cycle then only the output of the bottom amplifier will be positive. As a result, the diode on the output of the bottom amplifier will conduct and the signal will show at the output of the circuit. If VIN is in its negative half cycle then the output of the top amplifier will be positive, resulting in the diode on the output of the top amplifier conducting and, delivering the signal on the amplifier’s output to the circuits output. For R2/ R1 ≥ 2, the resistor values can be found by using the equation shown in Figure 9. If R2/ R1 = 1, then R3 should be left open, no resistor needed, and R4 should simply be shorted. (3) Calculating CF from Equation (3) can sometimes result in capacitor values which are less than 2 pF. This is especially the case for high speed applications. In these instances, its often more practical to use the circuit shown in Figure 7 in order to allow more sensible choices for CF. The new feedback capacitor, C'F, is (1+ RB/RA) CF. This relationship holds as long as RA << RF. 20150331 FIGURE 7. Modified Transimpedance Amplifier SENSOR INTERFACE The LMP7711/LMP7712 have low input bias current and low input referred noise, which make them ideal choices for sensor interfaces such as thermopiles, Infra Red (IR) thermometry, thermocouple amplifiers, and pH electrode buffers. www.national.com 20150374 FIGURE 9. Precision Rectifier 16 LMP7711/LMP7712 Physical Dimensions inches (millimeters) unless otherwise noted 6-Pin TSOT23 NS Package Number MK06A 10-Pin MSOP NS Package Number MUB10A 17 www.national.com LMP7711/LMP7712 Precision, 17 MHz, Low Noise, CMOS Input Amplifiers Notes National does not assume any responsibility for use of any circuitry described, no circuit patent licenses are implied and National reserves the right at any time without notice to change said circuitry and specifications. For the most current product information visit us at www.national.com. LIFE SUPPORT POLICY NATIONAL’S PRODUCTS ARE NOT AUTHORIZED FOR USE AS CRITICAL COMPONENTS IN LIFE SUPPORT DEVICES OR SYSTEMS WITHOUT THE EXPRESS WRITTEN APPROVAL OF THE PRESIDENT AND GENERAL COUNSEL OF NATIONAL SEMICONDUCTOR CORPORATION. As used herein: 1. Life support devices or systems are devices or systems which, (a) are intended for surgical implant into the body, or (b) support or sustain life, and whose failure to perform when properly used in accordance with instructions for use provided in the labeling, can be reasonably expected to result in a significant injury to the user. 2. A critical component is any component of a life support device or system whose failure to perform can be reasonably expected to cause the failure of the life support device or system, or to affect its safety or effectiveness. BANNED SUBSTANCE COMPLIANCE National Semiconductor manufactures products and uses packing materials that meet the provisions of the Customer Products Stewardship Specification (CSP-9-111C2) and the Banned Substances and Materials of Interest Specification (CSP-9-111S2) and contain no ‘‘Banned Substances’’ as defined in CSP-9-111S2. Leadfree products are RoHS compliant. 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