MAXIM MAX1184

19-2174; Rev 0; 10/01
Dual 10-Bit, 20Msps, +3V, Low-Power ADC with
Internal Reference and Parallel Outputs
Applications
High Resolution Imaging
I/Q Channel Digitization
Multchannel IF Undersampling
Instrumentation
♦ Single +3V Operation
♦ Excellent Dynamic Performance:
59.5dB SNR at fIN = 7.5MHz
74dB SFDR at fIN = 7.5MHz
♦ Low Power:
35mA (Normal Operation)
2.8mA (Sleep Mode)
1µA (Shutdown Mode)
♦ 0.02dB Gain and 0.25° Phase Matching (typ)
♦ Wide ±1Vp-p Differential Analog Input
Voltage Range
♦ 400MHz -3dB Input Bandwidth
♦ On-Chip +2.048V Precision Bandgap Reference
♦ User-Selectable Output Format—Two’s
Complement or Offset Binary
♦ 48-Pin TQFP Package with Exposed Pad for
Improved Thermal Dissipation
♦ Evaluation Kit Available
Ordering Information
PART
TEMP. RANGE
MAX1184ECM
PIN-PACKAGE
-40°C to +85°C
48 TQFP-EP
37
38
39
40
41
42
43
44
45
46
47
REFN
REFP
REFIN
REFOUT
D9A
D8A
D7A
D6A
D5A
D4A
D3A
D2A
Pin Configuration
48
Pin-compatible higher speed versions of the MAX1184
are also available. Please refer to the MAX1180 data
sheet for 105Msps, the MAX1181 data sheet for
80Msps, the MAX1182 data sheet for 65Msps, and the
MAX1183 data sheet for 40Msps. In addition to these
speed grades, this family includes a 20Msps multiplexed output version (MAX1185), for which digital data
is presented time-interleaved on a single, parallel 10-bit
output port.
Features
COM
VDD
1
36
2
35
GND
INA+
INA-
3
34
4
33
5
32
VDD
GND
INBINB+
6
GND
VDD
CLK
31
MAX1184
7
30
8
29
9
28
10
27
11
26
12
25
D1A
D0A
OGND
OVDD
OVDD
OGND
D0B
D1B
D2B
D3B
D4B
D5B
24
23
22
21
20
19
18
17
15
16
GND
T/B
SLEEP
PD
OE
D9B
D8B
D7B
D6B
14
GND
VDD
VDD
13
Video Application
48 TQFP-EP
________________________________________________________________ Maxim Integrated Products
For pricing, delivery, and ordering information, please contact Maxim/Dallas Direct! at
1-888-629-4642, or visit Maxim’s website at www.maxim-ic.com.
1
MAX1184
General Description
The MAX1184 is a +3V, dual 10-bit analog-to-digital
converter (ADC) featuring fully-differential wideband
track-and-hold (T/H) inputs, driving two pipelined, 9stage ADCs. The MAX1184 is optimized for low-power,
high-dynamic performance applications in imaging,
instrumentation, and digital communication applications. This ADC operates from a single +2.7V to +3.6V
supply, consuming only 105mW while delivering a typical signal-to-noise ratio (SNR) of 59.5dB at an input frequency of 7.5MHz and a sampling rate of 20Msps. The
T/H driven input stages incorporate 400MHz (-3dB)
input amplifiers. The converters may also be operated
with single-ended inputs. In addition to low operating
power, the MAX1184 features a 2.8mA sleep mode as
well as a 1µA power-down mode to conserve power
during idle periods.
An internal +2.048V precision bandgap reference sets
the full-scale range of the ADC. A flexible reference
structure allows the use of the internal or an externally
derived reference, if desired for applications requiring
increased accuracy or a different input voltage range.
The MAX1184 features parallel, CMOS-compatible
three-state outputs. The digital output format is set to
two’s complement or straight offset binary through a
single control pin. The device provides for a separate
output power supply of +1.7V to +3.6V for flexible interfacing. The MAX1184 is available in a 7mm x 7mm, 48pin TQFP package, and is specified for the extended
industrial (-40°C to +85°C) temperature range.
MAX1184
Dual 10-Bit, 20Msps, +3V, Low-Power ADC with
Internal Reference and Parallel Outputs
ABSOLUTE MAXIMUM RATINGS
VDD, OVDD to GND...............................................-0.3V to +3.6V
OGND to GND.......................................................-0.3V to +0.3V
INA+, INA-, INB+, INB- to GND ...............................-0.3V to VDD
REFIN, REFOUT, REFP, REFN, CLK,
COM to GND ..........................................-0.3V to (VDD + 0.3V)
OE, PD, SLEEP, T/B, D9A–D0A,
D9B–D0B to OGND .............................-0.3V to (OVDD + 0.3V)
Continuous Power Dissipation (TA = +70°C)
48-Pin TQFP (derate 12.5mW/°C above +70°C).......1000mW
Operating Temperature Range ...........................-40°C to +85°C
Junction Temperature ......................................................+150°C
Storage Temperature Range .............................-60°C to +150°C
Lead Temperature (soldering, 10s) .................................+300°C
Stresses beyond those listed under “Absolute Maximum Ratings” may cause permanent damage to the device. These are stress ratings only, and functional
operation of the device at these or any other conditions beyond those indicated in the operational sections of the specifications is not implied. Exposure to
absolute maximum rating conditions for extended periods may affect device reliability.
ELECTRICAL CHARACTERISTICS
(VDD = +3V, OVDD = +2.5V, 0.1µF and 1.0µF capacitors from REFP, REFN, and COM to GND; REFOUT connected to REFIN through
a 10kΩ resistor, VIN = 2Vp-p (differential w.r.t. COM), CL = 10pF at digital outputs (Note 5), fCLK = 20MHz, TA = TMIN to TMAX, unless
otherwise noted. Typical values are at TA = +25°C.)
PARAMETER
SYMBOL
CONDITIONS
MIN
TYP
MAX
UNITS
DC ACCURACY
Resolution
10
Bits
Integral Nonlinearity
INL
fIN = 7.5MHz
±0.5
±1.5
Differential Nonlinearity
DNL
fIN = 7.5MHz, no missing codes guaranteed
±0.25
±1.0
LSB
Offset Error
< ±1
±1.7
% FS
Gain Error
0
±2
% FS
LSB
ANALOG INPUT
Differential Input Voltage
Range
VDIFF
Common-Mode Input Voltage
Range
VCM
Input Resistance
RIN
Input Capacitance
CIN
Differential or single-ended inputs
Switched capacitor load
±1.0
V
VDD/2
± 0.5
V
100
kΩ
5
pF
5
Clock
Cycles
CONVERSION RATE
Maximum Clock Frequency
fCLK
20
Data Latency
MHz
DYNAMIC CHARACTERISTICS (fCLK = 20MHz, 4096-point FFT)
Signal-to-Noise Ratio
SNR
Signal-to-Noise and Distortion
SINAD
Spurious-Free Dynamic Range
SFDR
2
fINA or B = 7.5MHz, TA = +25°C
57.3
fINA or B = 12MHz
fINA or B = 7.5MHz, TA = +25°C
57
fINA or B = 12MHz
fINA or B = 7.5MHz, TA = +25°C
fINA or B = 12MHz
59.5
59.4
59.4
59.2
64
74
72
_______________________________________________________________________________________
dB
dB
dBc
Dual 10-Bit, 20Msps, +3V, Low-Power ADC with
Internal Reference and Parallel Outputs
(VDD = +3V, OVDD = +2.5V, 0.1µF and 1.0µF capacitors from REFP, REFN, and COM to GND; REFOUT connected to REFIN through
a 10kΩ resistor, VIN = 2Vp-p (differential w.r.t. COM), CL = 10pF at digital outputs (Note 5), fCLK = 20MHz, TA = TMIN to TMAX, unless
otherwise noted. Typical values are at TA = +25°C.)
PARAMETER
SYMBOL
Third-Harmonic Distortion
HD3
Intermodulation Distortion
IMD
Total Harmonic Distortion
(first 4 harmonics)
THD
Small-Signal Bandwidth
Full-Power Bandwidth
FPBW
CONDITIONS
MIN
TYP
fINA or B = 7.5MHz
-74
fINA or B = 12MHz
-72
fINA or B = 11.985MHz at -6.5dB FS
MAX
dBc
-76
fINA or B = 12.893MHz at -6.5dB FS (Note 2)
UNITS
dBc
fINA or B = 7.5MHz, TA = +25°C
-72
fINA or B = 12MHz
-71
-64
Input at -20dB FS, differential inputs
500
MHz
Input at -0.5dB FS, differential inputs
400
MHz
dBc
Aperture Delay
tAD
1
ns
Aperture Jitter
tAJ
2
psRMS
2
ns
For 1.5 ✕ full-scale input
Overdrive Recovery Time
±1
%
±0.25
degrees
0.2
LSBRMS
REFOUT
2.048
±3%
V
TCREF
60
ppm/°C
1.25
mV/mA
Differential Gain
Differential Phase
Output Noise
INA+ = INA- = INB+ = INB- = COM
INTERNAL REFERENCE
Reference Output Voltage
Reference Temperature
Coefficient
Load Regulation
BUFFERED EXTERNAL REFERENCE (VREFIN = +2.048V)
REFIN Input Voltage
VREFIN
2.048
V
Positive Reference Output
Voltage
VREFP
2.012
V
Negative Reference Output
Voltage
VREFN
0.988
V
Differential Reference Output
Voltage Range
∆VREF
REFIN Resistance
RREFIN
∆VREF = VREFP - VREFN
0.98
1.024
>50
1.07
V
MΩ
_______________________________________________________________________________________
3
MAX1184
ELECTRICAL CHARACTERISTICS (continued)
MAX1184
Dual 10-Bit, 20Msps, +3V, Low-Power ADC with
Internal Reference and Parallel Outputs
ELECTRICAL CHARACTERISTICS (continued)
(VDD = +3V, OVDD = +2.5V, 0.1µF and 1.0µF capacitors from REFP, REFN, and COM to GND; REFOUT connected to REFIN through
a 10kΩ resistor, VIN = 2Vp-p (differential w.r.t. COM), CL = 10pF at digital outputs (Note 5), fCLK = 20MHz, TA = TMIN to TMAX, unless
otherwise noted. Typical values are at TA = +25°C.)
PARAMETER
Maximum REFP, COM Source
Current
Maximum REFP, COM Sink
Current
Maximum REFN Source Current
Maximum REFN Sink Current
SYMBOL
CONDITIONS
MIN
TYP
MAX
UNITS
ISOURCE
5
mA
ISINK
-250
µA
ISOURCE
250
µA
ISINK
-5
mA
UNBUFFERED EXTERNAL REFERENCE (VREFIN = AGND, reference voltage applied to REFP, REFN, and COM)
REFP, REFN Input Resistance
RREFP,
RREFN
Measured between REFP and COM, and
REFN and COM
Differential Reference Input
Voltage
∆VREF
∆VREF = VREFP - VREFN
COM Input Voltage
4
kΩ
1.024
±10%
V
VCOM
VDD/2 ±
10%
V
REFP Input Voltage
VREFP
VCOM +
∆VREF /2
V
REFN Input Voltage
VREFN
VCOM ∆VREF /2
V
DIGITAL INPUTS (CLK, PD, OE, SLEEP, T/B)
Input High Threshold
VIH
Input Low Threshold
VIL
Input Hysteresis
Input Leakage
Input Capacitance
CLK
0.8 ✕ VDD
PD, OE, SLEEP, T/B
0.8 ✕ OVDD
V
0.2 ✕ VDD
CLK
PD, OE, SLEEP, T/B
0.2 ✕ OVDD
VHYST
0.1
V
IIH
VIH = OVDD or VDD (CLK)
±5
IIL
VIL = 0
±5
CIN
V
5
µA
pF
DIGITAL OUTPUTS (D9A–D0A, D9B–D0B)
Output Voltage Low
VOL
ISINK = 200µA
Output Voltage High
VOH
ISOURCE = 200µA
Three-State Leakage Current
ILEAK
OE = OVDD
Three-State Output Capacitance
COUT
OE = OVDD
4
0.2
OVDD - 0.2
V
V
±10
5
_______________________________________________________________________________________
µA
pF
Dual 10-Bit, 20Msps, +3V, Low-Power ADC with
Internal Reference and Parallel Outputs
(VDD = +3V, OVDD = +2.5V, 0.1µF and 1.0µF capacitors from REFP, REFN, and COM to GND; REFOUT connected to REFIN through
a 10kΩ resistor, VIN = 2Vp-p (differential w.r.t. COM), CL = 10pF at digital outputs (Note 5), fCLK = 20MHz, TA = TMIN to TMAX, unless
otherwise noted. Typical values are at TA = +25°C.)
PARAMETER
SYMBOL
CONDITIONS
MIN
TYP
MAX
UNITS
POWER REQUIREMENTS
Analog Supply Voltage Range
VDD
2.7
3.0
3.6
V
Output Supply Voltage Range
OVDD
1.7
2.5
3.6
V
Operating, fINA or B = 7.5MHz at -0.5dB FS
35
50
Sleep mode
2.8
Analog Supply Current
IVDD
Shutdown, clock idle, PD = OE = OVDD
Output Supply Current
IOVDD
Operating, CL = 15pF, fINA or B = 7.5MHz at
-0.5dB FS
3.8
Sleep mode
100
Shutdown, clock idle, PD = OE = OVDD
Power Dissipation
PDISS
PSRR
15
10
Operating, fINA or B = 7.5MHz at -0.5dB FS
105
150
Sleep mode
8.4
3
µA
mA
2
Shutdown, clock idle, PD = OE = OVDD
Power-Supply Rejection Ratio
1
mA
45
µA
mW
µW
Offset
±0.2
mV/V
Gain
±0.1
%/V
TIMING CHARACTERISTICS
CLK Rise to Output Data Valid
tDO
Figure 3 (Note 3)
5
8
ns
Output Enable Time
tENABLE
Figure 4
10
Output Disable Time
tDISABLE
Figure 4
1.5
ns
ns
CLK Pulse Width High
tCH
Figure 3, clock period: 50ns
25 ± 7.5
ns
CLK Pulse Width Low
tCL
Figure 3, clock period: 50ns
25 ± 7.5
ns
Wake-Up Time
tWAKE
Wakeup from sleep mode (Note 4)
0.51
Wakeup from shutdown (Note 4)
1.5
µs
CHANNEL-TO-CHANNEL MATCHING
Crosstalk
fINA or B = 7.5MHz at -0.5dB FS
-70
Gain Matching
fINA or B = 7.5MHz at -0.5dB FS
0.02
Phase Matching
fINA or B = 7.5MHz at -0.5dB FS
0.25
dB
±0.2
dB
degrees
Note 1: SNR, SINAD, THD, SFDR, and HD3 are based on an analog input voltage of -0.5dB FS referenced to a +1.024V full-scale
input voltage range.
Note 2: Intermodulation distortion is the total power of the intermodulation products relative to the individual carrier. This number is
6dB or better, if referenced to the two-tone envelope.
Note 3: Digital outputs settle to VIH, VIL. Parameter guaranteed by design.
Note 4: With REFIN driven externally, REFP, COM, and REFN are left floating while powered down.
Note 5: Equivalent dynamic performance is obtainable over full OVDD range with reduced CL.
_______________________________________________________________________________________
5
MAX1184
ELECTRICAL CHARACTERISTICS (continued)
Typical Operating Characteristics
(VDD = +3V, OVDD = +2.5V, VREFIN = +2.048V, differential input at -0.5dB FS, fCLK = 20MHz, CL ≈ 10pF, TA = +25°C, unless otherwise
noted.)
-40
-50
HD3
-70
-30
-40
-50
-60
HD3
-70
HD2
CHB
0
-20
HD2
-40
-50
-60
-90
-90
-90
-100
-100
2
3
4
5
6
7
8
9
10
0
1
2
3
4
5
6
7
8
9
0
10
2
3
4
5
6
7
8
ANALOG INPUT FREQUENCY (MHz)
FFT PLOT CHB (DIFFERENTIAL INPUT,
8192-POINT DATA RECORD)
TWO-TONE IMD PLOT DIFFERENTIAL
INPUT, 8192-POINT DATA RECORD
SIGNAL-TO-NOISE RATIO vs.
ANALOG INPUT FREQUENCY
HD3
HD2
-70
-30
-40
fIN1
MAX1184 toc05
-20
fIN2
-50
-60
-80
-90
-90
CHB
60
1
2
3
4
5
6
7
8
9
IMD3
IMD2
57
56
0
10
CHA
59
58
-100
-100
10
IMD3
-70
-80
9
61
SNR (dB)
-50
fCLK = 20.0005678MHz
fIN1 = 11.9852035MHz
fIN2 = 12.8934324MHz
AIN = -6.5dB FS
TWO-TONE ENVELOPE =
-0.498dB FS
-10
AMPLITUDE (dB)
-40
-60
0
MAX1184 toc04
CHB
-30
2
4
6
8
10 12 14 16 18 20
1
10
100
ANALOG INPUT FREQUENCY (MHz)
ANALOG INPUT FREQUENCY (MHz)
SIGNAL-TO-NOISE + DISTORTION vs.
ANALOG INPUT FREQUECNY
TOTAL HARMONIC DISTORTION vs.
ANALOG INPUT FREQUENCY
SPURIOUS-FREE DYNAMIC RANGE vs.
ANALOG INPUT FREQUENCY
CHB
60
-63
80
MAX1184 toc08
61
-65
CHA
76
MAX1184 toc09
ANALOG INPUT FREQUENCY (MHz)
MAX1184 toc07
0
1
ANALOG INPUT FREQUENCY (MHz)
fCLK = 20.0005678MHz
fINA = 7.5343935MHz
fINB = 11.9852035MHz
AINB = -0.471dB FS
-20
HD2
ANALOG INPUT FREQUENCY (MHz)
0
-10
HD3
-80
-100
1
CHA
-30
-70
-80
0
fCLK = 20.0005678MHz
fINA = 7.5343935MHz
fINB = 11.9852035MHz
AINA = -0.489dB FS
-10
MAX1184 toc03
-20
-80
AMPLITUDE (dB)
fCLK = 20.0005678MHz
fINA = 5.9742906MHz
fINB = 7.5243935MHz
AINB = -0.462dB FS
MAX1184 toc06
-30
-60
0
-10
AMPLITUDE (dB)
AMPLITUDE (dB)
-20
CHA
AMPLITUDE (dB)
fCLK = 20.0005678MHz
fINA = 5.9742906MHz
fINB = 7.5343935MHz
AINA = -0.525dB FS
MAX1184 toc01
0
-10
FFT PLOT CHA (DIFFERENTIAL INPUT,
8192-POINT DATA RECORD)
FFT PLOT CHB (DIFFERENTIAL INPUT,
8192-POINT DATA RECORD)
MAX1184 toc02
FFT PLOT CHA (DIFFERENTIAL INPUT,
8192-POINT DATA RECORD)
CHA
58
SFDR (dBc)
59
THD (dBc)
-67
SINAD (dB)
MAX1184
Dual 10-Bit, 20Msps, +3V, Low-Power ADC with
Internal Reference and Parallel Outputs
CHB
-69
-71
72
68
CHB
CHA
-73
64
57
-75
1
10
ANALOG INPUT FREQUENCY (MHz)
6
60
-77
56
100
1
10
ANALOG INPUT FREQUENCY (MHz)
100
1
10
ANALOG INPUT FREQUENCY (MHz)
_______________________________________________________________________________________
100
Dual 10-Bit, 20Msps, +3V, Low-Power ADC with
Internal Reference and Parallel Outputs
6
4
VIN = 100mVP-P
4
-2
55
SNR (dB)
0
0
-2
-4
-4
-6
-6
-8
10
100
1000
40
35
1
10
100
1000
-20
-16
-12
-8
-4
0
ANALOG INPUT FREQUENCY (MHz)
ANALOG INPUT FREQUENCY (MHz)
INPUT POWER (dB FS)
SIGNAL-TO-NOISE + DISTORTION vs.
INPUT POWER (fIN = 7.5343935MHz)
TOTAL HARMONIC DISTORTION vs.
INPUT POWER (fIN = 7.5343935MHz)
SPURIOUS-FREE DYNAMIC RANGE vs.
INPUT POWER (fIN = 7.5343935MHz)
-62
MAX1184 toc15
60
100
MAX1184 toc14
-58
MAX1184 toc13
65
90
80
50
SFDR (dBc)
THD (dBc)
55
-66
-70
70
60
45
-74
40
50
40
-78
35
-16
-12
-8
-4
-20
0
INTEGRAL NONLINEARITY
(BEST END-POINT FIT)
-8
-4
0
-0.1
-0.1
-0.2
-0.2
-0.3
-0.3
128 256 384 512 640 768 896 1024
-8
-4
0
0.6
0.5
GAIN ERROR (%FS)
DNL (LSB)
0
-12
GAIN ERROR vs. TEMPERATURE
0.1
DIGITAL OUTPUT CODE
-16
INPUT POWER (dB FS)
MAX1184 toc17
0.2
0.1
0
-20
0
DIFFERENTIAL NONLINEARITY
0.3
MAX1184 toc16
0.2
-12
INPUT POWER (dB FS)
INPUT POWER (dB FS)
0.3
-16
MAX1184 toc18
-20
INL (LSB)
50
45
-8
1
SINAD (dB)
60
2
GAIN (dB)
GAIN (dB)
2
65
MAX1184 toc12
6
SIGNAL-TO-NOISE RATIO vs.
INPUT POWER (fIN = 7.5343935MHz)
MAX1184 toc11
SMALL-SIGNAL INPUT BANDWIDTH vs.
ANALOG INPUT FREQUENCY, SINGLE-ENDED
MAX1184 toc10
FULL-POWER INPUT BANDWIDTH vs.
ANALOG INPUT FREQUENCY, SINGLE-ENDED
0.4
0.3
CHB
0.2
0.1
0
CHA
-0.1
0
128 256 384 512 640 768 896 1024
DIGITAL OUTPUT CODE
-40
-15
10
35
60
85
TEMPERATURE (°C)
_______________________________________________________________________________________
7
MAX1184
Typical Operating Characteristics (continued)
(VDD = +3V, OVDD = +2.5V, VREFIN = +2.048V, differential input at -0.5dB FS, fCLK = 20MHz, CL ≈ 10pF, TA = +25°C, unless otherwise
noted.)
Typical Operating Characteristics (continued)
(VDD = +3V, OVDD = +2.5V, VREFIN = +2.048V, differential input at -0.5dB FS, fCLK = 20MHz, CL ≈ 10pF, TA = +25°C, unless otherwise
noted.)
ANALOG SUPPLY CURRENT vs.
ANALOG SUPPLY VOLTAGE
OFFSET ERROR vs. TEMPERATURE
MAX1184 toc20
35
IVDD (mA)
0
OFFSET ERROR (%FS)
36
MAX1184 toc19
0.1
-0.1
CHB
-0.2
34
33
32
-0.3
CHA
31
-0.4
-15
-40
10
35
60
3.00
3.15
3.30
3.45
VDD (V)
ANALOG SUPPLY CURRENT vs.
TEMPERATURE
ANALOG POWER-DOWN CURRENT
vs. ANALOG POWER SUPPLY
OE = PD = OVDD
0.16
IVDD (µA)
34
3.60
MAX1184 toc22
MAX1184 toc21
0.20
0.12
32
0.08
30
0.04
0
28
-40
-15
10
35
60
2.70
85
2.85
3.00
3.15
3.30
3.45
TEMPERATURE (°C)
VDD (V)
SFDR, SNR, THD, SINAD vs.
CLOCK DUTY CYCLE
INTERNAL REFERENCE VOLTAGE
vs. ANALOG SUPPLY VOLTAGE
74
SNR
62
56
2.0080
VREFOUT (V)
THD
68
2.0090
3.60
MAX1184 toc24
fIN = 7.5343935MHz
SFDR
MAX1184 toc23
80
2.0070
2.0060
2.0050
SINAD
50
2.0040
30
35
40
45
50
55
60
CLOCK DUTY CYCLE (%)
8
2.85
TEMPERATURE (°C)
36
IVDD (mA)
2.70
85
38
SFDR, SNR, THD, SINAD (dB)
MAX1184
Dual 10-Bit, 20Msps, +3V, Low-Power ADC with
Internal Reference and Parallel Outputs
65
70
2.70
2.85
3.00
3.15
3.30
VDD (V)
_______________________________________________________________________________________
3.45
3.60
Dual 10-Bit, 20Msps, +3V, Low-Power ADC with
Internal Reference and Parallel Outputs
INTERNAL REFERENCE VOLTAGE
vs. TEMPERATURE
MAX1184 toc25
70,000
2.010
MAX1184 toc26
OUTPUT NOISE HISTOGRAM (DC INPUT)
2.015
64,515
63,000
56,000
COUNTS
VREOUT (V)
49,000
2.005
2.000
42,000
35,000
28,000
21,000
1.995
14,000
7,000
1.990
-40
-15
10
35
60
85
TEMPERATURE (°C)
0
0
869
N-2
N-1
N
152
0
N+1
N+2
DIGITAL OUTPUT CODE
Pin Description
PIN
NAME
1
COM
Common-Mode Voltage Input/Output. Bypass to GND with a ≥0.1µF capacitor.
VDD
Analog Supply Voltage. Bypass to GND with a capacitor combination of 2.2µF in parallel with
0.1µF.
3, 7, 10, 13, 16
GND
Analog Ground
4
INA+
Channel A Positive Analog Input. For single-ended operation, connect signal source to INA+.
5
INA-
Channel A Negative Analog Input. For single-ended operation, connect INA- to COM.
8
INB-
Channel B Negative Analog Input. For single-ended operation, connect INB- to COM.
9
INB+
Channel B Positive Analog Input. For single-ended operation, connect signal source to INB+.
12
CLK
Converter Clock Input
17
T/B
T/B selects the ADC digital output format.
High: Two’s complement.
Low: Straight offset binary.
18
SLEEP
19
PD
Power-Down Input.
High: Power-down mode
Low: Normal operation
20
OE
Output Enable Input.
High: Digital outputs disabled
Low: Digital outputs enabled
2, 6, 11, 14, 15
FUNCTION
Sleep Mode Input.
High: Deactivates the two ADCs, but leaves the reference bias circuit active.
Low: Normal operation.
_______________________________________________________________________________________
9
MAX1184
Typical Operating Characteristics (continued)
(VDD = +3V, OVDD = +2.5V, VREFIN = +2.048V, differential input at -0.5dB FS, fCLK = 20MHz, CL ≈ 10pF, TA = +25°C, unless otherwise
noted.)
Dual 10-Bit, 20Msps, +3V, Low-Power ADC with
Internal Reference and Parallel Outputs
MAX1184
Pin Description (continued)
10
PIN
NAME
21
D9B
Three-State Digital Output, Bit 9 (MSB), Channel B
FUNCTION
22
D8B
Three-State Digital Output, Bit 8, Channel B
23
D7B
Three-State Digital Output, Bit 7, Channel B
24
D6B
Three-State Digital Output, Bit 6, Channel B
25
D5B
Three-State Digital Output, Bit 5, Channel B
26
D4B
Three-State Digital Output, Bit 4, Channel B
27
D3B
Three-State Digital Output, Bit 3, Channel B
28
D2B
Three-State Digital Output, Bit 2, Channel B
29
D1B
Three-State Digital Output, Bit 1, Channel B
30
D0B
Three-State Digital Output, Bit 0 (LSB), Channel B
31, 34
OGND
Output Driver Ground
32, 33
OVDD
Output Driver Supply Voltage. Bypass to OGND with a capacitor combination of 2.2µF in
parallel with 0.1µF.
35
D0A
Three-State Digital Output, Bit 0 (LSB), Channel A
36
D1A
Three-State Digital Output, Bit 1, Channel A
37
D2A
Three-State Digital Output, Bit 2, Channel A
38
D3A
Three-State Digital Output, Bit 3, Channel A
39
D4A
Three-State Digital Output, Bit 4, Channel A
40
D5A
Three-State Digital Output, Bit 5, Channel A
41
D6A
Three-State Digital Output, Bit 6, Channel A
42
D7A
Three-State Digital Output, Bit 7, Channel A
43
D8A
Three-State Digital Output, Bit 8, Channel A
44
D9A
Three-State Digital Output, Bit 9 (MSB), Channel A
Internal Reference Voltage Output. May be connected to REFIN through a resistor or a resistor
divider.
45
REFOUT
46
REFIN
Reference Input. VREFIN = 2 ✕ (VREFP - VREFN). Bypass to GND with a >1nF capacitor.
47
REFP
Positive Reference Input/Output. Conversion range is ± (VREFP - VREFN). Bypass to GND with a
> 0.1µF capacitor.
48
REFN
Negative Reference Input/Output. Conversion range is ± (VREFP - VREFN). Bypass to GND with
a > 0.1µF capacitor.
______________________________________________________________________________________
Dual 10-Bit, 20Msps, +3V, Low-Power ADC with
Internal Reference and Parallel Outputs
The MAX1184 uses a 9-stage, fully-differential
pipelined architecture (Figure 1) that allows for highspeed conversion while minimizing power consumption. Samples taken at the inputs move progressively
through the pipeline stages every half clock cycle.
Counting the delay through the output latch, the clockcycle latency is five clock cycles.
1.5-bit (2-comparator) flash ADCs convert the heldinput voltages into a digital code. The digital-to-analog
converters (DACs) convert the digitized results back
into analog voltages, which are then subtracted from
the original held input signals. The resulting error signals are then multiplied by two and the residues are
passed along to the next pipeline stages, where the
process is repeated until the signals have been
processed by all nine stages. Digital error correction
compensates for ADC comparator offsets in each of
these pipeline stages and ensures no missing codes.
Input Track-and-Hold (T/H) Circuits
Figure 2 displays a simplified functional diagram of the
input track-and-hold (T/H) circuits in both track-and-
Σ
T/H
FLASH
ADC
x2
VIN
VOUT
Σ
T/H
FLASH
ADC
DAC
1.5 BITS
x2
VOUT
DAC
1.5 BITS
2-BIT FLASH
ADC
STAGE 1
STAGE 2
STAGE 8
2-BIT FLASH
ADC
STAGE 9
STAGE 1
DIGITAL CORRECTION LOGIC
T/H
VINB
10
D9B–D0B
STAGE 2
STAGE 8
STAGE 9
DIGITAL CORRECTION LOGIC
T/H
VINB
10
D9B–D0B
VINA = INPUT VOLTAGE BETWEEN INA+ AND INA- (DIFFERENTIAL OR SINGLE-ENDED)
VINB = INPUT VOLTAGE BETWEEN INB+ AND INB- (DIFFERENTIAL OR SINGLE-ENDED)
Figure 1. Pipelined Architecture—Stage Blocks
______________________________________________________________________________________
11
MAX1184
hold mode. In track mode, switches S1, S2a, S2b, S4a,
S4b, S5a, and S5b are closed. The fully differential circuits sample the input signals onto the two capacitors
(C2a and C2b) through switches S4a and S4b. S2a and
S2b set the common mode for the amplifier input, and
open simultaneously with S1, sampling the input waveform. Switches S4a and S4b are then opened before
switches S3a and S3b, connect capacitors C1a and
C1b to the output of the amplifier, and switch S4c is
closed. The resulting differential voltages are held on
capacitors C2a and C2b. The amplifiers are used to
charge capacitors C1a and C1b to the same values
originally held on C2a and C2b. These values are then
presented to the first-stage quantizers and isolate the
pipelines from the fast-changing inputs. The wide input
bandwidth T/H amplifiers allow the MAX1184 to trackand-sample/hold analog inputs of high frequencies (>
Nyquist). The ADC inputs (INA+, INB+, INA-, and INB-)
can be driven either differentially or single-ended.
Match the impedance of INA+ and INA-, as well as
INB+ and INB- and set the common-mode voltage to
midsupply (VDD/2) for optimum performance.
Detailed Description
MAX1184
Dual 10-Bit, 20Msps, +3V, Low-Power ADC with
Internal Reference and Parallel Outputs
INTERNAL
BIAS
COM
S5a
S2a
C1a
S3a
S4a
INA+
OUT
C2a
S4c
S1
OUT
INAS4b
C2b
C1b
S3b
S5b
S2b
INTERNAL
BIAS
COM
HOLD
INTERNAL
BIAS
TRACK
COM
CLK
HOLD
TRACK
INTERNAL
NONOVERLAPPING
CLOCK SIGNALS
S5a
S2a
C1a
S3a
S4a
INB+
OUT
C2a
S4c
S1
OUT
INBS4b
MAX1184
C2b
C1b
S3b
S2b
INTERNAL
BIAS
S5b
COM
Figure 2. MAX1184 T/H Amplifiers
12
______________________________________________________________________________________
Dual 10-Bit, 20Msps, +3V, Low-Power ADC with
Internal Reference and Parallel Outputs
ered as an analog input and routed away from any analog input or other digital signal lines.
The full-scale range of the MAX1184 is determined by the
internally generated voltage difference between REFP
(VDD/2 + VREFIN/4) and REFN (VDD/2 - VREFIN/4). The
full-scale range for both on-chip ADCs is adjustable
through the REFIN pin, which is provided for this purpose.
The MAX1184 clock input operates with a voltage threshold set to VDD/2. Clock inputs with a duty cycle other than
50%, must meet the specifications for high and low periods as stated in the Electrical Characteristics.
REFOUT, REFP, COM (VDD/2), and REFN are internally
buffered low-impedance outputs.
The MAX1184 provides three modes of reference operation:
• Internal reference mode
• Buffered external reference mode
• Unbuffered external reference mode
In internal reference mode, connect the internal reference output REFOUT to REFIN through a resistor (e.g.,
10kΩ) or resistor-divider, if an application requires a
reduced full-scale range. For stability and noise filtering
purposes, bypass REFIN with a >10nF capacitor to
GND. In internal reference mode, REFOUT, COM,
REFP, and REFN become low-impedance outputs.
In buffered external reference mode, adjust the reference voltage levels externally by applying a stable and
accurate voltage at REFIN. In this mode, COM, REFP,
and REFN become outputs. REFOUT may be left open
or connected to REFIN through a >10kΩ resistor.
In unbuffered external reference mode, connect REFIN
to GND. This deactivates the on-chip reference buffers
for REFP, COM, and REFN. With their buffers shut
down, these nodes become high impedance and may
be driven through separate external reference sources.
Clock Input (CLK)
The MAX1184’s CLK input accepts CMOS-compatible
clock signals. Since the interstage conversion of the
device depends on the repeatability of the rising and
falling edges of the external clock, use a clock with low
jitter and fast rise and fall times (< 2ns). In particular,
sampling occurs on the rising edge of the clock signal,
requiring this edge to provide lowest possible jitter. Any
significant aperture jitter would limit the SNR performance of the on-chip ADCs as follows:
SNRdB = 20 ✕ log10 (1 / [2π x fIN x tAJ]),
where fIN represents the analog input frequency and tAJ
is the time of the aperture jitter.
Clock jitter is especially critical for undersampling
applications. The clock input should always be consid-
System Timing Requirements
Figure 3 depicts the relationship between the clock
input, analog input, and data output. The MAX1184
samples at the rising edge of the input clock. Output
data for channels A and B is valid on the next rising
edge of the input clock. The output data has an internal
latency of five clock cycles. Figure 4 also determines
the relationship between the input clock parameters
and the valid output data on channels A and B.
Digital Output Data, Output Data Format
Selection (T/B), Output Enable (OE)
All digital outputs, D0A–D9A (Channel A) and D0B–D9B
(Channel B), are TTL/CMOS logic-compatible. There is
a 5-clock-cycle latency between any particular sample
and its corresponding output data. The output coding
can be chosen to be either straight offset binary or
two’s complement (Table 1) controlled by a single pin
(T/B). Pull T/B low to select offset binary and high to
activate two’s complement output coding. The capacitive load on the digital outputs D0A–D9A and D0B–D9B
should be kept as low as possible (<15pF), to avoid
large digital currents that could feed back into the analog portion of the MAX1184, thereby degrading its
dynamic performance. Using buffers on the digital outputs of the ADCs can further isolate the digital outputs
from heavy capacitive loads. To further improve the
dynamic performance of the MAX1184 small-series
resistors (e.g., 100Ω) may be added to the digital output paths close to the MAX1184.
Figure 4 displays the timing relationship between output enable and data output valid as well as powerdown/wake-up and data output valid.
Power-Down (PD) and
Sleep (SLEEP) Modes
The MAX1184 offers two power-save modes—sleep and
full power-down mode. In sleep mode (SLEEP = 1), only
the reference bias circuit is active (both ADCs are disabled), and current consumption is reduced to 2.8mA.
To enter full power-down mode, pull PD high. With OE
simultaneously low, all outputs are latched at the last
value prior to the power down. Pulling OE high forces
the digital outputs into a high-impedance state.
______________________________________________________________________________________
13
MAX1184
Analog Inputs and Reference
Configurations
MAX1184
Dual 10-Bit, 20Msps, +3V, Low-Power ADC with
Internal Reference and Parallel Outputs
5 CLOCK-CYCLE LATENCY
N
N+1
N+2
N+3
N+4
N+5
N+6
ANALOG INPUT
CLOCK INPUT
tDO
tCH
tCL
DATA OUTPUT
D9A–D0A
N-6
N-5
N-4
N-3
N-2
N-1
N
N+1
DATA OUTPUT
D9B–D0B
N-6
N-5
N-4
N-3
N-2
N-1
N
N+1
Figure 3. System Timing Diagram
amplifiers. The user may select the RISO and CIN values to optimize the filter performance, to suit a particular application. For the application in Figure 5, a RISO of
50Ω is placed before the capacitive load to prevent
ringing and oscillation. The 22pF CIN capacitor acts as
a small bypassing capacitor.
OE
tENABLE
OUTPUT
D9A–D0A
HIGH-Z
OUTPUT
D9B–D0B
HIGH-Z
tDISABLE
VALID DATA
VALID DATA
HIGH-Z
HIGH-Z
Figure 4. Output Timing Diagram
Applications Information
Figure 5 depicts a typical application circuit containing
two single-ended to differential converters. The internal
reference provides a V DD/2 output voltage for level
shifting purposes. The input is buffered and then split to
a voltage follower and inverter. One lowpass filter per
ADC suppresses some of the wideband noise associated with high-speed operational amplifiers follows the
14
Using Transformer Coupling
A RF transformer (Figure 6) provides an excellent solution to convert a single-ended source signal to a fully
differential signal, required by the MAX1184 for optimum performance. Connecting the center tap of the
transformer to COM provides a VDD/2 DC level shift to
the input. Although a 1:1 transformer is shown, a stepup transformer may be selected to reduce the drive
requirements. A reduced signal swing from the input
driver, such as an op amp, may also improve the overall distortion.
In general, the MAX1184 provides better SFDR and
THD with fully-differential input signals than singleended drive, especially for very high input frequencies.
In differential input mode, even-order harmonics are
lower as both inputs (INA+, INA- and/or INB+, INB-) are
balanced, and each of the ADC inputs only requires
______________________________________________________________________________________
Dual 10-Bit, 20Msps, +3V, Low-Power ADC with
Internal Reference and Parallel Outputs
MAX1184
Table 1. MAX1184 Output Codes For Differential Inputs
DIFFERENTIAL INPUT
VOLTAGE*
DIFFERENTIAL
INPUT
STRAIGHT OFFSET
BINARY
T/B = 0
TWO’S COMPLEMENT
T/B = 1
VREF x 511/512
+FULL SCALE - 1LSB
11 1111 1111
01 1111 1111
VREF x 1/512
+ 1 LSB
10 0000 0001
00 0000 0001
0
Bipolar Zero
10 0000 0000
00 0000 0000
- VREF x 1/512
- 1 LSB
01 1111 1111
11 1111 1111
-VREF x 511/512
- FULL SCALE + 1 LSB
00 0000 0001
10 0000 0001
- FULL SCALE
00 0000 0000
10 0000 0000
-VREF x 512/512
*VREF = VREFP - VREFN
half the signal swing compared to a single-ended
mode.
Grounding, Bypassing, and
Board Layout
Single-Ended AC-Coupled Input Signal
The MAX1184 requires high-speed board layout design
techniques. Locate all bypass capacitors as close to
the device as possible, preferably on the same side as
the ADC, using surface-mount devices for minimum
inductance. Bypass VDD, REFP, REFN, and COM with
two parallel 0.1µF ceramic capacitors and a 2.2µF
bipolar capacitor to GND. Follow the same rules to
bypass the digital supply (OVDD) to OGND. Multilayer
boards with separated ground and power planes produce the highest level of signal integrity. Consider the
use of a split ground plane arranged to match the physical location of the analog ground (GND) and the digital
output driver ground (OGND) on the ADCs package.
The two ground planes should be joined at a single
point such that the noisy digital ground currents do not
interfere with the analog ground plane. The ideal location of this connection can be determined experimentally at a point along the gap between the two ground
planes, which produces optimum results. Make this
connection with a low-value, surface-mount resistor (1Ω
to 5Ω), a ferrite bead, or a direct short. Alternatively, all
ground pins could share the same ground plane, if the
ground plane is sufficiently isolated from any noisy, digital systems ground plane (e.g., downstream output
buffer or DSP ground plane). Route high-speed digital
signal traces away from the sensitive analog traces of
either channel. Make sure to isolate the analog input
lines to each respective converter to minimize channelto-channel crosstalk. Keep all signal lines short and
free of 90 degree turns.
Figure 7 shows an AC-coupled, single-ended application. Amplifiers like the MAX4108 provide high-speed,
high-bandwidth, low noise, and low distortion to maintain the integrity of the input signal.
Typical QAM Demodulation Application
The most frequently used modulation technique for digital communications applications is probably the
Quadrature Amplitude Modulation (QAM). Typically
found in spread-spectrum based systems, a QAM signal represents a carrier frequency modulated in both
amplitude and phase. At the transmitter, modulating the
baseband signal with quadrature outputs, a local oscillator followed by subsequent up-conversion can generate the QAM signal. The result is an in-phase (I) and a
quadrature (Q) carrier component, where the Q component is 90 degree phase-shifted with respect to the inphase component. At the receiver, the QAM signal is
divided down into it’s I and Q components, essentially
representing the modulation process reversed. Figure 8
displays the demodulation process performed in the
analog domain, using the dual matched +3V, 10-bit
ADC (MAX1184), and the MAX2451 quadrature demodulator to recover and digitize the I and Q baseband signals. Before being digitized by the MAX1184, the mixed
down-signal components may be filtered by matched
analog filters, such as Nyquist or pulse-shaping filters
which remove any unwanted images from the mixing
process, thereby enhancing the overall signal-to-noise
(SNR) performance and minimizing intersymbol interference.
______________________________________________________________________________________
15
MAX1184
Dual 10-Bit, 20Msps, +3V, Low-Power ADC with
Internal Reference and Parallel Outputs
+5V
0.1µF
LOWPASS FILTER
INA+
MAX4108
RIS0
50Ω
0.1µF
300Ω
CIN
22pF
0.1µF
-5V
600Ω
600Ω
300Ω
COM
0.1µF
+5V
+5V
0.1µF
600Ω
INPUT
0.1µF
LOWPASS FILTER
MAX4108
300Ω
-5V
0.1µF
INA-
MAX4108
RIS0
50Ω
300Ω
CIN
22pF
0.1µF
-5V
300Ω
300Ω
+5V
600Ω
MAX1184
0.1µF
LOWPASS FILTER
INB+
MAX4108
RIS0
50Ω
0.1µF
300Ω
CIN
22pF
0.1µF
-5V
600Ω
600Ω
300Ω
0.1µF
+5V
+5V
0.1µF
600Ω
INPUT
0.1µF
LOWPASS FILTER
MAX4108
300Ω
-5V
0.1µF
INB-
MAX4108
RIS0
50Ω
300Ω
CIN
22pF
0.1µF
-5V
300Ω
300Ω
600Ω
Figure 5. Typical Application for Single-Ended to Differential Conversion
16
______________________________________________________________________________________
Dual 10-Bit, 20Msps, +3V, Low-Power ADC with
Internal Reference and Parallel Outputs
MAX1184
25Ω
INA+
22pF
0.1µF
1
VIN
N.C.
T1
6
5
2
3
4
COM
2.2µF
0.1µF
MINICIRCUITS
TT1–6
25Ω
INA22pF
MAX1184
25Ω
INB+
22pF
0.1µF
1
VIN
N.C.
T1
6
2
5
3
4
2.2µF
0.1µF
MINICIRCUITS
TT1–6
25Ω
INB22pF
Figure 6. Transformer-Coupled Input Drive
Static Parameter Definitions
Integral Nonlinearity (INL)
Integral nonlinearity is the deviation of the values on an
actual transfer function from a straight line. This straight
line can be either a best straight-line fit or a line drawn
between the endpoints of the transfer function, once
offset and gain errors have been nullified. The static linearity parameters for the MAX1184 are measured using
the best straight-line fit method.
Differential Nonlinearity (DNL)
Differential nonlinearity is the difference between an
actual step-width and the ideal value of 1LSB. A DNL
error specification of less than 1LSB guarantees no
missing codes and a monotonic transfer function.
Dynamic Parameter Definitions
Aperture Jitter
Figure 9 depicts the aperture jitter (tAJ), which is the
sample-to-sample variation in the aperture delay.
Aperture Delay
Aperture delay (tAD) is the time defined between the
falling edge of the sampling clock and the instant when
an actual sample is taken (Figure 9).
______________________________________________________________________________________
17
MAX1184
Dual 10-Bit, 20Msps, +3V, Low-Power ADC with
Internal Reference and Parallel Outputs
REFP
VIN
0.1µF
1kΩ RISO
50Ω
INA+
MAX4108
100Ω
CIN
22pF
1kΩ
COM
REFN
0.1µF
RISO
50Ω
INA-
100Ω
CIN
22pF
REFP
VIN
0.1µF
MAX1184
1kΩ RISO
50Ω
INB+
MAX4108
100Ω
CIN
22pF
1kΩ
REFN
0.1µF
RISO
50Ω
INB-
100Ω
CIN
22pF
Figure 7: Using an Op Amp for Single-Ended, AC-Coupled Input Drive
Signal-to-Noise Ratio (SNR)
Signal-to-Noise Plus Distortion (SINAD)
For a waveform perfectly reconstructed from digital
samples, the theoretical maximum SNR is the ratio of the
full-scale analog input (RMS value) to the RMS quantization error (residual error). The ideal, theoretical minimum
analog-to-digital noise is caused by quantization error
only and results directly from the ADC’s resolution
(N-Bits):
SNRdB[max] = 6.02dB x N + 1.76dB
SINAD is computed by taking the ratio of the RMS signal to all spectral components minus the fundamental
and the DC offset.
In reality, there are other noise sources besides quantization noise e.g. thermal noise, reference noise, clock
jitter, etc. SNR is computed by taking the ratio of the
RMS signal to the RMS noise, which includes all spectral components minus the fundamental, the first five
harmonics, and the DC offset.
18
Effective Number of Bits (ENOB)
ENOB specifies the dynamic performance of an ADC at
a specific input frequency and sampling rate. An ideal
ADC error consists of quantization noise only. ENOB is
computed from:
ENOB =
SINADdB − 1.76dB
6.02dB
______________________________________________________________________________________
Dual 10-Bit, 20Msps, +3V, Low-Power ADC with
Internal Reference and Parallel Outputs
MAX1184
MAX2451
INA+
INA0°
90°
MAX1184
DSP
POST
PROCESSING
INB+
INBDOWNCONVERTER
÷8
Figure 8. Typical QAM Application, Using the MAX1184
Total Harmonic Distortion (THD)
THD is typically the ratio of the RMS sum of the first four
harmonics of the input signal to the fundamental itself.
This is expressed as:
CLK


V2 2 + V3 2 + V4 2 + V5 2 
THD = 20 × log10 


V1


ANALOG
INPUT
tAD
tAJ
where V1 is the fundamental amplitude, and V2 through
V5 are the amplitudes of the 2nd- through 5th-order
harmonics.
SAMPLED
DATA (T/H)
T/H
TRACK
Figure 9. T/H Aperture Timing
HOLD
TRACK
Spurious-Free Dynamic Range (SFDR)
SFDR is the ratio expressed in decibels of the RMS
amplitude of the fundamental (maximum signal component) to the RMS value of the next largest spurious
component, excluding DC offset.
Intermodulation Distortion (IMD)
The two-tone IMD is the ratio expressed in decibels of
either input tone to the worst 3rd-order (or higher) intermodulation products. The individual input tone levels
are at -6.5dB full scale and their envelope is at -0.5dB
full scale.
Chip Information
TRANSISTOR COUNT: 10,811
PROCESS: CMOS
______________________________________________________________________________________
19
Dual 10-Bit, 20Msps, +3V, Low-Power ADC with
Internal Reference and Parallel Outputs
MAX1184
Functional Diagram
VDD
OGND
OVDD
GND
INA+
PIPELINE
ADC
T/H
10
DEC
OUTPUT
DRIVERS
10
D9A–D0A
INA-
CONTROL
CLK
OE
INB+
T/H
PIPELINE
ADC
10
DEC
OUTPUT
DRIVERS
10
D9B–D0B
INB-
REFERENCE
MAX1184
REFOUT
REFN COM REFP
20
REFIN
______________________________________________________________________________________
T/B
PD
SLEEP
Dual 10-Bit, 20Msps, +3V, Low-Power ADC with
Internal Reference and Parallel Outputs
48L,TQFP.EPS
Maxim cannot assume responsibility for use of any circuitry other than circuitry entirely embodied in a Maxim product. No circuit patent licenses are
implied. Maxim reserves the right to change the circuitry and specifications without notice at any time.
Maxim Integrated Products, 120 San Gabriel Drive, Sunnyvale, CA 94086 408-737-7600 ____________________ 21
© 2001 Maxim Integrated Products
Printed USA
is a registered trademark of Maxim Integrated Products.
MAX1184
Package Information