TPA2000D2 www.ti.com SLOS291F – MARCH 2000 – REVISED MARCH 2007 2-W FILTERLESS STEREO CLASS-D AUDIO POWER AMPLIFIER • FEATURES • • • • • Modulation Scheme Optimized to Operate Without a Filter 2 W Into 3-Ω Speakers (THD+N< 0.4%) < 0.08% THD+N at 1 W, 1 kHz, Into 4-Ω Load Extremely Efficient Third Generation 5-V Class-D Technology: – Low Supply Current (No Filter) . . . 8 mA – Low Supply Current (Filter) . . . 15 mA – Low Shutdown Current . . . 1 µA – Low Noise Floor . . . 56 µVRMS – Maximum Efficiency Into 3 Ω, 65-70% – Maximum Efficiency Into 8 Ω, 75-85% – 4 Internal Gain Settings . . . 8-23.5 dB – PSRR . . . -77 dB Integrated Depop Circuitry • Short-Circuit Protection (Short to Battery, Ground, and Load) -40°C to 85°C Operating Temperature Range PW OR PWP PACKAGE (TOP VIEW) PGND LOUTN GAIN0 PVDD LINN AGND COSC RINN PVDD SHUTDOWN ROUTN PGND 1 2 3 4 5 6 7 8 9 10 11 12 24 23 22 21 20 19 18 17 16 15 14 13 PGND LOUTP BYPASS PVDD LINP VDD ROSC RINP PVDD GAIN1 ROUTP PGND DESCRIPTION The TPA2000D2 is the third generation 5-V class-D amplifier from Texas Instruments. Improvements to previous generation devices include: lower supply current, lower noise floor, better efficiency, four different gain settings, smaller packaging, and fewer external components. The most significant advancement with this device is its modulation scheme that allows the amplifier to operate without the output filter. Eliminating the output filter saves the user approximately 30% in system cost and 75% in PCB area. The TPA2000D2 is a monolithic class-D power IC stereo audio amplifier, using the high switching speed of power MOSFET transistors. These transistors reproduce the analog signal through high-frequency switching of the output stage. The TPA2000D2 is configured as a bridge-tied load (BTL) amplifier capable of delivering greater than 2 W of continuous average power into a 3-Ω load at less than 1% THD+N from a 5-V power supply in the high fidelity range (20 Hz to 20 kHz). With 1 W being delivered to a 4-Ω load at 1 kHz, the typical THD+N is less than 0.08%. A BTL configuration eliminates the need for external coupling capacitors on the output. Low supply current of 8 mA makes the device ideal for battery-powered applications. Protection circuitry increases device reliability: thermal, over-current, and under-voltage shutdown. Efficient class-D modulation enables the TPA2000D2 to operate at full power into 3-Ω loads at an ambient temperature of 85°C. AVAILABLE OPTIONS (1) TA –40°C to 85°C (1) (2) PACKAGED DEVICE TSSOP (PW) TSSOP (PWP) (2) TPA2000D2PW TPA2000D2PWP For the most current package and ordering information, see the Package Option Addendum at the end of this document, or see the TI web site at www.ti.com. The PWP package is available taped and reeled. To order a taped and reeled part, add the suffix R to the part number (e.g., TPA2000D2PWPR). Please be aware that an important notice concerning availability, standard warranty, and use in critical applications of Texas Instruments semiconductor products and disclaimers thereto appears at the end of this data sheet. PRODUCTION DATA information is current as of publication date. Products conform to specifications per the terms of the Texas Instruments standard warranty. Production processing does not necessarily include testing of all parameters. Copyright © 2000–2007, Texas Instruments Incorporated TPA2000D2 www.ti.com SLOS291F – MARCH 2000 – REVISED MARCH 2007 These devices have limited built-in ESD protection. The leads should be shorted together or the device placed in conductive foam during storage or handling to prevent electrostatic damage to the MOS gates. VDD AGND PVDD VDD Gain Adjust RINN + _ Gate Drive ROUTN _ + PGND + _ PVDD _ Gain Adjust RINP Gate Drive + ROUTP PGND SHUTDOWN 2 GAIN1 GAIN0 Gain Biases and References Start-Up Protection Logic Ramp Generator COSC ROSC BYPASS Thermal OC Detect OC Detect VDD ok PVDD LINP Gain Adjust + _ Gate Drive _ + PGND + _ PVDD _ LINN LOUTP Gain Adjust + Gate Drive LOUTN PGND 2 Submit Documentation Feedback TPA2000D2 www.ti.com SLOS291F – MARCH 2000 – REVISED MARCH 2007 TERMINAL FUNCTION TERMINAL NAME NO. I/O DESCRIPTION AGND 6 - Analog ground BYPASS 22 I Tap to voltage divider for internal midsupply bias generator used for analog reference. COSC 7 I A capacitor connected to this terminal sets the oscillation frequency in conjunction with ROSC. For proper operation, connect a 220 pF capacitor from COSC to ground. GAIN0 3 I Bit 0 of gain control (TTL logic level) GAIN1 15 I Bit 1 of gain control (TTL logic level) LINN 5 I Left channel negative differential audio input LINP 20 I Left channel positive differential audio input LOUTN 2 O Left channel negative audio output LOUTP 23 O Left channel positive audio output PGND PVDD 1, 24 - Power ground for left channel H-bridge 12, 13 - Power ground for right channel H-bridge 4, 21 - Power supply for left channel H-bridge 9, 16 - Power supply for right channel H-bridge RINN 8 I Right channel negative differential audio input RINP 17 I Right channel positive differential audio input ROSC 18 I A resistor connected to this terminal sets the oscillation frequency in conjunction with COSC. For proper operation, connect a 120 kΩ resistor from ROSC to ground. ROUTN 11 O Right channel negative audio output ROUTP 14 O Right channel positive output SHUTDOWN 10 I Places the amplifier in shutdown mode if a TTL logic low is placed on this terminal; normal operation if a TTL logic high is placed on this terminal. VDD 19 - Analog power supply ABSOLUTE MAXIMUM RATINGS over operating free-air temperature range (unless otherwise noted) (1) UNIT VDD, PVDD Supply voltage VI Input voltage -0.3 V to 6 V -0.3 V to VDD+0.3 V Continuous total power dissipation See Dissipation Rating Table TA Operating free-air temperature range -40°C to 85°C TJ Operating junction temperature range -40°C to 150°C Tstg Storage temperature range -65°C to 150°C Lead temperature 1,6 mm (1/16 inch) from case for 10 seconds (1) 260°C Stresses beyond those listed under absolute maximum ratings may cause permanent damage to the device. These are stress ratings only, and functional operation of the device at these or any other conditions beyond those indicated under recommended operating conditions is not implied. Exposure to absolute-maximum-rated conditions for extended periods may affect device reliability. DISSIPATION RATING TABLE PACKAGE TA ≤ 25°C POWER RATING DERATING FACTOR ABOVE TA = 25°C TA = 70°C POWER RATING TA = 85°C POWER RATING PW 1.04 W 8.34 mW/°C 0.67 W 0.54 W PWP 2.7 W 21.8 mW/°C 1.7 W 1.4 W Submit Documentation Feedback 3 TPA2000D2 www.ti.com SLOS291F – MARCH 2000 – REVISED MARCH 2007 RECOMMENDED OPERATING CONDITIONS MIN TYP MAX 4.5 5.5 UNIT VDD, PVDD Supply voltage VIH High-level input voltage GAIN0, GAIN1, SHUTDOWN VIL Low-level input voltage GAIN0, GAIN1, SHUTDOWN ROSC Oscillator resistance 120 COSC Oscillator capacitance 220 fs Switching frequency 200 300 kHz TA Operating free-air temperature -40 85 °C 2 V V 0.8 V kΩ pF ELECTRICAL CHARACTERISTICS TA = 25°C, VDD = PVDD = 5 V (unless otherwise noted) PARAMETER TEST CONDITIONS MIN | VOO | Output offset voltage (measured differentially) VI = 0 V PSRR Power supply rejection ratio VDD=PVDD = 4.5 V to 5.5 V IIH High-level input current VDD=PVDD = 5.5 V, VI = VDD = PVDD IIL Low-level input current VDD=PVDD = 5.5 V, VI = 0 V IDD Supply current No filter (with or without speaker load) IDD Supply current With filter, L = 22 µH, C = 1 µF IDD(SD) Supply current, shutdown mode TYP MAX 25 mV 1 µA -77 8 UNIT dB 1 µA 10 mA 15 mA 1 15 TYP MAX µA OPERATING CHARACTERISTICS TA = 25°C, VDD = PVDD = 5 V, RL = 4 Ω, Gain = 8 dB (unless otherwise noted) PARAMETER TEST CONDITIONS PO Output power THD = 0.1%, f = 1 kHz, RL = 3 Ω THD+N Total harmonic distortion plus noise PO = 1 W, f = 20 Hz to 20 kHz BOM Maximum output power bandwidth THD = 5% kSVR Supply ripple rejection ratio f = 1 kHz, C(BYPASS) = 0.4 µF SNR Signal-to-noise ratio Integrated noise floor ZI MIN 2 20 20 Hz to 20 kHz, No input dB 87 dBV 56 µV >20 kΩ 4 AMPLIFIER GAIN (dB) INPUT IMPEDANCE (kΩ) TYP TYP 0 0 8 104 0 1 12 74 1 0 17.5 44 1 1 23.5 24 Submit Documentation Feedback kHz -60 Table 1. Gain Settings GAIN0 W <0.5% Input impedance GAIN1 UNIT TPA2000D2 www.ti.com SLOS291F – MARCH 2000 – REVISED MARCH 2007 TYPICAL CHARACTERISTICS Table of Graphs FIGURE η THD+N Efficiency vs Output power FFT at 1.5 W output power vs Frequency Total harmonic distortion plus noise 2, 3 4 vs Output power 5-7 vs Frequency 8, 9 Crosstalk vs Frequency 10 Power supply rejection ratio vs Frequency 11 TEST SET-UP FOR GRAPHS The THD+N measurements shown do not use an LC output filter, but use a low pass filter with a cutoff frequency of 20 kHz so the switching frequency does not dominate the measurement. This is done to ensure that the THD+N measured is just the audible THD+N. The THD+N measurements are shown at the highest gain for worst case. The LC output filter used in the efficiency curves (Figure 2 and Figure 3) is shown in Figure 1. L1 = L2 = 22 µH (DCR = 110 mΩ, Part number = SCD0703T-220 M-S, Manufacturer = GCI) C1 = C2 = 1 µF The ferrite filter used in the efficiency curves (Figure 2 and Figure 3) is shown in Figure 1, where L is a ferrite bead. L1 = L2 = ferrite bead (part number = 2512067007Y3, manufacturer = Fair-Rite) C1 = C2 = 1 nF L1 OUT+ C1 OUT– L2 C2 Figure 1. Class-D Output Filter Submit Documentation Feedback 5 TPA2000D2 www.ti.com SLOS291F – MARCH 2000 – REVISED MARCH 2007 TYPICAL CHARACTERISTICS EFFICIENCY vs OUTPUT POWER EFFICIENCY vs OUTPUT POWER 90 80 Ferrite Bead Filter LC Filter 80 70 70 No Filter 60 LC Filter Notebook Speaker Efficiency − % 60 Efficiency − % Ferrite Bead Filter 50 Class−AB 40 30 50 40 Class−AB 30 20 20 RL = 8 Ω, Multimedia Speaker VDD = 5 V 10 0 0 0.2 0.4 0.6 0.8 PO − Output Power − W 1 RL = 3 Ω, Notebook PC Speaker VDD = 5 V 10 0 1.2 0 0.5 1 1.5 PO − Output Power − W Figure 2. Figure 3. FFT AT 1.5 W OUTPUT POWER vs FREQUENCY +0 VDD = 5 V, Gain = 8 dB, f = 1 kHz, PO = 1.5 W, Bandwidth = 20 Hz to 22 kHz, 16386 Frequency Bins Power − VdB −20 −40 −60 −80 −100 −120 −140 0 2k 4k 6k 8k 10k 12k 14k f − Frequency − Hz Figure 4. 6 Submit Documentation Feedback 16k 18k 20k 22k 24k 2 TPA2000D2 www.ti.com SLOS291F – MARCH 2000 – REVISED MARCH 2007 TYPICAL CHARACTERISTICS (continued) TOTAL HARMONIC DISTORTION PLUS NOISE vs OUTPUT POWER TOTAL HARMONIC DISTORTION PLUS NOISE vs OUTPUT POWER 10 VDD = 5 V Gain = 23.5 dB RL = 3 Ω THD+N − Total Harmonic Distortion − % THD+N − Total Harmonic Distortion − % 10 1 1 kHz 20 Hz 0.1 20 kHz 0.01 10 m 100 m PO − Output Power − W 1 2 1 1 kHz 20 Hz 0.1 20 kHz 0.01 10 m 3 1 100 m 2 3 PO − Output Power − W Figure 5. Figure 6. TOTAL HARMONIC DISTORTION PLUS NOISE vs OUTPUT POWER TOTAL HARMONIC DISTORTION PLUS NOISE vs FREQUENCY 10 10 VDD = 5 V Gain = 23.5 dB RL = 8 Ω THD+N − Total Harmonic Distortion − % THD+N − Total Harmonic Distortion − % VDD = 5 V Gain = 23.5 dB RL = 4 Ω 1 1 kHz 20 Hz 0.1 20 kHz 0.01 10 m VDD = 5 V Gain = 23.5 dB RL = 4 Ω 1 0.2 W 0.75 W 0.1 1.5 W 0.01 100 m 1 2 20 PO − Output Power − W 100 1k 10 k 20 k f − Frequency − Hz Figure 7. Figure 8. Submit Documentation Feedback 7 TPA2000D2 www.ti.com SLOS291F – MARCH 2000 – REVISED MARCH 2007 TYPICAL CHARACTERISTICS (continued) THD+N − Total Harmonic Distortion − % TOTAL HARMONIC DISTORTION PLUS NOISE vs FREQUENCY 10 VDD = 5 V Gain = 23.5 dB RL = 8 Ω 1 0.1 W 1W 0.1 0.5 W 0.01 20 100 1k f − Frequency − Hz 20 k Figure 9. CROSSTALK vs FREQUENCY POWER SUPPLY REJECTION RATIO vs FREQUENCY −30 PSRR − Power Supply Rejection Ratio − dB −30 Crosstalk − dB −40 Left to Right −50 Right to Left −60 −70 1 10 100 1k 10 k 100 k −40 −50 −60 −70 −80 −90 10 f − Frequency − Hz Figure 10. 8 100 1k 10 k f − Frequency − Hz Figure 11. Submit Documentation Feedback 100 k TPA2000D2 www.ti.com SLOS291F – MARCH 2000 – REVISED MARCH 2007 APPLICATION INFORMATION ELIMINATING THE OUTPUT FILTER WITH THE TPA2000D2 This section focuses on why the user can eliminate the output filter with the TPA2000D2. EFFECT ON AUDIO The class-D amplifier outputs a pulse-width modulated (PWM) square wave, which is the sum of the switching waveform and the amplified input audio signal. The human ear acts as a band-pass filter such that only the frequencies between approximately 20 Hz and 20 kHz are passed. The switching frequency components are much greater than 20 kHz, so the only signal heard is the amplified input audio signal. TRADITIONAL CLASS-D MODULATION SCHEME The traditional class-D modulation scheme, which is used in the TPA005Dxx family, has a differential output where each output is 180 degrees out of phase and changes from ground to the supply voltage, VDD. Therefore, the differential prefiltered output varies between positive and negative VDD, where filtered 50% duty cycle yields 0 volts across the load. The traditional class-D modulation scheme with voltage and current waveforms is shown in Figure 12. Note that even at an average of 0 volts across the load (50% duty cycle), the current to the load is high causing high loss, thus causing a high supply current. OUT+ OUT– +5 V Differential Voltage Across Load OV –5 V Current Figure 12. Traditional Class-D Modulation Scheme's Output Voltage and Current Waveforms Into an Inductive Load With No Input TPA2000D2 MODULATION SCHEME The TPA2000D2 uses a modulation scheme that still has each output switching from 0 to the supply voltage. However, OUT+ and OUT- are now in phase with each other with no input. The duty cycle of OUT+ is greater than 50% and OUT- is less than 50% for positive voltages. The duty cycle of OUT+ is less than 50% and OUTis greater than 50% for negative voltages. The voltage across the load sits at 0 volts throughout most of the switching period greatly reducing the switching current, which reduces any I2R losses in the load. Submit Documentation Feedback 9 TPA2000D2 www.ti.com SLOS291F – MARCH 2000 – REVISED MARCH 2007 APPLICATION INFORMATION (continued) OUT+ OUT– Differential Voltage Across Load Output = 0 V +5 V 0V –5 V Current OUT+ OUT– Differential Voltage Across Load Output > 0 V +5 V 0V –5 V Current Figure 13. The TPA2000D2 Output Voltage and Current Waveforms Into an Inductive Load EFFICIENCY: WHY YOU MUST USE A FILTER WITH THE TRADITIONAL CLASS-D MODULATION SCHEME The main reason that the traditional class-D amplifier needs an output filter is that the switching waveform results in maximum current flow. This causes more loss in the load, which causes lower efficiency. The ripple current is large for the traditional modulation scheme because the ripple current is proportional to voltage multiplied by the time at that voltage. The differential voltage swing is 2 × VDD and the time at each voltage is half the period for the traditional modulation scheme. An ideal LC filter is needed to store the ripple current from each half cycle for the next half cycle, while any resistance causes power dissipation. The speaker is both resistive and reactive, whereas an LC filter is almost purely reactive. The TPA2000D2 modulation scheme has very little loss in the load without a filter because the pulses are very short and the change in voltage is VDD instead of 2 × VDD. As the output power increases, the pulses widen making the ripple current larger. Ripple current could be filtered with an LC filter for increased efficiency, but for most applications the filter is not needed. An LC filter with a cutoff frequency less than the class-D switching frequency allows the switching current to flow through the filter instead of the load. The filter has less resistance than the speaker, which results in less power dissipated and increased efficiency. EFFECTS OF APPLYING A SQUARE WAVE INTO A SPEAKER Audio specialists have said for years not to apply a square wave to speakers. If the amplitude of the waveform is high enough and the frequency of the square wave is within the bandwidth of the speaker, the square wave could cause the voice coil to jump out of the air gap and/or scar the voice coil. A 250-kHz switching frequency, however, is not significant because the speaker cone movement is proportional to 1/f2 for frequencies beyond the audio band. Therefore, the amount of cone movement at the switching frequency is very small. However, 10 Submit Documentation Feedback TPA2000D2 www.ti.com SLOS291F – MARCH 2000 – REVISED MARCH 2007 APPLICATION INFORMATION (continued) damage could occur to the speaker if the voice coil is not designed to handle the additional power. To size the speaker for added power, the ripple current dissipated in the load needs to be calculated by subtracting the theoretical supplied power, PSUP THEORETICAL, from the actual supply power, PSUP, at maximum output power, POUT. The switching power dissipated in the speaker is the inverse of the measured efficiency, ηMEASURED, minus the theoretical efficiency, ηTHEORETICAL. PSPKR = PSUP – PSUP THEORETICAL (at max output power) (1) PSPKR = PSUP / POUT – PSUP THEORETICAL / POUT (at max output power) (2) PSPKR = 1/ηMEASURED – 1/ηTHEORETICAL (at max output power) (3) The maximum efficiency of the TPA2000D2 with an 8-Ω load is 85%. Using Equation 3 with the efficiency at maximum power from Figure 2 (78%), we see that there is an additional 106 mW dissipated in the speaker. The added power dissipated in the speaker is not an issue as long as it is taken into account when choosing the speaker. WHEN TO USE AN OUTPUT FILTER Design the TPA2000D2 without the filter if the traces from amplifier to speaker are short. The TPA2000D2 passed FCC and CE radiated emissions with no shielding with speaker wires 8 inches (20,32 cm) long or less. Notebook PCs and powered speakers where the speaker is in the same enclosure as the amplifier are good applications for class-D without a filter. A ferrite bead filter can often be used if the design is failing radiated emissions without a filter, and the frequency sensitive circuit is greater than 1 MHz. This is good for circuits that just have to pass FCC and CE because FCC and CE only test radiated emissions greater than 30 MHz. If choosing a ferrite bead, choose one with high impedance at high frequencies, but very low impedance at low frequencies. Use an output filter if there are low frequency (< 1 MHz) EMI sensitive circuits and/or there are long leads from amplifier to speaker. GAIN SETTING VIA GAIN0 AND GAIN1 INPUTS The gain of the TPA2000D2 is set by two input terminals, GAIN0 and GAIN1. The gains listed in Table 2 are realized by changing the taps on the input resistors inside the amplifier. This causes the input impedance, ZI, to be dependent on the gain setting. The actual gain settings are controlled by ratios of resistors, so the actual gain distribution from part-to-part is quite good. However, the input impedance may shift by 30% due to shifts in the actual resistance of the input resistors. For design purposes, the input network (discussed in the next section) should be designed assuming an input impedance of 20 kΩ, which is the absolute minimum input impedance of the TPA2000D2. At the lower gain settings, the input impedance could increase to as high as 115 kΩ. Table 2. Gain Settings GAIN1 GAIN0 AMPLIFIER GAIN (dB) INPUT IMPEDANCE (kΩ) TYP TYP 0 0 8 104 0 1 12 74 1 0 17.5 44 1 1 23.5 24 Submit Documentation Feedback 11 TPA2000D2 www.ti.com SLOS291F – MARCH 2000 – REVISED MARCH 2007 INPUT RESISTANCE Each gain setting is achieved by varying the input resistance of the amplifier, which can range from its smallest value to over 6 times that value. ZF CI IN Input Signal ZI The -3 dB frequency can be calculated using Equation 4: 1 f *3 dB + 2p CI Z I (4) INPUT CAPACITOR, CI In the typical application an input capacitor, CI, is required to allow the amplifier to bias the input signal to the proper dc level for optimum operation. In this case, CI and the input impedance of the amplifier, ZI, form a high-pass filter with the corner frequency determined in Equation 5. −3 dB fc(highpass) + 1 2 p ZI C I fc (5) The value of CI is important, as it directly affects the bass (low frequency) performance of the circuit. Consider the example where ZI is 20 kΩ and the specification calls for a flat bass response down to 80 Hz. Equation 5 is reconfigured as Equation 6. CI + 1 2p Z I f c (6) In this example, CI is 0.1 µF, so one would likely choose a value in the range of 0.1 µF to 1 µF. If the gain is known and is constant, use ZI from Table 1 to calculate CI. A further consideration for this capacitor is the leakage path from the input source through the input network (CI) and the feedback network to the load. This leakage current creates a dc offset voltage at the input to the amplifier that reduces useful headroom, especially in high gain applications. For this reason a low-leakage tantalum or ceramic capacitor is the best choice. When polarized capacitors are used, the positive side of the capacitor should face the amplifier input in most applications as the dc level there is held at VDD/2, which is likely higher than the source dc level. Note that it is important to confirm the capacitor polarity in the application. CI should be 10 times smaller than the bypass capacitor to reduce clicking and popping noise from power on/off and entering and leaving shutdown. After sizing CI for a given cutoff frequency, size the bypass capacitor up to 10 times that of the input capacitor. CI ≤ CBYP / 10 12 (7) Submit Documentation Feedback TPA2000D2 www.ti.com SLOS291F – MARCH 2000 – REVISED MARCH 2007 SWITCHING FREQUENCY The switching frequency is determined using the values of the components connected to ROSC (pin 18) and COSC (pin 7) and is calculated with the following equation: fs + 6.6 ROSC C OSC (8) The switching frequency was chosen to be centered on 250 kHz. This frequency is the optimum audio fidelity of oversampling and of maximizing efficiency by minimizing the switching losses of the amplifier. The recommended values are a resistance of 120 kΩ and a capacitance of 220 pF. Using these component values, the amplifier operates properly by using 5% tolerance resistors and 10% tolerance capacitors. The tolerance of the components can be changed, as long as the switching frequency remains between 200 kHz and 300 kHz. Within this range, the internal circuitry of the device provides stable operation. POWER SUPPLY DECOUPLING, CS The TPA2000D2 is a high-performance CMOS audio amplifier that requires adequate power supply decoupling to ensure the output total harmonic distortion (THD) is as low as possible. Power supply decoupling also prevents oscillations for long lead lengths between the amplifier and the speaker. The optimum decoupling is achieved by using two capacitors of different types that target different types of noise on the power supply leads. For higher frequency transients, spikes, or digital hash on the line, a good low equivalent-series-resistance (ESR) ceramic capacitor, typically 0.1 µF placed as close as possible to the device VDD lead works best. For filtering lower-frequency noise signals, a larger aluminum electrolytic capacitor of 10 µF or greater placed near the audio power amplifier is recommended. MIDRAIL BYPASS CAPACITOR, CBYP The midrail bypass capacitor, CBYP, is the most critical capacitor and serves several important functions. During start-up or recovery from shutdown mode, CBYP determines the rate at which the amplifier starts up. The second function is to reduce noise produced by the power supply caused by coupling into the output drive signal. This noise is from the midrail generation circuit internal to the amplifier, which appears as degraded PSRR and THD+N. Bypass capacitor, CBYP, values of 0.47 µF to 1 µF ceramic or tantalum low-ESR capacitors are recommended for the best THD and noise performance. Increasing the bypass capacitor reduces clicking and popping noise from power on/off and entering and leaving shutdown. To have minimal pop, CBYP should be 10 times larger than CI. CBYP ≥ 10 × CI (9) DIFFERENTIAL INPUT The differential input stage of the amplifier cancels any noise that appears on both input lines of a channel. To use the TPA2000D2 EVM with a differential source, connect the positive lead of the audio source to the RINP (LINP) input and the negative lead from the audio source to the RINN (LINN) input. To use the TPA2000D2 with a single-ended source, ac ground the RINN and LINN inputs through a capacitor and apply the audio single to the RINP and LINP inputs. In a single-ended input application, the RINN and LINN inputs should be ac-grounded at the audio source instead of at the device inputs for best noise performance. SHUTDOWN MODES The TPA2000D2 employs a shutdown mode of operation designed to reduce supply current, IDD, to the absolute minimum level during periods of nonuse for battery-power conservation. The SHUTDOWN input terminal should be held high during normal operation when the amplifier is in use. Pulling SHUTDOWN low causes the outputs to mute and the amplifier to enter a low-current state, IDD(SD) = 1 µA. SHUTDOWN should never be left unconnected, because amplifier operation would be unpredictable. Submit Documentation Feedback 13 TPA2000D2 www.ti.com SLOS291F – MARCH 2000 – REVISED MARCH 2007 USING LOW-ESR CAPACITORS Low-ESR capacitors are recommended throughout this application section. A real (as opposed to ideal) capacitor can be modeled simply as a resistor in series with an ideal capacitor. The voltage drop across this resistor minimizes the beneficial effects of the capacitor in the circuit. The lower the equivalent value of this resistance the more the real capacitor behaves like an ideal capacitor. EVALUATION CIRCUIT C1 0.1 µF LEFT AUDIO INPUT+ LEFT AUDIO OUTPUT– VDD TPA2000D2 GAIN SELECT PGND PGND LOUTN LOUTP GAIN0 BYPASS LPVDD LPVDD C5 C17 C2 0.1 µF 0.1 µF LEFT AUDIO INPUT– C3 C7 0.1 µF LINN LINP AGND VDD COSC ROSC RINN RINP 220 pF RIGHT AUDIO INPUT+ RPVDD 10 TO SYSTEM CONTROL C18 0.1 µF SHUTDOWN ROUTN PGND C6 20 ROUTP LEFT AUDIO OUTPUT+ 10 µF C21 VDD 0.1 µF VDD C20 0.1 µF R1 120k C8 10 µF RPVDD GAIN1 1 µF C19 GAIN SELECT 0.1 µF RIGHT AUDIO OUTPUT + PGND VDD RIGHT AUDIO OUTPUT – C4 RIGHT AUDIO INPUT– 0.1 µF Table 3. TPA2000D2 Application Bill of Materials SIZE QUANTITY C1-4, C17-21 REFERENCE Capacitor, ceramic chip, 0.1 µF, ±10%, X7R, 50 V 0805 9 Kemet C0805C104K5RAC C5 Capacitor, ceramic, 1.0 µF, 80%/-20%, Y5V, 16 V 0805 1 Murata GRM40-Y5V105Z16 C6, C8 Capacitor, ceramic, 10 µF, 80%/-20%, Y5V, 16 V 1210 2 Murata GRM235-Y5V106Z16 C7 Capacitor, ceramic, 220 pF, ±10%, XICON, 50 V 0805 2 Mouser 140-CC501B221K R1 Resistor, chip, 120 kΩ, 1/10 W, 5%, XICON 0805 1 Mouser 260-120K U1 IC, TPA2000D2, audio power amplifier, 2-W, 2-channel, class-D 24 pin TSSOP 1 TI TPA2000D2PWP 14 DESCRIPTION Submit Documentation Feedback MANUFACTURER PART NUMBER PACKAGE OPTION ADDENDUM www.ti.com 18-Apr-2006 PACKAGING INFORMATION Orderable Device Status (1) Package Type Package Drawing Pins Package Eco Plan (2) Qty TPA2000D2PW ACTIVE TSSOP PW 24 60 Green (RoHS & no Sb/Br) CU NIPDAU Level-2-260C-1 YEAR TPA2000D2PWG4 ACTIVE TSSOP PW 24 60 Green (RoHS & no Sb/Br) CU NIPDAU Level-2-260C-1 YEAR TPA2000D2PWP ACTIVE HTSSOP PWP 24 60 Green (RoHS & no Sb/Br) CU NIPDAU Level-2-260C-1 YEAR TPA2000D2PWPG4 ACTIVE HTSSOP PWP 24 60 Green (RoHS & no Sb/Br) CU NIPDAU Level-2-260C-1 YEAR TPA2000D2PWPR ACTIVE HTSSOP PWP 24 2000 Green (RoHS & no Sb/Br) CU NIPDAU Level-2-260C-1 YEAR TPA2000D2PWPRG4 ACTIVE HTSSOP PWP 24 2000 Green (RoHS & no Sb/Br) CU NIPDAU Level-2-260C-1 YEAR TPA2000D2PWR ACTIVE TSSOP PW 24 2000 Green (RoHS & no Sb/Br) CU NIPDAU Level-2-260C-1 YEAR TPA2000D2PWRG4 ACTIVE TSSOP PW 24 2000 Green (RoHS & no Sb/Br) CU NIPDAU Level-2-260C-1 YEAR Lead/Ball Finish MSL Peak Temp (3) (1) The marketing status values are defined as follows: ACTIVE: Product device recommended for new designs. LIFEBUY: TI has announced that the device will be discontinued, and a lifetime-buy period is in effect. NRND: Not recommended for new designs. Device is in production to support existing customers, but TI does not recommend using this part in a new design. PREVIEW: Device has been announced but is not in production. Samples may or may not be available. OBSOLETE: TI has discontinued the production of the device. (2) Eco Plan - The planned eco-friendly classification: Pb-Free (RoHS), Pb-Free (RoHS Exempt), or Green (RoHS & no Sb/Br) - please check http://www.ti.com/productcontent for the latest availability information and additional product content details. TBD: The Pb-Free/Green conversion plan has not been defined. Pb-Free (RoHS): TI's terms "Lead-Free" or "Pb-Free" mean semiconductor products that are compatible with the current RoHS requirements for all 6 substances, including the requirement that lead not exceed 0.1% by weight in homogeneous materials. Where designed to be soldered at high temperatures, TI Pb-Free products are suitable for use in specified lead-free processes. Pb-Free (RoHS Exempt): This component has a RoHS exemption for either 1) lead-based flip-chip solder bumps used between the die and package, or 2) lead-based die adhesive used between the die and leadframe. The component is otherwise considered Pb-Free (RoHS compatible) as defined above. Green (RoHS & no Sb/Br): TI defines "Green" to mean Pb-Free (RoHS compatible), and free of Bromine (Br) and Antimony (Sb) based flame retardants (Br or Sb do not exceed 0.1% by weight in homogeneous material) (3) MSL, Peak Temp. -- The Moisture Sensitivity Level rating according to the JEDEC industry standard classifications, and peak solder temperature. Important Information and Disclaimer:The information provided on this page represents TI's knowledge and belief as of the date that it is provided. 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Addendum-Page 1 MECHANICAL DATA MTSS001C – JANUARY 1995 – REVISED FEBRUARY 1999 PW (R-PDSO-G**) PLASTIC SMALL-OUTLINE PACKAGE 14 PINS SHOWN 0,30 0,19 0,65 14 0,10 M 8 0,15 NOM 4,50 4,30 6,60 6,20 Gage Plane 0,25 1 7 0°– 8° A 0,75 0,50 Seating Plane 0,15 0,05 1,20 MAX PINS ** 0,10 8 14 16 20 24 28 A MAX 3,10 5,10 5,10 6,60 7,90 9,80 A MIN 2,90 4,90 4,90 6,40 7,70 9,60 DIM 4040064/F 01/97 NOTES: A. B. C. D. All linear dimensions are in millimeters. This drawing is subject to change without notice. Body dimensions do not include mold flash or protrusion not to exceed 0,15. Falls within JEDEC MO-153 POST OFFICE BOX 655303 • DALLAS, TEXAS 75265 IMPORTANT NOTICE Texas Instruments Incorporated and its subsidiaries (TI) reserve the right to make corrections, modifications, enhancements, improvements, and other changes to its products and services at any time and to discontinue any product or service without notice. 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