TI PTV08T250WAH

PTV08T250W
www.ti.com
SLTS260B – OCTOBER 2005 – REVISED NOVEMBER 2005
50-A, 8-V to 14-V INPUT, NON-ISOLATED, WIDE-OUTPUT ADJUST,
VERTICAL POWER MODULE w/ TurboTrans™ TECHNOLOGY
FEATURES
•
•
•
•
•
•
•
•
•
•
•
•
50-A Output Current
8-V to 14-V Input Voltage
Wide-Output Voltage Adjust (0.8 V to 3.6 V)
Efficiencies up to 95%
On/Off Inhibit
Differential Output Sense
Output Overcurrent Protection
(Nonlatching, Auto-Reset)
Overtemperature Protection
Start Up Into Output Prebias
Programmable Undervoltage Lockout (UVLO)
Safety Agency Approvals: UL/cUL 60950,
EN60950, VDE
Operating Temperature: –40°C to 85°C
•
•
•
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TurboTrans™Technology
Designed to meet ultra fast transient
requirements up to 300 A/µs
Multi-Phase, Switch-Mode Topology
AutoTrack™ Sequencing
APPLICATIONS
•
Advanced Computing and Server Applications
DESCRIPTION
The PTV08T250W is a high-performance 50-A rated, non-isolated, vertical power module which uses a
multi-phase switched-mode topology. This provides a small, ready-to-use module that can power the most
densely populated multiprocessor systems. The PTV08T250W is produced in a 21-pin, single in-line pin (SIP)
package. The SIP footprint minimizes board space, and offers an alternate package option for space conscious
applications. The modules use double-sided surface mount construction to provide a compact design.
Operating from an input voltage range of 8 V to 14 V, the PTV08T250W requires a single resistor to set the
output voltage to any value over the range, 0.8 V to 3.6 V. The wide input voltage range makes the
PTV08T250W suitable for advanced computing and server applications that use a loosely regulated 12-V
intermediate distribution bus.
A new feature included in this 2nd generation of PTH and PTV modules is TurboTrans™ technology (patent
pending). TurboTrans allows the transient response of the regulator to be optimized externally, resulting in a
reduction of output voltage deviation following a load transient and a reduction in required output capacitance.
This feature also offers enhanced stability when used with ultra-low ESR output capacitors.
The PTV08T250W incorporates a comprehensive list of standard features. They include on/off inhibit, a
differential remote output voltage sense which ensures tight load regulation, and an output overcurrent and
overtemperature shutdown to protect against load faults. A programmable undervoltage lockout allows the
turn-on and turn-off voltage thresholds to be customized. AutoTrack™ sequencing is a popular feature which
greatly simplifies the simultaneous power-up and power-down of multiple modules in a power system by allowing
the outputs to track a common voltage.
Please be aware that an important notice concerning availability, standard warranty, and use in critical applications of Texas
Instruments semiconductor products and disclaimers thereto appears at the end of this data sheet.
TurboTrans, AutoTrack, TMS320 are trademarks of Texas Instruments.
PRODUCTION DATA information is current as of publication date.
Products conform to specifications per the terms of the Texas
Instruments standard warranty. Production processing does not
necessarily include testing of all parameters.
Copyright © 2005, Texas Instruments Incorporated
PTV08T250W
www.ti.com
SLTS260B – OCTOBER 2005 – REVISED NOVEMBER 2005
These devices have limited built-in ESD protection. The leads should be shorted together or the device
placed in conductive foam during storage or handling to prevent electrostatic damage to the MOS gates.
STANDARD APPLICATION
AutoTrack
TurboTrans
15
9
AutoTrack
TurboTrans
+Sense 1
3
6,7
VI
13,14
20,21
VI
VO
PTV08T250W
+Sense
VO
10
17
2
16 Inhibit/
Prog UVLO
GND
CI
560 µF
(Required)
RTT
1%
0.05 W
(Optional)
–Sense
GND
12 18 19
4
VO Adj
5 11
8
CO
660 µF
(Required)
RSET
1%
0.05 W
COTT
(Optional)
L
O
A
D
–Sense
GND
A.
GND
RSET = Required to set the output voltage higher than the minimum value (see the electrical characteristic for values.)
ORDERING INFORMATION
PTV08T250W
(1)
(2)
PACKAGE OPTIONS (PTV08T250Wxx)
Pb – free and RoHS
Compatible (1)
PACKAGE REF (2)
Vertical T/H
No
EAN
Vertical T/H
Yes
EAN
VOLTAGE
CODE
DESCRIPTION
0.8 V – 3.6 V (Adjust)
AH
0.8 V – 3.6 V (Adjust)
AD
Pb – free option specifies Sn/Ag pin solder material.
Reference the applicable package reference drawing for the dimensions and PC board layout.
ABSOLUTE MAXIMUM RATINGS
over operating free-air temperature range (unless otherwise noted)
UNIT
Signal input voltages
Track control (pin 15)
TA
Operating temperature range over VI range
Twave
Wave solder
temperature
Tstg
Storage temperature
Surface temperature of module body or pins (5 seconds)
Per Mil-STD-883D, Method 2002.3, 1 msec, ½ Sine, mounted
Mechanical vibration
Mil-STD-883D, Method 2007.2, 20–2000 Hz
Weight
2
–40°C to 85°C
260°C
–40°C to 125°C
Mechanical shock
Flammability
–0.3 V to VI + 0.3 V
500 G
15 G
16.6 grams
Meets UL94V-O
PTV08T250W
www.ti.com
SLTS260B – OCTOBER 2005 – REVISED NOVEMBER 2005
ELECTRICAL CHARACTERISTICS
TA = 25°C, VI = 12 V, VO = 3.3 V, CI = 560 µF, CO = 660 µF, and IO = IOmax (unless otherwise stated)
PARAMETER
TEST CONDITIONS
IO
Output current
8 V ≤ VI ≤ 14 V
VI
Input voltage range
Over IO range
VOtol
Set-point voltage tolerance
∆Regte
Temperature variation
–40°C < TA < 85°C
Line regulation
MIN
TYP
MAX
25°C, Natural Convection
0
50 (1)
60°C, 200 LFM airflow
0
48 (1)
8
14
±2 (2)
UNIT
A
V
%VO
±0.5
%VO
Over VI range
±3
mV
Over IO range
±3
mV
mp
∆Reglin
e
∆Regloa Load regulation
d
∆Regtot
Total output variation
Includes set-point, line, load, –40°C ≤ TA ≤ 85°C
±3 (2)
∆Regadj Output adjust range
η
Efficiency
IOtrip
0.8
RSET = 2.49 kΩ, VO = 3.3 V
95
RSET = 6.98 kΩ, VO = 2.5 V
93
RSET = 13.0 kΩ, VO = 2 V
92
RSET = 16.9 kΩ, VO = 1.8 V
91
RSET = 27.4 kΩ, VO = 1.5 V
90
RSET = 53.6 kΩ, VO = 1.2 V
88
RSET = 113.0 kΩ, VO = 1 V
86
RSET = open circuit, VO = 0.8 V
82
All voltages
15
IO = 35 A
VO ripple (peak-to-peak)
20-MHz bandwidth
Overcurrent threshold
Reset, followed by auto-recovery
ttr
w/o TurboTrans
CO= 660 µF
∆Vtr
ttr
Transient response
∆Vtr
2.5 A/µs load step
50 to 100% IOmax
ttrTT
w/o TurboTrans
CO= 3300 µF, Type C
w/ TurboTrans
CO= 3300 µF, Type C
∆VtrTT
IILtrack
Track input current (pin 15)
3.6
75
100
Track slew rate capability
CO≤ CO(max)
UVLO
Undervoltage lockout threshold
Pin 16 open
Inhibit control (pin 16)
Referenced to GND
%
mVPP
115
µs
VO
over/undershoot
130
mV
Recovery time
50
µs
VO
over/undershoot
85
mV
Recovery time
50
µs
VO
over/undershoot
50
mV
–0.13
7.5 (4)
VI Increasing
VI Decreasing
6
(3)
mA
1
V/ms
7.8
6.5 (4)
Input high voltage
2.5
Open (5)
VIL
Input low voltage
–0.2
0.5
IILinhibi
t
Input low current
IIinh
Input standby current
Pin 16 to GND
fs
Switching frequency
Over VI and IO ranges
CI
External input capacitance
(3)
(4)
(5)
(6)
A
50
VIH
(1)
(2)
V
Recovery time
Pin to GND
dVtrack/
dt
%VO
Pin to GND
0.5
560 (6)
1050
V
mA
35
900
V
mA
1200
kHz
µF
See SOA curves or consult factory for appropriate derating.
The set-point voltage tolerance is affected by the tolerance of RSET. The stated limit is unconditionally met if RSET has a tolerance of 1%
with 100 ppm/°C or better temperature stability.
This control pin has an internal pull-up to 5 V. A small, low-leakage (<100 nA) MOSFET or open-drain/collector voltage supervisor IC is
recommended to control this pin. For further information, see the related application section.
These are the default voltages. They may be adjusted using the UVLO Prog control input. See the Application Information section for
further guidance.
This control pin has an internal pull-up to 5 V. When left open-circuit the module operates when input power is applied. A small,
low-leakage (<100 nA) MOSFET is recommended to control this pin. For further information, see the related application section.
A minimum capacitance of 560-µF is required at the input for proper operation. For best results, 1000 µF is recommended. The
capacitance must be rated for a minimum of 300 mArms of ripple current.
3
PTV08T250W
www.ti.com
SLTS260B – OCTOBER 2005 – REVISED NOVEMBER 2005
ELECTRICAL CHARACTERISTICS (continued)
TA = 25°C, VI = 12 V, VO = 3.3 V, CI = 560 µF, CO = 660 µF, and IO = IOmax (unless otherwise stated)
PARAMETER
TEST CONDITIONS
Capacitance Value
MIN
Nonceramic
w/out TurboTrans
CO
Ceramic
Equivalent series resistance (non-ceramic)
External output capacitance
w/ TurboTrans
660 (7)
Capacitance Value
(7)
Reliability
Per Bellcore TR-332 50% stress, TA = 40°C, ground benigh
MAX
14,000 (8)
3000
3 (9)
see TT
chart (10)
Capacitance X ESR product (CO*ESR)
MTBF
TYP
2.7
UNIT
µF
mΩ
14,000 (11)
µF
10,000 (12)
mΩ*µF
106 Hrs
A minimum value of output capacitance is required for proper operation. Adding additional capacitance at the load further improves
transient response. See the Capacitor Application Information section for further guidance.
(8) This is the calculated maximum. This value includes both ceramic and non-ceramic capacitors. The minimum ESR requirement often
results in a lower value. For further information, see the related application section.
(9) This is the typical ESR for all the electrolytic (nonceramic) output capacitance. Use 5 mΩ as the minimum when using manufacturer's
max-ESR values to calculate.
(10) Minimum capacitance is determined by the transient deviation requirement. A corresponding resistor, RTT is required for proper
operation. See the TurboTrans Selection section for guidance in selecting the capacitance and RTT value
(11) This is the calculated maximum output capacitance. This value includes both ceramic and non-ceramic capacitors.
(12) When calculating the Capacitance X ESR product use the capacitance and ESR values of a single capacitor. For an output capacitor
bank of several capacitor types and values, calculate the C*ESR product using the values of the capacitor that makes up the majority of
the capacitance.
4
PTV08T250W
www.ti.com
SLTS260B – OCTOBER 2005 – REVISED NOVEMBER 2005
DEVICE INFORMATION
PTV08T250W
(Top View)
PIN 1
TERMINAL FUNCTIONS
TERMINAL
NAME
DESCRIPTION
NO.
GND
4, 5, 11, 12, 18, This is the common ground connection for the VI and VO power connections. It is also the 0 Vdc reference
19
for the control inputs.
VI
6, 7, 13, 14, 20,
The positive input voltage power node to the module, which is referenced to common GND.
21
VO
Inhibit /
UVLO
VO Adjust
3, 10, 17
The regulated positive power output with respect to GND.
16
The Inhibit pin is an open-collector/drain negative logic input that is referenced to GND. Applying a
low-level ground signal to this input disables the module’s output and turns off the output voltage. When
the Inhibit control is active, the input current drawn by the regulator is significantly reduced. If the Inhibit
pin is left open-circuit, the module produces an output whenever the input voltage is above the UVLO
threshold.
This pin is also used for input undervoltage lockout (UVLO) programming. Connecting a resistor from this
pin to signal ground allows the ON threshold of the UVLO to be adjusted higher than the default value.
The hysterisis can also be independently reduced by connecting a second resistor from this pin to VI. For
further information, see the Application Information section.
8
A 1%, 0.05-W resistor must be connected between this pin and GND to set the output voltage higher
than the minimum value. The set-point range for the output voltage is from 0.8 V to 3.6 V. The resistor
required for a given output voltage may be calculated from the following formula. If left open circuit, the
module output defaults to its lowest output voltage value. For further information on the adjustment and/or
trimming of the output voltage, see the related Application Information section.
RSET = 30.1 x
0.8
( VO - 0.8)
- 7.135 kW
The specification table gives the preferred resistor values for a number of standard output voltages.
+Sense
1
The sense inputs allow the regulation circuit to compensate for voltage drop between the module and the
load. For optimal voltage accuracy, +Sense should be connected to VO. If it is left open, a low-value
internal resistor ensures that the output remains in regulation.
–Sense
2
For optimal voltage accuracy, –Sense should be connected to the ground return at the load. If it is left
open, a low-value internal resistor ensures that the output remains in regulation.
15
This is an analog control input that allows the output voltage to follow another voltage during power up
and power down sequences. The pin is active from 0 V, up to the nominal set-point voltage. Within this
range, the module output follows the voltage at the Track pin on a volt-for-volt basis. When the control
voltage is raised above this range, the module regulates at its nominal output voltage. If unused, this
input should be connected to VI for a faster power up. For further information, see the related Application
Information section.
9
This input pin adjusts the transient response of the regulator. For a given value of output capacitance, a
reduction in peak output voltage deviation and increased system stability is achieved by placing a resistor
between this pin and +Sense. A 1%, 0.05-W resistor must be connected between this pin and +Sense to
activate the TurboTrans feature. Suggested placement of this resistor is within 1 cm from pin 9. The
resistor value required can be selected from the TurboTrans resistor table. If unused, this input pin
should be left open-circuit. For further information, see the related Application Information section.
Track
TurboTrans
5
PTV08T250W
www.ti.com
SLTS260B – OCTOBER 2005 – REVISED NOVEMBER 2005
TYPICAL CHARACTERISTICS (VI = 12 V) (1) (2)
EFFICIENCY
vs
LOAD CURRENT
POWER DISSIPATION
vs
LOAD CURRENT
VO = 2.5 V
VO = 3.3 V
VO = 1.8 V
VO = 1.2 V
VO = 0.8 V
PD - Power Dissipation - W
Efficiency - %
VO = 3.3 V
VO = 2.5 V
VO = 1.8 V
VO = 1.2 V
VO = 0.8 V
IO- Output Current - A
IO- Output Current - A
Figure 2.
AMBIENT TEMPERATURE
vs
OUTPUT CURRENT
AMBIENT TEMPERATURE
vs
OUTPUT CURRENT
400 LFM
200 LFM
100 LFM
Nat Conv
IO- Output Current - A
Figure 3.
(2)
6
200 LFM
100 LFM
Nat Conv
VO = 3.3 V
VO = 1.8 V
(1)
400 LFM
Temperature Derating - °C
Temperature Derating - °C
Figure 1.
IO- Output Current - A
Figure 4.
The electrical characteristic data has been developed from actual products tested at 25°C. This data is considered typical for the
converter. Applies to Figure 1 and Figure 2.
The temperature derating curves represent the conditions at which internal components are at or below the manufacturer's maximum
operating temperatures. Derating limits apply to modules soldered directly to a 4-in. x 4-in., double-sided, 4-layer PCB with 1-oz. copper.
See the mechanical specification for more information. Applies to Figure 3 and Figure 4.
PTV08T250W
www.ti.com
SLTS260B – OCTOBER 2005 – REVISED NOVEMBER 2005
TYPICAL CHARACTERISTICS (VI = 8 V) (1) (2)
EFFICIENCY
vs
LOAD CURRENT
POWER DISSIPATION
vs
LOAD CURRENT
VO = 2.5 V
Efficiency - %
VO = 1.2 V
VO = 1.8 V
VO = 0.8 V
VO = 3.3 V
PD - Power Dissipation - W
VO = 3.3 V
VO = 2.5 V
VO = 1.8 V
VO = 1.2 V
VO = 0.8 V
IO- Output Current - A
Figure 5.
Figure 6.
AMBIENT TEMPERATURE
vs
OUTPUT CURRENT
AMBIENT TEMPERATURE
vs
OUTPUT CURRENT
400 LFM
200 LFM
100 LFM
Nat Conv
IO- Output Current - A
Figure 7.
(2)
200 LFM
100 LFM
Nat Conv
VO = 3.3 V
VO = 1.8 V
(1)
400 LFM
Temperature Derating - °C
Temperature Derating - °C
IO- Output Current - A
IO- Output Current - A
Figure 8.
The electrical characteristic data has been developed from actual products tested at 25°C. This data is considered typical for the
converter. Applies to Figure 5 and Figure 6.
The temperature derating curves represent the conditions at which internal components are at or below the manufacturer's maximum
operating temperatures. Derating limits apply to modules soldered directly to a 4-in. x 4-in., double-sided, 4-layer PCB with 1-oz. copper.
See the mechanical specification for more information. Applies to Figure 7 and Figure 8.
7
PTV08T250W
www.ti.com
SLTS260B – OCTOBER 2005 – REVISED NOVEMBER 2005
CAPACITOR APPLICATION INFORMATION
CAPACITOR RECOMMENDATIONS FOR THE PTV08T250W POWER MODULE
The PTV08T250W is a state-of-the-art multi-phase power converter topology that uses three parallel switching
and filter inductor paths between the common input and output filter capacitors. The three paths share the load
current, operate at the same frequency, and are evenly displaced in phase.
With multiple switching paths the transient output current capability is significantly increased. This reduces the
amount of external output capacitance required to support a load transient. As a further benefit, the ripple
current, as seen by the input and output capacitors, is reduced in magnitude and effectively tripled in frequency.
Input Capacitor (Required)
The improved transient response of a multi-phase converter places increased burden on the transient capability
of the input power source. The size and value of the input capacitor is therefore determined by the converter’s
transient performance capability. The minimum amount of required input capacitance is 560 µF, with an RMS
ripple current rating of 300 mA. This minimum value assumes that the converter is supplied with a responsive,
low inductance input source. This source should have ample capacitive decoupling, and be distributed to the
converter via PCB power and ground planes.
For high-performance applications, or wherever the input source performance is degraded, 1000 µF of input
capacitance is recommended. The additional input capacitance above the minimum level insures an optimized
performance.
Ripple current (rms) rating, less than 100 mΩ of equivalent series resistance (ESR), and temperature are the
main considerations when selecting input capacitors. The ripple current reflected from the input of the
PTV08T250W module is moderate to low. Therefore, any good quality, computer-grade electrolytic capacitor has
an adequate ripple current rating.
Regular tantalum capacitors are not recommended for the input bus. These capacitors require a recommended
minimum voltage rating of 2 × (maximum dc voltage + ac ripple). This is standard practice to ensure reliability. No
tantalum capacitors were found with a sufficient voltage rating to meet this requirement. When the operating
temperature is below 0°C, the ESR of aluminum electrolytic capacitors increases. For these applications,
Os-Con, poly-aluminum, and polymer-tantalum types should be considered. Adding one or two ceramic
capacitors to the input attenuates high-frequency reflected ripple current.
TurboTrans Output Capacitor
The PTV08T250W requires a minimum output capacitance of 660 µF. The required capacitance above 660µF is
determined by actual transient deviation requirements.
TurboTrans allows the designer to optimize the capacitance load according to the system transient design
requirement. High quality, ultra-low ESR capacitors are required to maximize TurboTrans effectiveness.
Capacitors with a capacitance (µF) X ESR (mΩ) product of ≤ 10,000 mΩ×µF are required.
Working Example:
A bank of 6 identical capacitors, each with a capacitance of 680 µF and 5 mΩ ESR, has a C × ESR product of
3400 µF x mΩ (680 µF × 5 mΩ).
Using TurboTrans in conjunction with the high quality capacitors (capacitance (µF) × ESR (mΩ)) reduces the
overall capacitance requirement while meeting the minimum transient amplitude level.
Table 1 includes a preferred list of capacitors by type and vendor. See the Output Bus / TurboTrans column.
Note: See the TurboTrans Technology Application Notes within this document for selection of specific
capacitance.
Non-TurboTrans Output Capacitor
The PTV08T250W requires a minimum output capacitance of 660 µF. Non-TurboTrans applications must
observe minimum output capacitance ESR limits.
A combination of 200 µF of ceramic capacitors plus low ESR (15 mΩ to 30 mΩ) Os-Con electrolytic/tantalum
type capacitors can be used. When using Polymer tantalum types, tantalum type, or Oscon types only, the
8
PTV08T250W
www.ti.com
SLTS260B – OCTOBER 2005 – REVISED NOVEMBER 2005
CAPACITOR APPLICATION INFORMATION (continued)
capacitor ESR bank limit is 3 mΩ to 5 mΩ. (Note: no ceramic capacitors are required). This is necessary for the
stable operation of the regulator. Additional capacitance can be added to improve the module's performance to
load transients. High quality computer-grade electrolytic capacitors are recommended. Aluminum electrolytic
capacitors provide adequate decoupling over the frequency range, 2 kHz to 150 kHz, and are suitable when
ambient temperatures are above -20°C. For operation below -20°C, tantalum, ceramic, or Os-Con type
capacitors are necessary.
When using a combination of one or more non-ceramic capacitors, the calculated equivalent ESR should be no
lower than 2 mΩ (4 mΩ when calculating using the manufacturer’s maximum ESR values). A list of preferred
low-ESR type capacitors, are identified in Table 1.
Ceramic Capacitors
Above 150 kHz the performance of aluminum electrolytic capacitors is less effective. Multilayer ceramic
capacitors have very low ESR and a resonant frequency higher than the bandwidth of the regulator. They can be
used to reduce the reflected ripple current at the input as well as improve the transient response of the output.
When used on the output their combined ESR is not critical as long as the total value of ceramic capacitors, with
values between 10 µF and 100 µF, does not exceed 3000 µF (non-TurboTrans). In TurboTrans applications,
when ceramic capacitors are used on the output bus, total capacitance including bulk and ceramic types is not to
exceed 14,000 µF.
Tantalum, Polymer-Tantalum Capacitors
Tantalum type capacitors are only used on the output bus, and are recommended for applications where the
ambient operating temperature is less than 0°C. The AVX TPS series and Kemet capacitor series are suggested
over many other tantalum types due to their higher rated surge, power dissipation, and ripple current capability.
As a caution, many general-purpose tantalum capacitors have higher ESR, reduced power dissipation, and lower
ripple current capability. These capacitors are also less reliable due to their reduced power dissipation and surge
current ratings. Tantalum capacitors that have no stated ESR or surge current rating are not recommended for
power applications.
Capacitor Table
Table 1 identifies the characteristics of capacitors from a number of vendors with acceptable ESR and ripple
current (rms) ratings. The recommended number of capacitors required at both the input and output buses is
identified for each capacitor type.
This is not an extensive capacitor list. Capacitors from other vendors are available with comparable
specifications. Those listed are for guidance. The RMS ripple current rating and ESR (at 100 kHz) are critical
parameters necessary to ensure both optimum regulator performance and long capacitor life.
Designing for Fast Load Transients
The transient response of the dc/dc converter has been characterized using a load transient with a di/dt of
2.5 A/µs. The typical voltage deviation for this load transient is given in the Electrical Characteristics table using
the minimum required value of output capacitance. As the di/dt of a transient is increased, the response of a
converter’s regulation circuit ultimately depends on its output capacitor decoupling network. This is an inherent
limitation with any dc/dc converter once the speed of the transient exceeds its bandwidth capability.
If the target application specifies a higher di/dt or lower voltage deviation, the requirement can only be met with
additional low ESR ceramic capacitor decoupling. Generally, with 50% load steps at > 100 A/µs, adding multiple
10 µF ceramic capacitors, 3225 case size, plus 10 × 1 µF, including numerous high frequency ceramics
(≤ 0.1 µF) are all that is required to soften the transient higher frequency edges. Special attention is essential
with regards to location, types, and position of higher frequency ceramic and lower ESR bulk capacitors. DSP,
FPGA and ASIC vendors identify types, location and capacitance required for optimum performance of the high
frequency devices. The details regarding the PCB layout and capacitor/component placement are important at
these high frequencies. Low impedance buses and unbroken PCB copper planes with components located as
close to the high frequency processor are essential for optimizing transient performance. In many instances
additional capacitors may be required to insure and minimize transient aberrations.
9
PTV08T250W
www.ti.com
SLTS260B – OCTOBER 2005 – REVISED NOVEMBER 2005
CAPACITOR APPLICATION INFORMATION (continued)
Table 1. Input/Output Capacitors (1)
Capacitor Characteristics
Capacitor Vendor,
Type Series (Style)
Working Value
Voltage
(µF)
Quantity
Max.
ESR
at 100
kHz
Max
Ripple
Physical
Current at
Size (mm)
85°C
(Irms)
Output Bus
Input
Bus
No
TurboTrans
TurboTrans
(Cap
Type) (2)
Vendor Part No.
Panasonic
25 V
1000
0.043Ω
>1690 mA
16 × 15
1
≥ 2 (3)
N/R (4)
EEUFC1E102S
FC (Radial)
25 V
1800
0.029Ω
2205 mA
16 × 20
1
≥ 1 (3)
N/R (4)
EEUFC1E182
FC(SMD)
25 V
2200
0.028Ω
>2490 mA
18 × 21,5
1
≥ 1 (3)
N/R (4)
EEVFC1E222N
FK(SMD)
25 V
1000
0.060Ω
1100 mA
12,5×13,5
1
≥ 2 (5)
N/R (4)
EEVFK1V102Q
PTB(SMD) Polymer
Tantalum
6.3 V
330
0.025Ω
2600 mA
7,3x 4,3x
2.8
N/R (6)
≥ 2 ~ ≤ 4 (3)
C ≥ 2 (2)
LXZ, Aluminum (Radial)
25 V
680
0.068Ω
1050 mA
10 × 16
1
≥ 1 ~ ≤ 3 (3)
N/R (4)
PS,
Poly-Aluminum(Radial)
16 V
330
0.014Ω
5060 mA
10 × 12,5
2
≥2~≤3
B ≥ 2 (2)
16PS330MJ12
PXA, Poly-Aluminum
(SMD)
16 V
330
0.014Ω
5050 mA
10 × 12,2
2
≥2~≤3
B ≥ 2 (2)
PXA16VC331MJ12TP
PS,
Poly-Aluminum(Radial)
6.3 V
680
0.010Ω
5500 mA
10 × 12,5
N/R (6)
≥1~≤2
C ≥ 1 (2)
6PS680MJ12
PXA,
Poly-Aluminum(Radial)
6.3 V
680
0.010Ω
5500 mA
10 × 12,2
N/R (6)
≥1~≤2
C ≥ 1 (2)
PXA6.3VC681MJ12TP
Nichicon, Aluminum
25 V
560
0.060Ω
1060 mA
12,5 × 15
1
≥ 2 (3)
N/R (4)
UPM1E561MHH6
2 (3)
N/R (4)
UHD1C681MHR
UPM1V561MHH6
United Chemi-Con
HD (Radial)
25 V
680
0.038Ω
1430 mA
10 × 16
1
≥
PM (Radial)
35 V
560
0.048Ω
1360 mA
16 × 15
1
≥ 2 (3)
N/R (4)
4000 mA
7,3 L×4,3
W ×4,2H
N/R (6)
N/R (6)
B ≥ 2 (2)
Panasonic,
Poly-Aluminum:
(1)
(2)
(3)
(4)
(5)
(6)
(7)
10
2.0 V
390
0.005Ω
4PTB337MD6TER
LXZ25VB681M10X20LL
EEFSE0J391R (VO ≤ 1.6V) (7)
Capacitor Supplier Verification
Please verify availability of capacitors identified in this table. Capacitor suppliers may recommend alternative part numbers because of
limited availability or obsolete products. In some instances, the capacitor product life cycle may be in decline and have short-term
consideration for obsolescence.
RoHS, Lead-free and Material Details
See the capacitor suppliers regarding material composition, RoHS status, lead-free status, and manufacturing process requirements.
Component designators or part number deviations can occur when material composition or soldering requirements are updated.
Required capacitors with TurboTrans. See the TransTrans Application information for Capacitor Selection
Capacitor Type Groups by ESR (Equivalent Series Resistance) :
•
Type A = (100 < capacitance × ESR ≤ 1000)
•
Type B = (1,000 < capacitance × ESR ≤ 5,000)
•
Type C = (5,001 < capacitance × ESR ≤ 10,000)
Total bulk nonceramic capacitors on the output bus with ESR of ≥ 15mΩ to ≤ 30mΩ requires an additional ≥ 200 µF of ceramic
capacitor.
Aluminum Electrolytic capacitor not recommended for the TurboTrans due to higher ESR × capacitance products. Aluminum and higher
ESR capacitors can be used in conjunction with lower ESR capacitance.
Output bulk capacitor's maximum ESR is ≥ 30 mΩ. Additional ceramic capacitance of ≥ 200 µF is required.
N/R – Not recommended. The voltage rating does not meet the minimum operating limits.
The voltage rating of this capacitor only allows it to be used for output voltage that is equal to or less than 80% of the working voltage.
PTV08T250W
www.ti.com
SLTS260B – OCTOBER 2005 – REVISED NOVEMBER 2005
CAPACITOR APPLICATION INFORMATION (continued)
Table 1. Input/Output Capacitors (continued)
Capacitor Characteristics
Capacitor Vendor,
Type Series (Style)
Working Value
Voltage
(µF)
Max.
ESR
at 100
kHz
Quantity
Max
Ripple
Physical
Current at
Size (mm)
85°C
(Irms)
Output Bus
Input
Bus
No
TurboTrans
TurboTrans
(Cap
Type) (2)
C ≥ 1 (9)
4TPE680MF (VO ≤ 2.8V) (10)
2R5TPE470M7 (VO ≤ 1.8V) (10)
2R5TPD1000M5(VO ≤1.8V) (10)
Vendor Part No.
Sanyo
TPE, Poscap (SMD)
TPE Poscap(SMD)
TPD Poscap (SMD)
4V
2.5 V
2.5 V
680
470
1000
0.015Ω
0.007Ω
0.005Ω
3900 mA
7,3 × 4,3
N/R (8)
≥1~≤3
4400 mA
7,3 × 4,3
N/R (8)
≥1≤2
B≥
2 (9)
6100 mA
7,3 × 4,3
N/R (8)
≤1
B≥
1 (9)
SA, Os-Con (Radial)
16 V
1000
0.015Ω
>9700 mA
16 × 26
1
≥1~≤3
N/R (11)
SP Oscon ( Radial)
10 V
470
0.015
>4500 mA
10 × 11,5
N/R (8)
≥1~≤3
C ≥ 2 (9)
10SP470M
SEPC, Os-Con (Radial)
16 V
330
0.016Ω
>4700 mA
10 × 12,7
2
≥2~≤3
B ≥ 2 (9)
16SVP330M
SVPA, Os-Con (SMD)
6.3 V
820
0.012Ω
4700 mA
8 × 11,9
N/R (8)
≥ 1 ~ ≤ 2 (12)
C ≥ 1 (9) (12)
6SVPC820M
AVX, Tantalum, Series III
TPM Multianode
6.3 V
6.3 V
680
470
0.035Ω
0.018Ω
>2400 mA
>3800 mA
7,3 L
× 4,3 W
× 4,1 H
N/R (8)
N/R (8)
≥ 2 ~ ≤ 7 (12)
≥ 2 ~ ≤ 3 (12)
N/R (11)
C ≥ 2 (9) (12)
TPSE477M010R0045
TPME687M006#0018
TPS Series III (SMD)
4V
1000
0.035Ω
2405
7,3 L × 5,7
W
N/R (8)
≥ 2 ~ ≤ 7 (12)
N/R (11)
TPSV108K004R0035
(VO ≤ 2.2V) (10)
Kemet, Poly-Tantalum
6.3 V
470
0.040Ω
2000 mA
4,3 W
N/R (8)
≥ 2 ~ ≤ 7 (12)
N/R (11)
T520X337M010AS
T520 (SMD)
6.3 V
330
0.015Ω
>3800 mA
× 7,3 L
N/R (8)
≥2~≤3
B ≥ 2 (9)
T530X337M010AS
T530 (SMD)
4V
680
0.005Ω
7300 mA
×4H
N/R (8)
≤1
B ≥ 1 (9)
T530X687M004ASE005
(VO ≤ 3.5V) (10)
T530 (SMD)
2.5 V
1000
0.005Ω
7300 mA
4,3 w ×
7,3 L
N/R (8)
≤1
B ≥ 1 (9)
T530X108M2R5ASE005
(VO ≤ 2.0V) (10)
594D, Tantalum (SMD)
6.3 V
1000
0.030Ω
2890 mA
7,2L ×5,7
W ×4,1H
N/R (8)
≥1~≤6
N/R (11)
594D108X06R3R2TR2T
94SA, Os-con (Radial)
16 V
1000
0.015Ω
9740 mA
16 × 25
1
≥1~≤3
N/R (11)
94SA108X0016HBP
94SVP Os-Con(SMD)
16 V
330
0.017Ω
>4500 mA
10 × 12,7
2
≥2~≤3
C ≥ 1 (9)
94SVP827X06R3F12
Kemet, Ceramic X5R
(SMD)
16 V
10
0.002Ω
–
3225
1
≥ 1 (13)
A (9)
C1210C106M4PAC
6.3 V
47
0.002Ω
N/R (8)
≥ 1 (13)
A (9)
C1210C476K9PAC
0.002Ω
N/R (8)
≥
1 (13)
A (9)
GRM32ER60J107M
N/R (8)
≥ 1 (13)
A (9)
GRM32ER60J476M
1 (13)
A (9)
GRM32ER61E226K
16SA1000M
Vishay-Sprague
Murata, Ceramic X5R
(SMD)
TDK, Ceramic X5R (SMD)
(8)
(9)
(10)
(11)
(12)
(13)
6.3 V
100
6.3 V
47
–
3225
25 V
22
1
≥
16 V
10
1
≥ 1 (13)
A (9)
GRM32DR61C106K
6.3 V
100
N/R (8)
≥ 1 (13)
A (9)
C3225X5R0J107MT
6.3 V
47
N/R (8)
≥ 1 (13)
A (9)
C3225X5R0J476MT
16 V
10
1
≥ 1 (13)
A (9)
C3225X5R1C106MT0
16 V
22
1
≥ 1 (13)
A (9)
C3225X5R1C226MT
0.002Ω
–
3225
N/R – Not recommended. The voltage rating does not meet the minimum operating limits.
Required capacitors with TurboTrans. See the TransTrans Application information for Capacitor Selection
Capacitor Type Groups by ESR (Equivalent Series Resistance) :
•
Type A = (100 < capacitance × ESR ≤ 1000)
•
Type B = (1,000 < capacitance × ESR ≤ 5,000)
•
Type C = (5,001 < capacitance × ESR ≤ 10,000)
The voltage rating of this capacitor only allows it to be used for output voltage that is equal to or less than 80% of the working voltage.
Aluminum Electrolytic capacitor not recommended for the TurboTrans due to higher ESR × capacitance products. Aluminum and higher
ESR capacitors can be used in conjunction with lower ESR capacitance.
Total bulk nonceramic capacitors on the output bus with ESR of ≥ 15mΩ to ≤ 30mΩ requires an additional ≥ 200 µF of ceramic
capacitor.
Maximum ceramic capacitance on the output bus is ≤ 3000 µF. Any combination of the ceramic capacitor values is limited to 3000 µF
for non-TurboTrans applications. The total capacitance is limited to 14,000 µF which includes all ceramic and non-ceramic types.
11
PTV08T250W
www.ti.com
SLTS260B – OCTOBER 2005 – REVISED NOVEMBER 2005
TurboTrans™ Technology
TurboTrans technology is a feature introduced in the T2 generation of the PTH/PTV family of power modules.
TurboTrans optimizes the transient response of the regulator with added external capacitance using a single
external resistor. The benefits of this technology include: reduced output capacitance, minimized output voltage
deviation following a load transient, and enhanced stability when using ultra-low ESR output capacitors. The
amount of output capacitance required to meet a target output voltage deviation is reduced with TurboTrans
activated. Likewise, for a given amount of output capacitance, with TurboTrans engaged, the amplitude of the
voltage deviation following a load transient is reduced. Applications requiring tight transient voltage tolerances
and minimized capacitor footprint area benefit from this technology.
TurboTrans™ Selection
Using TurboTrans requires connecting a resistor, RTT, between the +Sense pin (pin 1) and the TurboTrans pin
(pin 9). The value of the resistor directly corresponds to the amount of output capacitance added. All T2 products
require a minimum value of output capacitance whether or not TurboTrans is used. For the PTV08T250W, the
minimum required capacitance is 660 µF. When using TurboTrans, capacitors with a capacitance X ESR product
below 10,000 µFxmΩ are required. (Multiply the capacitance (in µF) by the ESR (in mΩ) to determine the
capacitance X ESR product.) See the Capacitor Selection section of the data sheet for a variety of capacitors
that meet this criteria.
Figure 9 through Figure 14 show the amount of output capacitance required to meet a desired transient voltage
deviation with and without TurboTrans for several capacitor types; Type A (e.g. ceramic), Type B
(e.g. polymer-tantalum), and Type C (e.g. OS-CON). To calculate the proper value of RTT, first determine the
required transient voltage deviation limits and magnitude of the transient load step. Next, determine the type of
output capacitors to be used. (If more than one type of output capacitor is used, select the capacitor type that
makes up the majority of the total output capacitance.) Knowing this information, use the chart in Figure 9,
through Figure 14, that corresponds to the capacitor type selected. To use the chart, begin by dividing the
maximum voltage deviation limit (in mV) by the magnitude of the load step (in Amps). This gives a mV/A value.
Find this value on the Y-axis of the appropriate chart. Read across the graph to the With TurboTrans plot. From
this point, read down to the X-axis which lists the minimum required capacitance, CO, to meet the transient
voltage deviation. The required RTT resistor value can then be calculated using Equation 1 or selected from the
TurboTrans table. The TurboTrans tables include both the required output capacitance and the corresponding
RTT values to meet several values of transient voltage deviation for 25% (12.5 A), 50% (25 A), and 75% (37.5 A)
output load steps.
The chart can also be used to determine the achievable transient voltage deviation for a given amount of output
capacitance. Selecting the amount of output capacitance along the X-axis, reading up to the With TurboTrans
curve, and then over to the Y-axis, gives the transient voltage deviation limit for that value of output capacitance.
The required RTT resistor value can be calculated using Equation 1 or selected from the TurboTrans table.
As an example, look at a 12-V input application requiring a 75 mV deviation during a 25 A, 50% load transient. A
majority of 330 µF, 10 mΩ (C X ESR = 3300 µFxmΩ) output capacitors are used. Use the 12 V, Type B capacitor
chart, Figure 11. Dividing 75 mV by 25 A gives 3 mV/A transient voltage deviation per amp of transient load step.
Select 3 mV/A on the Y-axis and read across to the With TurboTrans plot. Following this point down to the X-axis
gives us a minimum required output capacitance of approximately 2000 µF. The required RTT resistor value for
2000 µF can then be calculated or selected from Table 1. The required RTT resistor is approximately 7.5 kΩ.
To see the benefit of TurboTrans, follow the 3 mV/A marking across to the Without TurboTrans plot. Following
that point down shows that a minimum of 5800 µF of output capacitance is required to meet the same deviation
limit. This is the benefit of TurboTrans. A typical TurboTrans application schematic and TurboTrans waveforms
are shown in Figure 15 and Figure 16.
12
PTV08T250W
www.ti.com
SLTS260B – OCTOBER 2005 – REVISED NOVEMBER 2005
Type A Capacitor
12 V Input
6
10
9
8
7
5
6
Without TurboTrans
4
Transient - mV/A
With TurboTrans
3
2
Without TurboTrans
5
With TurboTrans
4
3
2
VI = 8 V
VI = 12 V
1
C - Capacitance - mF
5000
6000
7000
8000
9000
10000
4000
3000
600
700
800
900
1000
5000
6000
7000
8000
9000
10000
4000
3000
2000
600
700
800
900
1000
1
2000
Transient - mV/A
8
7
Type A Capacitor
8 V Input
C - Capacitance - mF
Figure 9. Cap Type A, 100 ≤ C(µF)xESR(mΩ) ≤ 1000, (e.g.
Ceramic)
Figure 10. Cap Type A, 100 ≤ C(µF)ESR(mΩ) ≤ 1000, (e.g.
Ceramic)
Table 2. Type A TurboTrans CO Values & Required RTT Selection Table
Transient Voltage Deviation (mV)
12 V Input
8 V Input
25%
load step
(12.5 A)
50%
load step
(25 A)
75%
load step
(37.5 A)
CO
Minimum Required
Output Capacitance
(µF)
RTT
Required
TurboTrans
Resistor (Ω)
CO
Minimum Required
Output Capacitance
(µF)
RTT
Required
TurboTrans
Resistor (Ω)
100
200
300
700
90
180
270
820
499 k
950
66.5 k
130 k
1100
42.2 k
80
160
240
70
140
210
960
63.4 k
1250
27.4 k
1200
34.8 k
1500
60
120
180
17.4 k
1450
19.6 k
1800
10.5 k
50
100
40
80
150
1850
9.76 k
2300
4.99 k
120
2600
3.32 k
3100
35
866
70
105
3100
845
3800
0
30
60
90
6400
0
7700
0
RTT Resistor Selection
The TurboTrans resistor value, RTT can be determined from the TurboTrans programming equation, see
Equation 1:
1 - (CO / 3300)
RTT = 40 ´
kW
5 x (CO / 3300) - 1
(1)
Where CO is the total output capacitance in µF. CO values greater than or equal to 3300 µF require RTT to be a
short, 0Ω.
13
PTV08T250W
www.ti.com
SLTS260B – OCTOBER 2005 – REVISED NOVEMBER 2005
Type B Capacitor
12 V Input
Type B Capacitor
8 V Input
8
7
8
7
6
6
Without TurboTrans
5
5
4
Transient - mV/A
3
With TurboTrans
2
4
With TurboTrans
3
2
VI = 12 V
VI = 8 V
C - Capacitance - mF
5000
6000
7000
8000
9000
10000
4000
3000
600
700
800
900
1000
5000
6000
7000
8000
9000
10000
3000
2000
4000
1
600
700
800
900
1000
1
2000
Transient - mV/A
Without TurboTrans
C - Capacitance - mF
Figure 11. Cap Type B, 1000 ≤ C(µF)xESR(mΩ) ≤ 5000,
(e.g. Polymer-Tantalum)
Figure 12. Cap Type B, 1000 ≤ C(µF)xESR(mΩ) ≤ 5000,
(e.g. Polymer-Tantalum)
Table 3. Type B TurboTrans CO Values & Required RTT Selection Table
Transient Voltage Deviation (mV)
12 V Input
8 V Input
25%
load step
(12.5 A)
50%
load step
(25 A)
75%
load step
(37.5 A)
CO
Minimum Required
Output Capacitance
(µF)
RTT
Required
TurboTrans
Resistor (Ω)
CO
Minimum Required
Output Capacitance
(µF)
RTT
Required
TurboTrans
Resistor (Ω)
90
180
270
660
open
660
open
80
160
240
660
open
820
133 k
70
140
210
660
open
1000
56.2
60
120
180
880
95.3 k
1250
28.0 k
50
100
150
1200
30.9 k
1650
13.7 k
40
80
120
1800
10.5 k
2300
5.11 k
35
70
105
2300
4.99 k
2800
1.96 k
30
60
90
3050
909
3900
0
25
50
75
6900
0
9900
0
RTT Resistor Selection
The TurboTrans resistor value, RTT can be determined from the TurboTrans programming equation, see
Equation 2:
1 - (CO / 3300)
RTT = 40 ´
kW
5 x (CO / 3300) - 1
(2)
Where CO is the total output capacitance in µF. CO values greater than or equal to 3300 µF require RTT to be a
short, 0Ω.
14
PTV08T250W
www.ti.com
SLTS260B – OCTOBER 2005 – REVISED NOVEMBER 2005
Type C Capacitor
12 V Input
Type C Capacitor
8 V Input
8
7
8
7
6
6
Without TurboTrans
5
5
4
Transient - mV/A
3
With TurboTrans
2
4
With TurboTrans
3
2
VI = 12 V
VI = 8 V
C - Capacitance - mF
5000
6000
7000
8000
9000
10000
4000
3000
600
700
800
900
1000
5000
6000
7000
8000
9000
10000
3000
2000
4000
1
600
700
800
900
1000
1
2000
Transient - mV/A
Without TurboTrans
C - Capacitance - mF
Figure 13. Cap Type C, 5000 ≤ C(µF)xESR(mΩ) ≤ 10,000,
(e.g. Os-Con)
Figure 14. Cap Type C, 5000 ≤ C(µF)xESR(mΩ) ≤ 10,000,
(e.g. Os-Con)
Table 4. Type C TurboTrans CO Values & Required RTT Selection Table
Transient Voltage Deviation (mV)
12 V Input
8 V Input
25%
load step
(12.5 A)
50%
load step
(25 A)
75%
load step
(37.5 A)
CO
Minimum Required
Output Capacitance
(µF)
RTT
Required
TurboTrans
Resistor (Ω)
CO
Minimum Required
Output Capacitance
(µF)
RTT
Required
TurboTrans
Resistor (Ω)
80
160
240
660
open
750
232 k
70
140
210
660
open
950
64.9 k
60
120
180
750
226 k
1200
31.6 k
50
100
150
1000
54.9 k
1600
14.7 k
40
80
120
1450
18.7 k
2300
4.87 k
35
70
105
1800
10.5 k
2800
1.87 k
30
60
90
2350
4.53 k
3900
0
25
50
75
3200
316
10800
0
RTT Resistor Selection
The TurboTrans resistor value, RTT can be determined from the TurboTrans programming equation, see
Equation 3:
1 - (CO / 3300)
RTT = 40 ´
kW
5 x (CO / 3300) - 1
(3)
Where CO is the total output capacitance in µF. CO values greater than or equal to 3300 µF require RTT to be a
short, 0Ω.
15
PTV08T250W
www.ti.com
SLTS260B – OCTOBER 2005 – REVISED NOVEMBER 2005
TurboTrans
15
AutoTrack
TurboTrans
+Sense 1
3
6,7
VI
13,14
20,21
VI
RTT
5.76 k
9
PTH08T250W
16 Inhibit /
Prog UVLO
VO
-Sense
GND
12 18 19
GND
4
5 11
+ Sense
VO
10
17
2
V OAdj
8
CI
L
O
A
D
COTT
560 mF
(Required)
RSET
1%
0.05 W
2200 mF
-Sense
GND
GND
Figure 15. Typical TurboTrans Application Schematic
VTR = 100 mV/div
CO = 2200 mF
No Turbo Trans
RTT = open
CO = 2200 mF
W/ Turbo Trans
RTT = 5.76 kW
Transient Load
Step = 25 A
t = 100 ms/div
Figure 16. Typical TurboTrans Waveforms
16
PTV08T250W
www.ti.com
SLTS260B – OCTOBER 2005 – REVISED NOVEMBER 2005
ADJUSTING THE OUTPUT VOLTAGE OF THE PTV08T250W WIDE-OUTPUT ADJUST POWER
MODULE
The VO Adjust control (pin 8) sets the output voltage of the PTV08T250W product. The adjustment range is from
0.8 V to 3.6 V. The adjustment method requires the addition of a single external resistor, RSET, that must be
connected directly between the VO Adjust and GND pins. Table 5 gives the preferred value of the external
resistor for a number of standard voltages, along with the actual output voltage that this resistance value
provides.
For other output voltages, the value of the required resistor can either be calculated using Equation 4, or by
selecting from the range of values given in Table 6. Figure 17 shows the placement of the required resistor.
RSET = 30.1 x
0.8
( VO - 0.8)
- 7.135 kW
(4)
Table 5. Standard Values of RSET for Common Output
Voltages
PTV08T250W
VO (Required)
RSET
VO (Actual)
3.3 V
2.49 kΩ
3.303 V
2.5 V
6.98 kΩ
2.5 V
2.0 V
13.0 kΩ
1.997 V
1.8 V
16.9 kΩ
1.796 V
1.5 V
27.4 kΩ
1.498 V
1.2 V
53.6 kΩ
1.202 V
1.0 V
113 kΩ
1V
0.8 V
Open
0.8 V
+Sense
+Sense
1
3
PTV08T250W
VO
-Sense
GND
GND
12 18 19 4 5 11
VO
10
17
2
VOAdj
8
CO1
RSET
1%
0.05 W
CO2
-Sense
GND
Figure 17. VO Adjust Resistor Placement
•
•
A 0.05-W rated resistor may be used. The tolerance should be 1%, and the temperature stability, 100
ppm/°C (or better). Place the resistor as close to the regulator as possible. Connect the resistor directly
between pin 8 and nearest GND pin (pin 11) using dedicated PCB traces.
Never connect capacitors from VO Adjust to either GND or VO. Any capacitance added to the VO Adjust pin
affects the stability of the regulator.
17
PTV08T250W
www.ti.com
SLTS260B – OCTOBER 2005 – REVISED NOVEMBER 2005
Table 6. Output Voltage Set-Point Resistor Values
VO
RSET
VO
RSET
VO
RSET
0.8
Open
1.375
34.8 kΩ
2.4
7.87 kΩ
0.825
953 kΩ
1.4
33.2 kΩ
2.45
7.50 kΩ
0.85
475 kΩ
1.425
31.6 kΩ
2.5
6.98 kΩ
0.875
316 kΩ
1.45
30.1 kΩ
2.55
6.65 kΩ
0.9
232 kΩ
1.475
28.7 kΩ
2.6
6.19 kΩ
0.925
187 kΩ
1.5
27.4 kΩ
2.65
5.90 kΩ
0.95
154 kΩ
1.55
24.9 kΩ
2.7
5.49 kΩ
0.975
130 kΩ
1.6
22.6 kΩ
2.75
5.23 kΩ
1
113 kΩ
1.65
21.0 kΩ
2.8
4.87 kΩ
1.025
100 kΩ
1.7
19.6 kΩ
2.85
4.64 kΩ
1.05
88.7 kΩ
1.75
18.2 kΩ
2.9
4.32 kΩ
1.075
80.6 kΩ
1.8
16.9 kΩ
2.95
4.02 kΩ
1.1
73.2 kΩ
1.85
15.8 kΩ
3
3.83 kΩ
1.125
66.5 kΩ
1.9
14.7 kΩ
3.05
3.57 kΩ
1.15
61.9 kΩ
1.95
13.7 kΩ
3.1
3.32 kΩ
1.175
57.6 kΩ
2
13.0 kΩ
3.15
3.09 kΩ
1.2
53.6 kΩ
2.05
12.1 kΩ
3.2
2.87 kΩ
1.225
49.9 kΩ
2.1
11.3 kΩ
3.25
2.67 kΩ
1.25
46.4 kΩ
2.15
10.7 kΩ
3.3
2.49 kΩ
1.275
43.2 kΩ
2.2
10.0 kΩ
3.35
2.32 kΩ
1.3
41.2 kΩ
2.25
9.53 kΩ
3.4
2.10 kΩ
1.325
38.3 kΩ
2.3
8.87 kΩ
3.5
1.78 kΩ
1.35
36.5 kΩ
2.35
8.45 kΩ
3.6
1.47 kΩ
ADJUSTING THE UNDERVOLTAGE LOCKOUT (UVLO) OF THE PTV08T250W POWER MODULES
The PTV08T250W power modules incorporate an input undervoltage lockout (UVLO). The UVLO feature
prevents the operation of the module until there is sufficient input voltage to produce a valid output voltage. This
enables the module to provide a clean, monotonic powerup for the load circuit, and also limits the magnitude of
current drawn from the regulator’s input source during the power-up sequence.
The UVLO characteristic is defined by the ON threshold (VTHD) and hysterisis (VHYS) voltages. Below the ON
threshold, the Inhibit control is overridden, and the module does not produce an output. The hysterisis voltage is
the difference between the ON and OFF threshold voltages. It ensures a clean power-up, even when the input
voltage is rising slowly. The hysterisis prevents start-up oscillations, which can occur if the input voltage droops
slightly when the module begins drawing current from the input source.
UVLO Adjustment
The UVLO feature of the PTV08T250W module allows for limited adjustment of both the on threshold and
hysterisis voltages. The adjustment is made via the UVLO Prog control pin. When the UVLO Prog pin is left open
circuit, the ON threshold and hysterisis voltages are internally set to their default values. The ON threshold has a
nominal voltage of 7.5 V, and the hysterisis 1 V. This ensures that the module produces a regulated output when
the minimum input voltage is applied (see specifications). The combination correlates to an OFF threshold of
approximately 6.5 V. The adjustments are limited. The ON threshold can only be adjusted higher, and the
hysterisis voltage can only be reduced in magnitude.
The ON threshold might need to be raised if the module is powered from a tightly regulated 12-V bus. This
prevents it from operating if the input bus fails to completely rise to its specified regulation voltage. The hysterisis
should not be changed unless absolutely necessary. The hysterisis ensures that the module exhibits a clean
startup. Therefore, adjustment of the hysterisis should only be considered if there is a system requirement to
specifically set the off threshold voltage (in addition to the on threshold). Depending on the load regulation of the
input source, the hysterisis should not be adjusted below 0.5 V without careful consideration.
18
PTV08T250W
www.ti.com
SLTS260B – OCTOBER 2005 – REVISED NOVEMBER 2005
Adjustment Method
The resistors, RTHD and RHYS (see Figure 18), provide the adjustment of the on-threshold and hysterisis voltages.
RTHD connects between the UVLO Prog control pin and GND, and RHYS is connected between the UVLO Prog
and VI. RTHD alone is used to adjust the on-threshold voltage higher. However, to adjust the hystersis to a lower
value requires both the RHYS and RTHD resistors to be placed in the circuit.
The recommended adjustment method requires that any change to the hysterisis be determined first. If the
hysterisis is changed, then a value for RTHD must also be calculated. This is irrespective of whether a change is
required to the value of VTHD. If there is no change to VHYS, then a resistor should not be placed in the RHYS
location. RHYS should then be assigned an infinite value for calculating the value of RTHD.
6, 7
VI
13, 14
20, 21
RHYS
VI
PTV08T250W
16 Inhibit/
UVLO Prog
GND
4
CI
5
11
RTHD
GND
Figure 18. UVLO Program Resistor Placement
Hysterisis Adjust
The hysterisis voltage, VHYS, is the difference between the ON and OFF threshold values. The default value is 1
V and it can only be adjusted to a lower value.
CAUTION: Caution should be used when changing the hysterisis voltage to a lower value, as it could induce
start-up oscillations.
Any change in the hysterisis voltage requires both RHYS and RTHD resistors be in place. Adding RHYS alone does
not have the desired effect. The value for RHYS must first be calculated using Equation 5, and then be used to
determine a value for RTHD, using Equation 6.
R HYS =
2 6 .1 ´ V H Y S
kΩ
0 .3 6 5 ´ (1 - V H Y S )
(5)
Threshold Adjust
Equation 6 determines the value of RTHD required to adjust VTHD to a new value. The default value is 7.5 V, and it
may only be adjusted to a higher value. If the hysterisis value has been adjusted, then a value for RTHD must also
be calculated. (This is irrespective of whether VTHD is being adjusted.) If there has been no adjustment for the
hystersis voltage, the term 1/RHYS in Equation 6, may be assigned the value, 0.
R THD =
39.2
kΩ
39.2[(1/R HYS + 0.014)(VTHD /2.5 - 1) - 0.0027] - 1
(6)
Calculated Values
Table 7 shows a matrix of standard resistor values for RHYS and RTHD, for different options of the on-threshold
(VTHD) and hysterisis (VHYS) voltages. For most applications, only the on-threshold voltage should need to be
adjusted. In this case select only a value for RTHD from far right-hand column.
19
PTV08T250W
www.ti.com
SLTS260B – OCTOBER 2005 – REVISED NOVEMBER 2005
The hysterisis should only be adjusted if there is a specific requirement to independently adjust the off-threshold,
separately from the on-threshold voltage. In this case, a value for both RHYS and RTHD must be selected from
Table 7. This is irrespective of whether the on-threshold voltage is being adjusted.
Table 7. Calculated Values of RHYS and RTHD, for Various Values of VHYS and
VTHD
VTHD
VHYS
0.5 V
RHYS
0.6 V
0.7 V
0.8 V
0.9 V
1V
(default)
71.5 kΩ
107 kΩ
165 kΩ
287 kΩ
649 kΩ
N/A
8V
30.1 kΩ
43.2 kΩ
63.4 kΩ
97.6 kΩ
169 kΩ
402 kΩ
8.5 V
25.5 kΩ
36.5 kΩ
51.1 kΩ
73.2 kΩ
110 kΩ
187 kΩ
9V
23.2 kΩ
30.9 kΩ
42.2 kΩ
57.6 kΩ
82.5 kΩ
124 kΩ
9.5 V
20 kΩ
27.4 kΩ
36.5 kΩ
48.7 kΩ
64.9 kΩ
90.9 kΩ
18.2 kΩ
24.3 kΩ
31.6 kΩ
41.2 kΩ
54.9 kΩ
73.2 kΩ
10.5 V
16.2 kΩ
21.5 kΩ
28 kΩ
36.5 kΩ
46.4 kΩ
60.4 kΩ
10 V
RTHD
11 V
15 kΩ
19.6 kΩ
25.5 kΩ
32.4 kΩ
41.2 kΩ
52.3 kΩ
11.5 V
14 kΩ
18.2 kΩ
23.2 kΩ
28 kΩ
36.5 kΩ
45.3 kΩ
12 V
12.7 kΩ
16.5 kΩ
21 kΩ
26.1 kΩ
32.4 kΩ
40.2 kΩ
FEATURES OF THE PTH/PTV FAMILY OF NONISOLATED WIDE OUTPUT ADJUST POWER
MODULES
Soft-Start Power Up
The Auto-Track feature allows the power-up of multiple PTH/PTV modules to be directly controlled from the
Track pin. However in a stand-alone configuration, or when the Auto-Track feature is not being used, the Track
pin should be directly connected to the input voltage, VI (see Figure 19).
15
Track
6, 7
VI
13, 14
20, 21
CI
VI
PTV08T250W
GND
4
5
11
GND
Figure 19. Soft-Start Power-Up Application Circuit
When the Track pin is connected to the input voltage the Auto-Track function is permanently disengaged. This
allows the module to power up entirely under the control of its internal soft-start circuitry. When power up is
under soft-start control, the output voltage rises to the set-point at a monotonic and quicker rate.
From the moment a valid input voltage is applied, the soft-start control introduces a short time delay (typically
8 ms–15 ms) before allowing the output voltage to rise.
20
PTV08T250W
www.ti.com
SLTS260B – OCTOBER 2005 – REVISED NOVEMBER 2005
VI (5 V/div)
VO (1 V/div)
II (2 A/div)
t - Time = 4 ms/div
Figure 20. Power-Up Waveform
The output then progressively rises to the module’s setpoint voltage. Figure 20 shows the soft-start power-up
characteristic of the PTV08T250W operating from a 12-V input bus and configured for a 3.3-V output. The
waveforms were measured with a 20-A constant current load and the Auto-Track feature disabled. The initial rise
in input current when the input voltage first starts to rise is the charge current drawn by the input capacitors.
Power-up is complete within 25 ms.
Overcurrent Protection
For protection against load faults, all modules incorporate output overcurrent protection. Applying a load that
exceeds the regulator’s overcurrent threshold causes the regulated output to shut down. Following shutdown, a
module periodically attempts to recover by initiating a soft-start power-up. This is described as a hiccup mode of
operation, whereby the module continues in a cycle of successive shutdown and power up until the load fault is
removed. During this period, the average current flowing into the fault is significantly reduced. Once the fault is
removed, the module automatically recovers and returns to normal operation.
Overtemperature Protection (OTP)
A thermal shutdown mechanism protects the module’s internal circuitry against excessively high temperatures. A
rise in the internal temperature may be the result of a drop in airflow, or a high ambient temperature. If the
internal temperature exceeds the OTP threshold, the module’s Inhibit control is internally pulled low. This turns
the output off. The output voltage drops as the external output capacitors are discharged by the load circuit. The
recovery is automatic, and begins with a soft-start power up. It occurs when the sensed temperature decreases
by about 10°C below the trip point.
The overtemperature protection is a last resort mechanism to prevent thermal stress to the regulator.
Operation at or close to the thermal shutdown temperature is not recommended and reduces the long-term
reliability of the module. Always operate the regulator within the specified safe operating area (SOA) limits for
the worst-case conditions of ambient temperature and airflow.
Output On/Off Inhibit
For applications requiring output voltage on/off control, the PTV08T250W incorporates an output Inhibit control
pin. The inhibit feature can be used wherever there is a requirement for the output voltage from the regulator to
be turned off.
The power modules function normally when the Inhibit pin is left open-circuit, providing a regulated output
whenever a valid source voltage is connected to VI with respect to GND.
21
PTV08T250W
www.ti.com
SLTS260B – OCTOBER 2005 – REVISED NOVEMBER 2005
Figure 21 shows the typical application of the inhibit function. Note the discrete transistor (Q1). The Inhibit input
has its own internal pull-up to a potential of 5 V. The input is not compatible with TTL logic devices and should
not be tied to VI. An open-collector (or open-drain) discrete transistor is recommended for control.
6, 7
VI
13, 14
20, 21
VI
CI
PTV08T250W
16 Inhibit/
UVLO
GND
4
1 = Inhibit
5
11
Q1
BSS138
GND
Figure 21. On/Off Inhibit Control Circuit
Turning Q1 on applies a low voltage to the Inhibit control pin and disables the output of the module. If Q1 is then
turned off, the module executes a soft-start power-up sequence. A regulated output voltage is produced within 25
ms. Figure 22 shows the typical rise in both the output voltage and input current, following the turn-off of Q1. The
turn off of Q1 corresponds to the rise in the waveform, Q1 VDS. The waveforms were measured with a 20-A
constant current load.
VINH (2 V/div)
VO (1 V/div)
II (2 A/div)
t - Time = 2 ms/div
Figure 22. Power-Up Response from Inhibit Control
22
PTV08T250W
www.ti.com
SLTS260B – OCTOBER 2005 – REVISED NOVEMBER 2005
Remote Sense
Products with this feature incorporate one or two remote sense pins. Remote sensing improves the load
regulation performance of the module by allowing it to compensate for any IR voltage drop between its output
and the load. An IR drop is caused by the high output current flowing through the small amount of pin and trace
resistance.
To use this feature simply connect the Sense pins to the corresponding output voltage node, close to the load
circuit. If a sense pin is left open-circuit, an internal low-value resistor (15-Ω or less) connected between the pin
and the output node, ensures the output remains in regulation.
With the sense pin connected, the difference between the voltage measured directly between the VO and GND
pins, and that measured at the Sense pins, is the amount of IR drop being compensated by the regulator. This
should be limited to a maximum of 0.3 V.
The remote sense feature is not designed to compensate for the forward drop of nonlinear or frequency
dependent components that may be placed in series with the converter output. Examples include OR-ing
diodes, filter inductors, ferrite beads, and fuses. When these components are enclosed by the remote sense
connection they are effectively placed inside the regulation control loop, which can adversely affect the
stability of the regulator.
23
PTV08T250W
www.ti.com
SLTS260B – OCTOBER 2005 – REVISED NOVEMBER 2005
Auto-Track™ Function
The Auto-Track function is unique to the PTH/PTV family, and is available with all POLA products. Auto-Track
was designed to simplify the amount of circuitry required to make the output voltage from each module power up
and power down in sequence. The sequencing of two or more supply voltages during power up is a common
requirement for complex mixed-signal applications that use dual-voltage VLSI ICs such as the TMS320™ DSP
family, microprocessors, and ASICs.
How Auto-Track™ Works
Auto-Track works by forcing the module output voltage to follow a voltage presented at the Track control pin (1).
This control range is limited to between 0 V and the module set-point voltage. Once the track-pin voltage is
raised above the set-point voltage, the module output remains at its set-point (2). As an example, if the Track pin
of a 2.5-V regulator is at 1 V, the regulated output is 1 V. If the voltage at the Track pin rises to 3 V, the regulated
output does not go higher than 2.5 V.
When under Auto-Track control, the regulated output from the module follows the voltage at its Track pin on a
volt-for-volt basis. By connecting the Track pin of a number of these modules together, the output voltages follow
a common signal during power up and power down. The control signal can be an externally generated master
ramp waveform, or the output voltage from another power supply circuit (3). For convenience, the Track input
incorporates an internal RC-charge circuit. This operates off the module input voltage to produce a suitable rising
waveform at power up.
Typical Application
The basic implementation of Auto-Track allows for simultaneous voltage sequencing of a number of Auto-Track
compliant modules. Connecting the Track inputs of two or more modules forces their track input to follow the
same collective RC-ramp waveform, and allows their power-up sequence to be coordinated from a common
Track control signal. This can be an open-collector (or open-drain) device, such as a power-up reset voltage
supervisor IC. See U3 in Figure 23.
To coordinate a power-up sequence, the Track control must first be pulled to ground potential. This should be
done at or before input power is applied to the modules. The ground signal should be maintained for at least
20 ms after input power has been applied. This brief period gives the modules time to complete their internal
soft-start initialization (4), enabling them to produce an output voltage. A low-cost supply voltage supervisor IC,
that includes a built-in time delay, is an ideal component for automatically controlling the Track inputs at power
up.
Figure 23 shows how the TL7712A supply voltage supervisor IC (U3) can be used to coordinate the sequenced
power up of PTV08T250W modules. The output of the TL7712A supervisor becomes active above an input
voltage of 3.6 V, enabling it to assert a ground signal to the common track control well before the input voltage
has reached the module's undervoltage lockout threshold. The ground signal is maintained until approximately 28
ms after the input voltage has risen above U3's voltage threshold, which is 10.95 V. The 28-ms time period is
controlled by the capacitor C3. The value of 2.2 µF provides sufficient time delay for the modules to complete
their internal soft-start initialization. The output voltage of each module remains at zero until the track control
voltage is allowed to rise. When U3 removes the ground signal, the track control voltage automatically rises. This
causes the output voltage of each module to rise simultaneously with the other modules, until each reaches its
respective set-point voltage.
Figure 24 shows the output voltage waveforms after input voltage is applied to the circuit. The waveforms, VO1
and VO2, represent the output voltages from the two power modules, U1 (3.3 V) and U2 (1.8 V), respectively.
VTRK, VO1, and VO2 are shown rising together to produce the desired simultaneous power-up characteristic.
The same circuit also provides a power-down sequence. When the input voltage falls below U3's voltage
threshold, the ground signal is re-applied to the common track control. This pulls the track inputs to zero volts,
forcing the output of each module to follow, as shown in Figure 25. Power down is normally complete before the
input voltage has fallen below the modules' undervoltage lockout. This is an important constraint. Once the
modules recognize that an input voltage is no longer present, their outputs can no longer follow the voltage
applied at their track input. During a power-down sequence, the fall in the output voltage from the modules is
limited by the Auto-Track slew rate capability.
24
PTV08T250W
www.ti.com
SLTS260B – OCTOBER 2005 – REVISED NOVEMBER 2005
Notes on Use of Auto-Track™
1. The Track pin voltage must be allowed to rise above the module set-point voltage before the module
regulates at its adjusted set-point voltage.
2. The Auto-Track function tracks almost any voltage ramp during power up, and is compatible with ramp
speeds of up to 1 V/ms.
3. The absolute maximum voltage that may be applied to the Track pin is the input voltage VI.
4. The module cannot follow a voltage at its track control input until it has completed its soft-start initialization.
This takes about 20 ms from the time that a valid voltage has been applied to its input. During this period, it
is recommended that the Track pin be held at ground potential.
5. The Auto-Track function is disabled by connecting the Track pin to the input voltage (VI). When Auto-Track is
disabled, the output voltage rises at a quicker and more linear rate after input power has been applied.
RTT
U1
Track
TurboTrans
+ Sense
VI = 12 V
VI
VO
PTV08T250W
VO1 = 3.3 V
Inhibit/
UVLO Prog
− Sense
VOAdj
GND
CO1
+
CI1
U3
7
2
1
3
RSET
8
2.49 kW
VCC
SENSE
5
RESET
RESIN
TL7712A
REF
6
RESET
CT
U2
NC
GND
4
CREF
CT
0.1 mF
2.2 mF
Track
+ Sense
RRST
10 W
VI
VO
PTV08040W
Inhibit/
UVLO Prog
VO2 = 1.8 V
− Sense
GND
VOAdj
+
CO2
CI2
RSET2
16.9 kW
Figure 23. Sequenced Power Up and Power Down Using Auto-Track
25
PTV08T250W
www.ti.com
SLTS260B – OCTOBER 2005 – REVISED NOVEMBER 2005
VTRK (1 V/div)
VTRK (1 V/div)
VO1 (1 V/div)
VO1 (1 V/div)
VO2 (1 V/div)
VO2 (1 V/div)
t - Time = 20 ms/div
Figure 24. Simultaneous Power Up With Auto-Track
Control
t - Time = 400 ms/div
Figure 25. Simultaneous Power Down With Auto-Track
Control
Prebias Startup Capability
A prebias startup condition occurs as a result of an external voltage being present at the output of a power
module prior to its output becoming active. This often occurs in complex digital systems when current from
another power source is backfed through a dual-supply logic component, such as an FPGA or ASIC. Another
path might be via clamp diodes, sometimes used as part of a dual-supply power-up sequencing arrangement. A
prebias can cause problems with power modules that incorporate synchronous rectifiers. This is because under
most operating conditions, such modules can sink as well as source output current. PTH modules all incorporate
synchronous rectifiers. Those that incorporate the prebias feature do not sink current during startup, or whenever
the Inhibit pin is held low. Start up includes an initial delay (approximately 8–15 ms), followed by the rise of the
output voltage under the control of the module’s internal soft-start mechanism; see Figure 26.
Conditions for PreBias Holdoff
For the module to allow an output prebias voltage to exist (and not sink current), certain conditions must be
maintained. The module holds off a prebias voltage when the Inhibit pin is held low, and whenever the output is
allowed to rise under soft-start control. Power up under soft-start control occurs upon the removal of the ground
signal to the Inhibit pin (with input voltage applied), or when input power is applied with Auto-Track disabled (see
Figure 26). To further ensure that the regulator doesn’t sink output current, (even with a ground signal applied to
its Inhibit), the input voltage must always be greater than the applied prebias source. This condition must exist
throughout the power-up sequence.
The soft-start period is complete when the output begins rising above the prebias voltage. Once it is complete
the module functions as normal, and sinks current if a voltage higher than the nominal regulation value is applied
to its output.
Note: If a prebias condition is not present, the soft-start period is complete when the output voltage has risen
to either the set-point voltage, or the voltage applied at the module’s Track control pin, whichever is lowest.
Demonstration Circuit
Figure 27 shows the startup waveforms for the demonstration circuit shown in Figure 28. The initial rise in VO2 is
the prebias voltage, which is passed from the VCCIO to the VCORE voltage rail through the ASIC. Note that the
output current from the PTH12010L module (IO2) is negligible until its output voltage rises above the applied
pre-bias.
26
PTV08T250W
www.ti.com
SLTS260B – OCTOBER 2005 – REVISED NOVEMBER 2005
UVLO
Threshold
VI (5 V/Div)
VO1 (1 V/Div)
VO (1 V/Div)
VO2 (1 V/Div)
IO2 (5 A/Div)
Startup Period
HORIZTAL SCALE: 10 ms/Div
HORIZTAL SCALE: 5 ms/Div
Figure 26. PTH08040W Startup
Figure 27. Prebias Startup Waveforms
Note
1. The prebias start-up feature is not compatible with Auto-Track. If the rise in the output is limited by the
voltage applied to the Track control pin, the output sinks current during the period that the track control
voltage is below that of the back-feeding source. For this reason, it is recommended that Auto-Track be
disabled when not being used. This is accomplished by connecting the Track pin to the input voltage, VI. This
raises the Track pin voltage well above the set-point voltage prior to the module’s start up, thereby defeating
the Auto-Track feature.
10 9
8
5
Up Dn Tra ck
VI = 12 V
2
VI
GND
7
1
+ C1
330 mF
10 9
Inhibit
3
TL7702B 8
VCC
7
SENSE
2
RESET
C5
0.1 mF
VO
6
VO2 = 1.8 V
+
Vadj
4
IO2
RESET
6
CT
GND
4
C6
0.68 mF
+
C3
330 mF
VC CI O
VC ORE
RESIN
REF
R4
100 kW
C2
330 mF
5
Sense
PTH12010L
GND
1
7
+
R2
130 W
5
1
3
VI
VO1 = 3.3 V
6
Adjust
4
R1
2 kW
8
Tra ck
2
VO
PTH12020W
Inhibit
3
R3
11 kW
Sense
+
C4
330 mF
ASIC
R5
10 kW
Figure 28. Application Circuit Demonstrating Prebias Startup
27
PACKAGE OPTION ADDENDUM
www.ti.com
9-Oct-2007
PACKAGING INFORMATION
Orderable Device
Status (1)
Package
Type
Package
Drawing
Pins Package Eco Plan (2)
Qty
PTV08T250WAD
ACTIVE
DIP MOD
ULE
EAN
21
21
Pb-Free
(RoHS)
Call TI
N / A for Pkg Type
PTV08T250WAH
ACTIVE
DIP MOD
ULE
EAN
21
21
TBD
Call TI
N / A for Pkg Type
Lead/Ball Finish
MSL Peak Temp (3)
(1)
The marketing status values are defined as follows:
ACTIVE: Product device recommended for new designs.
LIFEBUY: TI has announced that the device will be discontinued, and a lifetime-buy period is in effect.
NRND: Not recommended for new designs. Device is in production to support existing customers, but TI does not recommend using this part in
a new design.
PREVIEW: Device has been announced but is not in production. Samples may or may not be available.
OBSOLETE: TI has discontinued the production of the device.
(2)
Eco Plan - The planned eco-friendly classification: Pb-Free (RoHS), Pb-Free (RoHS Exempt), or Green (RoHS & no Sb/Br) - please check
http://www.ti.com/productcontent for the latest availability information and additional product content details.
TBD: The Pb-Free/Green conversion plan has not been defined.
Pb-Free (RoHS): TI's terms "Lead-Free" or "Pb-Free" mean semiconductor products that are compatible with the current RoHS requirements
for all 6 substances, including the requirement that lead not exceed 0.1% by weight in homogeneous materials. Where designed to be soldered
at high temperatures, TI Pb-Free products are suitable for use in specified lead-free processes.
Pb-Free (RoHS Exempt): This component has a RoHS exemption for either 1) lead-based flip-chip solder bumps used between the die and
package, or 2) lead-based die adhesive used between the die and leadframe. The component is otherwise considered Pb-Free (RoHS
compatible) as defined above.
Green (RoHS & no Sb/Br): TI defines "Green" to mean Pb-Free (RoHS compatible), and free of Bromine (Br) and Antimony (Sb) based flame
retardants (Br or Sb do not exceed 0.1% by weight in homogeneous material)
(3)
MSL, Peak Temp. -- The Moisture Sensitivity Level rating according to the JEDEC industry standard classifications, and peak solder
temperature.
Important Information and Disclaimer:The information provided on this page represents TI's knowledge and belief as of the date that it is
provided. TI bases its knowledge and belief on information provided by third parties, and makes no representation or warranty as to the
accuracy of such information. Efforts are underway to better integrate information from third parties. TI has taken and continues to take
reasonable steps to provide representative and accurate information but may not have conducted destructive testing or chemical analysis on
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Addendum-Page 1
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