Features • Integrated Reverse Phase Control • Mode Selection: • • • • • – Zero-voltage Switch with Static Output – Two-stage Reverse Phase Control with Switch-off – Two-stage Reverse Phase Control with Dimming Function Current Monitoring: – High-speed Short-circuit Monitoring with Output – High-current Monitoring with Integrating Buffer Integrated Chip Temperature Monitoring Adjustable and Retriggerable Tracking Time External Window Adjustment for Sensor Input Enable Input for Triggering Multifunction Timer IC U2102B Applications • • • • • • Two- or Three-wire Applications Motion Detectors Time-delay Relays Dimmers Reverse Phase Controls Timers 1. Description The timer control circuit U2102B is based on bipolar technology. The output stage can switch either a MOSFET or an IGBT. Two sensor inputs and the retriggerable and adjustable tracking time useful for a wide range of applications. By using the reverse phase-control technique, the resistive load can be dimmed without the need of a compensation inductance. The integrated current monitoring function provides a very fast switch-off in case of a short-circuit condition. No additional fuse is needed. Rev. 4767B–INDCO–10/05 Figure 1-1. Block Diagram 1 16 Voltage monitoring VRef 2 Synchronization 15 Reverse phase control 3 4 Control 5 RC oscillator 13 Voltage limitation 14 Push pull Divider logic 12 6 Current monitoring Programing Triggering with buffers 7 2 8 9 Temperature monitoring 11 Test logic 10 U2102B 4767B–INDCO–10/05 U2102B 2. Pin Configuration Figure 2-1. Pinning DIP16/SO16 16 SYNC VREF 1 CRAMP 2 15 +VS RRAMP 3 14 VO CONTROL 4 13 GND OSC 5 12 IOFF PROG 6 11 II EN 7 10 TEST TRIGGER 8 9 V9 U2102B Pin Description Pin Symbol Function 1 VREF 2 CRAMP Ramp capacitance 3 RRAMP Current setting for ramp 4 CONTROL 5 OSC 6 PROG 7 EN 8 TRIGGER 9 V9 10 TEST 11 II 12 IOFF Fast output current monitoring 13 GND Ground Reference voltage 5 V Control voltage RC oscillator Tri-state programming Enable input Trigger input (window) Window adjustment Test output Input current monitoring 14 VO Output voltage 15 +VS Supply voltage 16 SYNC Synchronization input 3 4767B–INDCO–10/05 4 Trigger signal 1 µF CRef R2 Enable +VS 220 nF C2 100 kΩ 22 kΩ 1 MΩ GND VRef Control R3 820 kΩ C3 10 nF 8 0.1/0.4 0.5 × VRef 7 - + - + 2 stage GND 0.45 × VRef - 0.2 V9 Trigger window 0.55 × VRef + 0.2 V9 Enable Voltage monitoring Divider Control Phase filter) (spike- Buffer logic Control Clock generator Reverse Clock 1 kΩ Test mode 2 stage/out +VS Stat. ZVS RC oscillator - + Ramp VRef VRef 0.02 × VRef 6 5 4 3 2 1 Push pull Clock Clock - + adjustment Window + Test logic Buffer 120 ms Current monitoring POR Q Q R S Temp monitoring Voltage limitation Synchronization 9 10 100 mV 11 500 mV 12 13 GND 14 15 +VS 16 RG 100 Ω C1 47 µF/25 V 68 kΩ 33 kΩ/2 W R1 NTC VRef 1 nF 1 kΩ Rsh IGBT Load 230 V ~ Vmains Figure 2-2. Block Diagram with Typical Circuit for DC Loads U2102B 4767B–INDCO–10/05 U2102B 3. Power Supply, Synchronization Pins 15 and 16 The U2102B’s voltage limitation circuit enables the power supply via the dropping resistor R1. In the case of DC loads, the entire supply current flows into pin 16 and is supplied via an internal diode to pin 15, where the resultant supply voltage is limited and smoothed by C1. The pull-down resistor at pin 16 is necessary in order to guarantee reliable synchronization. As a result, the rectified and divided line voltage appears at pin 16, where the amplitude is limited. The power supply for the circuit can be realized in all modes for DC loads as shown in Figure 2-2 on page 4. The voltage at pin 16 is used to synchronize the circuit with the mains and generate the system clock required for the buffers. The circuit detects a “zero crossing” when the voltage at pin 16 falls below an internal threshold of approximately 8 V. Figure 3-1. Power Supply for DC Loads (R1 is Identical with Rsync) Vmains R1 = Rsync Sync. 16 +VS Load 15 Voltage limitation C1 Push pull 14 IGBT RG Temp. monit. Rsh GND 13 R1 is calculated as follows: V Nmin – V S R 1max = 0.85 × ---------------------------I tot where: VNmin = Vmains – 15% VS = Supply voltage Itot = ISmax + Ix ISmax = Maximum current consumption of the IC Ix = Current consumption of the external components 5 4767B–INDCO–10/05 In the case of AC loads, it is necessary to distinguish the power supply purposes of the individual operating modes. In reverse phase control mode (see Figure 3-1 on page 5), pin 15 must be additionally supplied with power via a dropping resistor, since no current flows in pin 16 when the power switch is switched on. Here, the dropping resistor, R1, is connected to the AC line and has therefore only one mains half-wave. R1 is then calculated as follows: V Nmin – V S R 1max = 0.85 × ---------------------------2 × I tot Figure 3-2. Power Supply in Reverse Phase Control Mode for AC Loads Load Vmains Rsyn Sync. D1 16 R1 +VS 15 Voltage limitation C1 Push pull IGBT 14 Temp. monit. RG Rsh GND 13 In two-wire systems, the additional power supply at pin 15 is not possible (see Figure 3-1 on page 5, by omitting R1 and diode D1). In this case, the resistor Rsync is identical with R1 and should be as low as the power dissipation allows it. A sufficiently large residual phase angle must remain in this case to guarantee the device’s supply. The power supply is simplified if the device is operated as a static zero-voltage switch for AC loads (see Figure 3-2). All delay times are then twice as long, since the synchronization of the module is connected directly to the AC line. 6 U2102B 4767B–INDCO–10/05 U2102B Figure 3-3. Power Supply as Static Zero-voltage Switch for AC Loads Load Vmains R1 = Rsync Sync 16 +VS 15 Voltage limitation C1 Push pull 14 Temp. monit. IGBT RG Rsh GND 13 4. Voltage Monitoring The internal voltage monitoring circuit surpresses uncontrolled conditions or output pulses of insufficient amplitude which may occur while the operating voltage is being built up or reduced. All latches in the circuit, the divider and the control logic are reset. When the supply voltage is applied, the enable threshold (clamp voltage) of approximately 16 V must be reached so that the circuit is enabled. The circuit is reset at approximately 11 V if the supply voltage breaks down. A further threshold is activated in reverse phase control mode. If the supply voltage breaks down in this mode, after the circuit has been enabled, the output stage is switched off at approximately 12.5 V, while the other parts of the circuit are not affected. The output stage can then be switched on again in the following half-wave. As a result, the residual phase angle remains just large enough, (e.g., in two-wire systems), so that the circuit can still be properly supplied with power. In all operating modes, a single operating cycle is started after the supply voltage is applied, independently of the trigger inputs, in order to immediately demonstrate the overall function. 5. Chip Temperature Monitoring The U2102B includes a chip temperature monitoring circuit which disables the output stage when a temperature of approximately 140°C is reached. The circuit will only be enabled again after cooling down and when the operating voltage has been additionally switched off and on. 7 4767B–INDCO–10/05 6. Reverse Phase Control In the case of normal phase controls, e.g., with a triac, the load current will only be switched on at a certain phase angle after the zero crossing of the mains voltage. In the following zero crossing of the current, the triac gets extinguished (switched-off) automatically. Reverse phase control differs from this in that the load current is always switched on by a semiconductor switch (for example, IBGT) at the zero crossing of the mains voltage and then switched back off again after a certain phase angle α. This has the advantage that the load current always rises with the mains voltage in a defined manner and thus keeps the required interference suppression to a minimum. The charging current for the capacitor C3 at pin 2 is set with the resistor R3 at pin 3. When the synchronization circuit recognizes a zero crossing, an increased charging current of I2 ≈ 4 × I3 is enabled which then charges C3 up to ≈ 0.45 V. The output stage is switched on at this value and the charging current for C3 is reduced to I2 = I3. Since the actual zero crossing of the supply voltage occurs later than recognized by the circuit, the load current starts to flow quite close to the exact zero crossing of the supply voltage. While the output stage is switched on, C3 is charged until the control voltage, set externally at pin 4, is reached. When this condition is reached, the output stage is switched off and C3 is charged again with the increased current (I2 ≈ 4 × I3) to V2 ≈ 5.5 V. The charging current is switched off at this point and C3 is discharged internally. The whole process then starts again when the circuit recognizes another zero crossing (Figure 3-3 on page 7). Figure 6-1. Signal Characteristics of Reverse Phase Control Vmains t V2 1.1 V × VRef 0.09 V × VRef V4 t V14 t 8 U2102B 4767B–INDCO–10/05 U2102B 7. Programming Three operating modes can be programmed with the tri-state input pin 6: • Zero-voltage switch (ZVS) with static output (V6 = V1 = VRef): The reverse phase control is inactive here. The output stage is statically switched on after triggering by the timer and switched off again after the running down of the time (at the zero crossing of the supply voltage in each case). This operating mode is not possible in two-wire systems. • Reverse phase control with two-stage switch-off (V6 = V15 = VS): The maximum current flow angle, αmax, is set when the timer has enabled the output stage. Switchover to the phase angle α, which can be set arbitrarily at pin 4, takes place after expiry of 3/4 of the tracking time set at pin 5. The output stage switches off after expiry of the whole tracking time. • Two-stage reverse phase control with dimming function (V6 = V13 = GND): The output stage switches to the maximum current flow angle, αmax, (adjustable) if the trigger condition for both inputs (pins 7, 8) is satisfied. Switchover to the current flow angle, α, set at pin 4 takes place after expiry of 3/4 of the tracking time set at pin 5. The whole process is repeated from the beginning if renewed triggering takes place at pin 8. The lamp is switched-off in the following half-wave of the mains voltage if the trigger condition at pin 7 disappears. In this mode, the output stage is switched-on even if only pin 7 is in the ON state. The current flow angle is then determined by V4 (e.g., house number illumination, twilight switch). 8. Trigger Inputs The trigger condition of the timer is determined by the two inputs at pins 7 and 8. A Light Dependent Resistor (LDR) can be connected to pin 7, for example, and an IR sensor to pin 8. Since both inputs are equal and AND-gated they must both be in the ON state to initiate triggering. In the operating mode “2-stage reverse phase control”, the output stage can additionally be switched on and switched off by pin 7 alone and independently of the timer. The enable input pin 7 is implemented as a comparator with hysteresis. The enable threshold is approximately 2.5 V. The blocking threshold is switched by the control logic in order to avoid faults as a result of load switching. This threshold is approximately 2 V in switched off condition and also during the second current flow angle, α, in two-stage reverse phase control mode. Otherwise, the blocking or switch-off threshold is 0.5 V. The input pin 8 is designed as a window discriminator, its window is set at pin 9. The minimum window of approximately 250 mV is set with V9 = V13, and the maximum window of approximately 1.25 V with V9 = Vl. The window discriminator is in the OFF state when the voltage at pin 8 lies within the window set at pin 9. If a resistor divider with an NTC resistor is connected to pin 9, for example, it is possible to compensate the temperature dependence of the IR sensor, i.e., the range is made independent of temperature. Noise suppression for tON = 40 ms guarantees that there are no peak noise signals at the inputs which could trigger the circuit. Equally, renewed triggering is prevented for tOFF = 640 ms after load switch-off to avoid any self interference. 9 4767B–INDCO–10/05 Figure 8-1. Trigger Condition Pin 7 V7 VRef 0.5 × VRef ON Hysteresis 0.1/0.4 × VRef OFF 0 Figure 8-2. Trigger Condition Pin 8 V8 VRef ON 0.5 × VRef 0.05 × VRef + 0.2 × V9 0.05 × VRef + 0.2 × V9 OFF ON 0 9. RC Oscillator An internal RC oscillator with following divider stage 1:211 permits a very long and reproducible tracking time. The RC values for a certain tracking time, tt, are calculated as follows: 3 t t (s)10 R 2 (kΩ) = ------------------------------------------------1.4 × 2048 C 2 (µF) 3 t t (s)10 C 2 (µF) = -------------------------------------------------1.4 × 2048 R 2 (kΩ) In reverse phase control mode, switchover from maximum current flow angle to the value set at pin 4 takes place after expiry of 3/4 of the total tracking time tt. 10 U2102B 4767B–INDCO–10/05 U2102B 10. Current Monitoring The U2102B’s current monitoring circuit represents a double electronic fuse. The circuit measures the current flowing through the power switch by means of the voltage drop across the shunt resistor Rsh. This voltage is supplied to pin 11. If this voltage exceeds a value of 500 mV due to a high load current (e.g., short circuit), the switch-off latch is set and the switching output pin 11 closes immediately. Pin 11 can be connected to the gate via a resistor or network, depending on load conditions, thus allowing the switch-off behavior to be adapted to the respective requirements. The short-circuit current is reduced to a problem-free value by this procedure. There is a second threshold at 100 mV. Without exceeding the switch-off threshold of 500 mV, the output stage is also disabled in the voltage at pin 11 exceeds the value of 100 mV for ≥ 120 ms at one half-wave. To prevent the occurrence of high-voltage peaks in the over current condition due to the line and leakage inductances, the output stage is not switched off immediately. It is disabled during the next half-wave. 11. Absolute Maximum Ratings Stresses beyond those listed under “Absolute Maximum Ratings” may cause permanent damage to the device. This is a stress rating only and functional operation of the device at these or any other conditions beyond those indicated in the operational sections of this specification is not implied. Exposure to absolute maximum rating conditions for extended periods may affect device reliability. Reference point pin 13, unless otherwise specified. Parameters Pin Symbol Value Unit Power supply Current t < 10 µs 15 IS is 20 60 mA mA Synchronization Input current t ≤10 µs 16 II ii 20 60 mA mA Reference voltage source Output current 1 - IRef 10 mA Push-pull output stage Output current t ≤2 ms 14 14 ±IO ±io 10 60 mA mA Input currents 2 2 3 10 12 -II II -II ± II II 1 8 0.2 1 20 mA mA mA mA mA Input voltage 4, 5, 7, 8, 9, 11 6 and 12 VI VI 0 to V1 0 to V15 V V Tstg -40 to +125 °C Junction temperature Tj +125 °C Ambient temperature Tamb -10 to +100 °C Storage temperature range 11 4767B–INDCO–10/05 12. Thermal Resistance Parameters Symbol Value Unit RthJA 120 K/W SO16 on PC board RthJA 180 K/W SO16 on ceramic RthJA 100 K/W DIP16 Junction ambient 13. Electrical Characteristics VS = 15.0 V, fmains = 50 Hz, Tamb = 25°C, reference point pin 13, unless otherwise specified. Parameters Test Conditions Pin Symbol Min. Supply Voltage Limitation IS = 2 mA IS = 5 mA 15 VS VS 15 15.2 Current Consumption VS = 15 V 15 IS Voltage Monitoring Max. Unit 17 17.2 V V 2 mA 15 VSON VSOFF V15 14.8 10.4 11.7 11 12.5 16.5 11.6 13.3 V V V 1 VRef 4.75 5 5.25 V 15, 16 16 16 16 Vlimit - II VTON VTOFF 7.3 7.9 0.8 100 7.7 8.3 8.1 8.7 V µA V V -II V3 4.7 5 50 5.3 µA V 9 37 10 40 1 450 600 11 43 µA µA kΩ mV mV Switch-on threshold Switch-off threshold Undervoltage threshold Reference Voltage Typ. -I1 = 0 to 5 mA Synchronization Voltage limitation Input current Zero crossing switch-on threshold Zero crossing switch-off threshold I16 = 2 mA V16 = 0 V Reverse Phase Control 3 Ramp current setting Input current Input voltage I3 = -10 µA Ramp I3 = -10 µA Charging current 1 Charging current 2 Discharge impedance Switch-on threshold, output stage Discharge threshold voltage 1, 2 Control Voltage Input voltage Input current VI ±II V13 ≤V4 ≤Vl V13 ≤V6 ≤V15 RC Oscillator 12 410 490 0 VRef 500 V nA 1 µA 6 ±II Operating mode: Static zero-voltage switch 2-stage reverse phase control with switch-off 2-stage reverse phase control Input current Upper threshold Lower threshold Discharge impedance -Ich1 -Ich2 Rdis VTON Vdis 4 Programming, Tri-state Input Input current 2 VI 1 VRef + 1 VRef + 0.3 VS V VI 0 0.3 V ±II VTU VTL Rdis 3.6 0.9 500 4.4 1.1 nA V V kΩ 5 V13 ≤V5 < 3.6 V 4 1 1 U2102B 4767B–INDCO–10/05 U2102B 13. Electrical Characteristics (Continued) VS = 15.0 V, fmains = 50 Hz, Tamb = 25°C, reference point pin 13, unless otherwise specified. Parameters Test Conditions Pin Symbol 8 Min. Typ. Max. Unit ±II 500 nA 8, 9 VTU VTL 0.55 × VRef + (0.2 × V9) 0.45 × VRef - (0.2 × V9) V V 500 nA Window Discriminator Input current 0 V ≤V8 ≤Vl Upper threshold Lower threshold Input current window adjustment 0 V ≤V9 ≤V1 9 ±Ii Minimum window: Lower threshold Upper threshold V9 = V13 8 VTL1 VTU1 2.05 2.55 2.75 3.75 2.45 2.95 V V Maximum window: Lower threshold Upper threshold V9 = V1 8 VTL2 VTU2 1.1 3.4 1.25 3.75 1.4 4.1 V V 500 nA VT 2.3 2.5 2.7 V VT VT 1.8 0.45 2 0.5 2.2 0.55 V V VT 85 100 115 mV ±Ii VT1 VT2 80 450 100 500 500 120 550 nA mV mV Enable Schmitt Trigger Input current 7 0 V ≤V7 ≤Vl ±Ii Enable threshold Blocking threshold: Output stage OFF Output stage ON, except in the case of two-stage reverse phase control in second stage (α) Threshold for test mode Current Monitoring Input current Switch-off threshold 1 Switch-off threshold 2 11 0 V ≤V11 ≤V1 Switching Output 12 Leakage current V11 < 450 mV, V12 ≤V15 Ilkg 1 µA Saturation voltage V11 > 550 mV I12 = 0.5 mA I12 = 10 mA VSat VSat 1.0 1.2 V V Push-pull Output Stage Upper saturation voltage, ON state I14 = -10 mA 14, 15 -VSat 2.4 V Lower saturation voltage, OFF state I14 = 10 mA 14 VSatL 1.2 V Output current ON state OFF state 14 -IO IO 50 50 mA mA 13 4767B–INDCO–10/05 Figure 13-1. House Number or Staircase Illumination for AC Loads House Number Illumination: V6 = V13 Staircase Illumination: V6 = V15 Vmains 230 V ~ Load GND 1 nF Rsh 1 kΩ IGBT 22 kΩ/2 W R1 100 Ω 1N4007 Rsync 220 kΩ RG C1 47 µF/ 25 V 100 kΩ NTC VRef VS 16 15 14 13 12 11 10 9 6 7 8 U2102B 1 2 4 3 C3 10 nF 5 R3 820 kΩ Control VS GND 220 nF Enable 100 kΩ 22 kΩ 1 MΩ R2 14 C2 CRef Trigger signal 1 µF U2102B 4767B–INDCO–10/05 U2102B Figure 13-2. Zero-voltage Switch Mode for AC Loads Vmains 230 V ~ Load GND 1 nF Rsh 1 kΩ IGBT R1 = Rsync RG 68 kΩ 18 kΩ/2 W 100 Ω NTC VRef C1 47 µF/25 V 1N4007 VS 16 15 14 13 12 11 10 9 6 7 8 U2102B 1 2 3 4 5 R3 C3 22 nF 750 kΩ C2 Enable 220 nF 22 kΩ 1 MΩ Trigger signal R2 CRef 1 µF 15 4767B–INDCO–10/05 Figure 13-3. Reverse Phase Control for AC Loads Vmains 230 V ~ Load 1 nF Rsh R1 22 kΩ/2 W 1 kΩ IGBT 100 Ω VS 1N4007 100 kΩ Rsync = 220 kΩ RG C1 47 µF/ 25V 100 kΩ VS 16 15 14 13 12 11 10 9 6 7 8 U2102B 1 2 4 3 5 C3 100 kΩ 10 nF 100 kΩ R3 1 MΩ VS Control 100 kΩ CRef = 1 µF 16 U2102B 4767B–INDCO–10/05 U2102B 14. Ordering Information Extended Type Number Package U2102B-xY Remarks DIP16 Tube, Pb-free U2102B-xFPY SO16 Tube, Pb-free U2102B-xFPG3Y SO16 Taped and reeled, Pb-free 15. Package Information Package DIP16 Dimensions in mm 7.82 7.42 20.0 max 4.8 max 6.4 max 0.5 min 3.3 1.64 1.44 0.58 0.48 2.54 0.39 max 9.75 8.15 17.78 Alternative 16 9 technical drawings according to DIN specifications 1 8 17 4767B–INDCO–10/05 Package SO16 Dimensions in mm 5.2 4.8 10.0 9.85 3.7 1.4 0.25 0.10 0.4 1.27 0.2 3.8 6.15 5.85 8.89 16 9 technical drawings according to DIN specifications 1 8 16. Revision History Please note that the following page numbers referred to in this section refer to the specific revision mentioned, not to this document. 18 Revision No. History 4767B-INDCO-08/05 • Put datasheet in a new template • First page: Pb-free logo added • Page 17: Ordering Information changed U2102B 4767B–INDCO–10/05 Atmel Corporation 2325 Orchard Parkway San Jose, CA 95131, USA Tel: 1(408) 441-0311 Fax: 1(408) 487-2600 Regional Headquarters Europe Atmel Sarl Route des Arsenaux 41 Case Postale 80 CH-1705 Fribourg Switzerland Tel: (41) 26-426-5555 Fax: (41) 26-426-5500 Asia Room 1219 Chinachem Golden Plaza 77 Mody Road Tsimshatsui East Kowloon Hong Kong Tel: (852) 2721-9778 Fax: (852) 2722-1369 Japan 9F, Tonetsu Shinkawa Bldg. 1-24-8 Shinkawa Chuo-ku, Tokyo 104-0033 Japan Tel: (81) 3-3523-3551 Fax: (81) 3-3523-7581 Atmel Operations Memory 2325 Orchard Parkway San Jose, CA 95131, USA Tel: 1(408) 441-0311 Fax: 1(408) 436-4314 RF/Automotive Theresienstrasse 2 Postfach 3535 74025 Heilbronn, Germany Tel: (49) 71-31-67-0 Fax: (49) 71-31-67-2340 Microcontrollers 2325 Orchard Parkway San Jose, CA 95131, USA Tel: 1(408) 441-0311 Fax: 1(408) 436-4314 La Chantrerie BP 70602 44306 Nantes Cedex 3, France Tel: (33) 2-40-18-18-18 Fax: (33) 2-40-18-19-60 ASIC/ASSP/Smart Cards 1150 East Cheyenne Mtn. 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